CN203933397U - Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply - Google Patents
Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply Download PDFInfo
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- CN203933397U CN203933397U CN201420317161.9U CN201420317161U CN203933397U CN 203933397 U CN203933397 U CN 203933397U CN 201420317161 U CN201420317161 U CN 201420317161U CN 203933397 U CN203933397 U CN 203933397U
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Abstract
本实用新型公开了一种用于连续工作模式开关电源的多谷值电流型脉冲序列控制装置：在每个开关周期起始时刻，根据负载电流Io选择合适的电感电流谷值Iv，根据开关变换器输出电压Vo与基准电压Vref之间的关系选择该开关周期内的有效控制脉冲。该方法可用于控制工作于连续模式的大功率开关变换器，其控制稳定性和抗干扰能力强，动态性能良好，且适用于各种拓扑结构的开关变换器。
The utility model discloses a multi-valley current type pulse sequence control device for a switching power supply in a continuous working mode: at the initial moment of each switching cycle, an appropriate inductor current valley value Iv is selected according to the load current Io, and according to The relationship between the switching converter output voltage V o and the reference voltage V ref selects the effective control pulse during the switching period. The method can be used to control high-power switching converters working in continuous mode, has strong control stability and anti-interference ability, good dynamic performance, and is suitable for switching converters with various topological structures.
Description
Technical field
The utility model relates to Switching Power Supply, especially a kind of control method of switch converters and device thereof.
Background technology
Switching Power Supply is a kind of by controlling the conducting of master power switch pipe, the power supply that the turn-off time maintains output voltage stabilization.It has the advantages such as power consumption is little, energy conversion efficiency is high, and volume is little, voltage stabilized range is wide, in each electronic product, is all widely used.Along with the development of power electronic technology and popularizing of battery powered portable electric appts, more and more higher to the performance requirement of Switching Power Supply.For improving traditional pulse width modulation (PWM) technology, there is the shortcomings such as transient response speed is slow, COMPENSATION NETWORK DESIGN is difficult, some novel control methods have been proposed in recent years, to improve the performance of Switching Power Supply, make it meet the requirement of electronic equipment to Switching Power Supply.
Pulse train (PT) control technology is a kind of novel fixed-frequency control method that is operated in discontinous mode (DCM) proposition for switch converters, and it realizes the adjusting to output voltage by adjusting the compound mode of two groups of predefined control impuls.Because pulse train control switch converter has advantages of that circuit realization simply, does not need compensating network, transient response speed is fast and strong robustness, is highly suitable for the switching power control system higher to reliability requirement.But when pulse train control switch converter is operated in continuous current mode pattern (CCM), because pulse train controller is by regulating inductive current indirect regulation output voltage, make controller there is hysteresis quality to the adjusting of output voltage, cause switch converters to occur low-frequency fluctuation phenomenon, stable state and mapping variation.Current research shows, valley point current type pulse train (VCM-PT) control method, can solve low-frequency fluctuation phenomenon effectively, but because it only has a default inductive current valley, make bearing power scope less, when load variations is larger, control switch converter effectively.
Utility model content
The purpose of this utility model is to provide a kind of control device of Switching Power Supply, makes it to overcome the narrower technical disadvantages of existing valley point current type pulse train (VCM-PT) control change device loading range.This device can be used for controlling the high power switch converter that works in continuous mode, and its control technology is simple, and stability and antijamming capability are strong, and dynamic property is good, is applicable to the switch converters of various topological structures.
The technical solution of the utility model is: a kind of many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply, it is characterized in that by converter TD and controller group, controller comprises that voltage detecting circuit VD, load current detection and comparison circuit IDC1, valley point current selector IS, inductive current detect and comparison circuit IDC2, pulse selector PS, pulse generator PG, single triggering timing device OOT1, single triggering timing device OOT2, drive circuit DR; Load current detection is connected with valley point current selector with comparison circuit IDC1; Inductive current detection is connected with comparison circuit, pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2; Voltage detecting circuit VD, pulse selector PS, pulse generator PG, drive circuit are connected to DR successively; Pulse generator PG detects and is connected with comparison circuit IDC2, single triggering timing device OOT1, single triggering timing device OOT2 with inductive current.
Its working method comprises: at each switch periods initial time, according to switch converters load current, choose corresponding inductive current valley, according to switch converters output voltage, select the effective control impuls in this switch periods, thereby realize the control to continuous operation mode switch converters; Its inductive current valley selective rule is: if output current I
oless, choose small electric inducing current valley I
vif, output current I
olarger, choose larger inductive current valley I
v.Its control impuls selective rule is: if output voltage V
olower than output voltage fiducial value V
ref, adopt high power pulse P
hswitching tube S in control switch converter; Otherwise, if output voltage V
ohigher than output voltage fiducial value V
ref, adopt low powder pulsed P
lcontrol switch pipe S.
Compared with prior art, the beneficial effects of the utility model are:
One, the utility model provides a kind of simple and reliable control method for continuous operation mode switch converters.This control method, by onset detection output voltage, load current and an inductive current in each switch periods simple its size of judgement, can complete the control to main switch S in converter.Overcome the detection that traditional continuous mode inverter control method is difficult to avoid and processed the shortcomings such as feedback quantity is complicated, compensation tache design is loaded down with trivial details.
Two, control method provided by the utility model can suppressor pulse sequence be controlled the low-frequency fluctuation phenomenon of continuous operation mode switch converters.
Three, when converter load generation saltus step, can change rapidly suitable inductive current valley I
vwith pulse train compound mode, to adapt to the variation of load, make converter steady operation, widened range of application.
Below in conjunction with the drawings and specific embodiments, the utility model is described in further detail.
Accompanying drawing explanation
Fig. 1 is the signal flow graph of the utility model embodiment mono-method.
Fig. 2 is the circuit structure block diagram of the utility model embodiment mono-.
Fig. 3 is the load current detection of the utility model embodiment mono-and the circuit structure diagram of comparison circuit.
Fig. 4 is the circuit structure diagram of the valley point current selector of the utility model embodiment mono-.
Fig. 5 is the inductive current detection of the utility model embodiment mono-and the circuit structure diagram of comparison circuit
Fig. 6 is the circuit structure diagram of the pulse selector of the utility model embodiment mono-.
Fig. 7 is the circuit structure diagram of the pulse generator of the utility model embodiment mono-
Fig. 8 a is the utility model embodiment mono-output voltage V when load jumps to 16.5W from 8.5W under limit
o, inductive current I
lwith load current I
otime-domain-simulation oscillogram.
Fig. 8 b is the utility model embodiment mono-output voltage V o, inductive current I when load jumps to 24.5W from 8.5W under limit
lwith load current I
otime-domain-simulation oscillogram.
Fig. 8 c is the utility model embodiment mono-output voltage V o, inductive current I when load jumps to 32.5W from 8.5W under limit
lwith load current I
otime-domain-simulation oscillogram.
Fig. 8 d is the utility model embodiment mono-output voltage V o, inductive current I when load jumps to 32.5W continuously from 8.5W under limit
lwith load current I
otime-domain-simulation oscillogram.
Fig. 9 is for adopting the converter of above-mentioned control method and device thereof under steady-working state, and load jumps to the simulation waveform of 24.5W, 16.5W, 8.5W continuously from 32.5W.
Fig. 8,9 simulated conditions are as follows: input voltage V
in=5V, output reference voltage V
ref=8V, inductance L=10 μ H, capacitor C=470 μ F, control impuls P
hduration of high level be τ
on_Hthe duration of the high level of=10 μ s, control impuls PL is τ
on_L=4 μ s, default load current reference value I
1=3.75A, I
2=2.815A, I
3=1.875A, default inductive current valley I
v1=5A, I
v2=3.5, I
v3=2A, I
v4=0.5A.
Territory simulation waveform figure when Figure 10 (a) controls Boost converter load increases to 24.5W from 16.5W saltus step under limit for existing valley point current type pulse train; Territory simulation waveform figure when Figure 10 (b) controls Boost converter load is reduced to 8.5W from 16.5W saltus step under limit for existing valley point current type pulse train
The simulated conditions of Figure 10 is as follows: input voltage V
in=5V, output reference voltage V
ref=8V, inductance L=10 μ H, capacitor C=470 μ F, control impuls P
hduration of high level be τ
on_H=10 μ s, control impuls P
lduration of high level be τ
on_L=4 μ s, default valley point current Iv=2A.
Figure 11 is the circuit structure block diagram of the utility model embodiment bis-.
Figure 12 is the circuit structure block diagram of the utility model embodiment tri-.
Embodiment
Embodiment mono-
Fig. 1 illustrates, a kind of embodiment of the present utility model:
At each switch periods initial time, controller is according to the load current I of switch converters TD
owith load reference current I
1, I
2, I
3compare, and select suitable inductive current valley I according to result relatively
v, its valley point current selective rule is: if I
olarger, select larger I
vvalue, if I
oless, select less I
vvalue.Meanwhile, controller is according to the output voltage V of switch converters TD
owith reference voltage V
refbetween relation select the effective control impuls in this switch periods, thereby realize the control to switch converters TD.Its control impuls selective rule is: if V
olower than V
ref, adopt control impuls P
hswitching tube S in control switch converter; Otherwise, if V
ohigher than V
ref, adopt control impuls P
lcontrol switch pipe S.Controller produces control impuls P
hmethod be: at the initial t of certain switch periods
0constantly, single triggering timing device starts timing, control impuls P
hfrom low level, become high level, the switching tube S in converter TD is open-minded, inductive current I
lrise; At t
0+ τ
on_Hconstantly, single triggering timing device finishes timing, control impuls P
hremaining high level set time τ
on_Hafter become low level, switching tube S turn-offs, diode D is open-minded, inductive current declines; At inductive current, drop to default valley point current I
vconstantly, control impuls P
hremaining low level time τ
off_Hafter become high level, converter enters next switch periods.
Controller produces control impuls P
lmethod and said process similar, difference is control impuls P in a switch periods
lfor the low level duration is respectively τ
on_L(τ
on_L< τ
on_H).
Fig. 2 illustrates, the device of the control method of the Switching Power Supply that this is routine, by converter TD and controller, formed, controller comprises voltage detecting circuit VD, load current detection and comparison circuit IDC1, inductive current detects and comparison circuit IDC2, valley point current selector IS, pulse selector PS, pulse generator PG, single triggering timing device OOT1, single triggering timing device OOT2, drive circuit DR, its design feature is: load current detection is connected with valley point current selector IS with comparison circuit IDC1, inductive current detects and comparison circuit IDC2 and pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2 is connected, voltage detecting circuit VD, pulse selector PS, pulse generator PG, drive circuit be connected DR successively, pulse generator PG is connected with comparison circuit IDC, single triggering timing device OOT1, single triggering timing device OOT2 with current detecting.
Fig. 3 illustrates, and the load current detection that this is routine and comparison circuit IDC1 specifically consist of: load current detection circuit ID1 and comparator AC1, AC2, AC3, consist of; The positive ends of all comparators all meets load current I
o, the load current reference value I that negative polarity termination is default
1, I
2, I
3.
Fig. 4 illustrates: specifically the consisting of of the valley point current selector that this is routine: by forming with door AG1, AG2, AG3, AG4 and switch S 1, S2, S3, S4.The input termination load current detection of AG1 and the output signal V of comparison circuit IDC1
c1, V
c2, V
c3.The input termination of AG2
v
c2, V
c3, the input termination of AG3
v
c3, the input termination of AG4
the output of AG1, AG2, AG3, AG4 joins with switch S 1, S2, S3, S4 respectively.
Fig. 5 illustrates, and this routine inductive current detection specifically consists of with comparison circuit IDC2's: inductive current detection circuit ID2 and comparator AC4, consist of; Valley point current I is selected in the positive ends selecting of comparator AC4
v, the inductive current I of negative polarity termination current detection circuit ID2 output
l; The output of comparator AC4 is connected with pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2.
Fig. 6 illustrates, and the pulse selector PS that this is routine specifically consists of: comparator AC5 and d type flip flop DFF, consist of; The converter output voltage V of the positive polarity termination voltage detecting circuit VD output of comparator AC5
o, negative polarity termination reference voltage V
ref, the output of AC5 is connected with the D end of d type flip flop DFF; The output Q of d type flip flop DFF and
pG is connected with pulse generator.
Fig. 7 illustrates, and the pulse generator PG that this is routine specifically consists of: by rest-set flip-flop RSFF1, RSFF2, with door AG5, AG6, and or door OG form; The S end of rest-set flip-flop RSFF1 and RSFF2 all meets the output signal V of current detecting and comparison circuit
c4, the output signal V of R end difference order triggering timing device OOT1 and OOT2
tLand V
tH; With the Q end of the input termination rest-set flip-flop RSFF1 of door AG5 and the Q end of trigger DFF, hold with the Q of the input termination rest-set flip-flop RSFF2 of door AG6 and trigger DFF
end; Or the input termination of door OG and the output of door AG5 and AG6, the drive circuit DR of the output termination switching tube S of OG.
Its course of work of the device of this example and principle are:
Fig. 1-7 illustrate, and load current detection and comparison circuit IDC1 are by load current I now
ocompare with load current fiducial value, and signal is relatively outputed to valley point current selector IS; Valley point current selector is according to the suitable valley current value I of the output signal selection of load current detection and comparison circuit IDC1
v; Inductive current detects with comparison circuit IDC2 and produces the clock pulse signal V that the switching tube cycle starts
c4; As clock pulse signal V
c4arrive constantly, pulse selector PS is output voltage V more now
owith reference voltage V
refmagnitude relationship, and export the logical signal that represents comparative result to pulse generator PG; In this simultaneously, single triggering timing device OOT1 or OOT2 start timing; Pulse generator PG is according to the signal V that clocks of single triggering timing device OOT1 or OOT2
tLor V
tH, clock pulse signal V
c4produce all different control impuls P of frequency and duty ratio
h, P
lthe control of realization to converter switches pipe S.
Load current detection and comparison circuit IDC1 complete load current detection and comparison, and comparative result is outputed to the input that valley point current is selected IS: as Fig. 2,3 illustrates, load current detection circuit ID1 detects load current I
o; Comparator AC1, AC2, AC3 are by load current I
owith load current reference value I
1, I
2, I
3compare, as load current I
ohigher than I
1time, the output signal V of three comparators
c1, V
c2, V
c3be high level; As load current I
olower than I
1higher than I
2time, V
c1for low level, V
c2and V
c3for high level; As load current I
olower than I
2higher than I
3time, the output signal V of comparator
c1and V
c2for low level, V
c3for high level; As load current I
olower than default load current reference value I
3time, the output signal V of three comparators
c1, V
c2, V
c3be low level.
Valley point current selector IS chooses suitable valley current value: Fig. 2,4 according to the output signal of load current detection and comparison circuit IDC1 and illustrates: the input termination load current detection of AG1 and the output signal V of comparison circuit
c1, V
c2, V
c3.The input termination of AG2
v
c2, V
c3, the input termination of AG3
v
c3, the input termination of AG4
when AG1 output high level, switch S 1 conducting, outputting inductance electric current valley is I
v1, when AG2 output high level, switch S 2 conductings, outputting inductance electric current valley is I
v2, when AG3 output high level, switch S 3 conductings, outputting inductance electric current valley is I
v3, when AG4 output high level, outputting inductance electric current valley is I
v4.
Inductive current detects with comparison circuit IDC2 and completes inductive current detection and relatively produce the switch periods clock pulse signal V of the zero hour
c4: Fig. 2,5 illustrates, and inductive current detection circuit ID2 detects inductive current I
l; Comparator AC4 is by the valley point current I selecting
vwith inductive current I
lcompare; As inductive current I
llower than default valley point current I
vtime, the output signal V of comparator AC1
c4for high level, otherwise, I worked as
llower than I
vtime, V
c4for low level; Due to inductive current I
llower than default valley point current I
vconstantly, S is open-minded for converter switches pipe, I
lstart to rise, the output signal V of comparator AC4
c4for a series of narrow pulse signals.Pulse selector PS completes the comparison of output voltage and the selection of control impuls: Fig. 2,6 illustrates, and comparator AC5 is by output voltage V
osame reference voltage V
refcompare, work as output voltage V
olower than reference voltage V
reftime, the output signal V of comparator AC5
c5for low level, otherwise, V worked as
olower than V
reftime, V
c5for high level; Work as V
c4rising edge comes interim, and d type flip flop DFF is by the output signal V of comparator AC5 now
c5export Q end to, produce pulse selecting signal V
q, according to the operation principle of trigger: V
qat V
c4next rising edge remain unchanged before arriving, and
level height all the time with V
qon the contrary.
Pulse generator PG completes generation and the output of control impuls: Fig. 2,7 illustrates, and works as V
c4rising edge comes interim, the S end input high level of rest-set flip-flop RSFF1, the control wave P of RSFF1 output
lfor high level, when single triggering timing device OOT1 clocks end, the R end input high level of rest-set flip-flop RSFF1, the control wave P of RSFF1 output
lbecome low level; The course of work of rest-set flip-flop RSFF2 and above-mentioned RSFF1 are similar, but due to the R termination list triggering timing device OOT2 of RSFF2, the duration that clocks of single triggering timing device OOT2 is greater than the duration that clocks of single triggering timing device OOT1, the control wave P of RSFF2 output
hhigh level lasting time be greater than P
l; As pulse selecting signal V
qfor high level,
during for low level, AG5 is open-minded with door, and AG6 is blocked, or door OG output control pulse P
lto drive circuit; Otherwise, as pulse selecting signal V
qfor low level,
during for high level, AG6 is open-minded with door, and AG5 is blocked, or door OG output control pulse P
hto drive circuit.
This routine converter is Boost converter.
With PSIM software, this routine method is carried out to time-domain-simulation analysis, result is as follows.
The simulation waveform of the converter that Fig. 8 is the above-mentioned control method of employing and control device thereof under steady-working state.Output voltage V while as shown in Figure 8 a, jumping to 16.5W for load from 8.5W
o, inductive current I
lwith load current I
osimulation waveform, from Fig. 8 a, can find out, after load current generation saltus step increases, valley point current becomes 2A from 0.5A, output voltage is still stabilized in voltage reference value 8V.Fig. 8 b, Fig. 8 c are respectively the simulation waveform of load when 8.5W jumps to 24.5W and jump to 32.5W from 8.5W.Fig. 8 d is the simulation waveform of load while jumping to 32.5W continuously from 8.5W.As can be seen from Figure 8, adopt the converter of the utility model control method and device thereof when load generation saltus step increases, can promptly select larger valley point current, change its pulse train combination, make converter steady operation.
Fig. 9 is for adopting the converter of above-mentioned control method and device thereof under steady-working state, and load jumps to the simulation waveform of 24.5W, 16.5W, 8.5W continuously from 32.5W.As can be seen from Figure 9, adopt the converter of the utility model control method and device thereof when load generation saltus step reduces, can promptly select less valley point current, change its pulse train combination, make converter steady operation.
Figure 10 is existing valley point current type pulse train control change device output voltage V when load generation saltus step
o, inductive current I
lwith load current I
osimulation waveform.From Figure 10 (a), can find out, when load generation saltus step increases to 24.5W from 16.5W, load current Io increases, and bearing power has exceeded the maximum power that converter can reach, and falling appears in output voltage V o, and converter is steady operation again.From Figure 10 (b), can find out, when load generation saltus step is reduced to 8.5W from 16.5W, load current Io reduces, and bearing power has exceeded the minimum power that converter can reach, and upper punch appears in output voltage V o, and converter is steady operation again.Therefore adopt converter of the present utility model, can not only suppressor pulse sequence control the low-frequency fluctuation phenomenon of continuous operation mode switch converters, and can be according to the valley point current of load current size adjustment inductance, to adapt to the variation of load, effectively widened the loading range of converter.
Embodiment bis-
Figure 11 illustrates, and this example is basic identical with embodiment mono-, and difference is: the converter TD of the Switching Power Supply that this example is controlled is Buck converter.
Embodiment tri-
Figure 12 illustrates, and this example is basic identical with embodiment mono-, and difference is: the converter TD of the Switching Power Supply that this example is controlled is Buck-Boost converter.
The utility model method can realize with analogue device or digital device easily; Except the Switching Power Supply that the converter can be used in above embodiment forms, also can be used for the multiple power the electric circuit constitute Switching Power Supplies such as Cuk converter, BIFRED converter, anti exciting converter, half-bridge converter, full-bridge converter.
Claims (1)
1. many valley point currents type pulse-sequence control device of a continuous operation mode Switching Power Supply, it is characterized in that by converter TD and controller group, controller comprises that voltage detecting circuit VD, load current detection and comparison circuit IDC1, valley point current selector IS, inductive current detect and comparison circuit IDC2, pulse selector PS, pulse generator PG, single triggering timing device OOT1, single triggering timing device OOT2, drive circuit DR; It is characterized in that: load current detection is connected with valley point current selector with comparison circuit IDC1; Inductive current detection is connected with comparison circuit, pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2; Voltage detecting circuit VD, pulse selector PS, pulse generator PG, drive circuit are connected to DR successively; Pulse generator PG detects and is connected with comparison circuit IDC2, single triggering timing device OOT1, single triggering timing device OOT2 with inductive current.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201420317161.9U CN203933397U (en) | 2014-06-15 | 2014-06-15 | Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201420317161.9U CN203933397U (en) | 2014-06-15 | 2014-06-15 | Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN203933397U true CN203933397U (en) | 2014-11-05 |
Family
ID=51829149
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201420317161.9U Expired - Fee Related CN203933397U (en) | 2014-06-15 | 2014-06-15 | Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN203933397U (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107769606A (en) * | 2017-12-05 | 2018-03-06 | 西南交通大学 | Capacitance current bifrequency pulse sequence control method and its device |
| CN113315374A (en) * | 2021-05-28 | 2021-08-27 | 电子科技大学 | Duty ratio modulation pulse sequence control method and device based on Buck converter |
-
2014
- 2014-06-15 CN CN201420317161.9U patent/CN203933397U/en not_active Expired - Fee Related
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107769606A (en) * | 2017-12-05 | 2018-03-06 | 西南交通大学 | Capacitance current bifrequency pulse sequence control method and its device |
| CN107769606B (en) * | 2017-12-05 | 2023-10-20 | 西南交通大学 | Capacitive current double-frequency pulse sequence control method and device thereof |
| CN113315374A (en) * | 2021-05-28 | 2021-08-27 | 电子科技大学 | Duty ratio modulation pulse sequence control method and device based on Buck converter |
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