CN112615541B - Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter - Google Patents
Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter Download PDFInfo
- Publication number
- CN112615541B CN112615541B CN202011564219.6A CN202011564219A CN112615541B CN 112615541 B CN112615541 B CN 112615541B CN 202011564219 A CN202011564219 A CN 202011564219A CN 112615541 B CN112615541 B CN 112615541B
- Authority
- CN
- China
- Prior art keywords
- power switch
- resonant
- capacitor
- inductor
- current
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/0013—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries acting upon several batteries simultaneously or sequentially
- H02J7/0014—Circuits for equalisation of charge between batteries
- H02J7/0016—Circuits for equalisation of charge between batteries using shunting, discharge or bypass circuits
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention provides a bus type energy storage element equalization circuit, a system and a method based on a zero-current PWM bidirectional DC-DC CUK converter, comprising the following steps: the positive output end of the first equalization circuit is connected with the positive end of the equalization bus, the negative output end of the first equalization circuit is connected with the negative end of the equalization bus, the positive output end of the second equalization circuit is connected with the positive end of the equalization bus, the negative output end of the second equalization circuit is connected with the negative end of the equalization bus, the positive output end of the Nth equalization circuit is connected with the positive end of the equalization bus, the negative output end of the Nth equalization circuit is connected with the negative end of the equalization bus, and N is a positive integer. By using the equalization circuit in the equalization bus, the energy balance in the bus is realized, so that the equalization bus system operates more stably and smoothly, and the energy loss is smaller.
Description
Technical Field
The invention relates to the field of electronic circuits, in particular to a bus type energy storage element equalization circuit, a system and a method based on a zero-current PWM bidirectional DC-DC CUK converter.
Background
The direct current converter generally adopts a PWM control mode, a switching tube works in a hard switching state, and the bidirectional DC-DC CUK converter is a typical direct current converter and is widely applied to a bus type energy storage element equalizing circuit, and the structure of the direct current converter is shown in fig. 10. Since the actual switching tube is not an ideal device, the voltage of the switch does not drop immediately to zero when it is turned on, but rather has a fall time, and its current does not rise immediately to the load current, and has a rise time. During this time, there is an overlap between current and voltage, resulting in a loss, known as turn-on loss. When the switching tube is turned off, the voltage of the switching tube does not immediately rise from zero to the power supply voltage, but has a rise time, and the current thereof does not immediately drop to zero, and also has a fall time. During this time, there is also an overlap of current and voltage, creating a loss, known as turn-off loss. The switching loss and the turn-off loss are collectively referred to as switching loss, under certain conditions, the switching loss of the switching tube in each switching period is constant, the total switching loss of the converter is proportional to the switching frequency, the higher the switching frequency is, the larger the total switching loss is, the lower the efficiency of the converter is, and the lower the equalization efficiency of the bus type energy storage element equalization system is caused. The presence of the switch therefore limits the increase in the switching frequency of the converter and thus limits the miniaturization and weight saving of the converter and of the equalization system.
Disclosure of Invention
The invention aims at least solving the technical problems in the prior art, and particularly creatively provides a bus type energy storage element equalization circuit, an equalization system and a bus type energy storage element equalization method based on a zero-current PWM bidirectional DC-DC CUK converter.
In order to achieve the above object of the present invention, the present invention provides a bus type energy storage element equalization circuit based on a zero-current PWM bidirectional DC-DC CUK converter, comprising:
the first power switch comprises a first inductor, a fourth inductor, a first a capacitor, a first b capacitor, a second capacitor, a first power switch, a second power switch, a first auxiliary switch, a first resonant inductor, a second resonant inductor and a first resonant capacitor;
the energy storage device comprises a first inductor, a first power switch drain electrode, a first resonant capacitor, a first auxiliary switch drain electrode, a first power switch source electrode, a second power switch source electrode, a fourth inductor, a first auxiliary switch source electrode, a first a capacitor, a second resonant inductor, a second power switch source electrode, a first b capacitor, a second power switch source electrode, a fourth inductor, and a fourth inductor.
Preferably, the method further comprises: a first diode, a second power switch freewheel diode, and a first resonant diode; the positive pole of the first diode is connected with the source electrode of the first power switch, the negative pole of the first diode is connected with the drain electrode of the first power switch, the positive pole of the second power switch freewheeling diode is connected with the source electrode of the second power switch, the negative pole of the second power switch freewheeling diode is connected with the drain electrode of the second power switch, the positive pole of the first resonance diode is connected with the source electrode of the first auxiliary switch, and the negative pole of the first resonance diode is connected with the drain electrode of the first auxiliary switch.
Preferably, the method further comprises: the second inductance is provided with a second inductance,
one end of the second inductor is connected with the negative electrode of the power supply, and the other end of the second inductor is connected with the source electrode of the first power switch.
Preferably, the method further comprises: the third inductance is provided with a third inductance,
one end of the third inductor is connected with the source electrode of the second power switch, and the other end of the third inductor is connected with one end of the second capacitor.
Preferably, the energy storage element comprises a battery or a super capacitor.
The invention also discloses a bus type energy storage element balancing system based on the zero-current PWM bidirectional DC-DC CUK converter, which comprises the following components: the positive output end of the first equalization circuit is connected with the positive end of the equalization bus, the negative output end of the first equalization circuit is connected with the negative end of the equalization bus, the positive output end of the second equalization circuit is connected with the positive end of the equalization bus, the negative output end of the second equalization circuit is connected with the negative end of the equalization bus, the positive output end of the Nth equalization circuit is connected with the positive end of the equalization bus, the negative output end of the Nth equalization circuit is connected with the negative end of the equalization bus, and N is a positive integer.
The invention also discloses a working method of the bus type energy storage element equalizing circuit based on the zero-current PWM bidirectional DC-DC CUK converter, which comprises the following steps:
the equalization circuit is divided into six stages when power is supplied from the left side to the right side,
s1, in the stage of t0-t1, the first auxiliary switch and the first power switch are turned off, and input current flows through a first resonant inductor and a second resonant inductor, -i Lr1 ＝i Lr2 ＝I i ，
Wherein i is Lr1 And i Lr1 Representing the current flowing through the first and second resonant inductances, respectively, I i Representing the input current, which can be considered as a constant value when the first inductance value is selected appropriately;
the input current and the output current both flow through the second power switch freewheel diode, i D2 ＝I i +I o ；
Wherein i is D2 Indicating the current flowing through the freewheeling diode of the second power switch, I o Representing the output current, which may be considered as a constant value when the fourth inductance value is selected appropriately;
when the first power switch is switched from off to on, the stage is ended;
s2, at the stage of t1-t2, the first power switch is turned on, the first auxiliary switch is kept turned off, under the action of the first a capacitor and the first b capacitor, the current flowing through the first resonant inductor and the second resonant inductor is linearly reduced from the input current value, is reversely increased to the output current value after being reduced to zero,
wherein L is r1 And L r2 Respectively representing a first resonance inductance value and a second resonance inductance value, U Ca And U Cb Respectively representing a first a capacitance terminal voltage and a first b capacitance terminal voltage, when the first a capacitance value and the first b capacitance value are properly selected, U Ca And U Cb Can be regarded as a constant value, and U Ca +U Cb ＝U i +U o ，U i And U o Respectively representing the input voltage and the output voltage, i, of the equalizing circuit S1 Indicating a flow through the firstCurrent of power switch, R S1 Representing the on-resistance, i, of the first power switch D2 Representing the current flowing through the freewheeling diode of the second power switch, R D2 Representing the on-resistance of the freewheeling diode of the second power switch; neglecting the pressure drop of the tube, solving the formula (1) to obtain,
wherein t is e [ t ] 1 ,t 2 ]When i S1 ＝I i +I o When the current flowing through the freewheeling diode of the second power switch is automatically cut off, the stage is ended;
s3, in the stage of t2-t3, the first power switch is kept on, the first auxiliary switch is kept off, and the output current flows through the first resonant inductor and the second resonant inductor, i Lr1 ＝-i Lr2 ＝I o ，i Lr1 Representing the current through the first resonant inductor, i Lr2 Representing the current flowing through the second resonant inductor,
the input current and the output current both flow through the first power switch, i S1 ＝I i +I o ；i S1 Indicating the current through the first power switch,
when the first auxiliary switch is switched from off to on, the circuit enters a resonance mode from a PWM mode, and the stage is ended;
s4, in the stage of t3-t4, the first power switch is kept on, resonance is generated by opening the first auxiliary switch, conditions are created for soft turn-off of the first power switch, the first resonance inductor, the first resonance capacitor, the first power switch and the first auxiliary switch form a first resonance loop, meanwhile, the second resonance inductor, the first resonance capacitor, the first a capacitor, the first b capacitor, the second power switch freewheeling diode and the first auxiliary switch also form a second resonance loop,
wherein u is Cr Representing the terminal voltage of the first resonant capacitor, C r Representing the first resonance capacitance value, i Sr Indicating the value of the current flowing through the first auxiliary switch, R Sr Representing the on-resistance of the first auxiliary switch; neglecting the pressure drop of the tube, solving the formulas (3) and (4) to obtain,
wherein t is e [ t ] 3 ,t 4 ]，ω 1 Representing the overall equivalent resonant angular frequency of the two resonant tanks,U Cr0 the terminal voltage of the first resonant capacitor at the time t 3;
when the current flowing through the freewheeling diode of the second power switch resonates from a positive value back to zero, the second resonant tank stops resonating, and the phase ends;
s5, in the stage of t4-t5, the first power switch and the first auxiliary switch are kept on, the second resonant circuit stops resonating, the first resonant circuit continues resonating,
neglecting the pressure drop of the tube, solving the formulas (8) and (9) to obtain,
u Cr (t)＝(I i +I o -I S11 )Z 1 sin[ω 2 (t-t 4 )]+U Cr1 cos[ω 2 (t-t 4 )] (11)
wherein t is e [ t ] 4 ,t 5 ]，ω 2 Representing the resonant angular frequency of the first resonant tank,Z 1 representing the first resonant tank impedance +.>U Cr1 For the terminal voltage of the first resonant capacitor at time t4, I S11 The current of the first power switch at the time t 4;
when i S1 <When 0, the first power switch is turned off to realize zero-current switching of the first power switch, when i Sr <When 0, the first auxiliary switch is turned off, so that zero-current switching of the first auxiliary switch can be realized;
s6, at the stage of t5-t6, the first power switch is turned off, the first resonant circuit stops resonance, the second resonant circuit starts resonance again,
neglecting the pressure drop of the tube, solving the formulas (12) and (13) to obtain,
u Cr (t)＝U Ca +U Cb +(I i +I o )Z 2 sin[ω 3 (t-t 5 )]+[U Cr2 -(U Ca +U Cb )]cos[ω 3 (t-t 4 )](15)
wherein t is e [ t ] 5 ,t 6 ]，ω 3 Representing the resonant angular frequency of the second resonant tank,Z 2 representing the second resonant tank impedance +.>U Cr2 The terminal voltage of the first resonant capacitor at the time t 5;
when i D2 ＝I i +I o When the second resonant circuit stops resonating, the phase ends, the circuit enters a PWM mode from a resonating mode, the phase ends, and the circuit returns to the first phase;
the derivation of the input voltage versus output voltage is as follows,
the average voltage value of the fourth inductor is zero in one period, so that the average value of the second power switch terminal voltage in one period is equal to the output voltage,
wherein T is s Representing PWM control period, the first stage (t 0-t 1), the second stage (t 1-t 2), the fourth stage (t 3-t 4), the sixth stage (t 5-t 6) and the second power switch terminal voltage are zero, the third stage (t 2-t 3) and the second power switch terminal voltage are the first a capacitor and the first b capacitorThe second power switch terminal voltage in the fifth stage (t 4-t 5) is the difference between the terminal voltage of the first resonant capacitor and the sum of the terminal voltages of the first a capacitor and the first b capacitor, and at time t4, the first resonant inductor current is near the maximum value, at which time the terminal voltage of the second resonant capacitor is approximately equal to zero, U Cr1 =0, and thus can be obtained,
wherein DeltaT 3 And DeltaT 5 Time intervals of the third phase and the fifth phase are respectively represented, T LC For the resonance period of the first resonant tank,ω 2 ΔT 5 ＝ω 2 (t 5 -t 4 ) Approximately pi, under soft-switching conditions, it is generally desirable that the peak value of the first power switch current be as small as possible, thus having I S11 ≈2(I i +I o ) The method comprises the steps of carrying out a first treatment on the surface of the The relation between the output voltage and the input voltage can be obtained by the formula (17),
as can be seen from equation (18), the output voltage can be varied by varying the PWM period, the third phase time, after the circuit parameters are determined.
In summary, due to the adoption of the technical scheme, the beneficial effects of the invention are as follows:
1, the circuit is introduced into a resonant circuit to realize soft switching of a switching tube, so that switching loss is reduced;
the 2 converter may employ constant frequency control, PWM control;
the circuit can apply a higher frequency switching tube to realize miniaturization and light weight of the converter and the equalization system;
4, the energy bidirectional flow analysis of the circuit is consistent;
the circuit can be used in an equalizing network, and each equalizing circuit can work independently and has small mutual interference.
Additional aspects and advantages of the invention will be set forth in part in the description which follows, and in part will be obvious from the description, or may be learned by practice of the invention.
Drawings
The foregoing and/or additional aspects and advantages of the invention will become apparent and may be better understood from the following description of embodiments taken in conjunction with the accompanying drawings in which:
FIG. 1 is a schematic diagram of a bus type energy storage element equalization system based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 2 is a schematic diagram of the bus type energy storage element balancing circuit connection based on a zero current PWM bidirectional DC-DC CUK converter of the present invention;
FIG. 3 is a first stage of operation of the bus type energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 4 is a second phase of operation of the bus type energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 5 is a third stage of operation of the bus type energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 6 is a fourth stage of operation of the bus energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 7 is a fifth stage of operation of the bus energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 8 is a sixth stage of operation of the bus energy storage element balancing circuit of the present invention based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 9 is a timing diagram of a bus type energy storage element equalization circuit based on a zero current PWM bi-directional DC-DC CUK converter;
FIG. 10 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 11 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 12 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 13 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 14 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 15 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
FIG. 16 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter of the present invention;
fig. 17 is a schematic diagram of a bus type energy storage element equalization circuit connection based on a zero-current PWM bidirectional DC-DC CUK converter of the present invention.
Detailed Description
Embodiments of the present invention are described in detail below, examples of which are illustrated in the accompanying drawings, wherein like or similar reference numerals refer to like or similar elements or elements having like or similar functions throughout. The embodiments described below by referring to the drawings are illustrative only and are not to be construed as limiting the invention.
As shown in fig. 1, the present invention provides a bus energy storage element equalization system based on a zero-current PWM bidirectional DC-DC CUK converter, which is characterized by comprising: the positive output end of the first equalization circuit is connected with the positive end of the equalization bus, the negative output end of the first equalization circuit is connected with the negative end of the equalization bus, the positive output end of the second equalization circuit is connected with the positive end of the equalization bus, the negative output end of the second equalization circuit is connected with the negative end of the equalization bus, the positive output end of the Nth equalization circuit is connected with the positive end of the equalization bus, the negative output end of the Nth equalization circuit is connected with the negative end of the equalization bus, and N is a positive integer.
By using the converter in the balance bus, the balance of energy in the bus is realized, so that the balance bus system operates more stably and smoothly, and the energy loss is smaller.
As shown in fig. 2 and 10, the present invention provides a bus type energy storage element equalization circuit based on a zero-current PWM bidirectional DC-DC CUK converter, comprising: the first power switch comprises a first inductor, a fourth inductor, a first a capacitor, a first b capacitor, a second capacitor, a first power switch, a second power switch, a first auxiliary switch, a first resonant inductor, a second resonant inductor and a first resonant capacitor;
the energy storage device comprises a first inductor, a first power switch drain electrode, a first resonant capacitor, a first auxiliary switch drain electrode, a first power switch source electrode, a second power switch source electrode, a fourth inductor, a first auxiliary switch source electrode, a first a capacitor, a second resonant inductor, a second power switch source electrode, a first b capacitor, a second power switch source electrode, a fourth inductor, and a fourth inductor.
The beneficial effects of the technical scheme are as follows: the controllable resonant circuit is added for the circuit, so that soft switching of all switching tubes is realized, the overall efficiency and energy density of the equalization circuit are improved, and the energy bidirectional flow analysis of the circuit is consistent.
The bus type energy storage element equalization circuit based on the zero-current PWM bidirectional DC-DC CUK converter preferably further comprises: a first diode, a second power switch freewheel diode, and a first resonant diode; the positive pole of the first diode is connected with the source electrode of the first power switch, the negative pole of the first diode is connected with the drain electrode of the first power switch, the positive pole of the second power switch freewheeling diode is connected with the source electrode of the second power switch, the negative pole of the second power switch freewheeling diode is connected with the drain electrode of the second power switch, the positive pole of the first resonance diode is connected with the source electrode of the first auxiliary switch, and the negative pole of the first resonance diode is connected with the drain electrode of the first auxiliary switch.
The beneficial effects of the technical scheme are as follows: the first diode, the second power switch freewheeling diode and the first resonant diode can improve the switching speed of the corresponding power switch.
The bus type energy storage element equalization circuit based on the zero-current PWM bidirectional DC-DC CUK converter preferably further comprises: the second inductance is provided with a second inductance,
one end of the second inductor is connected with the negative electrode of the power supply, and the other end of the second inductor is connected with the source electrode of the first power switch.
The beneficial effects of the technical scheme are as follows: the circuit can be applied to an equalizing network, and each equalizing circuit can realize independent work and has small mutual interference.
The bus type energy storage element equalization circuit based on the zero-current PWM bidirectional DC-DC CUK converter preferably further comprises: the third inductance is provided with a third inductance,
one end of the third inductor is connected with the source electrode of the second power switch, and the other end of the third inductor is connected with one end of the second capacitor.
The beneficial effects of the technical scheme are as follows: the circuit can be applied to an equalizing network, and each equalizing circuit can realize independent work and has small mutual interference.
The power supply principle of the circuit from the left side to the right side is the same as that of the circuit from the right side to the left side. The circuit is divided into six stages from left to right (the second power switch is constantly turned off),
FIG. 3 is a first stage (t 0-t 1) of the equalizer circuit operation;
at this stage, the first auxiliary switch and the first power switch are turned off, and the input current flows through the first resonant inductor and the second resonant inductor, -i Lr1 ＝i Lr2 ＝I i ，
Wherein i is Lr1 And i Lr1 Representing the electricity flowing through the first resonant inductor and the second resonant inductor, respectivelyFlow, I i Representing the input current, which can be considered as a constant value when the first inductance value is selected appropriately;
the input current and the output current both flow through the second power switch freewheel diode, i D2 ＝I i +I o ；
Wherein i is D2 Indicating the current flowing through the freewheeling diode of the second power switch, I o Representing the output current, which may be considered as a constant value when the fourth inductance value is selected appropriately;
when the first power switch is switched from off to on, the stage is ended;
FIG. 4 is a second phase (t 1-t 2) of the equalizer circuit operation;
in this stage, the first power switch is turned on, the first auxiliary switch is kept turned off, under the action of the first a capacitor and the first b capacitor, the current flowing through the first resonant inductor and the second resonant inductor is linearly reduced from the input current value, is reversely increased to the output current value after being reduced to zero,
wherein L is r1 And L r2 Respectively representing a first resonance inductance value and a second resonance inductance value, U Ca And U Ca Respectively representing a first a capacitance terminal voltage and a first b capacitance terminal voltage, when the first a capacitance value and the first b capacitance value are properly selected, U Ca And U Ca Can be regarded as a constant value, and U Ca +U Cb ＝U i +U o ，U i And U o Respectively representing the input voltage and the output voltage, i, of the equalizing circuit S1 Indicating the current flowing through the first power switch, R S1 Representing the on-resistance of the first power switch, R D2 Representing the on-resistance of the freewheeling diode of the second power switch; neglecting the pressure drop of the tube, solving the formula (1) to obtain,
wherein t is e [ t ] 1 ,t 2 ]When i S1 ＝I i +I o When the current flowing through the freewheeling diode of the second power switch is automatically cut off, the stage is ended;
FIG. 5 is a third stage (t 2-t 3) of the equalizer circuit operation;
at this stage, the first power switch remains on, the first auxiliary switch remains off, and the output current flows through the first resonant inductor and the second resonant inductor, i Lr1 ＝-i Lr2 ＝I o ，
The input current and the output current both flow through the first power switch, i S1 ＝I i +I o ；
When the first auxiliary switch is switched from off to on, the circuit enters a resonance mode from a PWM mode, and the stage is ended;
FIG. 6 is a fourth stage (t 3-t 4) of the equalizer circuit operation;
in this stage, the first power switch is kept on, the circuit is made to resonate by opening the first auxiliary switch, conditions are created for soft turn-off of the first power switch, the first resonant inductor, the first resonant capacitor, the first power switch and the first auxiliary switch form a first resonant circuit, and the second resonant inductor, the first resonant capacitor, the first a capacitor, the first b capacitor, the second power switch freewheeling diode and the first auxiliary switch also form a second resonant circuit,
wherein u is Cr Representing the terminal voltage of the first resonant capacitor, C r Representing a first resonanceCapacitance value, i Sr Indicating the value of the current flowing through the first auxiliary switch, R Sr Representing the on-resistance of the first auxiliary switch; neglecting the pressure drop of the tube, solving the formulas (3) and (4) to obtain,
wherein t is e [ t ] 3 ,t 4 ]，L e1 ＝L r1 ||L r2 ，/> U Cr0 The terminal voltage of the first resonant capacitor at the time t 3;
when the current flowing through the freewheeling diode of the second power switch resonates from a positive value back to zero, the second resonant tank stops resonating, and the phase ends;
FIG. 7 is a fifth stage (t 4-t 5) of the equalizer circuit operation;
at this stage, the first power switch and the first auxiliary switch are kept on, the second resonant circuit stops resonating, the first resonant circuit continues resonating,
neglecting the pressure drop of the tube, solving the formulas (8) and (9) to obtain,
u Cr (t)＝(I i +I o -I S11 )Z 5 sin[ω 2 (t-t 4 )]+U Cr1 cos[ω 2 (t-t 4 )] (11)
wherein t is e [ t ] 4 ,t 5 ]，U Cr1 IS11 IS the terminal voltage of the first resonant capacitor at the time t4 and IS the current of the first power switch at the time t 4;
when i S1 <When 0, the first power switch is turned off to realize zero-current switching of the first power switch, when i Sr <When 0, the first auxiliary switch is turned off, so that zero-current switching of the first auxiliary switch can be realized;
FIG. 8 is a sixth stage (t 5-t 6) of the equalizer circuit operation;
at this stage, the first power switch is turned off, the first resonant tank stops resonating, the second resonant tank starts resonating again,
neglecting the pressure drop of the tube, solving the formulas (12) and (13) to obtain,
u Cr (t)＝U Ca +U Cb +(I i +I o )Z 6 sin[ω 3 (t-t 5 )]+[U Cr2 -(U Ca +U Cb )]cos[ω 3 (t-t 4 )](15)
wherein t is e [ t ] 5 ,t 6 ]，U Cr2 The terminal voltage of the first resonant capacitor at the time t 5;
when i D2 ＝I i +I o When the second resonant circuit stops resonating, this phase ends, the circuit enters PWM mode from resonant mode, this phase ends, and the phase returns to the first phase.
The derivation of the input voltage versus output voltage is as follows,
the average voltage value of the fourth inductor is zero in one period, so that the average value of the second power switch terminal voltage in one period is equal to the output voltage,
the first phase (t 0-t 1), the second phase (t 1-t 2), the fourth phase (t 3-t 4) and the sixth phase (t 5-t 6) have the second power switch terminal voltage of zero, the third phase (t 2-t 3) has the second power switch terminal voltage of the sum of the terminal voltages of the first a capacitor and the first b capacitor, the fifth phase (t 4-t 5) has the second power switch terminal voltage of the difference between the terminal voltage of the first resonant capacitor and the sum of the terminal voltages of the first a capacitor and the first b capacitor, and at the moment t4, the first resonant inductor current is near the maximum value, the terminal voltage of the second resonant capacitor at the moment is approximately equal to zero, U Cr1 =0, and thus can be obtained,
wherein DeltaT 3 And DeltaT 5 Time intervals of the third phase and the fifth phase are respectively represented, T LC For the resonance period of the first resonant tank,ωΔT 5 approximately pi, under soft switching conditions, it is generally desirable that the peak-to-peak value of the first power switch current be as small as possible, thus having I S11 ≈2(I i +I o ) The method comprises the steps of carrying out a first treatment on the surface of the The relation between the output voltage and the input voltage can be obtained by the formula (17),
as can be seen from equation (18), after the circuit parameters are determined, the output voltage can be changed by changing the PWM period, the third phase time;
fig. 9 is a timing diagram of a bus type energy storage element equalization circuit based on a zero current PWM bidirectional DC-DC CUK converter, by which the equalization circuit is timing controlled.
FIG. 10 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
FIG. 11 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
the energy storage device comprises a first power switch source electrode, a second inductor, a first resonant inductor, a first power switch drain electrode, a second resonant capacitor, a first auxiliary switch source electrode, a second power switch source electrode, a first capacitor, a second capacitor, a third inductor and a third inductor.
FIG. 12 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter in accordance with an embodiment of the present invention;
the energy storage device comprises a first inductor, a first power switch drain electrode, a first resonant capacitor, a first auxiliary switch drain electrode, a first power switch source electrode, a second power switch drain electrode, a third inductor, a first power switch source electrode, a second power switch source electrode, a first capacitor, a second capacitor, a third inductor and a third inductor.
FIG. 13 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
one end of the second inductor is connected with the negative electrode of the energy storage element, the other end of the first inductor is connected with the source electrode of the first power switch, one end of the first resonant inductor is connected with the source electrode of the first auxiliary switch, the other end of the first resonant inductor is connected with the positive electrode of the energy storage element, the other end of the first resonant inductor is also connected with the drain electrode of the first power switch, one end of the first resonant capacitor is connected with the drain electrode of the first auxiliary switch, the other end of the first resonant capacitor is connected with the source electrode of the first power switch, one end of the first a capacitor is connected with the source electrode of the first auxiliary switch, the other end of the first capacitor a is connected with one end of a second resonant inductor, the other end of the second resonant inductor is connected with a source electrode of a second power switch, one end of the first capacitor b is connected with a drain electrode of the second power switch, the other end of the first capacitor b is connected with the source electrode of the first power switch, one end of the second capacitor is connected with the source electrode of the second power switch, the other end of the second capacitor is connected with one end of a fourth inductor, and the other end of the fourth inductor is connected with the drain electrode of the second power switch.
FIG. 14 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
the energy storage device comprises a first inductor, a second inductor, a first power switch drain electrode, a second power switch source electrode, a first capacitor, a second capacitor, a third capacitor, a first auxiliary switch drain electrode, a second capacitor, a third capacitor and a third capacitor.
FIG. 15 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
one end of the first inductor is connected with the positive electrode of the energy storage element, the other end of the first inductor is connected with the drain electrode of the first power switch, one end of the second inductor is connected with the negative electrode of the energy storage element, the other end of the first inductor is connected with the source electrode of the first power switch, one end of the first resonant inductor is connected with the source electrode of the first auxiliary switch, the other end of the first resonant inductor is connected with the drain electrode of the first power switch, one end of the first resonant capacitor is connected with the drain electrode of the first auxiliary switch, the other end of the first resonant capacitor is connected with the source electrode of the first power switch, one end of the first capacitor a is connected with the source electrode of the first auxiliary switch, the other end of the first capacitor a is connected with one end of the second resonant inductor, the other end of the second resonant inductor is connected with the source electrode of the second power switch, one end of the first capacitor b is connected with the drain electrode of the second power switch, the other end of the first capacitor b is connected with the source electrode of the first power switch, one end of the second capacitor is connected with the source electrode of the second power switch, the other end of the second capacitor is connected with one end of the fourth inductor, and the other end of the fourth inductor is connected with the drain electrode of the second power switch.
FIG. 16 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter in accordance with an embodiment of the present invention;
one end of the first inductor is connected with the positive electrode of the energy storage element, the other end of the first inductor is connected with the drain electrode of the first power switch, one end of the first resonant capacitor is connected with the drain electrode of the first auxiliary switch, the other end of the first resonant capacitor is connected with the negative electrode of the energy storage element, the other end of the first resonant capacitor is also connected with the source electrode of the first power switch, one end of the first resonant inductor is connected with the source electrode of the first auxiliary switch, the other end of the first resonant inductor is connected with the drain electrode of the first power switch, one end of the first a capacitor is connected with the source electrode of the first auxiliary switch, the second power switch is characterized in that the other end of the first capacitor a is connected with one end of a second resonant inductor, the other end of the second resonant inductor is connected with a source electrode of the second power switch, one end of the first capacitor b is connected with a drain electrode of the second power switch, the other end of the first capacitor b is connected with the source electrode of the first power switch, one end of the third inductor is connected with the source electrode of the second power switch, the other end of the third inductor is connected with one end of the second capacitor, the other end of the second capacitor is connected with one end of a fourth inductor, and the other end of the fourth inductor is connected with the drain electrode of the second power switch.
FIG. 17 is a schematic diagram of a bus type energy storage element balancing circuit connection based on a zero current PWM bi-directional DC-DC CUK converter according to an embodiment of the present invention;
one end of the second inductor is connected with the negative electrode of the energy storage element, the other end of the first inductor is connected with the source electrode of the first power switch, one end of the first resonant inductor is connected with the source electrode of the first auxiliary switch, the other end of the first resonant inductor is connected with the positive electrode of the energy storage element, the other end of the first resonant inductor is also connected with the drain electrode of the first power switch, one end of the first resonant capacitor is connected with the drain electrode of the first auxiliary switch, the other end of the first resonant capacitor is connected with the source electrode of the first power switch, one end of the first a capacitor is connected with the source electrode of the first auxiliary switch, the second power switch is characterized in that the other end of the first capacitor a is connected with one end of a second resonant inductor, the other end of the second resonant inductor is connected with a source electrode of the second power switch, one end of the first capacitor b is connected with a drain electrode of the second power switch, the other end of the first capacitor b is connected with the source electrode of the first power switch, one end of the third inductor is connected with the source electrode of the second power switch, the other end of the third inductor is connected with one end of the second capacitor, the other end of the second capacitor is connected with one end of a fourth inductor, and the other end of the fourth inductor is connected with the drain electrode of the second power switch.
While embodiments of the present invention have been shown and described, it will be understood by those of ordinary skill in the art that: many changes, modifications, substitutions and variations may be made to the embodiments without departing from the spirit and principles of the invention, the scope of which is defined by the claims and their equivalents.
Claims (7)
1. A bus type energy storage element equalization circuit based on zero-current PWM bidirectional DC-DC CUK converter is characterized by comprising:
the first power switch comprises a first inductor, a fourth inductor, a first a capacitor, a first b capacitor, a second capacitor, a first power switch, a second power switch, a first auxiliary switch, a first resonant inductor, a second resonant inductor and a first resonant capacitor;
the energy storage device comprises a first inductor, a first power switch drain electrode, a first resonant capacitor, a first auxiliary switch drain electrode, a first power switch source electrode, a second power switch source electrode, a fourth inductor, a first auxiliary switch source electrode, a first a capacitor, a second resonant inductor, a second power switch source electrode, a first b capacitor, a second power switch source electrode, a fourth inductor, and a fourth inductor.
2. The zero current PWM bi-directional DC-DC CUK converter bus energy storage element equalization circuit of claim 1, further comprising: a first diode, a second power switch freewheel diode, and a first resonant diode; the positive pole of the first diode is connected with the source electrode of the first power switch, the negative pole of the first diode is connected with the drain electrode of the first power switch, the positive pole of the second power switch freewheeling diode is connected with the source electrode of the second power switch, the negative pole of the second power switch freewheeling diode is connected with the drain electrode of the second power switch, the positive pole of the first resonance diode is connected with the source electrode of the first auxiliary switch, and the negative pole of the first resonance diode is connected with the drain electrode of the first auxiliary switch.
3. The zero current PWM bi-directional DC-DC CUK converter bus energy storage element equalization circuit of claim 1, further comprising: the second inductance is provided with a second inductance,
one end of the second inductor is connected with the negative electrode of the power supply, and the other end of the second inductor is connected with the source electrode of the first power switch.
4. The zero current PWM bi-directional DC-DC CUK converter bus energy storage element equalization circuit of claim 1, further comprising: the third inductance is provided with a third inductance,
one end of the third inductor is connected with the source electrode of the second power switch, and the other end of the third inductor is connected with one end of the second capacitor.
5. The zero current PWM bi-directional DC-DC CUK converter bus-based energy storage element balancing circuit according to claim 1, wherein the energy storage element comprises a battery or a super capacitor.
6. An equalization system based on the zero-current PWM bidirectional DC-DC CUK converter bus energy storage element equalization circuit of claim 1, comprising: the positive output end of the first equalization circuit is connected with the positive end of the equalization bus, the negative output end of the first equalization circuit is connected with the negative end of the equalization bus, the positive output end of the second equalization circuit is connected with the positive end of the equalization bus, the negative output end of the second equalization circuit is connected with the negative end of the equalization bus, the positive output end of the Nth equalization circuit is connected with the positive end of the equalization bus, the negative output end of the Nth equalization circuit is connected with the negative end of the equalization bus, and N is a positive integer.
7. A method of operating a zero current PWM bi-directional DC-DC CUK converter bus energy storage element equalization circuit based on claim 1, comprising:
the equalization circuit is divided into six stages when power is supplied from the left side to the right side,
s1, in the stage of t0-t1, the first auxiliary switch and the first power switch are turned off, and input current flows through a first resonant inductor and a second resonant inductor, -i Lr1 ＝i Lr2 ＝I i ，
Wherein i is Lr1 And i Lr1 Representing the current flowing through the first and second resonant inductances, respectively, I i Representing the input current, which is considered as a constant value when the first inductance value is selected appropriately;
the input current and the output current both flow through the second power switch freewheel diode, i D2 ＝I i +I o ；
Wherein i is D2 Indicating the current flowing through the freewheeling diode of the second power switch, I o Representing the output current, which is considered as a constant value when the fourth inductance value is selected appropriately;
when the first power switch is switched from off to on, the stage is ended;
s2, at the stage of t1-t2, the first power switch is turned on, the first auxiliary switch is kept turned off, under the action of the first a capacitor and the first b capacitor, the current flowing through the first resonant inductor and the second resonant inductor is linearly reduced from the input current value, is reversely increased to the output current value after being reduced to zero,
wherein L is r1 And L r2 Respectively representing a first resonance inductance value and a second resonance inductance value, U Ca And U Cb Respectively representing a first a capacitance terminal voltage and a first b capacitance terminal voltage, when the first a capacitance value and the first b capacitance value are properly selected, U Ca And U Cb Regarded as constant value, and U Ca +U Cb ＝U i +U o ，U i And U o Respectively representing the input voltage and the output voltage, i, of the equalizing circuit S1 Indicating the current flowing through the first power switch, R S1 Representing the on-resistance, i, of the first power switch D2 Representing the current flowing through the freewheeling diode of the second power switch, R D2 Representing the on-resistance of the freewheeling diode of the second power switch; neglecting the pressure drop of the tube, solving the formula (1) to obtain,
wherein t is e [ t ] 1 ,t 2 ]When i S1 ＝I i +I o When the current flowing through the freewheeling diode of the second power switch is automatically cut off, the stage is ended;
s3, in the stage of t2-t3, the first power switch is kept on, the first auxiliary switch is kept off, and the output current flows through the first resonant inductor and the second resonant inductor, i Lr1 ＝-i Lr2 ＝I o ，i Lr1 Representing the current through the first resonant inductor, i Lr2 Representing the current flowing through the second resonant inductor,
the input current and the output current both flow through the first power switch, i S1 ＝I i +I o ；i S1 Indicating the current through the first power switch,
when the first auxiliary switch is switched from off to on, the circuit enters a resonance mode from a PWM mode, and the stage is ended;
s4, in the stage of t3-t4, the first power switch is kept on, resonance is generated by opening the first auxiliary switch, conditions are created for soft turn-off of the first power switch, the first resonance inductor, the first resonance capacitor, the first power switch and the first auxiliary switch form a first resonance loop, meanwhile, the second resonance inductor, the first resonance capacitor, the first a capacitor, the first b capacitor, the second power switch freewheeling diode and the first auxiliary switch also form a second resonance loop,
wherein u is Cr Representing the terminal voltage of the first resonant capacitor, C r Representing the first resonance capacitance value, i Sr Indicating the value of the current flowing through the first auxiliary switch, R Sr Representing the on-resistance of the first auxiliary switch; neglecting the pressure drop of the tube, solving the formulas (3) and (4) to obtain,
wherein t is e [ t ] 3 ,t 4 ]，ω 1 Representing the overall equivalent resonant angular frequency of the two resonant tanks,U Cr0 the terminal voltage of the first resonant capacitor at the time t 3;
when the current flowing through the freewheeling diode of the second power switch resonates from a positive value back to zero, the second resonant tank stops resonating, and the phase ends;
s5, in the stage of t4-t5, the first power switch and the first auxiliary switch are kept on, the second resonant circuit stops resonating, the first resonant circuit continues resonating,
neglecting the pressure drop of the tube, solving the formulas (8) and (9) to obtain,
u Cr (t)＝(I i +I o -I S11 )Z 1 sin[ω 2 (t-t 4 )]+U Cr1 cos[ω 2 (t-t 4 )] (11)
wherein t is e [ t ] 4 ,t 5 ]，ω 2 Representing the resonant angular frequency of the first resonant tank,Z 1 representing the first resonant tank impedance +.>U Cr1 For the terminal voltage of the first resonant capacitor at time t4, I S11 The current of the first power switch at the time t 4;
when i S1 <When 0, the first power switch is turned off to realize zero-current switching of the first power switch, when i Sr <When 0, the first auxiliary switch is turned off, so that zero-current switching of the first auxiliary switch can be realized;
s6, at the stage of t5-t6, the first power switch is turned off, the first resonant circuit stops resonance, the second resonant circuit starts resonance again,
neglecting the pressure drop of the tube, solving the formulas (12) and (13) to obtain,
u Cr (t)＝U Ca +U Cb +(I i +I o )Z 2 sin[ω 3 (t-t 5 )]+[U Cr2 -(U Ca +U Cb )]cos[ω 3 (t-t 4 )] (15)
wherein t is e [ t ] 5 ,t 6 ]，ω 3 Representing the resonant angular frequency of the second resonant tank,Z 2 representing the second resonant tank impedance +.>U Cr2 The terminal voltage of the first resonant capacitor at the time t 5;
when i D2 ＝I i +I o When the second resonant circuit stops resonating, the phase ends, the circuit enters a PWM mode from a resonating mode, the phase ends, and the circuit returns to the first phase;
the derivation of the input voltage versus output voltage is as follows,
the average voltage value of the fourth inductor is zero in one period, so that the average value of the second power switch terminal voltage in one period is equal to the output voltage,
wherein T is s Representing PWM control period, the first stage (t 0-t 1), the second stage (t 1-t 2), the fourth stage (t 3-t 4), and the sixth stage (t 5-t 6) have the second power switch terminal voltage of zero, the third stage (t 2-t 3) has the second power switch terminal voltage of the sum of the terminal voltages of the first a capacitor and the first b capacitor, the fifth stage (t 4-t 5) has the second power switch terminal voltage of the difference between the terminal voltages of the first resonant capacitor and the sum of the terminal voltages of the first a capacitor and the first b capacitor, and at time t4, the first resonant inductor current is near the maximum value, the terminal voltage of the second resonant capacitor at this time is approximately equal to zero, U Cr1 =0, and thus can be obtained,
wherein DeltaT 3 And DeltaT 5 Time intervals of the third phase and the fifth phase are respectively represented, T LC For the resonance period of the first resonant tank,ω 2 ΔT 5 ＝ω 2 (t 5 -t 4 ) Approximately pi, the peak value of the first power switch current is as small as possible under the condition of realizing soft switching, thus I S11 ≈2(I i +I o ) The method comprises the steps of carrying out a first treatment on the surface of the The relation between the output voltage and the input voltage can be obtained by the formula (17),
as can be seen from equation (18), the output voltage can be changed by changing the PWM period, the third stage time, after the circuit parameters are determined.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011564219.6A CN112615541B (en) | 2020-12-25 | 2020-12-25 | Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011564219.6A CN112615541B (en) | 2020-12-25 | 2020-12-25 | Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN112615541A CN112615541A (en) | 2021-04-06 |
| CN112615541B true CN112615541B (en) | 2024-03-22 |
Family
ID=75247931
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202011564219.6A Active CN112615541B (en) | 2020-12-25 | 2020-12-25 | Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN112615541B (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114123763B (en) * | 2021-10-29 | 2024-05-14 | 江苏大学 | Low-ripple soft-switching Cuk converter circuit and modulation method |
| CN114629216B (en) * | 2022-04-22 | 2024-08-23 | 重庆大学 | Expansion type equalization system based on bidirectional CUK converter and working method thereof |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5486752A (en) * | 1994-06-17 | 1996-01-23 | Center For Innovative Technology** | Zero-current transition PWM converters |
| WO2011051099A1 (en) * | 2009-10-30 | 2011-05-05 | Siemens Aktiengesellschaft | A method for controlling the turning-off process of a soft switch and a soft switch |
| CN104410133A (en) * | 2014-12-19 | 2015-03-11 | 山东大学 | Equalization circuit based on Buck-Boost convertor and bidirectional LC (inductance capacitance) resonant convertor as well as implementation method |
| CN108712070A (en) * | 2018-05-31 | 2018-10-26 | 重庆大学 | Based on ZCS PWM bi-directional DC-DC CUK converters, transformation system and method |
| CN108736704A (en) * | 2018-05-31 | 2018-11-02 | 重庆大学 | Bus type energy-storage travelling wave tube equalizing circuit, system and method based on quasi-resonance bi-directional DC-DC CUK converters |
| CN110165886A (en) * | 2019-05-30 | 2019-08-23 | 重庆大学 | Based on ZCT PWM bi-directional DC-DC CUK converter, transformation system and method |
-
2020
- 2020-12-25 CN CN202011564219.6A patent/CN112615541B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5486752A (en) * | 1994-06-17 | 1996-01-23 | Center For Innovative Technology** | Zero-current transition PWM converters |
| WO2011051099A1 (en) * | 2009-10-30 | 2011-05-05 | Siemens Aktiengesellschaft | A method for controlling the turning-off process of a soft switch and a soft switch |
| CN104410133A (en) * | 2014-12-19 | 2015-03-11 | 山东大学 | Equalization circuit based on Buck-Boost convertor and bidirectional LC (inductance capacitance) resonant convertor as well as implementation method |
| CN108712070A (en) * | 2018-05-31 | 2018-10-26 | 重庆大学 | Based on ZCS PWM bi-directional DC-DC CUK converters, transformation system and method |
| CN108736704A (en) * | 2018-05-31 | 2018-11-02 | 重庆大学 | Bus type energy-storage travelling wave tube equalizing circuit, system and method based on quasi-resonance bi-directional DC-DC CUK converters |
| CN110165886A (en) * | 2019-05-30 | 2019-08-23 | 重庆大学 | Based on ZCT PWM bi-directional DC-DC CUK converter, transformation system and method |
Also Published As
| Publication number | Publication date |
|---|---|
| CN112615541A (en) | 2021-04-06 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN111049369B (en) | Hybrid control method for resonant converter in distributed power system | |
| CN101572488B (en) | Dual output DC-DC converter for multiplexing bridge arm | |
| CN111525809B (en) | High-frequency hybrid direct-current converter with adjustable output voltage | |
| CN111478612B (en) | Phase-correlated voltage-regulator tube clamped auxiliary resonance converter pole inverter | |
| CN103944397A (en) | Boost type isolated DC/DC converter and its control method | |
| CN108418434B (en) | High-frequency isolated soft-switching DC-DC converter and modulation method for high voltage and high power | |
| CN111490698B (en) | Auxiliary resonance converter pole inverter with minimized phase-correlated ZVT magnetizing current | |
| CN103441680A (en) | Soft-switching full-bridge direct-current converter capable of reducing current-circulation loss | |
| CN103501109B (en) | There is converter bridge arm circuit and the converter of energy active feedback absorption loop | |
| CN112615541B (en) | Bus type energy storage element equalization circuit, system and method based on zero-current PWM bidirectional DC-DC CUK converter | |
| CN105207486B (en) | A kind of two-way resonance DC converter and its control method | |
| CN110190752B (en) | A bidirectional CLLLC-DCX resonant converter and its control method | |
| CN111478611A (en) | An auxiliary resonant commutated pole inverter with bidirectional reset of phase-dependent magnetizing current | |
| CN111682780A (en) | Control method for improving light-load efficiency of primary-side feedback active-clamp flyback converter | |
| CN109194135B (en) | An adaptive efficiency optimization method for a resonant state adjustable power converter | |
| CN115864859B (en) | Novel PWM control soft switch half-bridge DC-DC converter | |
| CN110061624B (en) | Soft switch resonance BUCK converter controlled by pulse width modulation | |
| CN117118238A (en) | Control circuit and control method of half-bridge flyback converter | |
| CN115776238A (en) | Soft switch control circuit and control method of flyback converter | |
| CN105207490B (en) | Inverse-excitation type multi-resonant Sepic converters | |
| CN108712070B (en) | Based on ZCS PWM bi-directional DC-DC CUK converter, transformation system and method | |
| CN108736704B (en) | Bus type energy-storage travelling wave tube equalizing circuit, system and method based on quasi-resonance bi-directional DC-DC CUK converter | |
| CN111934576B (en) | Auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetric reset | |
| CN112615542B (en) | ZVS_PWM based bidirectional DC-DC CUK converter, conversion system and method | |
| CN112366944B (en) | Soft switch resonance BOOST converter controlled by pulse width modulation |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |