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WO2012163248A1 - 开关电源控制装置及包含该控制装置的反激式开关电源 - Google Patents

开关电源控制装置及包含该控制装置的反激式开关电源 Download PDF

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Publication number
WO2012163248A1
WO2012163248A1 PCT/CN2012/076083 CN2012076083W WO2012163248A1 WO 2012163248 A1 WO2012163248 A1 WO 2012163248A1 CN 2012076083 W CN2012076083 W CN 2012076083W WO 2012163248 A1 WO2012163248 A1 WO 2012163248A1
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WO
WIPO (PCT)
Prior art keywords
voltage
comparator
output
power supply
short circuit
Prior art date
Application number
PCT/CN2012/076083
Other languages
English (en)
French (fr)
Inventor
汤仙明
姚云龙
吴建兴
Original Assignee
杭州士兰微电子股份有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 杭州士兰微电子股份有限公司 filed Critical 杭州士兰微电子股份有限公司
Priority to US14/123,038 priority Critical patent/US9263956B2/en
Publication of WO2012163248A1 publication Critical patent/WO2012163248A1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33515—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33538—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
    • H02M1/0035—Control circuits allowing low power mode operation, e.g. in standby mode using burst mode control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to the field of flyback switching power supplies, and more particularly to a flyback switching power supply technology with short circuit protection. Background technique
  • Switching power supplies are power supplies that use modern power electronics to control the ratio of turn-on and turn-off times of switching transistors to maintain a stable output voltage.
  • switching power supplies there are DC-DC or AC-DC converter circuits, isolated or non-isolated converter circuits, boost (BOOST) or step-down (BUCK) converter circuits, continuous current mode (CCM) or discontinuous current Classification such as mode (DCM).
  • the isolated conversion circuit has a single-ended (flyback or forward), double-ended (push-pull, half-bridge or full-bridge) structure.
  • the flyback switching power supply is more suitable for high voltage and low power applications (voltage is not more than 5000V, power is less than 15W).
  • the flyback switching power supply can also be used in a power supply with an output power of 150W.
  • the main advantage of the flyback switching power supply is that it does not require an output filter inductor, which is especially important for reducing the converter volume and reducing the cost.
  • the flyback switching power supply does not require a high voltage freewheeling diode to The application is more advantageous in high voltage applications.
  • the transformer when the switch is turned on, the transformer stores energy, and the load current is provided by the output filter capacitor; when the switch is turned off, the transformer transfers the stored energy to the load and the output filter capacitor to The energy consumed by the compensation capacitor alone to provide the load current.
  • the flyback switching power supply 100 is composed of a flyback converter and a PWM controller 101.
  • the flyback converter includes: a transformer 102, a switching transistor S1, and an output rectification. Tube D1 and output filter capacitor C1. It is easy to discriminate that it is a flyback converter type from the same-named end of the primary winding L1 and the secondary winding L2 of the transformer.
  • the AC input voltage VIN is connected to the same-name end of the primary winding L1 of the transformer, and the different-name end of the primary winding L1 is connected to the drain end of a switching transistor S1, and the gate of the switching transistor S1 is connected to the P-controller, the switch The source end of the tube S1 is grounded.
  • the same-side end of the secondary winding L2 is grounded, the opposite end is connected to the anode of an output rectifier D1, the cathode of the output rectifier D1 is connected to an output filter capacitor C1 to the output stage VOUT, and the output filter capacitor The other end of the CI is grounded.
  • the switch S1 When the switch S1 is turned on, the AC input voltage VIN stores energy to the transformer through the primary winding L1 and the switch S1 of the transformer, and the voltage of the opposite end of the secondary winding L2 is lower than the voltage of the same name, and the output rectifier D1 Reverse bias, the output filter capacitor C1 is separately supplied to the load; when the switch S1 is turned off, the current of the magnetizing inductance of the transformer causes the voltage of the secondary winding L2 to be reversed, and the output rectifier D1 is positively biased, and the transformer will store Energy is transferred to the load and output filter capacitor C1.
  • the PWM controller controls the turn-on and turn-off time ratio of the switch S1 according to the feedback voltage of the output stage V0UT to achieve the purpose of stabilizing the output voltage VOUT.
  • the flyback converter typically also includes an auxiliary winding L3, a diode D2 and a capacitor C2.
  • the auxiliary winding L3 has the same name grounded, the opposite end is connected to the anode of a diode D2, the cathode of the diode D2 is connected to the capacitor C2 to the power supply terminal VCC of the PWM control chip, and the other end of the capacitor C2 is grounded.
  • the switch S1 When the switch S1 is turned on, the voltage of the opposite end of the auxiliary winding L3 is lower than the voltage of the same name terminal, the diode D2 is reverse biased, and the capacitor C2 supplies power to the PWM controller separately.
  • the switch S1 When the switch S1 is turned off, the current of the magnetizing inductor causes the auxiliary winding L2 voltage to reverse, the diode D2 is positively biased, and the auxiliary winding L3 supplies power to the PWM controller and the capacitor C2 at the same time.
  • the waveforms of the power supply terminal VCC and the driving terminal GD of the PWM control chip are schematic.
  • the time for the system to enter the short-circuit protection is determined by the capacitance of the capacitor C2 and the PWM controller. If the capacitor C2 is too large, the time to enter the short-circuit protection is too long, and the current will be large when the system is short-circuited. Saturated, burned out the power tube, damaging the circuit; if capacitor C2 is too small, the time is shortened, but the PWM controller may not work properly. Therefore, the short-circuit protection performance is difficult to debug, and the consistency of mass production will be poor. Summary of the invention
  • the invention solves the deficiencies of the prior art, and provides a switching power supply control device with a short circuit protection function, and also provides a flyback switching power supply including the device.
  • the switching power supply control device comprises a P-controller and a short-circuit protection module:
  • the PWM controller outputs a driving signal
  • the short circuit protection module is connected to the detecting end, and the detecting end inputs a zero-crossing detecting voltage.
  • the short-circuit protection module determines that the occurrence occurs.
  • the short circuit protection module outputs a short circuit signal to the PWM controller, and the PWM controller output drive signal becomes a shutdown signal; if the short circuit protection module does not detect a short circuit abnormal condition, the PWM controller normal work.
  • the short circuit protection module includes:
  • the input end of the detecting module is connected to the detecting end, and the detecting module compares the detecting voltage input by the detecting end with the first reference voltage, and when the detecting end detecting voltage is greater than the first reference voltage, the detecting The module outputs a high level, and when the detecting end detecting voltage is less than or equal to the first reference voltage, the detecting module outputs a low level;
  • timing module an input end of the timing module is connected to an output end of the detection module, an output end of the timing module is connected to the P-controller, and when the detection module outputs a low level, and is low-powered The flat duration exceeds a predetermined time of the timing module, and the timing module outputs a short circuit signal to the PWM controller.
  • the detection terminal detects that the input detection voltage is derived from the voltage of the opposite end of the auxiliary winding of the flyback switching power supply controlled by the switching power supply control device.
  • the driving signal is supplied to a switching tube of a flyback switching power supply controlled by the switching power supply control device, and the switching transistor is controlled to be turned on and off.
  • Flyback switching power supply including:
  • a flyback converter converts an AC input voltage into a DC output voltage, the flyback converter including a flyback transformer, a switching transistor, an output rectifier, an output filter capacitor, an auxiliary winding, and a a diode and a second capacitor;
  • a switching power supply control device includes: a P-controller and a short-circuit protection module:
  • the P-controller outputs a driving signal, the driving signal is provided to the switch tube, and the control is The switching tube is turned on and off, the P controller determines a ratio of the on and off times of the switch; the short circuit protection module is connected to the detecting end, and the detection voltage input by the detecting end is from the auxiliary winding The voltage of the different name end, when the detection terminal detects that the voltage is lower than the first reference voltage for more than a preset time, the short circuit protection module determines that the flyback switching power supply has a short circuit abnormal condition, and the short circuit protection module Outputting a short-circuit signal to the P-controller, the P-controller outputting the drive signal as a shutdown signal, thereby turning off the switch; if the short-circuit protection module does not detect a short-circuit abnormality, the P-control The device works normally.
  • the short circuit protection module includes:
  • the input end of the detecting module is connected to the detecting end, and the detecting module compares the detecting voltage input by the detecting end with the first reference voltage, and when the detecting end detecting voltage is greater than the first reference voltage, the detecting The module outputs a high level, and when the detecting end detecting voltage is less than or equal to the first reference voltage, the detecting module outputs a low level;
  • timing module an input end of the timing module is connected to an output end of the detection module, an output end of the timing module is connected to the P-controller, and when the detection module outputs a low level, and is low-powered The flat duration exceeds a predetermined time of the timing module, and the timing module outputs a short circuit signal to the PWM controller.
  • the switching power supply control device proposed by the present invention is applied to a flyback switching power supply, and has a short circuit protection function, and the flyback switching power supply has a short circuit protection power consumption.
  • the flyback switching power supply does not have transformer saturation, which causes the switching tube of the flyback switching power supply to burn out, and the short circuit protection performance is no longer affected by the second capacitor C2 and the switching power supply control device.
  • the impact of consumption, easier to debug, the consistency of mass production will be very good.
  • Figure 1 shows the topology of a conventional flyback switching power supply.
  • Figure 2 is a schematic diagram of the waveform of a conventional flyback switching power supply in the event of a short circuit.
  • FIG. 3 is a topological structural diagram of a flyback switching power supply according to the present invention.
  • FIG. 4 is a schematic diagram of a waveform of a flyback switching power supply according to the present invention.
  • FIG. 5 is a specific embodiment of a short circuit protection module of a flyback switching power supply according to the present invention.
  • FIG. 6 is another specific embodiment of the short circuit protection module of the flyback switching power supply provided by the present invention.
  • FIG. 7 is a specific embodiment of a detection module of a flyback switching power supply according to the present invention.
  • the flyback switching power supply 300 includes: a flyback converter 302 and a switching power supply control device 301:
  • the flyback converter 302 converts the AC input voltage into a DC output voltage, including a flyback transformer, a switching transistor S1, an output rectifier D1, an output filter capacitor Cl, and an auxiliary winding of the flyback transformer. L3, diode D2 and second capacitor C2.
  • the AC input voltage VIN is connected to the same end of the primary winding L1 of the flyback transformer, and the different end of the primary winding L1 is connected to the drain end of the switching transistor S1, and the source end of the switching transistor S1 is grounded; the secondary winding L2 The same name end is grounded, the opposite end of the secondary winding L2 is connected to the anode of the output rectifier D1, the cathode of the output rectifier D1 is connected to one end of the output filter capacitor C1, the other end of the output filter capacitor C1 is grounded, and the output filter capacitor C1 is two As the output stage V0UT, the same name end of the auxiliary winding L3 is grounded, the different name of the auxiliary winding L3 is connected to the anode of the diode D2, the cathode of the diode D2 and one end of the second capacitor C2 are connected to the power supply terminal VCC, and the second capacitor C2 The other end is grounded.
  • the switch S1 When the switch S1 is turned on, the AC input voltage VIN stores energy to the flyback transformer through the primary winding L1 and the switch S1, and the voltage of the opposite end of the secondary winding L2 is lower than the voltage of the same name, and the output rectifier D1 Reverse bias, the output filter capacitor C1 is separately supplied to the load; when the switch S1 is turned off, the current of the excitation inductor of the flyback transformer causes the voltage of the secondary winding L2 to be reversed, and the output rectifier D1 is positively biased, the reverse The excitation transformer transfers the stored energy to the load and output filter capacitor Cl.
  • the flyback converter typically also includes an auxiliary winding L3, a diode D2 and a capacitor C2.
  • the same name end of the auxiliary winding L3 is grounded, and the opposite end is connected to the anode of a diode D2.
  • the cathode of the diode D2 is connected to a capacitor C2 to the power supply terminal VCC of the switching power supply control device, and the other end of the capacitor C2 is grounded.
  • the switch S1 When the switch S1 is turned on, the voltage of the opposite end of the auxiliary winding L3 is lower than the voltage of the same name terminal, the diode D2 is reverse biased, and the capacitor C2 supplies power to the switching power supply control device separately.
  • the switch S1 When the switch S1 is turned off, the current of the magnetizing inductance of the flyback transformer causes the voltage of the auxiliary winding L3 to be reversed, and the diode D2 is positively biased.
  • the auxiliary winding L3 simultaneously supplies power to the switching power supply control device and the capacitor C2.
  • the switching power supply control device 301 includes a PWM controller 303 and a short circuit protection module.
  • the PWM controller 303 controls the turn-on and turn-off time ratio of the switch S1 according to the feedback voltage of the output stage V0UT to achieve the purpose of stabilizing the output voltage VOUT.
  • the short circuit protection module 304 detects the voltage of the different end of the auxiliary winding L3. When the voltage of the different end of the auxiliary winding L3 is lower than the first reference voltage for a predetermined time, the short circuit protection module 304 It is judged that the short-circuit abnormality has occurred in the flyback switching power supply, and at the same time, the short-circuit signal is output to the P-controller, and the P-controller 303 turns off the switching transistor.
  • the short circuit protection module 304 includes:
  • a detecting module 305 the input end of the detecting module 305 is connected to the different end of the auxiliary winding L3 through the detecting end ZCD, and the detecting module performs the voltage of the different name of the auxiliary winding L3 with the first reference voltage Comparing, when the voltage of the opposite end of the auxiliary winding L3 is greater than the first reference voltage, the detecting module outputs a high level, and when the voltage of the different name of the auxiliary winding L3 is less than or equal to the first reference voltage, the detecting module Output low level;
  • timing module 306 an input end of the timing module 306 is connected to an output end of the detecting module 305, an output end of the timing module is connected to the PWM controller 303, when the detecting module outputs a low level, And the duration of the low level exceeds a preset time of the timing module, the timing module outputs a short circuit signal to the P controller, and turns off the switch tube; if the short circuit protection module does not detect a short circuit In the abnormal situation, the P ⁇ VM controller 303 operates normally.
  • the timing module After the short circuit protection module is adopted, the time when the system enters the short circuit protection is given by the timing module. In order to distinguish the normal start and short circuit conditions, the timing module sets a time within a preset time. , is considered to be a normal startup process; beyond a given time, the system is considered to be in a short circuit state. The time that the system enters the short circuit protection is no longer determined by the capacitance of the capacitor C2 and the switching power supply control unit. Therefore, the short-circuit protection performance is no longer affected by the power consumption of the capacitor C2 and the switching power supply control device, and it is easier to debug, and the consistency of mass production is good.
  • the power consumption of the system is low when the short circuit protection occurs, and the transformer saturation does not occur, which causes the switch tube to burn out.
  • the output stage of the flyback switching power supply with the short circuit protection circuit is short-circuited.
  • the waveforms of the power supply terminal VCC and the driving terminal GD of the switching power supply control device 301 are schematic.
  • FIG. 5 is a first embodiment of the short circuit protection module 304, including:
  • the detecting module 501 includes a comparator 501, the non-inverting input of the comparator 501 is connected to the different end of the auxiliary winding L3, and the inverting input of the comparator 501 inputs the first reference voltage: when the comparator 501 The voltage of the non-inverting input terminal is higher than the voltage of the inverting input terminal, and the comparator 501 outputs det to "1"; when the voltage of the non-inverting input terminal of the comparator 501 is lower than the voltage of the inverting input terminal, the comparator 501 outputs det to "0". .
  • the timing module 502 is a counter group.
  • the counter group includes six frequency dividers DIV, an inverter N1, and a three-input NOR gate N0R1.
  • the output terminal QP of the first frequency divider DIV is connected to the input terminal CKN of the second frequency divider DIV; the output terminal QN of the first frequency divider DIV is connected to the input terminal CKP of the second frequency divider DIV;
  • the output terminal QP of the DIV is connected to the input terminal CKN of the third frequency divider DIV; the output terminal QN of the second frequency divider DIV is connected to the input terminal CKP of the third frequency divider DIV... and so on. .
  • the number of dividers can be increased arbitrarily.
  • the output driving signal GD of the P controller is used as the gate driving signal of the switching transistor S1, which is simply referred to as a driving signal, and the driving signal GD is connected to the input terminal CKN of the first frequency divider DIV and the input terminal of the inverter N1,
  • the output of the phaser N1 is connected to the input CKP of the first driver DIV.
  • the output terminal QN of the fourth frequency divider DIV, the output terminal QN of the fifth frequency divider DIV and the output terminal QN of the sixth frequency divider DIV are connected to the input terminal of the three-input NOR gate N0R1, the three-input NOR gate N0R1 Output short circuit signal 0C.
  • comparator 501 The output of comparator 501 is connected to the control terminal CTL of all dividers DIV, when the comparator
  • FIG. 6 is a second embodiment of the short circuit protection module 304, including:
  • the detecting module 601 is a second comparator 601.
  • the non-inverting input terminal of the second comparator 601 is connected to the different-name end of the auxiliary winding L3, and the inverting input terminal of the second comparator 601 is input with the first reference voltage:
  • the second The comparator 601 outputs det "1";
  • the second comparator 601 outputs det to "0".
  • the timing module includes a first current source II, a second switching transistor S2, a third capacitor C3, and a third comparator 603.
  • the drain terminals of the first constant current source II and the second switching transistor S2 are connected to the third comparator 603.
  • the positive current input terminal, the other end of the first constant current source II is connected to the power supply terminal VCC, and the source end of the second switching transistor S2 is grounded.
  • the third phase of the third comparator 603 is connected to a third capacitor C3, the other end of the third capacitor C3 is grounded, and the inverting input of the third comparator 603 is input with a second reference voltage.
  • the third comparator 603 outputs a short circuit signal 0C.
  • the second comparator 601 outputs a gate connected to the second switching transistor S2.
  • the second switching transistor S2 is turned on, and the voltage of the non-inverting input terminal of the third comparator 603 is 0 volts, lower than the second reference voltage of the inverting input terminal, and the third comparator 603 outputs the short circuit signal 0C to "0".
  • the second switch S2 is turned off, the first constant current source II starts charging the third capacitor C3, and the voltage of the positive input terminal of the third comparator 603 starts to rise.
  • the third comparator 603 outputs the short-circuit signal 0C from "0" to "1".
  • FIG. 7 is a second embodiment of the detection module 305, including:
  • the follower 701 inputs a ZCD terminal detection voltage, the output of the follower 701 is connected to the switch S3, the output voltage of the follower 701 and the input ZCD terminal detect voltage, and maintain a following relationship; the other end of the switch S3 Connected to one end of the fourth capacitor C4, to the positive input terminal of the fourth comparator 702, the inverting input terminal of the fourth comparator 702 inputs a third reference voltage.
  • the fourth comparator 702 outputs a short detection signal det.
  • the switch S3 is controlled by the falling edge delay pulse generator 703, and the falling edge delay pulse generator 703 inputs a driving signal GD, and the falling edge delay pulse generator 703 drops in the driving signal GD.
  • a sampling pulse CS is generated, the switch S3 is closed, and the ZCD terminal detection voltage is sampled to the non-inverting input terminal of the fourth comparator 702.
  • the switch S3 is turned off, the fourth capacitor C4 holds the previously sampled voltage.
  • the fourth comparator 702 When the voltage of the non-inverting input terminal of the fourth comparator 702 is higher than the voltage of the inverting input terminal, the fourth comparator 702 outputs det "1"; when the voltage of the non-inverting input terminal of the fourth comparator 702 is lower than the inverting input At the input voltage, the fourth comparator 702 outputs det to "0".
  • the present invention discloses a switching power supply control device and a flyback switching power supply including the same, and describes specific embodiments and effects of the present invention with reference to the accompanying drawings. It is to be understood that the above-described embodiments are merely illustrative of the invention, and are not intended to limit the invention, any inventions that are within the scope of the spirit of the invention, including modifications and substitutions of the specific implementation lines of the detection module and the timing module. And other non-substantial alternatives or modifications are intended to fall within the scope of the invention.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种开关电源控制装置（301）及包含该控制装置的反激式开关电源（300）。开关电源控制装置包括PWM控制器（303）和短路保护模块（304）。PWM控制器输出驱动信号。短路保护模块连接检测端（ZCD），检测端输入一过零检测电压。当检测端输入的检测电压低于第一基准电压（REF1）的时间超过预先设定的时间，短路保护模块判断为发生短路异常情况，短路保护模块输出短路信号（OC）给PWM控制器，PWM控制器输出驱动信号变为关断信号。若短路保护模块未检测到短路异常情况时，PWM控制器正常工作。反激式开关电源在发生短路保护时功耗很低，也不会出现变压器饱和以及功率管烧坏的情况，同时短路性能更容易调试。

Description

开关电源控制装置及包含该控制装置的反激式开关电源 技术领域
本发明涉及反激式开关电源领域， 尤其涉及一种具有短路保护的反激式开关 电源技术。 背景技术
开关电源是利用现代电力电子技术， 控制开关晶体管开通和关断时间比率， 维持稳定输出电压的一种电源。关于开关电源， 有 DC-DC或 AC-DC转换电路， 隔离 型或非隔离型转换电路， 升压型 （BOOST) 或降压型 （BUCK) 转换电路， 连续电流 模式（CCM)或非连续电流模式（DCM)等分类。其中隔离型转换电路又有单端式（反 激式或正激式） ， 双端式 （推挽式、 半桥式或全桥式） 结构。
开关电源常用的基本拓扑结构约有 14种， 每种拓扑都有其自身的特点和适用 场合。 其中反激式开关电源比较适合应用在高电压、 小功率场合 （电压不大于 5000V, 功率小于 15W) 。 当输入电压较高、 初级电流合适时， 所述反激式开关电 源也可以用在输出功率达到 150W的电源中。 所述反激式开关电源的主要优点是不 需要输出滤波电感， 这点对减小转换器体积， 降低成本尤为重要， 另外所述反激式 开关电源也不需要高压续流二极管， 使其在高电压场合下应用更有利。
在所述反激式开关电源的拓扑结构中， 开关管开通时， 变压器存储能量， 负 载电流由输出滤波电容提供； 开关管关断时，变压器将存储的能量传送到负载和输 出滤波电容， 以补偿电容单独提供负载电流时消耗的能量。
图 1是反激式开关电源的基本拓扑结构， 反激式开关电源 100由反激式转换 器和 PWM控制器 101组成， 所述反激式转换器包括： 变压器 102、 开关管 Sl、 输出 整流管 D1以及输出滤波电容 Cl。从所述变压器的原边绕组 L1和副边绕组 L2的同 名端标识很容易判别出其为反激式转换器类型。
交流输入电压 VIN连接到所述变压器的原边绕组 L1 的同名端， 原边绕组 L1 的异名端连接到一开关管 S1 的漏端， 开关管 S1 的栅极接到 P丽控制器， 开关管 S1的源端接地。 副边绕组 L2的同名端接地， 异名端接到一输出整流管 D1的阳极， 输出整流管 D1的阴极与一输出滤波电容 C1相连接到输出级 V0UT, 输出滤波电容 CI的另一端接地。
当开关管 S1开通时， 交流输入电压 VIN通过所述变压器的原边绕组 L1和开 关管 S1向所述变压器存储能量， 副边绕组 L2的异名端电压低于同名端电压，输出 整流管 D1反偏， 输出滤波电容 C1单独向负载供电； 当开关管 S1关断时， 所述变 压器的励磁电感的电流使得副边绕组 L2电压反向，输出整流管 D1正偏，所述变压 器将存储的能量传送到负载和输出滤波电容 Cl。 所述 PWM控制器根据输出级 V0UT 的反馈电压来控制开关管 S1开通和关断时间比例，以达到稳定输出电压 V0UT的目 的。
为了给所述 PWM控制器供电，所述反激式转换器里面一般还包括辅助绕组 L3， 二极管 D2和电容 C2。辅助绕组 L3的同名端接地，异名端接到一二极管 D2的阳极， 二极管 D2的阴极与电容 C2相连接到 PWM控制芯片的电源端 VCC， 电容 C2的另一 端接地。
当开关管 S1开通时， 辅助绕组 L3的异名端电压低于同名端电压， 二极管 D2 反偏， 电容 C2单独向所述 PWM控制器供电。 当开关管 S1关断时， 励磁电感的电流 使得辅助绕组 L2电压反向， 二极管 D2正偏， 辅助绕组 L3同时向所述 PWM控制器 和电容 C2供电。
当所述反激式开关电源的输出级发生短路的异常情况时， 副边绕组 L2的电流 急剧上升， 消耗了所述变压器原边提供的绝大部分能量， 输出电压降低， 从而使得 输出反馈电压下降， 导致所述 PWM控制器全占空比输出。 同时导致辅助绕组 L3异 名端的电压很低无法给所述 PWM控制器和电容 C2供电， 使得所述 PWM控制器的电 源电压 VCC下降， 当 VCC降低至设定值时， 所述 P丽控制器关断， 电源电压 VCC 开始上升， 进入重启阶段， 从而实现所谓的打嗝保护。
如图 2所示， 所述反激式开关电源的输出级发生短路的异常情况时， PWM控制 芯片的电源端 VCC和驱动端 GD的波形示意图。 然而系统进入短路保护的时间是由 电容 C2和所述 PWM控制器功耗决定的，如果电容 C2太大，进入短路保护的时间就 太长， 系统的短路时电流会很大， 所述变压器会饱和， 烧坏功率管， 损坏电路； 如 果电容 C2太小， 时间是变短了， 但是所述 PWM控制器可能无法正常工作。 因此短 路保护性能就很难调试， 批量生产的一致性也会很差。 发明内容
本发明要解决现有技术的不足， 提供一种具有短路保护功能的开关电源控制 装置， 同时还提供了包含该装置的反激式开关电源。
开关电源控制装置， 包括一 P丽控制器和一短路保护模块：
所述 PWM控制器输出驱动信号；
所述短路保护模块连接检测端， 检测端输入一过零检测电压， 当所述检测端 输入的检测电压低于第一基准电压的时间超过预先设定的时间，所述短路保护模块 判断为发生短路异常情况，所述短路保护模块输出短路信号给所述 PWM控制器， PWM 控制器输出驱动信号变为关断信号； 若所述短路保护模块未检测到短路异常情况 时， 所述 PWM控制器正常工作。
进一步， 所述短路保护模块包括：
一检测模块， 所述检测模块的输入端连接检测端， 所述检测模块将检测端输 入的检测电压同第一基准电压进行比较， 当所述检测端检测电压大于第一基准电 压， 所述检测模块输出高电平， 当所述检测端检测电压小于等于第一基准电压， 所 述检测模块输出低电平；
一定时模块， 所述定时模块的输入端连接到所述检测模块的输出端， 所述定 时模块的输出端连接到所述 P丽控制器， 当所述检测模块输出低电平时，且低电平 的持续时间超过所述定时模块预先设定的时间，所述定时模块输出短路信号给所述 PWM控制器。
所述检测端检测输入的检测电压来自于开关电源控制装置所控制的反激式开 关电源的辅助绕组的异名端的电压。
所述驱动信号提供给开关电源控制装置所控制的反激式开关电源的开关管， 控制所述开关管开通和关断。
反激式开关电源， 包括：
一反激式转换器， 将交流输入电压转换成直流输出电压， 所述反激式转换器 包括一个反激式变压器， 一个开关管， 一个输出整流管， 一个输出滤波电容， 一个 辅助绕组， 一个二极管和第二电容；
一开关电源控制装置， 包括： 一 P丽控制器和一短路保护模块：
所述 P丽控制器输出驱动信号， 所述驱动信号提供给所述开关管， 控制所述 开关管开通和关断， 所述 P丽控制器决定所述开关管的导通与关断时间比例； 所述短路保护模块连接检测端， 所述检测端输入的检测电压来自于所述辅助 绕组的异名端的电压，当所述检测端检测电压低于第一基准电压的时间超过预先设 定的时间，所述短路保护模块判断反激式开关电源已经发生短路异常情况，所述短 路保护模块输出短路信号给所述 P丽控制器， P丽控制器输出驱动信号为关断信号， 从而关断所述开关管； 若所述短路保护模块未检测到短路异常情况时， 所述 P丽 控制器正常工作。
进一步， 所述短路保护模块包括：
一检测模块， 所述检测模块的输入端连接检测端， 所述检测模块将检测端输 入的检测电压同第一基准电压进行比较， 当所述检测端检测电压大于第一基准电 压， 所述检测模块输出高电平， 当所述检测端检测电压小于等于第一基准电压， 所 述检测模块输出低电平；
一定时模块， 所述定时模块的输入端连接到所述检测模块的输出端， 所述定 时模块的输出端连接到所述 P丽控制器， 当所述检测模块输出低电平时，且低电平 的持续时间超过所述定时模块预先设定的时间，所述定时模块输出短路信号给所述 PWM控制器。
本发明的有益效果是： 同背景技术相比， 本发明提出的开关电源控制装置应 用在反激式开关电源时， 由于具有短路保护功能，所述反激式开关电源发生短路保 护时功耗很低，所述反激式开关电源也不会出现变压器饱和， 导致反激式开关电源 的开关管烧坏的情况， 同时短路保护性能不再受到第二电容 C2和所述开关电源控 制装置的功耗的影响， 更容易调试， 批量生产的一致性会很好。 附图概述
图 1为传统的反激式开关电源的拓扑结构图。
图 2为传统的反激式开关电源的短路时波形示意图。
图 3为本发明提出的反激式开关电源的拓扑结构图。
图 4为本发明提出的反激式开关电源的短路时波形示意图。
图 5是本发明提出的反激式开关电源的短路保护模块的一个具体实施例。 图 6是本发明提出的反激式开关电源的短路保护模块的另外一个具体实施例。 图 7是本发明提出的反激式开关电源的检测模块的一个具体实施例。 具体实施方式
以下结合附图对本发明内容进一步说明。
图 3是本发明提出的具有短路保护电路的反激式开关电源的拓扑结构。 如 图 3所示， 所述反激式开关电源 300包括： 一反激式转换器 302和一开关电源 控制装置 301 :
所述反激式转换器 302将交流输入电压转换成直流输出电压， 包括一反 激式变压器、 一开关管 S l、 一输出整流管 Dl、 一输出滤波电容 Cl、 反激式变 压器的辅助绕组 L3， 二极管 D2和第二电容 C2。 交流输入电压 VIN连接到所述 反激式变压器的原边绕组 L1的同名端， 原边绕组 L1的异名端连接到开关管 S1 的漏端， 开关管 S1 的源端接地； 副边绕组 L2 的同名端接地， 副边绕组 L2 的 异名端连接输出整流管 D1的阳极，输出整流管 D1的阴极连接输出滤波电容 C1 的一端， 输出滤波电容 C1的另外一端接地， 输出滤波电容 C1的两端作为输出 级 V0UT， 辅助绕组 L3的同名端接地， 辅助绕组 L3的异名端接到二极管 D2的 阳极， 二极管 D2的阴极与第二电容 C2的一端连接到电源供电端 VCC， 第二电 容 C2的另一端接地。
当开关管 S1开通时， 交流输入电压 VIN通过原边绕组 L1和开关管 S 1 向 所述反激式变压器存储能量， 副边绕组 L2 的异名端电压低于同名端电压， 输 出整流管 D1反偏， 输出滤波电容 C1单独向负载供电； 当开关管 S1关断时， 所述反激式变压器的励磁电感的电流使得副边绕组 L2 电压反向， 输出整流管 D1正偏， 所述反激式变压器将存储的能量传送到负载和输出滤波电容 Cl。
为了给所述开关电源控制装置 301供电， 所述反激式转换器里面一般还包 括辅助绕组 L3， 二极管 D2和电容 C2。 辅助绕组 L3 的同名端接地， 异名端接 到一二极管 D2 的阳极， 二极管 D2 的阴极与一电容 C2相连接到所述开关电源 控制装置的电源端 VCC， 电容 C2的另一端接地。
当开关管 S 1开通时， 辅助绕组 L3的异名端电压低于同名端电压， 二极管 D2反偏， 电容 C2单独向所述开关电源控制装置供电。 当开关管 S1关断时， 所 述反激式变压器的励磁电感的电流使得辅助绕组 L3电压反向，二极管 D2正偏， 辅助绕组 L3同时向所述开关电源控制装置和电容 C2供电。
所述开关电源控制装置 301包括一个 PWM控制器 303和一个短路保护模块
304。
所述 PWM控制器 303根据输出级 V0UT的反馈电压来控制开关管 S 1开通和 关断时间比例， 以达到稳定输出电压 V0UT的目的。
所述短路保护模块 304检测所述辅助绕组 L3 的异名端的电压， 当所述辅 助绕组 L3 的异名端的电压低于第一基准电压的时间超过预先设定的时间， 所 述短路保护模块 304判断反激式开关电源已经发生短路异常情况， 同时输出短 路信号给 P丽控制器， P丽控制器 303关断所述开关管。
进一步所述短路保护模块 304包括：
一检测模块 305， 所述检测模块 305的输入端通过检测端 ZCD连接到所述 辅助绕组 L3的异名端， 所述检测模块将所述辅助绕组 L3的异名端电压同第一 基准电压进行比较， 当所述辅助绕组 L3 的异名端电压大于第一基准电压， 所 述检测模块输出高电平， 当所述辅助绕组 L3 的异名端电压小于等于第一基准 电压， 所述检测模块输出低电平；
一定时模块 306， 所述定时模块 306的输入端连接到所述检测模块 305的 输出端， 所述定时模块的输出端连接到所述 PWM控制器 303， 当所述检测模块 输出低电平时， 且低电平的持续时间超过所述定时模块预先设定的时间， 所述 定时模块输出短路信号给所述 P丽控制器， 关断所述开关管； 若所述短路保护 模块未检测到短路异常情况时， 所述 P^VM控制器 303正常工作。
采用所述短路保护模块之后， 系统进入短路保护的时间是由所述定时模块 给定的， 为了把正常启动和短路情况区分出来， 所述定时模块设定一时间， 在 预先设定的时间内， 认为是正常启动过程； 超过给定的时间， 认为系统处于短 路状态。 系统进入短路保护的时间不再由电容 C2 和所述开关电源控制装置的 功耗决定了。 因此短路保护性能就不再受到电容 C2 和所述开关电源控制装置 的功耗的影响， 更容易调试， 批量生产的一致性会很好。
采用所述短路保护电路之后， 系统发生短路保护时功耗很低， 也不会出现 变压器饱和， 导致开关管烧坏的情况。
如图 4所示， 所述具有短路保护电路的反激式开关电源的输出级发生短路 的异常情况时， 所述开关电源控制装置 301 的电源端 VCC和驱动端 GD的波形 示意图。
图 5是所述短路保护模块 304的第一个具体实施例， 包括：
所述检测模块 501包括一个比较器 501， 比较器 501的正相输入端连接 到所述辅助绕组 L3 的异名端， 比较器 501 的反相输入端输入第一基准电压： 当比较器 501的正相输入端的电压高于反相输入端的电压，比较器 501输出 det 为 " 1 " ； 当比较器 501 的正相输入端的电压低于反相输入端的电压， 比较器 501输出 det为 " 0 " 。
所述定时模块 502是一个计数器组， 作为示例， 所述计数器组包括 6个 分频器 DIV， 反相器 Nl， 三输入或非门 N0R1。 第一分频器 DIV的输出端 QP接 到第二分频器 DIV的输入端 CKN;第一分频器 DIV的输出端 QN接到第二分频器 DIV的输入端 CKP; 第二分频器 DIV的输出端 QP接到第三分频器 DIV的输入端 CKN; 第二分频器 DIV的输出端 QN接到第三分频器 DIV的输入端 CKP ......以此 类推。 分频器的个数可以任意增加。 P丽控制器的输出驱动信号 GD作为所述开 关管 S1 的栅级驱动信号， 简称驱动信号， 驱动信号 GD连接到第一分频器 DIV 的输入端 CKN和反相器 N1的输入端，反相器 N1的输出端连接到第一驱动器 DIV 的输入端 CKP。 第四分频器 DIV的输出端 QN， 第五分频器 DIV的输出端 QN和 第六分频器 DIV的输出端 QN连接到三输入或非门 N0R1的输入端， 三输入或非 门 N0R1输出短路信号 0C。
比较器 501的输出 det连接到所有分频器 DIV的控制端 CTL， 当比较器
501输出 det为 " 1 " ， 所有分频器 DIV不工作， 所述计数器不计数， 所述三输 入或非门 N0R1的三个输入都为 " 1 " ， 因此输出短路信号 0C为 " 0 " 。 当比较 器 501输出 det为 " 0 " ， 所述计数器开始计数， 在经过 56个驱动信号 GD的 开关周期之后， 所述三输入或非门 N0R1的三个输入同时为 " 0 " 时， 输出短路 信号 0C从 " 0 "变为 " 1 " 。
图 6是所述短路保护模块 304的第二个具体实施例， 包括：
所述检测模块 601是一个第二比较器 601， 第二比较器 601的正相输入 端连接所述辅助绕组 L3 的异名端， 第二比较器 601 的反相输入端输入第一基 准电压： 当第二比较器 601的正相输入端的电压高于反相输入端的电压， 第二 比较器 601输出 det为 " 1 " ； 当第二比较器 601 的正相输入端的电压低于反 相输入端的电压， 第二比较器 601输出 det为 " 0 " 。
所述定时模块包括第一电流源 I I， 第二开关管 S2， 第三电容 C3以及第三 比较器 603， 第一恒流源 I I与第二开关管 S2的漏端连接到第三比较器 603的 正相输入端， 第一恒流源 I I另外一端连接到电源端 VCC， 第二开关管 S2的源 端接地。 第三比较器 603的正相输入端连接一第三电容 C3， 第三电容 C3的另 外一端接地，第三比较器 603的反相输入端输入第二基准电压。第三比较器 603 输出短路信号 0C。
第二比较器 601 输出连接到第二开关管 S2 的栅极， 当第二比较器 601 输出 det为 " 1 " ， 第二开关管 S2导通， 第三比较器 603的正相输入端的电压 为 0伏， 低于反相输入端的第二基准电压， 第三比较器 603 输出短路信号 0C 为 " 0 " 。 当第二比较器 601 输出为 " 1 " ， 第二开关管 S2关断， 第一恒流源 I I开始对第三电容 C3充电， 第三比较器 603的正相输入端的电压开始上升， 当第三比较器 603的正相输入端的电压上升到高于反相输入端的参考电压时， 第三比较器 603输出短路信号 0C从 " 0 " 变为 " 1 " 。
图 7是所述检测模块 305的第二个具体实施例， 包括：
一跟随器 701， 一开关 S3， 第四电容 C4， 第四比较器 702以及下降沿延时 脉冲发生器 703。 所述跟随器 701输入 ZCD端检测电压， 所述跟随器 701 的输 出连接到所述开关 S3， 所述跟随器 701的输出电压与输入 ZCD端检测电压， 保 持跟随关系； 所述开关 S3另外一端与第四电容 C4一端相连， 接到所述第四比 较器 702正相输入端，所述第四比较器 702的反相输入端输入一第三基准电压。 所述第四比较器 702输出短路检测信号 det。
所述开关 S3受到所述下降沿延时脉冲发生器 703 的控制， 所述下降沿延 时脉冲发生器 703输入一驱动信号 GD，所述下降沿延时脉冲发生器 703在驱动 信号 GD的下降沿， 经过一段延时， 产生一采样脉冲 CS， 将所述开关 S3闭合， 将 ZCD端检测电压采样到所述第四比较器 702 的正相输入端。 当所述开关 S3 断开时， 所述第四电容 C4， 会将之前采样的电压保持住。
当第四比较器 702的正相输入端的电压高于反相输入端的电压， 第四比较 器 702输出 det为 " 1 " ； 当第四比较器 702 的正相输入端的电压低于反相输 入端的电压， 第四比较器 702输出 det为 " 0 " 。
本发明公开了开关电源控制装置及包含该控制装置的反激式开关电源， 并 且参照附图描述了本发明的具体实施方式和效果。 应该理解到的是上述实施例 只是对本发明的说明， 而不是对本发明的限制， 任何不超出本发明实质精神范 围内的发明创造， 包括对检测模块和定时模块的具体实施线路的修改、 替换， 以及其他非实质性的替换或修改， 均落入本发明保护范围之内。

Claims

权 利 要 求
1、 开关电源控制装置， 其特征在于包括一 PWM控制器和一短路保护模块： 所述 PWM控制器输出驱动信号；
所述短路保护模块连接检测端， 检测端输入一过零检测电压， 当所述检测 端输入的检测电压低于第一基准电压的时间超过预先设定的时间， 所述短路保 护模块判断为发生短路异常情况，所述短路保护模块输出短路信号给所述 PWM 控制器， PWM 控制器输出驱动信号变为关断信号； 若所述短路保护模块未检 测到短路异常情况时， 所述 PWM控制器正常工作。
2、 如权利要求 1所述开关电源控制装置， 其特征在于所述短路保护模块包括： 一检测模块， 所述检测模块的输入端连接检测端， 所述检测模块将检测端 输入的检测电压同第一基准电压进行比较， 当所述检测端检测电压大于第一基 准电压， 所述检测模块输出高电平， 当所述检测端检测电压小于等于第一基准 电压， 所述检测模块输出低电平；
—定时模块， 所述定时模块的输入端连接到所述检测模块的输出端， 所述 定时模块的输出端连接到所述 PWM控制器， 当所述检测模块输出低电平时， 且低电平的持续时间超过所述定时模块预先设定的时间， 所述定时模块输出短 路信号给所述 PWM控制器。
3、 如权利要求 1 所述开关电源控制装置， 其特征在于所述检测端检测输入的 检测电压来自于开关电源控制装置所控制的反激式开关电源的辅助绕组的 异名端的电压。
4、 如权利要求 1 所述开关电源控制装置， 其特征在于所述驱动信号提供给开 关电源控制装置所控制的反激式开关电源的开关管，控制所述开关管开通和 关断。
5、 反激式开关电源， 其特征在于包括：
一反激式转换器， 将交流输入电压转换成直流输出电压， 所述反激式转换 器包括一个反激式变压器， 一个开关管， 一个输出整流管， 一个输出滤波电容， 一个辅助绕组， 一个二极管和第二电容；
一开关电源控制装置， 包括： 一 PWM控制器和一短路保护模块： 所述 PWM控制器输出驱动信号， 所述驱动信号提供给所述开关管， 控制 所述开关管开通和关断， 所述 PWM控制器决定所述开关管的导通与关断时间 比例；
所述短路保护模块连接检测端， 所述检测端输入的检测电压来自于所述辅 助绕组的异名端的电压， 当所述检测端检测电压低于第一基准电压的时间超过 预先设定的时间， 所述短路保护模块判断反激式开关电源已经发生短路异常情 况， 所述短路保护模块输出短路信号给所述 PWM控制器， PWM控制器输出驱 动信号为关断信号， 从而关断所述开关管； 若所述短路保护模块未检测到短路 异常情况时， 所述 PWM控制器正常工作。
6、 如权利要求 5所述反激式开关电源， 其特征在于所述短路保护模块包括： 一检测模块， 所述检测模块的输入端连接检测端， 所述检测模块将检测端 输入的检测电压同第一基准电压进行比较， 当所述检测端检测电压大于第一基 准电压， 所述检测模块输出高电平， 当所述检测端检测电压小于等于第一基准 电压， 所述检测模块输出低电平；
—定时模块， 所述定时模块的输入端连接到所述检测模块的输出端， 所述 定时模块的输出端连接到所述 PWM控制器， 当所述检测模块输出低电平时， 且低电平的持续时间超过所述定时模块预先设定的时间， 所述定时模块输出短 路信号给所述 PWM控制器。
7、 如权利要求 6所述反激式开关电源， 其特征在于：
所述检测模块包括一个比较器， 比较器的正相输入端连接到所述辅助绕组 的异名端， 比较器的反相输入端输入第一基准电压： 当比较器的正相输入端的 电压高于反相输入端的电压， 比较器输出为高电平； 当比较器的正相输入端的 电压低于反相输入端的电压， 比较器输出为低电平；
所述定时模块是一个计数器组， 所述计数器组包括 N个分频器， 反相器， 三输入或非门。 第一分频器的输出端 QP接到第二分频器的输入端 CKN; 第一 分频器的输出端 QN接到第二分频器的输入端 CKP， 以此类推； PWM控制器 的输出驱动信号作为所述开关管的栅级驱动信号， 驱动信号连接到第一分频器 的输入端 CKN和反相器的输入端， 反相器的输出端连接到第一驱动器的输入 端 CKP。 第 N-2个分频器的输出端 QN， 第 N-1分频器的输出端 QN和第 N个 分频器 DIV的输出端 QN连接到三输入或非门的输入端， 三输入或非门输出短 路信号；
比较器的输出连接到所有分频器的控制端， 当比较器输出为高电平， 所有 分频器不工作，所述计数器不计数，所述三输入或非门的三个输入都为高电平， 因此输出短路信号为低电平； 当比较器输出为低电平， 所述计数器开始计数， 在经过若干个驱动信号的开关周期之后， 所述三输入或非门的三个输入同时为 低电平时， 输出短路信号从低电平变为高电平。
8、 如权利要求 6所述反激式开关电源， 其特征在于：
所述检测模块是一个第二比较器， 第二比较器的正相输入端连接所述辅助 绕组的异名端， 第二比较器的反相输入端输入第一基准电压： 当第二比较器的 正相输入端的电压高于反相输入端的电压， 第二比较器输出为高电平； 当第二 比较器的正相输入端的电压低于反相输入端的电压， 第二比较器输出为低电 平；
所述定时模块包括第一电流源， 第二开关管， 第三电容以及第三比较器， 第一恒流源与第二开关管的漏端连接到第三比较器的正相输入端， 第一恒流源 另外一端连接到电源端， 第二开关管的源端接地， 第三比较器的正相输入端连 接一第三电容， 第三电容的另外一端接地， 第三比较器的反相输入端输入第二 基准电压， 第三比较器输出短路信号；
第二比较器输出连接到第二开关管的栅极， 当第二比较器输出为高电平， 第二开关管导通， 第三比较器的正相输入端的电压为零伏， 低于反相输入端的 第二基准电压， 第三比较器输出短路信号为低电平； 当第二比较器输出为高电 平， 第二开关管关断， 第一恒流源开始对第三电容充电， 第三比较器的正相输 入端的电压开始上升， 当第三比较器的正相输入端的电压上升到高于反相输入 端的参考电压时， 第三比较器输出短路信号从低电平变为高电平。
9、 如权利要求 7或 8所述反激式开关电源， 其特征在于所述检测模块按照如 下结构替换：
所述检测模块包括一跟随器， 一第二开关， 第四电容， 第四比较器以及下 降沿延时脉冲发生器， 所述跟随器输入检测端检测电压， 所述跟随器的输出连 接到所述第二开关的一段， 所述跟随器的输出电压保持跟随检测端检测电压， 所述第二开关另外一端与第四电容一端相连， 接到所述第四比较器正相输入 端， 所述第四比较器的反相输入端输入一第三基准电压， 所述第四比较器输出 短路检测信号；
所述第二开关受到所述下降沿延时脉冲发生器的控制， 所述下降沿延时脉 冲发生器输入所述驱动信号， 所述下降沿延时脉冲发生器在驱动信号的下降 沿， 经过一段延时， 产生一采样脉冲， 将所述第二开关闭合， 将检测端检测电 压采样到所述第四比较器的正相输入端； 当所述开关断开时， 所述第四电容， 会将之前采样的电压保持住； 当第四比较器的正相输入端的电压高于反相输入 端的电压， 第四比较器输出为高电平； 当第四比较器的正相输入端的电压低于 反相输入端的电压， 第四比较器输出为低电平。
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