RU2371736C2 - Method for generation of current energy spectrum of receiver output signal, device for its realisation and method for distance measurement - Google Patents

Abstract

FIELD: radio engineering.

SUBSTANCE: method for generation of current energy spectrum (CES) of receiver output signal, consists in the fact that in digital sequence of receiver output signal numerical counts (NC) are squared, the first count of CES is produced by summation of the first squares of NC, number N of which is equal to number if NC, which characterise duration of signal reflected from target. In order to produce the following counts, serial selection of two count squares separated into N counts is carried out, and CES count values are produced by subtracting value of the first count square in the sample from previous value of CES count value and summing the result with the second count square in the sample. Device is also suggested, which realises the method, being arranged in a certain manner. In method of distance detection, received signal is transformed into digital form, numerical array of counts is generated, number of which is limited with duration of receiver time strobe and frequency characteristic of analog-digital transformation, CES of receiver output signal is generated, compared to maximum value from its previous counts, the highest value of CES count is memorised, as well as number of corresponding count of receiver output signal, after calculation of the last CES value, distance R to the target is defined using a certain formula.

EFFECT: reduction of time for measurement of distance to the target.

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Description

The group of inventions relates to digital computing and can be used mainly in radar systems (radar) to measure the range to the target on the basis of one processor, as well as in other areas of technology, including the use of electromagnetic radiation other than radio waves.

In digital receivers of modern radars processing large digital arrays, the classical method for detecting signals carrying information about the range to the target is carried out on the basis of correlation analysis and optimal filtering, using multichannel digital processing of small digital arrays (channel spacing) [1] . The disadvantage of the classical method of radar ranging is the multichannel digital signal processing in real time, which greatly complicates their hardware implementation based on the construction of specialized multiprocessor systems.

There is a method for estimating the range, in which a signal limited in time by a controlled time strobe of the receiver, containing a useful signal reflected from the target, noise and interference, is converted into a digital form in the form of a sequence of digital codes of length L samples; form and store sequences of digital samples in the form of two coherent numerical samples of length L samples. If the radar probe signal is not modulated, then coherent numerical samples are added and the sequence of numbers overlapping on Δn samples of a number of length equal to the number N of samples of the probe signal is formed from the obtained sequence, the Fourier spectral density function is determined for each of the sequences and compared with a threshold value, by the value of the magnitude and coordinate of the threshold excess of the Fourier spectral density function determines the sign of the presence of a reflected signal from the target in the gate, the Doppler frequency offset and the position of the sequence of 2N samples containing the samples of the reflected signal — the interval of linear convolutions, which determine a rough estimate of the range with an accuracy corresponding to the overlap interval Δn and the target speed with an accuracy corresponding to the duration of the probe signal. If the radar probe signal is modulated, then coherent numerical samples of 2N samples length are generated and summed, the resulting sequence is stored, by adding the first and second halves of this sequence by element-by-element addition, a cyclic signal of N samples length is formed, fast cyclic convolution calculations are performed using the fast Fourier or Hartley transform , determine the values of the values and coordinates of the threshold excess values of convolution accurate to the count, which determine the radial range to the target with an accuracy corresponding to the interval of digitization of the reflected signal.

This method provides a simplification of the structural diagram of a digital range estimation device, reducing the complexity and volume of hardware implementation while maintaining the high quality of the radar. The use of fast Hartley transforms for performing cyclic convolution does not require devices for generating quadrature channels; it helps to obtain a simpler form of program code, which also simplifies the device as a whole [2].

The reasons that impede the achievement of the technical result indicated below when using the known range estimation method are the considerable complexity and computational costs due to the large amount of calculations associated with determining the linear convolution interval, which requires the use of a large amount of complex and expensive digital signal processing processors (DSP) and limits the performance of the radar in the process of detecting a target and measuring the range to it.

The essence of the group of inventions is as follows. A single inventive concept is to simplify the method of measuring range and expand its capabilities while significantly reducing the volume, complexity and cost of hardware implementation. The technical result obtained by the implementation of the invention is expressed in reducing the time of measuring the distance to the target.

The specified technical result is achieved by the fact that according to the invention, the current energy spectrum (TES) of the output signal of the receiver is formed, for which, in a numerical sequence characterizing the output signal of the receiver, the numerical samples are squared, the first TES sample is obtained by summing the first squares of the numerical samples, the number N which is equal to the number of samples characterizing the duration of the signal reflected from the target, sequential sampling of two squares of samples separated by N samples, and the values obtained by subtracting the TPS samples from the prior values of the square of the reference TES first sample in the sample and summing the squared result with the second reference in the sample.

The specified technical result is achieved by the fact that according to the invention, the device for generating a TPP of the output signal of the receiver contains a storage device (memory), a first and second multiplier, an inverter, a first and second adder, an adder storage device, while the input of the memory device, which is the input of the device, is connected to the first and the second inputs of the first multiplier, and the output with the first and second inputs of the second multiplier; the output of the first multiplier is connected to the first input of the first adder, to the second input of which the output of the accumulator-accumulator is connected; the output of the second multiplier through the inverter is connected to the first input of the second adder, the second input of which is connected to the output of the first adder, and the output to the input of the adder-drive, the output of which is the output of the device.

The memory device is configured for sequential access of the FIFO type.

The specified technical result is achieved by the fact that in the known method of measuring range, in which a signal limited by the receiver’s time strobe, containing the useful signal reflected from the target, noise and interference, is converted to a digital form, according to the invention, a numerical sample array is received, the number of which is limited by the duration of the receiver’s temporary gate and the frequency response of the analog-to-digital conversion, form the TES of the receiver’s output signal, for which the numerical sequence characterizing the output signal of the receiver, the numerical samples are squared, the first TES sample is obtained by summing the first squares of the numerical samples, the number N of which is equal to the number of samples characterizing the duration of the signal reflected from the target, in order to obtain subsequent TES samples, two squares of samples are sequentially sampled spaced by N samples, and the values of the TPP readings are obtained by subtracting from the previous value of the TPP readout us square sample in the first sample and summing the squared result with the second reference in the sample; each i-th value of TPP is compared with the maximum value from its previous samples, the largest value of the TPP sample and the number of the corresponding sample of the output signal of the receiver are stored, after calculating the last (LN) -th value of TPP and its comparison with the highest value from its previous samples range R to the target by the formula:

,

,

where t ₀ is the beginning of the temporary gate of the receiver;

M is the reference number of the output signal of the receiver, corresponding to the largest sample of the TPP;

Δt is the sampling interval of the analog-to-digital conversion;

C is the speed of propagation of radio waves in free space (speed of light).

In the application, the unity of invention is respected, because in the group of inventions, the second of them is intended for the implementation of the first, and together they are intended for use in the third. Causal relationships between the features of inventions and the technical result are expressed in the following. Based on the well-known Parseval equality [3, 4], which states the identity of the estimates of energy relations in the frequency and time domains, the distance to the target is determined by the fact that the ratio (signal + noise) / noise in the time domain is exceeded by forming a recursive algorithm for calculating the signal energy in each position the sequence of samples obtained as a result of analog-to-digital conversion of the output signal of the receiver. The criterion for the presence of a useful signal in the digital strobe is the condition

,

,

where j = 1, 2, ..., L;

L is the length of the sequence of samples in the numerical strobe.

The value of Energy [(signal + noise), j] is equal to the sum of N squares of the samples of the digital strobe, starting from position j. The value of Energy (noise) is determined by the sum of N squares of the samples of the digital strobe, determined in any position provided there is no reflected signal in it, or is set a priori. Since it is not required to perform the operations of computing the cyclic convolution using the fast Fourier or Hartley transform, the time of determining the range in comparison with the prototype is significantly reduced. Accordingly, the number of used elements of digital signal processing devices is significantly reduced, which greatly simplifies the apparatus of the device for implementing the method and significantly improves its speed.

The group of inventions is illustrated by drawings, on which:

figure 1 is a structural diagram of a device for forming a TPP;

figure 2 is a view of a sounding signal;

figure 3 - spectrum of the probing signal;

figure 4 - view of the received signal (waveform) in the noise of the digital strobe;

5 is an illustration of the formation of a sequence of samples of the current energy spectrum of the output signal of the receiver;

6 is a current energy spectrum of the output signal of the receiver;

Fig.7 is a view of the additive sum "signal + noise" in the digital strobe;

Fig - spectrum of the additive sum "signal + noise";

Fig.9 is a structural diagram of a device for implementing the method of measuring range;

figure 10 is a block diagram of the algorithm of the DSP.

The method of forming a TPP of the output signal of the receiver is as follows. It is known that the signal energy for the time interval T is determined by the expression

Using Parseval's equation, expression (1) can be written using the Fourier transform of a time function that describes the signal, or using its representation in the form of a Fourier series [4].

Representation of Parseval equality through the spectrum of a function

representation of the Parseval equality in terms of the coefficients of the Fourier series of the function

where x (t) is the function that describes the signal;

S [ω] is the Fourier transform for the continuous-time function x (t),

A _i are the coefficients of the Fourier series of the function x (t).

The right-hand sides of expressions (2) and (3) are used to formulate the criterion of signal-to-noise energy ratios in the classical multichannel version of constructing a range-determining device. But from the Parseval equality it also follows that the energy of a pulse signal in the time domain at time t on the interval of its existence T can be calculated by the formula:

Using expression (4), it is possible to determine the TES of the signal x (t) on the interval t ₁ ≤t≥t _{2 by the} discrete values of the function E _x (iΔt, N), that is, in digital form expression (1) for the TES is represented as:

where E _i - readings of the current energy spectrum,

x _i - ADC output samples (elements of a numerical array)

T ₁ ≤i≥T ₂ ;

T ₁ = t ₁ / Δt, T ₂ = t ₂ / Δt (the symbol "/" is an integer division);

Δt is the sampling interval of the analog-to-digital converter;

N is the number of samples of the function that describes the signal.

This expression can be represented in a simple recursive form:

where E ₀ = 0, T ₁ ≤i≥T ₂ .

As can be seen from the example illustrated by the diagram of Fig. 5, where x _i are the samples of the signal, T ₁ = 1, T ₂ = L, N = 10, the sequence for obtaining the sums, that is, the TES samples, is represented as follows:

;

;

;

;

;

;

The first TES sample is obtained by direct summation of the squares of the first ten samples of the L-sequence. The second TES reference can be obtained by subtracting from the value of the 1st TES reference the square of the 1st reference from the L-sequence and adding the square of the 11th reference of this sequence. The third TES reference can be obtained by subtracting from the 2nd TES reference value the square of the 2nd reference from the L-sequence and adding the square of the 12th reference of this sequence, and so on; the i-th TES reference can be obtained by subtracting from the value of the (i-1) th TES reference the square of the i-th reference from the L-sequence and adding the square of the (N + 1) -th reference of this sequence, etc. according to the same rule until the last (L-9) th count is calculated.

Figure 4 shows a numerical array consisting of 4096 samples of normal noise from a position corresponding to the 2500th sample. It contains an additive mixture of the signal, the type and spectrum of which are presented, respectively, in figure 2 and figure 3 with this noise. Figure 6 presents the TPP function for this array, having a maximum in the position corresponding to the beginning of the signal placement. A sample of the additive mixture of the signal with noise and its spectrum are presented, respectively, in Fig.7 and Fig.8. The identity of the maximum positions of the spectra depicted in Fig. 3 and Fig. 8 confirms the identity of the structures of the probe and reflected from the target signal, and hence the efficiency of the application of the method of forming TES.

Thus, the method of generating a TES of the output signal of the receiver is that in a numerical sequence characterizing the output signal of the receiver, the numerical samples are squared, the first TES sample is obtained by summing the first squares of the numerical samples, the number N of which is equal to the number of samples characterizing the duration of the reflected from the signal target, in order to obtain subsequent TES samples, two squares of samples separated by N samples are sequentially sampled and the value of the TPP samples by subtracting from the previous value of the TPP sample value the square of the first sample in the sample and summing the result with the square of the second sample in the sample.

Since the elements of a numerical array can correspond to different physical processes, and the array itself can be of different dimensions (vector, matrix, tensor, etc.), the method of generating a TES of the output signal of the receiver is also applicable in systems using other methods of obtaining numerical arrays other than radio waves. For example, if there is a numerical matrix that displays the smoothness of the surface, then using this method and the corresponding device for its implementation, by setting various values of the parameter N, it is possible to determine the coordinates of the anomalies corresponding to this parameter in the matrix, and therefore on the surface under study.

The device for forming the current energy spectrum (figure 1) contains a storage device (memory) 1, the first 2 ₁ and second 2 ₂ multipliers, an inverter 3, the first 4 ₁ and second 4 ₂ adders, the adder-drive 5. The input of the memory 1, which is the input device connected to the first and second inputs of the first multiplier 2 ₁ , and the output to the first and second inputs of the second multiplier 2 ₂ . The output of the first multiplier 2 _{1 is} connected to the first input of the first adder 4 ₁ , to the second input of which the output of the accumulator-accumulator 5 is connected. The output of the second multiplier 2 ₂ through an inverter 3 is connected to the first input of the second adder 4 ₂ , the second input of which is connected to the output of the first adder 4 ₁ , and the output - with the first input of the adder-drive 5, the second input of which is reset, and its output is the output of the device.

The device is made on known elements of digital technology. In particular, memory 1 can be made in the form of a register with sequentially connected memory cells and parallel transfer of their contents and direct access to the first and last memory cells with the possibility of sequential access of the type "first entered - first out" (FIFO) [5]. Shaper TPP can be performed on FPGA type EP1S10 firm ALTERA [6].

The device for forming a thermal power plant operates as follows. The numerical sequence characterizing the output signal of the receiver is fed to the input of the memory 1 and to the first and second inputs of the first multiplier 2 ₁ . The memory 1 has a register of N memory cells previously zeroed. At each step, in accordance with the organization of memory on a first-come-first-go basis (FIFO), in the register of memory cells of memory 1, their contents are overwritten from the previous cell to the next cell, and the previous contents of the last N-th memory cell of the register are not saved . The calculation of the next step of counting the numerical value of the thermal power plant, as shown in the table (for example, at N = 4), is performed during the arrival of a new count.

Table Step 0 0 0 0 0 E ₀ = 00 + 00 + 00 + 00 Step 1 x ₁ 0 0 0 E ₁ = E ₀ + x ₁ x ₁ -00 Step 2 x ₂ x ₁ 0 0 E ₂ = E ₁ + x ₂ x ₂ -00 Step 3 x ₃ x ₂ x ₃ 0 E ₃ = E ₂ + x ₃ x ₃ -00 Step 4 x ₄ x ₃ x ₂ x ₁ E ₄ = E ₃ + x ₄ x ₄ -x ₁ x ₁ Step 5 x ₅ x ₄ x ₃ x ₂ E ₅ = E ₄ + x ₅ x ₅ -x ₂ x ₂ Step 6 x ₆ x ₅ x ₄ x ₃ E ₆ = E ₅ + x ₆ x ₆ -x ₃ x ₃

For this, in parallel with the input number arriving at the first multiplier 2 ₁ , the first and second inputs of the second multiplier 2 ₂ receive a number from the N-th cell of the memory register 1. The result of multiplication from the output of the first multiplier 2 ₁ goes to the input of the first adder 4 ₁ , the second input of which numerical value is output from the adder-accumulator 5. The result representing the sum of two numbers, from the output of the first adder January ₄ provided to a first input of the second adder February _4, the second input of which the output from the numerical value nvertora 3 obtained by inverting the (number of sign change) the result obtained from the output of the second multiplier February _2. From the output of the second adder 4 _{2, the} result of the summation is fed to the input of the adder-accumulator 5, the number obtained in it is the output of the adder-accumulator 5 and the output of the TPP device, representing successive readings of the TPP.

The method of measuring range is as follows. A probe signal is emitted in the direction of the target, for example, in the form of harmonic oscillations (Fig. 2). The spectrum of this signal is presented in figure 3. With the frequency of the sensing clock cycles, a signal x (t) containing noise, possibly interference, and a useful signal reflected from the target is received in the time gate of the receiver (Fig. 4). The received signal is converted to digital form and form a numerical array of samples x _i , where i = 1, 2, ..., L (figure 5). The number of L samples in the array is limited by the length of the receiver's time gate, and the number of N samples is limited by the duration of the probe signal. Assume that in the numerical array of FIG. 5, the useful signal reflected from the target is positioned from the reference i = 2500. Determine the values of the TES of the output signal of the receiver, which is characterized by the obtained numerical array of samples. For this, the numerical samples are squared, the first TES sample is obtained by summing the first squares of the numerical samples, the number N of which is equal to the number of samples characterizing the duration of the signal reflected from the target. To obtain subsequent TES samples, two squares of samples separated by N samples are sequentially sampled, and TES samples are obtained by subtracting the square of the first sample in the sample from the previous TES sample value and summing the result with the square of the second sample in the sample. Due to the random nature of the values of the samples of the receiver’s temporary gate x _i caused by analog-to-digital conversion noise, system noise, random noise, fluctuations of the signal reflected from the target, and other reasons, the TES values are also random in nature, numerically showing the degree of influence of each of the listed reasons . For the case of the reflected signal in white noise, which is most often encountered in practice, the corresponding numerical array will have a numerical anomaly (due to the addition of the energy of the reflected signal and the noise energy) in the area of the reflected signal (Fig. 6). The maximum value of the numerical anomaly corresponds to the maximum contribution of the energy of the reflected signal and thereby determines its position in the numerical array. To determine this position, each of the successively obtained TPP values is compared with the maximum value from its previous samples, and if the new sample exceeds the existing maximum, then it is stored as the new maximum TPP value and the corresponding reference number, otherwise, the previous maximum TPP value is saved and number of its reference according to the formula:

where i = 2, 3, ..., L-N.

The obtained maximum value of the energy spectrum of MaxE is compared with the threshold value Epor, which can be taken as any value of the energy spectrum E _i in the interval (M-N <i> M + N), where the received signal is absent, or is set a priori. If the threshold is exceeded, that is, the condition MaxЕ-Epor≥S _{0 is} fulfilled, where the value S ₀ = N / 2 corresponds to the minimum TEC of the reflected signal, the presence of a useful signal from the target in the sequence of samples is judged. The distance R to the target is determined by the formula

, (8)

, (8)

where t ₀ is the beginning of the temporary gate of the receiver;

M is the reference number of the output signal of the receiver, corresponding to the largest sample of the TPP;

Δt is the sampling interval of the analog-to-digital conversion;

C is the speed of propagation of radio waves in free space (speed of light).

The described method of measuring the range can be carried out using the device (Fig. 9), containing a series-connected analog-to-digital converter (ADC) 6, a first storage device (memory) 7, a thermoelectric generator 8 and an arithmetic logic device (ALU) 9. The input device is the input of the ADC 6, which is connected to the corresponding output of the radar receiver (not shown in the diagram), the output is the output of the ALU 9. The generator of the TPP 8 contains the second memory 1, the first 2 ₁ and second 2 ₂ multipliers, inverter 3, the first 4 ₁ and second 4 ₂ adders, accumulator adder Itel 5. The input of the second memory 1 is connected to the output of the first memory 7, the first and second inputs of the first multiplier 2 ₁ , and the output is connected with the first and second inputs of the second multiplier 2 ₂ . The output of the first multiplier 2 _{1 is} connected to the first input of the first adder 4 ₁ , to the second input of which the output of the accumulator-accumulator 5 is connected. The output of the second multiplier 4 ₂ through an inverter 3 is connected to the first input of the second adder 4 ₂ , the second input of which is connected to the output of the first adder 2 ₁ , and the output is with the input of the accumulator-drive 5, the output of which is connected to the input of ALU 9. ALU 9 is made according to well-known rules on the logical elements of digital technology, its structure is clear from the flowchart of the operation algorithm shown in Fig.10.

The described device for measuring range works as follows. An analog signal x (t) is received at the ADC input 6 from the output of the radar receiver, the duration of which is limited by the receiver’s time gate - T. At the ADC output 6, a sequence of samples x (i · Δt) is formed, with a length L = Т / Δt, where "/" - the operation of integer division, which is recorded in the first memory 6 in the form of a numerical array x _i (figure 5). Over time, determined by the calculation time of the TPP readout, to the TPP shaper 8 from the output of the first memory 6, the samples x _i sequentially arrive at the input of the second memory 1, the first and second inputs of the first multiplier 2 ₁ . In parallel, the first and second inputs of the second multiplier 2 ₂ receive a number from the N-th cell of the memory register of the second memory 1. The result of multiplication from the output of the first multiplier 2 ₁ goes to the input of the first adder 4 ₁ , its second input receives a numerical value from the output of the adder- accumulator 5. The result, representing the sum of two numbers, from the output of the first adder February ₁ comes to a first input of the second adder 2 _2, the second input of which the numeric value from the output of inverter 3 obtained by inverting the (number of sign change) D ultata obtained from the output of the second multiplier February _2. From the output of the second adder 4 _{2, the} result of the summation is fed to the input of the adder-accumulator 5 and the number obtained in it is the output of the adder-accumulator and the output of the TPP formation device 8, representing sequential readings of the TPP (Fig. 6), which are received in sequence in the order of their calculation to the input of ALU 9. Here, according to the algorithm shown in Fig. 10, each sample from successively obtained values of TPPs is compared with the maximum value from its previous samples and if the new sample exceeds the available maximum maximum of the then stores it as a new maximum value of the power plant and the corresponding reference number. Otherwise, the previous maximum value of the thermal power station and its reference number are retained. The obtained maximum value of the reference energy spectrum MaxЕ is compared with the threshold value Epor, which can be taken as any value of the energy spectrum E, in the interval (M-N <i> M + N), where the received signal is absent, or is set a priori. If the threshold is exceeded, i.e. the fulfillment of the condition MaxE-Epor≥S ₀ , where the value S ₀ = N / 2 corresponds to the minimum value of the current sample of the energy spectrum of the reflected signal, judge the presence of a useful signal from the target in the sequence of samples. The distance R to the target is determined by the formula

,

,

where M is the reference number of the output signal of the receiver, corresponding to the largest sample of the TPP;

Δt is the sampling interval of the analog-to-digital conversion;

t ₀ - the beginning of the temporary gate of the receiver;

C is the speed of propagation of radio waves in free space (speed of light).

As can be seen from the flowchart of FIG. 10, all the technical components included in its composition are digital and constitute the nomenclature of a typical DSP, for example, processors of the type TMSXXX, ADSPXXX, etc. Therefore, in general, a ranging device can be made on the basis of a single processor.

Example. Let L = 4096 = 4N, N = 1024 = 2 ^r , r = 10.

An estimate of the number Ks of arithmetic operations necessary for the implementation of the claimed method can be written as:

Kc = (L-N) (2 + 2 + 1 + 1 + 1) = 18N,

those. To calculate one TES reference, it is necessary to perform two operations of multiplication, two operations of addition, one operation of subtraction. To find the maximum TPP, you must perform one comparison operation and one assignment operation.

An estimate of the number Kp of arithmetic operations necessary for the implementation of the prototype can be written as:

Kp = (8 + 3) Kbpf≈550N,

where the FFT score estimate is [1,2] Kbpf = (N / 2) r · 10.

In the prototype, to determine the position of linear convolutions or roughly determine the range, it is necessary to calculate eight FFT algorithms, and to accurately calculate the range, it is necessary to calculate three FFT algorithms corresponding to the calculation of the fast cyclic convolution algorithm.

The given performance estimates show that, according to this criterion, the claimed method of measuring range is approximately 30 times more effective than its prototype. Obviously, an advantage in the technical implementation of the claimed solution.

The implementation of the inventions allows you to build channelless digital receivers of electromagnetic waves, including other than radio waves, for various purposes on the basis of a single processor, which provides not only their significant simplification and low cost, but also a significant reduction in time for their development, debugging and implementation.

Information sources

1. Rabiner L., Gould B. Theory and application of digital signal processing. M., "WORLD", 1978.

2. RU 2264650, G06F 17/14, G01S 13/26, 2005.

3. Sergienko A.B. Digital signal processing. Textbook for high schools. - Moscow, Minsk. PETER, 2003, pp. 54-55, 253.

4. Denisenko A.M. Signals. Theoretical radio engineering. Reference manual. - M., Hotline - Telecom, 2005, p. 28-29.

5. Novozhilov O.P. Fundamentals of digital technology / study guide. - M .: IP Radiosoft, 2004, pp. 322-327.

6. www.Altera.com.

Claims (4)

1. The method of forming the current energy spectrum (TES) of the output signal of the receiver, which consists in the fact that in a numerical sequence characterizing the output signal of the receiver, the numerical samples are squared, the first TES sample is obtained by summing the first squares of the numerical samples, the number N of which is equal to the number samples characterizing the duration of the signal reflected from the target, to obtain subsequent samples of the TPP, a sequential sampling of two squares of samples spaced by N count in, and the values obtained by subtracting the TPS samples from the prior values of the square of the reference TES first sample in the sample and summing the squared result with the second reference in the sample. 2. A device for forming the current energy spectrum (TES) of the output signal of the receiver, characterized in that it contains a storage device (memory), the first and second multipliers, an inverter, the first and second adders, the adder-drive, while the input of the memory, which is the input of the device connected to the first and second inputs of the first multiplier, and the output to the first and second inputs of the second multiplier, the output of the first multiplier is connected to the first input of the first adder, to the second input of which the output of the accumulator-accumulator is connected, you od the second multiplier via an inverter connected to the first input of the second adder, a second input coupled to an output of the first adder and an output - to an input of adder-accumulator, the output of which is an output device. 3. The device according to claim 2, characterized in that the storage device is made with the possibility of sequential access of the FIFO type. 4. A method of measuring range, in which a signal limited by the receiver’s time strobe, containing a useful signal reflected from the target, noise and interference, is converted into a digital form, characterized in that they form a numerical array of samples, the number of which is limited by the duration of the time the receiver gate and the frequency response of the analog-to-digital conversion, form the current energy spectrum (TES) of the output signal of the receiver, for which, in a numerical sequence, ha which characterizes the receiver output signal, the numerical samples are squared, the first TES sample is obtained by summing the first squares of samples, the number N of which is equal to the number of samples characterizing the duration of the signal reflected from the target, in order to obtain subsequent TES samples, two squares of samples separated by N samples, and get the values of the TPP readings by subtracting from the previous value of the TPP readout the value of the square of the first sample in the sample and mumming the result with the square of the second sample in the sample, each ie TES value, where i = 1, 2, ..., L, L is the number of samples limited by the duration of the receiver’s temporary gate, compare it with the maximum value from its previous samples, remember the largest TES sample value and the number of the corresponding sample of the output signal of the receiver, after calculating the last (LN) th value of the TES and comparing it with the highest value from its previous samples, determine the distance R to the target using the formula

where t ₀ is the beginning of the temporary gate of the receiver;
M is the reference number of the output signal of the receiver corresponding to the largest sample of the TPP;
Δt is the sampling interval of the analog-to-digital conversion;
c is the speed of propagation of radio waves in free space (speed of light).

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