MXPA01001753A

MXPA01001753A - Stacked-carrier discrete multiple tone communication technology.

Info

Publication number: MXPA01001753A
Application number: MXPA01001753A
Authority: MX
Inventors: Brian G Agee
Original assignee: Beamreach Networks Inc
Priority date: 1998-08-18
Filing date: 1998-08-18
Publication date: 2002-06-04
Also published as: BR9816015A; CN1237746C; JP2002523969A; AU8911798A; CN1310894A; KR20010106445A; EP1119932A1; CA2340716A1; WO2000011823A1; EP1119932A4; IL141464A; IL141464A0

Abstract

A "stacked-carrier" spread spectrum communication system (10) based on frequency domain spreading that multiplies a time-domain representation of a baseband signal by a set of superimposed, or stacked, complex sinusoid carrier waves. In a preferred embodiment (10), the spreading energizes the bins of a large fast Fourier transform (FFT). This provides a considerable savings in computational complexity for moderate output FFT sizes. Point-to-Multipoint and multipoint-to-multipoint (nodeless) network topologies are possible. A code-nulling method is included for interference cancellation and enhanced signal separation by exploiting the spectral diversity of the various sources (11). The basic system (10) may be extended to include multi-element antenna array (26/18) nulling methods also for interference cancellation and enhanced signal separation using spatial separation. Such methods permit directive and retrodirective transmission systems that adapt or can be adapted to the radio environment. Such systems are compatible with bandwidth-on-demand and higher-order modulation formats and use advanced (maximum-SINR) despreader adaptation algorithms.

Description

MULTITONQ COMMUNICATION TECHNOLOGY OF STACKED CARRIER SEPARATION DESCRIPTION OF THE INVENTION This invention relates generally to radio communications and more specifically to communication technologies for multiple access in difficult and hostile environments combined with dynamic environmental changes. The communication technology developed in the 40's, during World War II, included "frequency diversity communication" or "stacked carrier communications" to aid in high frequency band (HF) traffic. J. Proakis refers to frequency diversity communication technology in, Digital Communications, McGraw-Hill, 1989, see, sections 7.4 to 7.7. Diversity techniques are said by Proakis that are based on the notion of errors occurring in the reception of widely attenuated channels, for example, deep fade channels. By supplying the receiver with various duplicates of the original signal, though on channels that melt independently of each other, it has the potential to ensure continuous communication except during the unlikely event that all duplicate channels are fused together. Such a probability can be estimated.

Frequency diversity is one of many methods of diversity. The same modulation is carried by various carrier channels nominally separated by the coherence bandwidth of each respective channel. In the diversity of time, the same information is transmitted on different emission boxes. Multiple antennas can be used in a diversity scheme. Various reception antennas can be used to receive the signals sent from an individual transmission antenna. For the best effect, the receiving antennas are separated far enough to vary the different multipath interference between the group. A separation of ten wavelengths is nominally usually needed to observe the signal fading independently. A signal having a bandwidth much larger than the coherence bandwidth of the channel can be used in a more sophisticated diversity scheme. Such a signal with a W bandwidth will resolve the multipath components and provide the receiver with fading signal paths independently. Other diversity schemes of the prior art have included diversity of arrival or spatial angle and polarization diversity. When a bandwidth W much larger than the coherence bandwidth of each respective channel is available to the user, the channel can be subdivided into a number of frequency division multiplexed subchannels having a mutual separation at central frequencies of at least the coherence bandwidth of each respective channel. The same signal can then be transmitted over the multiplexed sub-channels of division frequency to establish the frequency diversity operation. The same result can be achieved by using a broadband binary signal that covers the bandwidth. G. K. Kaleh describes in an article, "Frequency-Diversity Spread-Spectrum Communication System to Counter Band-limited Gaussian Interference," IEEE Transactions on Communications, Sept. 1994. In this one a secure exhibition is represented so that it can operate in deliberately hostile signal environments. J. Proakis describes the propagated spectrum of frequency diversity and multiple access concepts in chapter eight. "Spread Spectrum Signáis for Digital Communication", supra. Diversity transmission combined with propagated hop frequency spectrum is detailed for protection against partial-band interference multipath fading. Retrodirectivity was proposed and was used early in 1959 to 'adapt a multiple-element antenna array to provide gain patterns Í. ? . . *. Identical spatial I '? * During the transmission and reception of operations, see. R. Monzingo, T. Miller, Introduction to Adaptive Arrays, Wiley Interscience Publications, 1980; L. Van Atta, "Electromagnetic Reflection", US Patent 2,908,002, 1959; and B. Glance, P. Henry, "High Capacity Mobile Radio System", US Patent 4,383,332, May 10, 1983, during a discussion of such techniques. TDD systems provide an effective means to implement retrodirective antenna arrays, for example, by minimizing the channel variation between reception and transmission trajectories. It is therefore an object of this invention to provide a radio communication system for proving data over widely separated frequency bands that manifest differences in channel distortion without physically propagating the signals between the intervention frequencies, as required with the spectrum propagated direct sequence. It is another object of the invention to provide a radio communication system for communication under strong shortband interference, for example, conventional cellular signal waveforms, by turning off the affected frequency channels in a receiver spreader. It is an object of the invention to provide a radio communication system with simple compensation of _j_? the multipath distortion of linear channel. It is an object of the invention to provide a radio communication system that is compatible with discrete multi-tone channeling and orthogonal frequency division multiplexer techniques. And that it is compatible with modulation / demodulation techniques such as discrete multitone multiplexer and orthogonal frequency division of packaged time for frequency channeling and reverse channeling. It is another object of this invention to provide a radio communication system that is compatible with time division duplex systems where the stacked bearer propagated spectrum modulation format is generated using discrete multi-tone multiplexer based frequency channelers and / or orthogonal frequency division and diverse channelers. It is an object of the invention to provide a multiple access frequency division radio communication system as the multiple access capability. It is an object of the invention to provide a radio communication system for the division of the multiple access code as the capacity in a stacked bearer multiple access matrix. It is an object of the invention to provide a radio communication system compatible with high-order digital modulations. It is an object of the invention to provide a radio communication system for flexible data percentage connections of bandwidth on demand. It is an object of the invention to provide a radio communication system for multiple access and multiple access type division, interference excision, and channel compensation capability in a code override application. It is an object of the invention to provide a radio communication system for use with adaptive antenna arrays by spatially extending a propagation code to propagate data using independent complex gains in each spatial channel or antenna beam, to control the dispersion of the matrix bandwidth of the channel. It is an object of the invention to provide a radio communication system compatible with advanced matrix adaptation techniques, for example, a non-blind directed pilot, targeted data, blind and other techniques that have advantages of reinforced data properties baseband, channel structure, or stackable carrier propagation format. It is an object of the invention to provide a radio communication system compatible with the retrodirective communication techniques. It is an object of the invention to provide a radio communication system for backup compatibility with conventional code division multiple access, data activation system. Briefly, one embodiment of the invention comprises a propagated spectrum communication system "stacked carrier" wherein the propagation is made in the frequency domain by multiplying a domain time representation of a baseband signal by a set of waves complex sinusoid carriers, superimposed, or stacked. In practice, propagation is done by simply energizing the deposits of a large fast Fourier transform (FFT). This provides considerable savings in computational complexity for moderate output FFT sizes. A Kaiser-Bessel window, for example, with ß = 9, can be used to "fill" the space between the tones without subjecting these tones to unacceptable interference from adjacent tones, for example, inter-tone interference. In particular, a high value of ß provides acceptable interference between adjacent tones and extremely low interference between the farthest tones. This basic technology is then combined with split-time duplex, code-division multiple access, division-by-space multiple access, frequency division multiple access, adaptive antenna arrangement, and interference cancellation techniques. An advantage of the invention is that a radio communication method is provided to propagate data over widely separated frequency bands for spectral diversity. This provides an efficient way to take advantage of frequency diversity, especially in applications where the bands are widely separated. An advantage of the invention is that a radio communication method is provided to communicate even under strong narrowband interference. In this way, a stacked bearer propagated spectrum (SCSS) link can be maintained in the presence of strong narrow band (FDMA) division multiple division access and time division multiple access (TDMA), cellular radio signals, as in cellular superposition applications. It also allows such a link to be maintained in the presence of unwanted interference due to signal harmonics outside the band. An advantage of the invention is that it is provided in a radio communication method that allows simple compensation of the linear channel distortion, and allows for the distortion of a stationary, or quasi-stationary linear channel approaching as a multiplicative effect.

F-? t l t iHrUTi on the transmission propagation code. It also allows the channel compensation operation to be assumed within the depropagation or propagation operation without the additional filtering operations, apart from the removal of the intrapaired propagated Doppler. The basic technique equalizes the multipath dispersion in proportion to the bandwidth of the band base, the pre-propagated menscje signal. This multi-path compensation operation can be extremely simple if the bandwidth of the message signal is low. If the bandwidth of the message signal is pre-propagated is sufficiently low, for example, the correlation width of the inverse bandwidth of the pre-projected message signal is a large multipath of multipath delay plus long in the transmission channel, this compensation operation reduces to a multiple complex operation that is automatically incorporated into the adaptive propagation operation. This is in contrast to conventional CDMA systems, which require additional compensation operations, except that the correlation width of the propagated signal is a large multiple of the largest multipath delay in the transmission channel. Another advantage of the invention is that a radio communication method is provided to be compatible Ii? r¡r tlk¿U. with frequency channeling techniques such as discrete multiple tone multiplexer and division by orthogonal frequency. This allows the stationary and linear channel distortion to be modeled as an exact multiplicative effect 5 in the transmission propagation code. An advantage of the invention is that a radio communication method is provided to be compatible with time division split duplex systems. In this way, division duplex communication formats by time 10 may be used where the spread spectrum format of the stacked bearer carrier is packaged, for example, if the stacked bearer propagated spectrum signal is generated by using discrete multiple tone multiplexer-based frequency channelers and / or splitting. 15 orthogonal frequency and inverse channelers. A "local" estimate of the channel transmitted at either end of the communication link becomes possible, to a large extent by simplifying the implementation of channel pre-emphasis, channel compensation topologies transmitted on the site and data transmission techniques. 20 retrodirective transmission. An advantage of the invention is that a radio communication method is provided with a multiple access code type multiple access access, for example, the multiple access access 25 stacked carrier. The point communication links to ^ m ^ nm i ^ multipoint, is implemented by the transmission of signals on the same subset of frequency channels, using linearly independent sets (orthogonal or non-orthogonal) of propagation gains for the signals at 5 the depropagator. Since the propagation codes may not be orthogonal, a main advantage of this invention when used in conjunction with the code cancellation technique is that the use of non-orthogonal propagation codes is possible. One advantage of the invention is that a radio communication method is provided to be compatible with flexible data rate "demand bandwidth" techniques. The proportion of data supplied in a given link can be increased or decreased in small 15 increments for the primitive transmission to a single user on stacked or multiple time, frequency or stacked bearer channels. The data proportion is then adjusted without any increase in the bandwidth of the proportion of data that increases using the channels 20 multiple stacked carriers. An advantage of the invention is that a radio communication method is provided to be compatible with high-order digital modulations. This will be compatible with 'baseband modulation' formats 25 digital arbitrary Mary and allows the ability to improve ^^^ ááM through the transmission of higher numbers of bits / symbols in each frequency channel. The re-use is improved and the "load balance" in multicellular communication networks can be included by varying the bits per symbol in each primitive. An advantage of the invention is that a radio communication method is provided to have multiple division-by-space access, interference excision, and channel compensation capability, for example, in the code cancellation technique. Such a division-by-space multi-access code bypass technique, in near-optimal and optimal linear interference cancellation techniques and signal extraction, are useful for separating the stacked spread carrier-separated spectrum signals in the unpair, based on the frequency diversity or spectral diversity of the signals. The excision by interference against the signals of propagated spectrum of carrier stacked in cells, is provided with this, as well as the elimination of interferences outside the cell, for example, the capacity of increase of re-use. This then allows the most effective use of code override, which can generally be applied to a wide range of propagation formats. In particular, it provides a factor of two capacity improvements over code cancellation techniques developed for use with propagated spectrum formats of direct symbol modulation sequence where the propagation gain repeats once again each overlay message symbol. An advantage of the invention is that a radio communication method is provided so that it can be used with adaptive antenna arrays. An advantage of the invention is that a radio communication method is provided to be compatible with advanced matrix adaptation techniques and thereby separate the signals based on spatial diversity, frequency spectrum diversity, polarization diversity, and combinations of spatial / spectral / polarization diversity. An advantage of the invention is that a radio communication method is provided to be compatible with back-direction communication techniques. This allows a straight extension of the spatial retro-directivity technique for the propagated spectrum systems of stacked carrier 20 including individual antennas or antenne arrays. And it allows the concentration of more complex operations in the base station in point-to-multipoint communication links, greatly reducing the cost of the total system. 25 An additional advantage is that a method of ^^^ jÉ ^ - * - '• - - ~ "- * ...- ~ &l radio communication is provided to be backward compatible with multiple division access by conventional code, activation techniques of These and other objects and advantages of the invention will undoubtedly become obvious to those skilled in the art, after having read the following detailed description of the preferred embodiment which is illustrated in the various figures BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 is a block diagram of one embodiment of a communication system of the invention wherein the various remote mobile units are distributed in space around one or more central base stations, Figure 2A is a block diagram representing one embodiment of the invention wherein a stacked carrier propagated spectrum transmitting bank is connected to a set of antennas for a point-to-point transmitter, and another set of antennas is connected to a stacked carrier propagated spectrum receiver bank 5 for a point-to-point receiver Figure 2B is a block diagram representing another embodiment of the invention wherein a stacked carrier multiple access transmitter bank is connected to a set of antennas for a network transmitter and another set of antennas is connected to an access receiving bank ? *. * 1ít -? multiple stacked carrier for a network receiver; Figure 3A is a block diagram representing another embodiment of the invention wherein a stacked carrier propagated spectrum transmitter is connected to a division duplexer by time for a point-to-point transmitter, and another division duplexer by time is connects to a stacked carrier propagated spectrum receiver for a point-to-point receiver Figure 3B is a block diagram representing another embodiment of the invention wherein a stacked bearer multiple access transmitter is connected to a division by time duplexer for one network transmitter, and another time division duplexer is connected to a stacked bearer multiple access receiver for a network receiver; Figure 4A is a block diagram representing another embodiment of the invention wherein a stacked carrier propagated spectrum transmitter is connected to a code override for a point-to-point transmitter, and another code override is connected to a receiver of propagated spectrum of the stacked carrier for a point-to-point receiver; Figure 4B is a block diagram representing another embodiment of the invention wherein a stacked bearer multiple access transmitter is connected to a code scrambler for a network transmitter, and another code scrambler is connected to an access receiver multiple of stacked carrier for a network receiver; Figure 5A is a block diagram representing another embodiment of the invention wherein a stacked carrier propagated spectrum transmitter is connected to a widely separated frequency changer, for a point-to-point transmitter, and another frequency changer broadly separate is connected to a stacked carrier propagated spectrum receiver for a point-to-point receiver Figure 5B is a block diagram representing another embodiment of the invention wherein a stacked carrier multiple access transmitter is connected 15 to a channelizer of widely separated frequency for a network transmitter, and another widely separated frequency channel is connected to a stacked bearer multiple access receiver for a network receiver; Figure 6A is a block diagram representing another embodiment of the invention wherein a stacked bearer propagated spectrum transmitter bank is connected to a synchronized time division duplexer bank that is connected to a set of antennas and a bank of propagated spectrum receiver of stacked carrier 25 with a retro-adapter in transmitter bank control itttr '* ipt? miitt? ríTtñ v ". ? ¿. 4, «-_ .., • t,? «- - -f, r-, t -, .., _f > - - - - - - * .-- • - »- * - propagated spectrum of stacked carrier for a point-to-point transceiver system; Figure 6B is a block diagram representing another embodiment of the present invention, wherein a stacked bearer multiple access transmitter bank is connected to a synchronized time division duplexer that is connected to a set of antennas and a receiving bank multiple-access stacked carrier with a retro-adapter in stacked carrier multiple access transmitter bank control for a network system; Figure 7A is a functional block diagram of a stacked carrier propagated spectrum transmitter similar to those included in Figures 2A, 3A, 4A, 5A and 6A; Figure 7B is a functional block diagram of a stacked carrier propagated spectrum receiver similar to those included in Figures 2A, 3A, 4A, 5A and 6A; Figure 8 is a block diagram of the base station included in the system of Figure 1 and showing the possibility that arrays of antennas allow spatial distinction between members of the communication system. Each functional transmitter and receiver line is represented as comprising many channels in support of the propagated spectrum communication medium of basic stacked carrier; Figure 9 is a block diagram of a typical remote unit included in the system of Figure 1 and showing the adaptive channel compensation and the pre-emphasis functions in support of the stacked carrier propagated spectrum communication medium; Figure 10 is a block diagram of a multi-element T / R module that includes a plurality of individual T / R modules, one for each antenna. The complexity of the system can be extended or reduced to scale with the number of antennas. The spatial process occurs after the process of analog-to-digital conversion (ADC) during the reception operation, and before the conversion operation from digital to analog (DAC) during the transmission operation. All spatial as well as spectral propagation operations are performed on the digital data. All key frequency and clock references in the system are derived from a common clock, such as a GPS clock. A mechanism is shown for the calibration of the module, which is necessary for the exact retro-directivity in the TDD system; Figure 11 is a block diagram of a stacked carrier propagated spectrum modulator wherein baseband data are reproduced on separate propagation cells Kpr0paid multiplied by a separate scalar that is passed to a time multiplexer for the > »< ** ^^^^^^ combination in a complex data vector; Figure 12 is a block diagram of a stacked carrier propagated spectrum depropagator in a fully digital adaptive implementation. The depropagator includes various channels for processing each of the tones in a carrier medium of spread spectrum of stacked carrier; Figure 13 graphically represents an exemplary BPSK multitone having a data length of six, a propagation factor of Kpr0paid of four and a separation between each group of two. Each group of cells, gl-g4, represented as having an independent amplitude that can be manipulated by channel compensation and pre-emphasis to combat interference and other problems; Figure 14 graphically represents a processor "SCORE" used to restore a received signal x (t) from a set of antennas. Processor controls include control filters h (t), alpha frequency switching value, and conjugation control (*); Figure 15 is a data flow diagram representing a code gate SCORE depropagation operation with gates on two subsets of cells; Figure 16 is a data flow diagram depicting a SCORE propagation operation of code gates with gates on two subsets of cells, and demonstrates a symmetry with those of Figure 15; Figure 17 is a frequency-by-time format for a division-by-time duplex communication system of the embodiment of the invention; Figure 18 is an active tone format of a basic DMT modem; Figure 19 is a flowchart of data representing a transmission / reception calibration method; Figure 20 is a diagram of a discrete multi-tone modem and T / R single-antenna modem (DMT) integrated to implement a stacked bearer multiple access system based on DMT (SCMA) of the embodiment of the invention; Figure 21 is a general example of an individual link code gate SCORE depropagator of the embodiment of the invention; Figure 22 is a data flow diagram depicting a crosslink SCORE depropagation operation of individual link code gate with subsets of Kpropagada ceda / Figure 23 is a data flow diagram representing a cross SCORE algorithm of individual link with adaptation box / Ncuadro packets Figure 24 is a data flow diagram representing a calculation of individual adaptation table autocorrelation statistics; Figure 25 is a data flow diagram representing a cross-SCORE equation of own with subsets of Kpropaged cells; Figure 26 is a data flow diagram representing a code key generator with subsets of cells of Kparte < Kpropagada; Figure 27 is a data flow diagram representing an equivalent code key applier with subsets of propagated Kparte cells; Figure 28 is a data flow diagram representing a cross-SCORE equation with subsets of Kparte; Figure 29 is a data flow diagram representing an SCORE-own equation crossed with two subsets of cells; Figure 30 is a data flow diagram representing a cross SCORE depropagator of multiple link gate gates of the embodiment of the invention; Figure 31 is a data flow diagram representing an auto-SCORE gateway propagation operation of individual link code with gates on the frequency and two subsets of cells in one embodiment of the invention; Figure 32 is a data flow diagram representing an auto-SCORE despreading operation of individual link code gateways with gates on frequency and two subsets of cells; Figure 33 is a data flow diagram that represents a self-SCORE equation with gates on the frequency and two subsets of cells; Figure 34 is a data flow diagram representing an auto-SCORE propagation or individual link counting gates with time gates and a half-rate redundancy gate; and Figure 35 is a data flow diagram representing a self-SCORE despreading with individual link code gate with time gates and a half speed redundancy gate. Figure 1 illustrates a communication system of the embodiment of the invention, referred to herein by the general reference number 10. The system 10 comprises a base station 11 in two-way radio communication with a plurality of remote units 12-17. The positions of the remote units 12-17 surround the base station 11 in Figure 1 which represents the variety of different positions in three-dimensional space that can be assumed by all, or by one or more remote units at various points in time. The base station 11 has a multi-element antenna 18. - a - * - 1n? _? R * i_t > - • * - * • - * • ----- - ** • "-? Mtáü m Each 12-17 remote unit has a corresponding 19-24 antenna, some or all may include multiple element antennas, for example, antennas 21, 23 and 24. The antennas 18-24 represent alternatives that vary from a single physical antenna connected to a transceiver, to separate the antennas of transmission and reception and sets of antennas so that each one expresses the signal sensitivities. Differential spatiality On the other hand, some or all of the antennas 18-24 may have different polarization. 10 say, some of the antennas 18-24 can be polarized with positive perception (e.g., antenna 20) and some can be polarized into negative perception (e.g., antenna 22). The perception of "positive / negative" polarization can be based on linear polarization 15"horizontal / vertical", circular polarization "clockwise / counterclockwise", polarization "inclination 45/135", etc. The real noise invades the system 10 equally from all directions and sources of interference that is 20 typically define by their signals arriving from particular addresses. Multiple path signals between base 11 and remote units 12-17 represent a type of interference that can cause channel fading and other problems. 25 The system 10 can also include topologies of multipoint to multipoint network and point to point, as represented by a second base station 25 with a multi-element antenna 26. The multipoint-to-multipoint network is a superset of that shown in Figure 1, and is useful in cell systems where the adjacent cell interface needs to be controlled. Each base or remote transceiver in the network may have arbitrarily different numbers of antenna elements and propagation factors, for example, they may propagate over different numbers of frequency cells. The spatially localized interference may arrive from other stacked carrier networks and cells within the network and from other interferences, for example, jammers, or FDMA signals in such a way that the network is being covered. Real noise can invade the system equally or unevenly from all directions, where "equally" can imply isotropic noise. The basic means of radio communication in the system 10 is, so in the present it is called "piled carrier propagation spectrum" (SCSS), wherein discrete multiple tones (DMT) have a substantial frequency diversity that are transmitted simultaneously by station 11 and for each remote unit 12-17 to the other. A baseband data symbol is the propagated spectrum modulated on each set of discrete multitone transmissions from a single 11-17 unit. Accurate data retrieval can be achieved by the intended recipient although some of the individual channels that carry the information in a discrete tone may have faded or interfered with too severely. This invention may be further represented in various forms, for example, by the various combinatorial modalities illustrated in Figures 2A-6B. Each of the main elements introduced in Figures 2A-6B are described in further detail together with Figures 7-16. The antennas in each set may have arbitrary spatial placement, for example, the assembly does not require a special antenna geometry in order to function properly. On the other hand, the antennas can be displaced in p-olarization as well as the space. Figure 2A shows a point-to-point transmitter 30 comprising a stacked carrier propagated spectrum transmitting bank 32 (SCSS) connected to a multi-element antenna array (AA). A point-to-point receiver 36 comprises an array of multiple element antenna (AA) connected to a multiple carrier propagated spectrum receiver bank (SCSS). Each array of antennas comprises a plurality of spatially separate antennas for transmitting and receiving data. The adaptable antenna array process, for example the combination and / or . . A ^ * - adaptive linear transmission on multiple spatially separated antennas, is not combined in the present, or in Figures 2B, 6A or 6B, with propagation and depropagation of the stacked carrier. The assembly adaptation process is incorporated in the propagation and dispropagation operation of the stacked carrier. Figure 2B shows a network transmitter 42 comprising a stacked bearer multiple access transmitter bank 44 (SCMA) connected to a multi-element antenna array 46 (AA). A network receiver bank 48 comprises a set 50 of multiple element antennas (AA) connected to a stacked bearer multiple access receiver (SCMA) bank 52. Figure 3A shows a point-to-point transmitter 54 comprising a stacked bearer propagated spectrum transmitter 56 (SCSS) connected to a time division (TDD) duplexer 58. A point-to-point receiver 60 includes a time division duplexer 62 connected to a stacked carrier propagated spectrum receiver 64 (SCSS). Figure 3B shows a network transmitter 66 including a stacked bearer multiple access transmitter 68 (SCMA) connected to a time division duplexer 70 (TDD). A network receiver 72 comprises a time division duplexer 74 (TDD) connected to a stacked bearer multiple access receiver 76 (SCMA).

Fig. 4A shows a point-to-point transmitter 78 comprising a stacked bearer propagated spectrum transmitter 80 (SCSS) connected to a code nuller 82. A point-to-point receiver 84 includes a code scrambler 86 connected to a stacked bearer propagated spectrum receiver 88 (SCSS). Figure 4B shows a network transmitter 90 comprising a stacked bearer multiple access transmitter 92 (SCMA) connected to a code nuller 94. A network receiver 96 includes an annular code 98 connected to a stacked bearer multiple access receiver 100 (SCMA). Figure 5A shows a point-to-point transmitter 102 that includes a stacked bearer propagated spectrum transmitter 104 (SCSS) connected to a broadly spaced frequency channel 106. A point-to-point receiver 108 comprises a widely separated frequency channel 110 connected to a stacked carrier propagated spectrum receiver 112 (SCSS). Figure 5B shows a network transmitter 114 that includes a stacked bearer multiple access transmitter 116 (SCMA) connected to a broadly spaced frequency changer 118. A network receiver 120 comprises a widely separated frequency channel 122 connected to a stacked bearer multiple access receiver 124 (SCMA). Figure 6A shows a point-to-point transceiver system 126 wherein a stacked bearer propagated spectrum transmitter bank 128 (SCSS) is connected to a synchronized time division (TDD) duplexer bank 130 that is connected to a multi-element antenna array 132 (AA), and a stacked bearer propagated spectrum receiver (SCSS) bank 134 with a back-adapter 136 in control of spectrum transmitter bank 128 10 propagated stacked carrier (SCSS). Figure 6B shows a network system 138 that includes a stacked bearer multiple access transmitter 140 (SCMA) connected to a synchronized time division (TDD) duplexer 142 that is connected to a set 144 of 15 multiple element antenna (AA) and to a bank 146 stacked bearer multiple access receiver (SCMA) with a rearward adapter 148 in bank control 140 stacked bearer multiple access transmitter (SCMA). Figure 7A illustrates a spectrum transmitter 150 20 propagated from stacked carrier (SCSS) similar to those included in Figures 2A, 3A, 4A, 5A, and 6A, the transmitter 150 SCSS includes a digital-to-analog converter 152 (DAC) that converts the incoming digital data into a signal analogous to the transmission. The analogous information25 for the transmission can be entered directly without the -alB * 'Maiífat-ia - 5 ^' 'DAC 152. The two or more channels (for example l, ...., k) are included so that each module modulates the corresponding radiofrequency carriers in an upconversion process . For example, each upconversion channel comprises an infase mixer 154 (I) and a quadrature mixer 156 (Q) connected to a phase shifter 158 of 90 ° and a local oscillator 160 (LO). Therefore the modulation information controls the amplitude of the infase phases and the quadrature of the AM carrier radio frequency. A pair of controlled gain amplifiers 162 and 164 allow independent adjustment of each of the infas and quadrature amplitudes before being recombined by a master beam 166. A filter 168 (BPF) eliminates out-of-band signals that could interfere with the adjacent channels. A final master beam 160 combines the signals from all channels and produces an output transmitter, for example, which is then applied to an antenna. A propagation gain generator 172 periodically outputs a parallel output that controls all gain controlled amplifiers 162 and 164 in each channel as a group. Each signal control to each controlled gain amplifier 162 and 164 may comprise a digital signal line for one bit on / off control, digital multi-bit parallel control for the initial discrete gray scale configuration or an analogous control for the configuration .. *. l .. Jr., j ».». i. -______ »____ _. _. _. .. _ _. ._ -. _ _ _ _ _ _, __, __.__ ,, __ JiSt¿ftí | f¡tfp »< Initial gain continuously variable. An obvious variation in the analog circuit shown in Figures 7A and 7B for the transmitter 150 and the receiver 180 is to use an all-digital transmultiplexer ("transmux") design, for example, with a discrete digital logic processor or with a digital signal processor. A preferred alternative for direct propagation or transmux and despreading thrusts illustrated by way of example in Figures 7A and 7B is the discrete multitone method (DMT) orthogonal frequency division multiplexer (OFDM) described herein. With reference to Figure 7A, in the operation of the transmitter 150, part of the propagation gain output from the propagation gain generator 172 is probably for the output which is more easily received by a intended receiver unit than that which could obtained using a different propagation gain output. The radio communication environment between the transmitter and the receiver will attenuate or interfere in an ordinary way with some phases and frequencies more than others. The radio communication environment contains co-channel interference, additive inter-network, intra-network and jam / coated signals that are more easily circumvented with propagation code that can not be eliminated in the receiver. The propagation gain output therefore has the ability to compensate for the effects of the intervening radio communication environment, both channel distortion and co-channel interference. The optimal propagation gain outputs that can be generated at any time can be set at frequencies molded according to time or place, or adjusted according to the results obtained from some type of measurement related to the quality of communication, for example, data of reverse channel. The propagation code provides compensation for co-channel interference sources, as well as channel distortion. Figure 7B illustrates a stacked bearer propagated spectrum receiver 180 (SCSS) similar to those included in Figures 2A, 3A, 4A, 5A, and 6A, and complementary to the transmitter 150 shown in Figure 7A. The receiver 180 SCSS accepts the analog signals in a separator 181 which drives the various parallel spaced frequency channels. A typical channel comprises a band pass filter 182, a separator 183, an inflow controlled gain amplifier 184, a quadrature phase controlled gain amplifier 185, a pair of phase detectors 186 and 187 driven by a phase shifter 188 and a local oscillator 189 and an analog-to-digital converter (ADC) 190 that again combines all receiving signals into a signal Xá ^ iJSS ^ - ^^ digital. Each downconversion channel comprises an inflow 186 mix (I) and quadrature mixer 187 (Q) connected to the 90 ° phase shifter 188 and local oscillator 189 (LO). A dispropagation weight generator 191 is connected to control the individual infase and quadrature amplifiers 184 and 185 of each channel. A base station 230 is shown in Figure 8. For "code override", the despreading weights are adapted to maximize the signal to interference and noise ratio of the message sequence unprobed in the preferred embodiment; and to introduce directivity and retrodirectivity, noting that the propagation gains are derived from the locally adapted depropagation weights in the preferred embodiment. The base station 230 is similar to the base station 11 (Figure 1) and comprises an array 132 of antennas for radio address communication with remote units by beamforming, a front end 234 of transmission / reception (T / R) a frequency channel bank 236, a data cell cartographer 238, a weight adaptation algorithm generator 240, a multiple antenna multiple link disproader 242, a Doppler and delay estimator 243, an equalizer bank 244 Doppler and delay, and a bank 246 symbol decoder, "for example, a Trellis decoder, which outputs various coated baseband data channels." None, part or all of the antennas in the array of 232 antennas can be of different polarization (eg antenna 233) Various outgoing baseband data channels 5 are connected to a bank 248 symbol decoder, eg, a Trellis decoder. the transmission involves a bank 250 of Doppler preemphasis and delay, a multiplexer multiple link extender 252, a frequency channel cartographer 254 and 10, a transmit / receive compensation bank 255 connected to a transmission / reception compensation algorithm 256, and a reverse frequency channel bank 257 connected to the front end 234 of T / R. A transmit / receive packet trigger 258 receives 15 GPS time transfer information and controls the interleaving interval and duration of the individual transmission and the reception times at the front end 234 T / R. The base station can also have as much as one antenna element as a whole. In a preferred embodiment, the The base station uses a packet time division or OFDM duplex DMT modulator and demodulates to perform the reverse frequency and frequency channeling operations. For more information on the alternative use of 25 encoded modulation of Trellis, see, Boulle, et al., "An Overview of Trellis Coded Modulation Research in COST 231, "IEEE PIMRC * 94, pp. 105-109.A remote unit 260 is shown in Figure 9 in a preferred embodiment.The remote unit 260 is similar to 5 units 12-17 remote (Figure 1) and comprises a set of antennas 262 for radio communication with the base station by combined and spectral spatial diversity, a transmit / receive front end (T / R) 266, a frequency channel bank 266, a cell cartographer 268 of 10 data, a weight adaptation algorithm generator 270, a multiple antenna deprogrammer 272, a Doppler estimator 273 and delay, a Doppler equalizer 274 and delay, a symbol decoder 276, for example, a data decoder, that leaves a data channel of 15 coated baseband. None, part or all of the antennas in antenna array 262 can be of different polarization (eg, antenna 263). The outgoing baseband data channel is connected to a symbol decoder 278, for example, a 20 data decoder. The transmission further involves a Doppler pre-emphasis and delay unit 280, a multi-antenna propane 282, a frequency channel cartographer 284 and antenna, a transmit / receive compensation bank 285 connected to a generator 286 of 25 transmission / reception compensation algorithm, and a reverse frequency channel bank 287 connected to front end 264 T / R. A transmit / receive packet trigger 288 receives GPS tie transfer information and controls the interleaving and duration of the individual transmission and reception times at the front end 274 T / R. The remote unit can have as much as one antenna element as a whole. The number of antennas of each unit may vary from unit to unit. This can allow remote units to have a variable cost, based on the importance or speed of data used by a given unit. Remote units can use different propagation speeds. They can propagate their data on different subsets of the frequency channels used by the base station transceiver. In a preferred mode, the remote unit uses a packet-time or OFDM division duplex DMT modulator and demodulator to perform the reverse frequency channeling and frequency channeling operations. A difference between the base station and the remote unit is that the base station transfers and receives signals from the multiple nodes, for example, multiple access. Each remote unit sends and transfers only the single data stream intended for it. Channel compensation and code cancellation techniques are limited methods for adapting propagation and depropagation weights. Figure 10 illustrates a module 290 for transmitting / receiving multiple antennas. The module 290 includes a set 291 of multiple element antennas with each element connected to a single channel T / R module 292, for example, four in number. Each 292 T / R module is connected to a packet trigger 293, a receiver calibration generator 294, a local oscillator 295 and a system clock 296. These in turn are driven by the GPS clock and Doppler correction signals. Each T / R module 292 comprises a T / R switch 297, an immediate low frequency (IF) converter 298, an analog-to-digital converter 299 (ADC), a digital-to-analog converter (PA) 300 upstream converter 301 of IF and a power amplifier 302 (PA). It is learned to receive the weight information during the reception process and is used in the transmission process to establish the relative transmission powers applied to each antenna element, for example, to compensate channel fading or interference. It should be noted that the transmit / receive module can separately excite the polarizations if the base station is of different polarization. Transmission and reception emission boxes are triggered at particular times, which can be determined at random, according to an independent source of universally accessible exact time, for example from the global positioning system (GPS) maintained by the Department of Transportation. Defense of the United States. The 5 GPS moments are derived from a navigation system that resides on board a communication platform so that the receiving side of each module 292 of the T / R always knows which emission box corresponds to a packet. The GPS moment is also used to derive the 10 local oscillator and the ADC / DAC clocks used in the system. The receiving side is not necessarily synchronized for the remote transmission source. In particular, the range of propagation delay and Dopler change between communicators does not need to be known by the receiver system 15 before receiving a first data packet. However, the range, speed, delay and change of Doppler between communicators can be known to a certain degree of accuracy in certain applications. The range, delay of propagation, and change of Doppler between the communicators do not 20 needs to be known before the receipt of the first data packet. The calibration mode is optional, and is used only on a base as needed. For example, intermittently, at the beginning of a given transmission, or after or when internal diagnostics indicate that such 25 calibration is required.

The operations of coding, propagation, and modulation, for example, as shown in Figure 11, are preferably reflected by the operations of analog modulation, despreading, and decoding, for example, as in Figure 12. The data flow in the Figure 11 is reflected in Figure 12 as a signal flow, for example, the same data flows are in both Figures 11 and 12, with the adders in a Figure replaced by logical circuit numbers in the other Figure. Such symmetry is exemplified by DMT modulators and demodulators and frequency mapping and inverse mapping operations, propagation and depropagation operations, and propagation and depropagation operations of code gates. The structure of the propagator reflects the structure of the depropagator. The CDMA transeptors of the prior art do not have such symmetry. Thus, such symmetry is a critical feature in embodiments of this invention. Figure 11 illustrates a discrete multitone stacked bearer propagated spectrum modulator (SCSS) used for frequency channeling in the present mode. A frame generation command from the navigation and coding system 302 causes a signal modulator 304 to encode ephemeris, position, velocity, acceleration, and other messages in a Kceida symbol data vector. These symbols are then used to Modulate a set of baseband tones or Fast Fourier Transform (FFT) tanks. In a propagator 306, the base band tones Kceida are applied on the propagated separate propagation cells K propagated multiplied by a separate propagation gain for that antenna "1" and complex "H" of frequency cell, for example, complex constant also multiplying each symbol in the cell and passed to a time multiplexer that combines the cells into a large vector of Kact? Va of complex data, where Kact? va = ceida * pr0pagada- This complex data vector is passed to an operator 308 of Inverse FFT of zero tablets that converts the data vector directly to time samples KFFT > (1 + SF) -Kactiva real-IF, where "SF" represents the "configuration factor" or the band-to-band ratio of phase for this system. The first samples of Eron'Krrr in these time samples are then repeated 310 to form a long data sequence of Kpaquete = (+ Eroi?) 'FFT. A multiplier 312 multiplies this large Kpacket data from a Kaiser-Bessel window 314 to generate the final sample signal. The sample signal is then passed to a digital-to-analog converter which results in a long data burst from Tpackage / F packet passed to the upstream frequency converter and to the communication channel where f? is the complex sample rate of the PDC / DNC nodes. The parameters used to reduce the characteristics of the transmitted signal are all coordinated for the GPS time, so that the nodes in the communication network transmit simultaneously. This process is repeated for each antenna in this system. 5 A decoding symbol in the baseband tones is included in the baseline system 300. Each bit of Kceida data modulates a separate tone in the signal baseband, so that a tone is the phase modulated by O or 180 ° if the data bit that modulates that tone is equal to zero or 10 one, respectively. Such a modulation tone is highly efficient in terms of allowing transmission power. It offers a vulnerability for radiometric detection techniques and allows the releasable demodulation of bit streams transmitted in Eb / N0 from as slow as three 15 dB. The BPSK format allows the use of sophisticated and powerful methods to remove time and bearer shifts from the de-propagated signal, when based on the conjugate auto-coherence of the tone phase sequence. Such operations are for an individual antenna, for example, using a different complex propagation gain of g_i for each cell of frequency k and antenna 1 used by the transceiver. Does the passage use the erol factor? of package extension and the length of samples of 25 Kpaquetf; = (l + eron) KFFT before the conversion operation of digital to analog (Tpacket = (l + eroi?) TFFT duration time after the DAC operation). The earnings of g ?? of propagation can be determined by a number of means, for example by means of the codebook, randomly, pseudo-randomly, or adaptively, based on the weights of k propagation. The number of information bits per data symbol is Kb? T • The BPSK is a simple coding strategy where coding is ignored and Kb? T = l • Platform ephemeris, position, acceleration information speed, are examples of data that could be transmitted in some applications. The BPSK is a preferred modulation for applications where data speed is not the main issue of the system. The Doppler pre-emphasis and delay operation is optionally included in alternative modes. Such that can be included after the initial packet to remove the effects of DMT switching and delay in the intended receivers of the signal that is transmitted from the DMT modulator. This operation can simplify the design of the transceivers in the network, for example, allowing Doppler and delay removal operations to concentrate on the base stations in the network. As a generalization of the propagation concept for multiplying the access transceivers, a separate set of propagation gains (gki (m)) can be used to propagate the data symbols intended by a user m in the multi-user transceiver. Figure 12 shows an adaptive beam and de-propagating receiver 320, specifically all digital. For an antecedent of this technology see, Tsoulos, et al., "Application of Adaptive Antenna Technology to Third Generation Mixed Cell Radio Architectures," March 1994, IEEE # 1-7803-1927, p. 615-619. A frame receiving command from a receiver navigation and coding system 322 causes a signal demodulator 324 to collect and convert from analog to digital a series of large transmission frames from a gateway from a set of antenna array 326, where T gateway is the length of time extended by Kcompuerta samples • This includes a large Tguard guard emission box to explain the unknown propagation of delay between the transmission and reception links (TCompuerta = Tpaquete + Tguard? A) / where Tpacket is the time extension of the package and Tguard? a is the time interval extended by the Kquard samples. A large digitized Kcompuerta data table is an output of each ADC and then is passed to FFC 328 scattered from zero tablets seen in the window that converts the packets into the frequency domain with each tone separated by a whole number of FFT repositories . ^ t ^ e ^ ^ ^ The FFT deposits are passed to a demultiplexer 330 that removes any unused FFT repository from the received data set, and groups the remaining deposits in the KceidaX data matrices (Kpr0pagada 'coroa ) that contain the received tones on each transmitted propagation cell, where Kpropagac? a is the propagated frequency factor, Kceida is the number of symbols per pre-propagated data cell, and Kcon;] is the number of antennas. Each propagated data cell is passed through a bank of linear combiners 332 that remove the co-channel interference that covers each cell and de-propagate the original baseband simboLo tones from the received data set. The combining weights are adapted using a method for restoring code gate self-consistency that simultaneously deproduces the received data signal and makes the reception of frequency-dependent multi-stars and the spatial filtering of the propagated signal of interest. Combinator weights are used to construct a set of transmission weights that are used in any subsequent return transmission. Such tones are then passed to a Doppler compensation unit 334 and delay that estimates and removes Doppler switching (non-integer FFT deposit switching) and message propagation delay (phase process) from the received data set. A symbol demodulator 336 estimates the transmitted message symbols. Due, the received data packet transmitted from each user is depropagated and extracted from the received interference environment. The processor does not require 5 good time / carrier synchrony to the transmitter until after the baseband signal has been depropagated with a high signal to interference and noise ratio, even in the presence of strong noise and co-channel interference. 10 Kce? Da symbols transmitted from user m are extracted from the channel in the receiver by weighing each of the Kceida tones received in frequency cell k and antenna 1 by the same weights of wk? complex propagation (m), and then adding the cells together in a tone-by-tone base, so that the tone q in each received frequency cell is assumed over all the Kpropagated frequency cells' Kcon:) together and the antennas used by the system. Each multiple element transceiver 20 preferably has the minimum number of combined and spectral spatial degrees of K with "Kpr0paid to successfully override any source of non-stacked bearer interference that pervades each cell frequency." Any excess of remaining degrees of freedom is used to improve the SINR of the de-propagated baseband signal or to separate the overlapping stacked carrier signals. The multi-element depropagator weights are then adjusted to decrease the power of the de-propagated baseband signals. This leads to code cancellation solutions that can be considerably more powerful than conventional methods of depropagation. The ideal depropagator adjusts the disproportionate weights to cancel the interference sources of stacked carrier to less than a weight of noise on each frequency cell, and 10 simultaneously increases the SINR of the de-propagated signals. The multi-element depropagator also preferably directs the weakest cancellations significantly against sources of interference with the weakest radio signals in a frequency cell 15 given. Soft cancellations can therefore be directed to sources of interference received with the weakest power in a given frequency cell. For example, a weak override can be directed at the far edge of an interference source bandpass, if the source spectrum of 20 interference has a weak value particularly in those frequencies. In general, the weights of the depropagator include adaptive antenna assemblies that significantly improve the quality and capacity of the signal transmission and the 25 reception operation. For the receiving side of a system, St "- * - *" * ^^ - ^ "8 Blind or uncalibrated methods can be used to direct almost optimal beams in signals of interest, and to simultaneously drive cancellations in clogging signals. adjust 5 to decrease the interference signal and the noise ratio (SINR) of the de-propagated baseband signals, for example estimated data symbols.This typically results in a set of code cancellation dispropagation weights that are significantly different from 10 the propagation gains used to propagate the baseband signals at the other ends of the link. In particular, such resulting propagation weights will simultaneously remove the channel distortion, such as selective gain and fades caused by the path 15 multiple. Depropagation provides an optimal tradeoff between the cancellation interferences received by the transceiver, maximizing the signal to interference ratio, and decreasing the signal-to-noise ratio (SNR) of the depropagator. The codes of depropagation in the 20 conventional DSSS and CDMA communication systems are set equal to the propagation codes and the other ends of the link and only maximize the SNR of the de-propagated baseband signals. Such an operation is carried out blindly in the 25 preferred embodiments of the invention, the gains of iMfliMif < Ml ^ -r ~ ** ^^ j ^ jg spread transmitted and channel distortions are not known in the depropagator. This simplifies the protocols used within the network allowing the use of unknown propagation gains in the transceivers in the network. This also allows the use of adaptively determined propagation gains that are continually optimized to mitigate the noise, interference, and channel solution found by the transceiver over the course of a transmission. Such an approach provides an update for multiple element SCMA or SCSS transceivers using antenna arrays, but does not require any qualitative change in the propagation, despreading, or gain weighting algorithms. One difference lies in the multi-element transceiver in the dimension of multi-element propagation and despreading operations. However, the multi-element transceiver has great capacity due to the large degrees of freedom that can be used to separate SCSS signals. The range and / or immunity to intercept the radiometric detection means is increased due to its ability to direct the space beams in other communicators in the network. The immunity to clog non-SCSS signals is also improved due to the ability to spatially cancel such signals, even from broad frequency ranges.

LJ "M" -'- "'- - Rapid convergence methods that work on individual data packets can also be combined with channelized signals of frequency of interest or processor structures to allow selective frequency cancellation of source signals of interference without the need for the calibration of data sets or the need to know or estimate the direction of arrival of the signal of interest or signals of interference source.The system 10 (Figure 1) can therefore decree and demodulate the data packets in highly dynamic environments where channel geometry is significantly changed between packets, so that a processor can operate in typical overloaded environments where the number of interferences is not less than the number of antennas in the array of antennas For the receiver, on the transmit side of a system, direct or retrodirective adaptation methods can already be used either to direct the return signals of interest back to the source of transmission with maximum power and / or with minimum transmission radio signals (steering mode) or to jointly direct the return signals of interest back to the source of transmission with minimum radiation in the direction of the interference sources (retrodirective mode). The steering mode is used in applications where compatibility with non-SCSS interference is not a major issue for the communicator, or where interference transmission and receiving platforms are not likely to be placed in the same location. This mode is also useful in applications where the communication platform is subjected to heavy non-SCSS interference, so that the maximum power must be supplied to the other end of the communication link. The processors can be used to accurately measure the received signal of interest that is directed to the vector and direct a maximum back to the other end of the communication beam without knowledge of the received signal of interest of arrival address, even if the sources of interference cover completely the baseband interest signal and the packet interval. The system 10 (Figure 1) preferably supplies a more powerful K-factor to the other end of the communication link, providing the system with additional immunity to any clogging. This can be achieved even if the other end of the communication link is transmitted and received on an individual antenna. Conversely, system 10 (Figure 1) can maintain the communication link using a K-factor with less power point. This reduces the geographical area within which the system can be detected by adversaries by KCOn factor: .... i. The retrodirective mode, modified in Figures 6A and 6B as retroadapters 136 and 148, is useful in applications where interceptors are placed in the same location with the sources of interference, for example, with 5 in order to have access to the effectiveness of the jam strategy. This strategy is most useful in overloaded environments where broad band overruns can be directed to sources of interference. Figure 13 illustrates a multi-tone modulation 10 digital single frame (DMT) and propagation format 340. Format 340 is used for an example environment with Kce? Da = 6 and Kpropagada = 4, and with each propagation cell separated by two FFT deposits, so that space = 2. The six bits of data that are transmitted first 15 are transformed to a set of data symbols of ± 1. The symbols energize six baseband FFT tanks that replicate over four cells of FFT tanks, for example, propagation cells, with a weight of g \ < Separate complex in each cell. The complex weights are the profits 20 of propagation, and they are random or pseudo-random sets on each data packet. The propagation is done in the frequency domain by multiplying the time-domain representation of the baseband signal by a set of sinusoidal carrier waves 25 complex superimposed, or stacked. In practice, ^^^ j t *? * * m? ^^^^^^^^ k? - ^^ * m ^ * ^ - ^ -. ^^? ^^^ i k m * ^^ - í * t ^^ m * k ^ propegation is done simply by energizing the deposits of a large TFT, at considerable savings in computational complexity for moderate output FFT sizes. A Kaiser-Bessel window with ß = 9 is used in this invention to "fill" the space between the tones without subjecting these tones to unacceptable interference from adjacent tones, for example intertone interference. In particular, the high value of ß provides acceptable interference between the adjacent tones and the extremely low interference between the farthest tones. Calibrated or non-blinded techniques use a knowledge of the baseband data sequence or channel distortion and propagation link to develop ideal weights based on optimal signal estimation methods; for example, less square techniques. The uncalibrated or blind techniques use more general properties of the baseband data signals to adapt the weights of despropagation. Mixtures of these techniques that use known and unknown components of the baseband signal and / or the transmission channel can also be used to build an effective solution. Examples of blind techniques that are used in particular include constant modules, multiple modules, and decision-direction techniques. Such use properties of the message symbol constellation to adapt the weights of despropagation.

A number of methods can be used to adapt multiple element depropagate weights in the demodulator 332 (Figure 12). First, there are dominant mode prediction (DMP) methods that take advantage of known packet arrival times or known propagation parameters of the discrete multitone stacked carrier signal. Second, there are methods of restoring code gate self-consistency (SCORE), which take advantage of the self-coherence correlation, or non-zero known among the spectrally separated signal components, in the stacked discrete multitone carrier signal. Of these two basic types, the auto-coherence restoration technique has the greatest utility for individual packet acquisition and the detection of discrete multi-tone stacked carrier signals. The conventional spectrum and other types of self-coherence restoration take advantage of adequate spectral and / or conjugate self-coherence known. This is a zero-zero correlation between the conjugated and / or switched-frequency components of a given communication signal. Blind methods do not require any prior knowledge of the content of the signals of interest or directions of arrival. In this way no specific receiver calibration information is needed to point the set of antennas for the receiver. Instead of it, the blind method uses its own local knowledge of the specific response switches that the signals of interest are over-correlated. See B. Agee, S. Schell, W. Gardrer, "Self-Coherence Restoral: A New Approach to Blind Adaptation of Antenna Arrays," in Proceedings of the Twenty-First Asilomar Conference on Signs, Systems and Computers, 1987. And see , B. Agee, S. Schell, W. Gardner, "Self-Coherence Restoral: A New Approach to Blind Adaptative Signal Extraction Using Antenna Arrays", IEEE Proceedings, Vol. 78, No. A, pp. 753-767, April 1990. See also, B. Agee, "The Property Restoral Approach to Blind Adaptative Signal Extraction," Ph. D. Dissertation, University of California, Davis, CA, 1989. In a double-sideband modulated amplitude signal, the real-IF presentation of any signal has conjugate symmetry over its carrier frequency, because the modulation format of modulated amplitude of double sideband and DC, due to the presentation of real-IF. These symmetries move between them, causing the negative and positive frequency components of the signal to be equal to each other. This perfect spectral self-coherence is observed by computing the correlation coefficient between the double-sideband modulated amplitude signal of interest and a replica of itself which is a frequency switched twice by the carrier. The frequency switching operator mixes the negative frequency components to the frequency band occupied by the positive frequency components, causing the correlation coefficient to have a value without zero. Such a value without zero occurs only when this frequency switching value is applied to the replica. The correlation coefficient is less than one unit in this example. A unit correlation coefficient is obtained by filtering the odd non-overlapping signal of radio signals of interest in the double-sided modulated amplitude signals of the switched and original frequency. In Figure 14, a transverse auto-coherence restoration processor 350 (SCORE) is used to make a restoration that is applied to a data signal received from multiple reference antennas x (t). The processor 350 first passes the received data through a series of optional filtering, frequency switching, and conjugating operators, which result in a signal u (t) that correlates only to the target signals by the processor. The processed and original signals x (t) = u (t) are then passed through a pair of beam and nuller guides 352 and 354 (linear element combiners) that are acted together to maximize the correlation coefficient between the two signals y (t) = w "x (t) and r (t) = c" u (t) of combinatorial output. The control parameters used to direct the processor are the filter operator, typically set to a delay operator, frequency switching value a, and flag (*). The parameters of the processor are established for values that yield the strong correlation coefficients in the absence of interference, for example, in the signal transmitted of interest to the processor. Figures 15 and 16 show the operation of code gateways used in the SCORE operation of general code gates. Certain configurations of 0 code gate require some significant modification for the propagator and depropagator data flow, and therefore the structure. These illustrate a method for enabling the code gate SCORE depropagation adaptation algorithm described in the present invention. There are other methods for applying the cross-sectional packets of code gates or internally with frequency cells, instead of transverse frequency cells. For example, by repeating the data symbols with a gate code applied through the Kceida baseband symbols 0 on the even packs, and consequently without affecting the data flow through the propagator and unpacker. 5 What is it? • Divide the propagation cells in your Kparte folder. 2, cells / subset KSCORE - Kparte - Kpr? Paid / cells processed in subsets in dividuals, KSCORE = 1 cells / subassemblies Kpcirte = 2, separate cells, in even and odd subsets, KSCORE = Kpropagada / 2 cells / subassemblies _ Kparte • KSCORE = Kpropagada in each case • Same use of code key for each cell in subset: -C (n; Kparte / + k) = c (n; k), K = 0, i Kpa te-1; / = 0, KSCORE- i - Alternate form: c (n; k) = c (n; (k) Kparte), k = 0, Kpropagada 1 / part modulo-K part of k Transmission over multiple SCSS subchannels (multiple access of stacked bearer), using different code keys with the same structure in each subchannel - Allows the separation of Kcon subchannels:] Note SCORE SCSS per eubset (code override performed) Allows higher data rates per user (multiple subchannels per user) Allows multiple access communications (multiple users communicating with the cell) Allows rejection of interferences -i KSCORE SCSS (cellular communications) Requires high bandwidth product to achieve the same level of mismatch • In practice, Kparte adjusted to the specific application of part = Kpropagada in asynchronous point-to-point links, cellular superposition systems where fast convergence time, high interference time is important of no SCSS K, part 2 in point-to-multipoint links, SCMA systems where high SCSS interference The restoration of self-coherence of code gates takes advantage of the information of self-consistency that has been deliberately added by the communication system to facilitate the adaptive propagator, although it can not be discerned without having access to the gate information in the communication network. Two methods of SCORE of code gates are included in this invention. A preferred auto-echo restoration method for multiple access communications includes 10 apply single code gate operations to the baseband message signals prior to the propagation operation, which is determined only for each link in the system. For example, where the frequency cells disintegrate into two subsets of cells, even and odd, 15 with the code key applied on only the odd cells, as represented in Figures 15 and 16. The data symbols are propagated over the even cells using the method shown in Figure 11 and the related text. 20 A similar propagation operation can be applied on the odd cells. However, the data symbols transmitted on these cells are first subjected to a code gate operation where they are multiplied by a code key 'of constant modules c (m) = [c (m)] 25 that is different for each user in the network. This operation MMMWUüi ^ i. it is invested in the multiple access unpacker. The odd frequency cells are multiplied by the conjugate of the code keys c * (m) after the despreading operation, but before combining the outputs of the debonders used in the odd and even frequency cells. In the user use transceiver (SCSS) the operation of the code gates is also performed by the individual code key used by the SCSS transceiver. During the individual packet acquisition operations, the code key is depropagated (conjugate) is applied for each received frequency cell odd and indicated to each of the antennas of the transceiver, that is, before the linear combination operation. The operation effect of code gates is to cause the signal transmitted with that of the code key to have a unit correlation coefficient between odd and even frequency cells after the odd frequency cells are multiplied by the key of dispropagated code. Conversely, the same code gate operation will cause all transmitted signals to use different code keys to have low correlation coefficients between odd and even frequency cells. This condition will nevertheless maintain the Doppler switching and the delay (assumed unknown) infringed on the received signals. The signal ... - ^ - ^^ ñ resultant can then be introduced ctly to the transverse SCORE algorithm shown in Figure 14, where x (t) is replaced by the even frequency cells (without gate) and u (t) is replaced by the odd frequency cells (with gate), and where t refers to the symbol Index q = 1, ..., Kceida instead of a time index. The depropagation weights are adapted to decrease the correlation coefficient between the outputs of the disprogated linear combiners applied to the odd and even frequency cells. Such a method provides an ambiguous detection and depropagation of any link in the network, based only on the code key known by that link. In single-user SCSS transceivers, the transceiver only disproves the link that is being communicated, without the need for additional operations to acquire a link and verify that the correct signal is being carried. The link is automatically acquired again if it is temporarily lost due to adverse channel conditions, for example, a "port station" that occurs over large transmissions. In multi-user SCMA transceivers, the method allows ambiguous detection, de-propagation, and identification of each link supported by the transceiver without port exchange or mixing as channel conditions vary, based only on known code keys used by the nodes linked to the transceiver. The code keys provide some privacy for mixing included in the operation of code gateways. The SCORE method of basic code gateways can also be generalized in many ways. In particular, code keys can be applied to even and odd frequencies, in order to provide increased security and correlation between the frequency cells, The code gates can also be applied over time instead of frequency, transmitting the data symbols in consecutive packets with codec gates omitted during paired and reviewed packets on all frequency cells during the extraneous packets. 15 If the propagation codes are kept constant over the packet pairs, this approach allows the use of the most powerful auto-SCORE method to adapt to the weights of despropagation.

• Most powerful algorithm allowed in some environments - Resposal of approximate channel as identical or almost identical (differs by the complex scale) or in each propagation subset - Ant eateries of approximate interference as identical in each subset of propagation «É¡ • Leads to the maximum probable estimator Identical or almost identical forced propagation gains in each propagation subset - Exact or almost identical forced dispropagation weights in each propagation subset - Depropagation weights are set to dominant modes of auto-own equation -SCORE • Has advantages over the SCORE-transversal equation itself - Lower complexity - Lower mismatch in the same bandwidth product per time. Force the maximum SINR equal in each subset in the network applications - No asymmetric mismatch • Some disadvantages - Sensitive to the modeling error if the channel response is truly unequal in each subset. - Requires search / removal of time during and / or Doppler during the depropagation operation (typically quite simple algorithm) The largest frequency numbers or packet subsets can also be used in the -aMataifa system, with a separate set of code keys used on each subset, in this case, the depropagator uses a generalization of the transverse SCORE method that derives from a super-vector interpretation of the transverse SCORE equation. See, B. Agree, "The Property-Restoral Approach to Blind Adaptive Signal Extraction." in Proc. 1989 CSI-ARO Workshop on Accelerated Topics in Communications May 1989, Ruidoso, NM; and, B. Agree, "The Property Restoral Approach to Blind Adaptive Signal Extraction." Ph. D. Dissertation, University of California, David, CA, June 1989. As the number of frequency subsets increases, the number of multiple access communications that can be supported by transceiver drops, while improving the stability of computing of weight, and noise reduction and non-stacking bearer void capability that the algorithm remains unchanged. At the limit as the number of subsets of frequency equals the propagation factor ae Kp 0paid • The method of restoring code gate self-consistency extracts the baseband interest signal directly from the channeled data super-vector, using the dominant mode of an own equation of multicell autocoherence restoration. The method simultaneously makes spatial filtering dependent on the i * frequency, combines the antenna elements within each cell in the propagated signal of interest, and deproduces the resulting data signal to combine the frequency cells. The method of restoring autocoherence of 5 code gateways can operate effectively in SINRs by positive or negative reception, since the maximum obtainable depropagated and SINR formed of beam of the data packet received is positive. The method adapts the set of antennas as an intrinsic component of the despropagation operator 10 and linear combination. The same method is used for arbitrary antenna numbers, including individual antenna systems where Kcon;) unto = one. The method of restoring code gate self-consistency does not require prior knowledge of the propagation gains or 15 underlying message sequence at some point in its implementation. The method does not require a search on time or switched Doppler frequency to deproduct a message sequence. The dominant eigenvalue of the equation proper to 20 autocoherence restoration of code gates provides detection of new signal packets when the communication link first opens. The receiver works on an "on demand" basis, which returns the pulsations back to the other end when a packet is 25 transmits to the communication channel. fg ^ H ^^. r * rt £ H &t * rí k Additional methods increase or confirm the detection of a multitone stacked bearer data packet after the restoration of code gate self-consistency. In particular, the reliability of the detection can be greatly increased by using the smaller eigenvalues of the self-coherence restoration equation of code gates to predict the mean and the standard deviation of the self-coherence restoration value of maximum code gates. The actual maximum eigenvalue is then de-incremented by the predicted medium and scaled by the predicted standard deviation, resulting in a corrected detection statistic of much stronger direction. Other methods use downstream despreading and modulation operators to confirm the detection of packets during the restoration of code gate self-consistency. The initial Doppler recovery during the acquisition of the first data packet uses a frequency domain analog of a fractional separate compensator to extract the first data packet in full FFT reception site mode, and sub-sampling the signal from Resulting output under the frequency mode of transmission at the site using a 'linear intercolation method. The linear combination weights re-sample the data to the pitch centers that use part of the appropriate matching method. A suitable least squares restoration algorithm, such as a constant module method, decreases variations in the modules in the 5 disproved data symbols. The method of constant least squares modules takes advantage of what is appropriate for the transmitted data tones to have a constant modulus if they are generated using a BPSK modulation format, even if this is destroyed if the signal 10 transmitted is subjected to a Doppler switch that is not a multiple integer of the pitch space. The least squares constant modulus method restores this suitable for the output signal of the depropagator. All technique operate in the presence of Doppler switches 15 signifiers and trajectory delays. See B. Agree, "The Leas t-Squares CMA: A New Approach to Rapid Correction of Constant Modulus Signis", in Proc. 1986, International Conference on Acoustics, Speech and Signal Processing, Vol. 2, pg. 19.2.1, April 1986, Tokyo, Japan. Two general methods are useful in the generation of antenna array weights for data transmission. The retrodirective transmission establishes the transmission steps proportional to the conjugate reception weights, and the directive mode establishes the weights of 25 transmission proportional to the direction vectors of - ffliíiliiaf "'"' - ** '- "- conjugate packets The retrodirective mode is well suited for commercial telecommunications and military intraflight communication applications where the interference signals can be the other members in a communication network of Multipoint: The management mode is most useful in applications where the conversion ratio is the main issue for the communicator and the jamming and interception platforms are probably not to be placed in the same location.This mode is useful in applications where the communication platform it is subjected to heavy interference, so that the maximum power must be supplied to the other end of the communication link in order to communicate in the presence of the radio interference emissions, however, this method does not possess the attractive property to direct the energy away from other interferences in cooperative communication networks. a multiplier adaptation strategy that can greatly simplify the depropagation complexity if the large spectral propagation factors are used by the air link. The retrodirective transmission mode is illustrated herein. The retrodirective mode sets the weights of the set of transmitter antennas equal to the conjugate set weights calculated during signal reception. If the transmission and reception operators are made on the same frequency band and any internal differences between the transmission and reception paths are equalized, then the set of transmitter antennas will have the same gain pattern as the set of antennas for the transmission. receiver. The set of transmitter antennas will estimate the direction of bypasses in the direction of any interference that was present during the reception of the signal. The depths of cancellation for use for each one are determined by the relative resistance of the received interferences. During the same, g < is a dimensional vector of Kset x 1 and represents the propagation vectors of 15 multiple elements used in the transmission on the frequency cell "k". The multiple element despreading vectors used in the receiver on the frequency cell "k" is represented by Wk which is also a dimensional vector of K with 3 x 1 point. 20 Modes of the present invention are preferably configured to provide the transmission weights frequency selective propagating the transmission packet using a different set of propagation weights (gk) of Kcon- | Unto x 1 on each propagation cell. This establishes 25 that the retrodirective transmission weights of selection of itT rtátififcMfrííii ^ ^^ £ g5ílfc¿_ frequency, establishing the gain g¡ ,. Proportional propagation (multiple elements) for the wk weights of linear combinators of Kwith3point x 1 employees on each frequency cell during signal reception so that gv. =? w. This mode is especially effective in elements dominated by sources of broadband interference, since the resulting cancellation depths will be limited by the dispersion of antenna arrays made on each frequency cell. In this case, the processor will cancel the source of interference over the frequency as well as the space. The set of transmitter antennas only cancels each source of interference on the frequency cells occupied by the interference source. This is good for receiving a signal packet of interest, although it is ineffective for transmitting a packet if the goal is to direct the packet radio signals away from the source locations of interference over the full packet pass band. . Such a goal can not be met by any means if the number of partial band interference sources equals or exceeds the number of elements in the antenna array. The directive transmission mode sets the weights of the set of transmitter antennas equal to the packet address vector of Kwith3point x 1 (conjugate). If the transmission and reception operators are based on the same frequency band, with the appropriate compensation of any difference between the transmission and reception paths that pass the transmission / reception change, then the resulting array of antennas will direct the maximum radio power to the other end of the communication link and close the link with the power of minimum transmission radius. The managerial group typically ignores the locations of the sources of interference, for example, implicitly assumes that the interceptors are anywhere in the communication link emission field. The steering method can be implemented on a frequency selection basis of the present invention. This may provide some benefit in exceptionally broadband communication links, for example, due to large Kpropagada values or highly dispersed communication channels where the packet address vector changes significantly over the packet pass band. However, this is not important since the maximum power mode is not strongly degraded by minor errors in the packet address vector. Such an estimation error can be large if the communication link is jammed in heavy form, or if the packet address vector can be estimated over short communication intervals, for example individual packets, in particular, a very simple method can - »* * • * * -» cause the transmitter array of the direct transmitter to point to stronger beams of transmitting power in the transfer sources in the environment. A directive transmission method or 5-pack direction vector estimator needs to be simple enough to be implemented cheaply, yet sophisticated enough to operate reliably under expected ranges of jam and transmission scenarios. Three methods of address vector estimation General are preferred. First, the correlation methods which estimate the packet address vector use the correlation between the estimated packet data received. Second, the ML-like multi-cell type methods, which estimate the packet address vector that it uses 15 the maximum type estimator (ML) under appropriate simplification conditions and in the presence of channelized frequency data (multicell). And third, parametric meters that further refine the multicell estimators by restricting the package address vector that it uses 20 appropriate parametric models. The correlative method is the simplest of the three methods for estimating the packet address vector. A weakness of this method is seen considering the estimate obtained in the presence of a source of interference 25 individual, the estimate reduces to the direction vector of .Mm ~? ßi ***? *. .. ___. > _.a &. ,,. a. package plus the interference source address vector in scale by the transverse correlation between the source of received interference and the packet signals. The product of time bandwidth (samples) required to reduce this cross-correlation to zero is much larger than l '/ S of the interference source signal, for example, 1,000,000 samples if the interference source is fifty dB stronger than the pack signal. As a consequence, this method is usually inadequate. The other two methods can solve this limitation by using optimal maximum likelihood estimation (ML) procedures to estimate the packet address vector. The resulting estimators can provide accurate direction vector estimators in the presence of wide-band or partial-band interference sources, using simple (nonparametric) or sophisticated (parametric) direction vector models. On the other hand, the yields of these estimators can be predicted using Cramer-Rao link analysis. A useful performance link is derived for any estimated nonparametric address vector obtained in a multicell environment. The received data is divided into separate frequency cells Kpropagada each containing a base band of known (or estimated) packet in scale by an unknown complex address vector and t «i« j. corrupted by additive complex Gaussian interference. The direction vector in the cell Pe is modeled where "a" is the packet address vector (independent frequency) and gk is the scale received in the gain of 5 packet propagation of individual antennas that is obtained over the cell of propagation of kth. Complex Gaussian interference is assumed to be independent from cell to cell, and temporarily white with zero means and the unknown autocorrelation matrix. { i i} in cell kth. 10 The packet address vector a is assumed to be an arbitrary complex of the dimension vector of Kcon- | Unto of dimension KCOn3 for example, a is not constrained to adhere to any parameterized model set (for example, a complex set parameterized with respect 15 to azimuth and elevation). The developed direction vector estimates that use this model are, for example, non-parametric techniques. See, H. Van Trees. Detection, Estimation, and Modulation Theory, Part I, New York: Wiley, 1968. By using the Cramer-Rao link theory, 20 any estimator without a base of a will have an exact estimate (mean square error) linked by the given Cramer-Rao link. The matrix R is interpreted as a generalized "percentage" of the interference autocorrelation matrices. { i i} equal to the inverse of the inverse autocorrelation matrices 25 in percentage. • fr - **** »* - * - ^ - In the preferred embodiment, the spatial direction vector a and the spectral propagation gains (gk) are often computed using the formula H wy a Sk a HR «A where HkHk is the data autocorrelation matrix measured on an adaptation block in the spectral cell k, and wk is the spatial component of the dispropagation weights used in the spectral cell k. The vector of direction and the propagation gains can also be used to compute the improved depropagation weights w, which can then be used in a multiple depropagation procedure that performs spatial processing (linear combination in each frequency cell) followed by spectral processing , linear combination on the frequency cells. The stacked carrier propagated spectrum radio communication devices shown in FIGS. 1-14 in combination with the code cancellation techniques representative of the alternative embodiments of the invention. The code cancellation interference cancellation techniques can be effectively combined with stacked carrier propagated spectrum techniques. For more 10 of a code override design, see, Brian Agee "Solving the Near-Far Problem: Exploitation of Spatial and Spectral Diversity in Wireless Personal Communication Networs," Wireless Personal Communications, edited by Theodore S. Rappaport, et al., Kluwer Academic Publishers, 15 1994, Ch. 7. And see, Sourour et al., "Two Stage Co-channel Interference Cancellation in Orthogonal Multicarrier CDMA in a Frequency Selective Fading Channel", IEEE PIMRC '94, p. 189-193. See also, Kondo, et al., "Multicarrier CDMA System with Cochannel Interference Cancellation", March 1994, 20 IEEE, # 0-7803-1927, pp. 1640-1644. The basic stacked carrier propagated spectrum radio communication devices shown in Figures 1-14 can be combined in multiple access modes of the present invention that separate the channels 25 simultaneous independents by space, frequency and / or code or, for example, space division multiple access (SDMA), frequency division multiple access (FDMA), and code division multiple access (CDMA). In SDMA modalities, the antenna assemblies are used so that they can be selectively addressed in space, for example, to establish a minimum of two zones. Each transmitter and receiver pair in the zone tunes its corresponding array of antennas to encompass only the other in its receiver-transmitter pair and to extrude other pairs in 10 other zones that represent the other multiple access channels. Modalities of the present invention distinguish themselves by the combination of SDMA techniques with propagated spectrum techniques of stacked carrier. For more on the design of SDMA, see, Forssen, et al., "Adaptive Antenna 15 Arrays for GSM900 / DSC1800", March 1994, IEEE # 0-7803-1927, pp. 605-609 and see Talwar, et al.," Reception of Multiple Co-Channel Digital Signal using Antenna Arrays with Applications to PCS " , 1994, IEEE # 0-7803-1825, pp. 790-794 See also, Weis, et al., "A novelAlgorithm For Flexible 20 Beam Forming for Adaptive Space Multiple Access Systems Division, "IEEE PIMRC '94, pp. 729a-729e. The combination of CDMA with antenna arrays is addressed by, Naguib et al., In" Performance of CDMA Cellular Networks with Base-Station Antenna Arrays: The Downlink ", 1994 IEEE, # 0-7803-1825, pp. 25 795-799, and see Xu, et al.," Experimental Studies of Space- ^^ gjj ^ ¡^ ¡^ ¿^ ^ ^ ^ Division-Multiple-Access Schemes for Spectral Efficient Wireless Communications ", 1994 IEEE, # 0-7803-1825, pp. 800, -804. See also, M. Tangemann, "Influence of the User Mobil and on the Spatial Multiplex Gain of an Adaptive SDMA Systen", IEEE PIMRC 94, p. 745-749. In FDMA modalities the subsets of the multiple carriers are used for each channel, for example, a minimum of two subsets each having a minimum of two different frequency carriers to establish a minimum of two channels. Each transmitter and receiver pair in one zone tunes its corresponding carrier subset to exclude other bearer subsets representing the other multiple access channels. Modalities of the present invention are likewise distinguished by combining FDMA techniques with spread spectrum techniques of stacked carrier. In CDMA modalities, several propagation and depropagation weights are used, one set for each channel. Such multiple access is used by the navigation receivers in the global positioning system (GPS). Modalities of the present invention distinguish themselves over the prior art by combining the CDMA techniques with the stacked carrier propagated spectro techniques illustrated in Figures 1-14. For more on the design of CDMA in a multi-carrier environment, see, Fettweis, et al., "On Multi- Carrier Code Multiple Access Division (MC-CDMA) Modem Design", 1994 IEEE # 0-7803-1927, pp . 1670-1674. And see, DaSilva, et al., "Multicarrier Orthogonal CDMA Signáis for Quasi -Synchronous Communication Systems," IEEE Journal on Selected Areas in Communication, Vol. 12, No. 5, June 1994. And also, Reiners, et al., "Multicarrier Transmission Technique in Cellular Mobile Communications Systems", March 1994, IEEE # 0-7803-1927, pp. 1645-1649. Also see, Yee, et al., "Multicarrier CDMA in Indoor Wireless Radio Networks," IEEE Trans. Comm., Vol. E77-B, No. 7, July 1994, pp. 900-904. Using CDMA in the presence of fading channels is addressed by Stefan Kaiser, "On the Performance of Different Detection Techniques for OFDM-CDMA in Fading Channels", Institute for Communication Technology, German Aerospace Research Establishment (DLR), Oberpfaffenhofen, Germany, 1994 And see, Chandler, et al., "" An ATM-CDMA Air Interface for Mobile Personal Communications, "IEEE PIMRC '94, pp. 110-113, and also the writing on this technology is, Chouly, et al., in "Orthogonal multicarrier techniques applied to direct sequence spread spectrum CDMA systems", 1993 IEEE, # 0-7803- 0917, pp. 1723-1728.A combination of multiple carrier CDMA and correlation interference cancellation is described by, Bar- ess et al., in "Synchronous Multi-User Multi-Carrier CDMA Communication System With Decorrelating Interference ^ H ^ ^^^^^^^^^ Canceller ", IEEE PIMRC '94, pp. 184-188.A multiple access method for each radio communication of spread spectrum of stacked carrier comprises constructing in a propagation gain of transmitter stacked bearer from the complex amplitude and phase gain of a sinusoid complex for each of a plurality of discrete frequency channels, then propagate arbitrary narrowband baseband data with a vector multiplier and transmit to the transmitter; An inverse frequency channelizer The next step is to transmit the data simultaneously after propagating over the plurality of discrete frequency channels with the stacked carrier propagation gain, the receiver de-propagates the plurality of discrete frequency channels with a linear combiner of inner product vector and frequency channels, in this way, the data of pre-propagated narrowband baseband arbitra is coated with immunity relative to channel interference. The frequency channels may be non-contiguous and distributed within the multiple bands. Alternatively, the transmission is so that the frequency channels overlap and include the autonomous frequency division multiplexer type modeling formats. And alternatively, the transmission of the data is in packets, wherein the baseband data is propagated, transmitted and dispropagated into discrete packets in a frequency channeling structure based on orthogonal frequency division multiplexer type. Packages can overlap, contiguous or non-contiguous in time. The preferred embodiment sequentially transmits one or more packets after sequentially receiving one or more packets from the other end of the link. Sequential transmission and reception of multiple packets can allow communications, for example, transporting more packets in one direction than another, and can provide increased protection time between transmission and reception mode, for example, to combat interference problems based on cellular communication networks. Combining discrete multiple pitch orthogonal frequency division multiplexer processing techniques and array of antennas with the discrete multi-tone stacked carrier and antenna array processing techniques takes advantage of the discrete multiple-tone scatter-free properties and discrete multiple tone stacked carriers. An important improvement in the realization of adaptive antenna arrays in any application requires that the cancellation of spatial interference be eliminated by eliminating the need to mitigate the quasi-stationary linear stationary dispersion in front of the adaptive receiver (due to the imperfections of the front receiver). to end, zero-set openings, and fixed multiple-path scatters and reflectors). This is particularly useful in cellular point-to-multipoint communication networks that include space division multiple access (SDMA) topologies to communicate between multiple users over the same set of frequency channels, since each space processor must form the depth cancellations 10 (potentially) in the address of the interference users within that cell. Code division multiple access (CDMA) transmits multiple signals over the same set of frequency channels using separate sets 15 linear (typically orthogonal) propagation gains. These codes are separated into a depropagator using appropriate combinator weights. Direct sequence propagated spectrum systems can benefit multi-access type of 20 space division multiple access, interference excision, and channel equalization capability (code cancellation techniques). The cancellation of codes has been applied to the spread spectrum formats of direct sequence of modulation symbol (MOS-DSSS) or spectrum 25 propagated direct sequence with pulse in modulation of (MOP-DSSS) where the propagation gain period is exactly equal to a whole number of message symbols (usually a symbol interval). The code override can be successfully combined with stacked carrier modulation formats. For example, for the cancellation of redundant interactions spectrally on a frequency of HF / VHF that jumps the intersection system. In the prior art, general frequency skip intersection techniques include cancel cancellation interference 10 code that has been used with a stacked carrier signal that simulates a tropospheric scatter communication link. Although this technique is extended by the present invention to point-to-point and point-to-multipoint communications where the intended communicators, as well as the 15 interferences, include stacked carrier propagated spectrum modulation formats. For example, methods of blind adaptation of targeted data are additionally included to optimize debuggers based on known properties of traffic and pilot data. 20 conveyors for communication systems. The present invention combines communications based on spread spectrum of stacked carrier and code bypass based on interference cancellation for a communication system with higher capacity, tolerance 25 higher channel distortion and less reliability in Correlation between the propagation gains. The near orthogonality is not required and embodiments of the invention have less sensitivity for narrowband interference or other propagated spectrum signals of stacked bearer of the system member. Such effects are optimized when the code override is based on interference cancellation that is combined in a stacked bearer propagated spectrum communication network. In particular, a stacked bearer propagated spectrum communication link that includes code cancellation based on interference cancellation can support two or more links as the equivalent sequence modulated direct symbol spectrum system, given to the same propagation gain and complexity of code override (linear combiner). The invention combines the cancellation of code based on the cancellation of interference and the methods by other directed used to adapt the debonders in the network. Such a combination provides a system with significant advantages over competing methods for point-to-point and point-to-multipoint communications (multiple access). Such systems can take advantage of a full-time bandwidth product of the communication system, thereby reducing the acquisition and time tracking of debonders in the system.

Such systems can also depropagate and demodulate the propagated carrier signals propagated from the intended stacked carrier of interest to the depropagator, without knowledge of the propagation gains included in the signal transmitters (property of blind depropagation) thereby simplifying or eliminating the strategy of selection of code in the network, and allowing the use of retrodirective techniques that optimize the propagation gain based on the communication channel and the network. The spread signals of stacked carrier modulation interference (inside the cell or outside the cell) is received by the depropagator, without knowledge of the propagation gains contained in the interference signals, thereby providing the environments of significant complexity over sequential methods (typically non-linear) that must demodulate and re-modulate the interferences as well as the signals of interest to the receiver. Automatic composition is provided for stationary linear channel dispersion, including induced dispersive effects within the extreme front system, without knowledge of the current estimation of the channel dispersion, thereby reducing the complexity of the depropagation methods as well as the hardware of the system. The code override extends to spatial processing techniques, and facilitates the use of back-transmission transmission methods to greatly improve the performance and cost efficiency of the entire network. The combination of code override and spatial processing techniques with adaptive antenna arrays so that the beam direction improves the range of a conventional communication transceiver in another way. The combination can also increase the capacity of a network of ironic cells by reproducing the interference presented to the underlying cells, the cancellation address for interference cancellation improves the capacity of a communication network by allowing tight packing. Tight packing becomes possible by separating users into frequency matching cells into multiple space division access topologies. Antenna arrays can be combined with code cancellation techniques in a direct way by increasing the dimensions of the code canceller to combine the spatial channels as well as the time channels, for example, in the MOS-DSSS systems, or by increasing the dimensions code canceller to combine spatial channels as well as frequency channels, for example, in stacked carrier propagated spectrum systems. The stacked carrier spread spectrum formulation format allows a depropagator to reduce the spread propagation gain of stacked carrier as the number of spatial channels grows, in order to maintain the complexity of the code null constant as a function of number of antenna elements. This provides the tuning time of the constant directed data receiver. Linear complexity grows as the number of user antennas in the communication link grows. And, the user spatial distribution is reduced as the number of antenna beams grows. The combination of retrodirective transmission techniques of directed data adaptation of code override and spread propagation of stacked carrier provides a superior communications mode. Point-to-point communication links, as well as point-to-multipoint communication links, have increased user capacity, range, power and / or cost efficiencies that exceed those for full-channel pre-emphasis methods. Combining the stacked carrier spectrum and the processing of adaptive antenna assemblies helps remove spatially coherent interference, for example, in stacked carrier-propagated spectrum networks where interference can be other member signals in the network and where Multi-element antenna arrays are "primarily used in base stations in the network. "- + - - - -« - - ir státaáiiWt An example of the time frequency format of a time-division duplex communication system is shown in Figure 17. Figure 18 shows an active tone format of 5. a basic DMT modem A transmission / reception calibration method is shown in Figure 19. There are two separate modes for system calibration and compensation: the SCSS calibration signal injected into the receiver at the calibration change , measurement to receive path spread The SCSS calibration signal routed through a transmit modulator to the output receiver through the transfer change measures the combined transmission and the receive path spread. it is derived from the combined reception and the transmission calibration data.The compensation is done at the rear end of DSP transmitting and pro stopping the SCSS calibration waveform. Figure 20 schematizes a T / R and DMT modem of a single integrated antenna (DMT based on SCMA). Figure 21 is a diagram of a transverse SCORE propagation operation of individual link code gates of the general example. It is a preferred mode for individual link processing. It allows the use of a transverse SCORE algorithm with time of pifTMlff mrff "" - J1t aj faster convergence (lowest TBP). It is not affected by synchronization and Doppler shift. Interferences from Kcon? UntQ can be removed within each cell. It can separate the signals of Kcon;) unto SCSS. Its shortcomings are that it can not separate the signals from > Kcon] ano SCSS reliably (code override is not performed) and the relationship to solution relative to maximum solution of SINR is not adjusted in highly varying frequency environments. Figure 22 is an example of a cross-SCORE depropagation operation of individual link code gates with the Kspread cell subsets. Figure 23 is an example of an individual link cross SCORE algorithm with Nframe packets / adaptation chart. Depropagator weights are computed from the dominant mode of the cross-set multiple SCORE equation. Figure 24 is an example of a statistical computation of individual adaptation framework autocorrelation. Figure 25 is an example of a SCORE-own equation crossed with Kpread cell subsets. Depropagator weights are computed from the dominant mode of the cross-set multiple SCORE equation. Figure 26 is an example of a code key generator with cell subsets of Kpart < Kspread Figure 27 is an example of an equivalent code key applier with subsets of Kpart cells < Kspread • Figure 28 is an example of a SCORE-own equation crossed with Kpart cell subsets. Depropagator weights are computed from the dominant mode of the cross-set multiple SCORE equation. Figure 29 is an example of the SCORE-own equation crossed with two cell subsets. The defragger weights are computed from the dominant mode of the cross-set multiple SCORE equation. Figure 30 is an example of a SCORE cross propagator of multiple link code gateways. It is an improved mode for processing multiple links. It allows the adjustment of the crossed SCORE convergence time for the SCSS interference conditions. Synchronization and Doppler shift are not affected. It can remove the Kcon:) interference reliably within each cell. They can separate the signals from Kcon-, to 'KSCore SCSS. Their shortcomings are that they can not separate the signals from > Kcon:] unto "Kscore SCSS reliably (incomplete code override) and mismatch the solution relative to STAR maximum in highly varying frequency environments." Figure 31 is an example of the auto-SCORE propagation operation of code gates of link ^ fcs = ^ as ,. individual with gates on frequency and two cell subsets. It is a preferred mode for high mobility systems. You can separate the links from Kcon- | Unto KScoe SCSS. You can remove Kcon interference:] without SCSS inside each cell. The tuning and displacement of Doppler is not affected. Its shortcomings are that it can not separate links from > Kscore SCSS and requires time tracking (simple) as part of the depropagation algorithm. Figure 32 is an example of the self-SCORE depropagation operation of individual link code gates with gates on the frequency and two subsets of cells. Figure 33 is an example of a self-SCORE equation with gates on the frequency and two subsets of cells. Figure 34 is an example of the self-SCORE propagation of individual link code gates with time gates and an average ratio of the redundancy gate. It is the preferred mode for low mobility systems. It can separate the set links "KSCORE SCSS.It can remove Kconnurite interferences without SCSS within each cell.It is not affected by synchronization and Doppler shift.There are three dB SNR gains in the depropagator.Its shortcomings are that it can cut capacity in half and __ÍÍÍÉÉÍÍÍRIÍII ^ M ^ rf iHMtll ^^^^^^ M ^ 1? TT mili -. ,. ,, And - - - -,. * -, »» ^ v ^. requires Doppler tracking (simple) as part of the depropagation algorithm. Figure 35 is an example of the self-SCORE depropagation of individual link code gates with time gates and an average ratio of the redundancy gate. In summary, the adaptive antenna assemblies can be used to increase the capacity of the network system by the beam direction, bypass direction, or bypass and combined beam direction. Such an override address or combined beam and override address override technologies are combined in this invention with DMT / OFDM frequency channellers away from the use of channelizers as SCSS propagators / depropagators. Although the present invention has been described in terms of currently preferred embodiments, it will be understood that the description should not be limited as limiting. Various alterations and modifications will undoubtedly become apparent to those skilled in the art after having read the above description. Accordingly, it is intended that the appended claims be interpreted as covering all alterations and modifications that fall within the true spirit and scope of the invention. • teM ^ b ^^^ O

Claims

DEVICES 1. A multiple access communication system characterized in that it comprises: at least one radio transmitter for transmitting a plurality of radio frequency (RF) bearers: at least one radio receiver for receiving at least one subset of at least two of a plurality of radio frequency carriers; at least one propagator connected to each of the transmitters to independently and redundantly modulate the amplitude and phase of at least two of the carriers (RF) with a first digital propagation gain and first data: at least one de-propagator connected to each of the receivers to independently demodulate the amplitude and phase of at least two of the carriers (RF) with the first digital propagation gain to coat the first data; and multiple access means connected to the transmitters, propagating and disprobing receivers to provide the separate communication channels for at least one space division multiple access (SDMA), frequency division multiple access (FDMA) and multiple division access code (CDMA). The system according to claim 1, characterized in that: the SDMA further comprises a set of antennas connected to the transmitters and receivers, and provides the selective data channel transmission and the reception between the transmitter and receiver pairs according to with their relative spatial positions. The system according to claim 1, characterized in that: the FDMA further comprises a minimum number of radio frequency bearers to provide at least two subsets of carriers to communicate with the additional data channels between the transmitter and receiver pairs. according to the correspondence subsets of the radio frequency bearers. 4. The system in accordance with the claim 1, characterized in that: the CDMA comprises including at least a second digital propagation gain and second data, and provides for the communication of at least the first and second data between the transmitter and receiver pairs according to the correspondence subsets of the digital propagation gain. 5. A radio transmitter system that provides spatial and frequency dispersion, characterized in that it comprises: an antenna system having a positive integer "n" of individual antennas spatially distributed in a group and providing as many positive integers "n" of spatially distributed communication channels; a radio frequency amplifier bank has individual amplifiers connected to corresponding antennas of the antenna system where each amplifier has an adjustable gain to provide a controlled beam direction and overrides of radio frequency signal transmission to the radially distributed space communication channels; a discrete multi-tone stacked bearer propagated spectrum transmission modulator connected to the amplifier bank and provides a plurality of sparse frequency of communication channels; a propagator having respective outputs connected to the modulator and a data input and providing a data propagation concurrently throughout the plurality of dispersed frequency of communication channels; and address means connected to the radio frequency amplifier bank and provides a selection of a positive integer "n" of radially distributed spatial communication channels. 6. The system according to claim 5, characterized in that the system also provides polarization dispersions wherein the individual antennas are further distributed in polarization. 7. A radio receiver system provides spatial and frequency dispersion, characterized in that it comprises: an antenna system having a positive integer "n" of individual antennas spatially distributed in a group and providing as many positive integers "n" of radially distributed space communications channels; a radio frequency amplifier bank has individual amplifiers connected to the corresponding antennas of the antenna system in each amplifier having an adjustable gain which provides a controlled direction of beams and cancellations of radio frequency signal transmissions in the radio channels spatial communication radially distributed. a spread propagated spectrum of discrete multi-tone stacked bearer connected to the amplifier bank and provides a plurality of dispersed frequency of communication channels; a depropagator having respective inputs connected to the demodulator and a data output and providing a depropagation of data included throughout the plurality of dispersed frequency of communication channels; and address means connected to the bank 5 radio frequency amplifier and provides a selection of a positive integer "n" of radially distributed spatial communication channels. 8. The system according to claim 6, characterized in that it further comprises: computational means for determining a radially distributed spatial communication channel direction of a target receiver. 9. A multiple access method for propagated spectrum radio communication of stacked carrier 15 characterized in that it comprises the steps of: building in a transmitter a stacked carrier propagation gain from the complex amplitude and phase gain of a complex sinusoid for each of a plurality of frequency communication channels 20 discreet; de-propagating arbitrary narrow-band baseband pre-propagated data with a vector multiplier and a reverse frequency communication channelizer in the transmitter; 25 simultaneously transmit from the transmitter the m? m ^^? ^ m data after propagation on the plurality of discrete frequency communication channels with the stacked carrier propagation gain; and dispropagating the plurality of discrete frequency communication channels in a receiver with a vector internal product linear combiner and the frequency communication channelizer, wherein the arbitrary narrowband baseband co-pre-p data is overlaid. with the tive immunity for interference 10 of the communication channel. The method according to claim 9, characterized in that: the construction is such that the frequency communication channels are not contiguous and are distributed within the multiple bands. The method according to claim 10, characterized in that: the simultaneous transmission is such that the frequency communication channels overlap and include orthogonal frequency division multiplexer formulation formats. The method according to claim 11, characterized in that: the simultaneous transmission is so that the data 25 is packaged, where the baseband data is propagated, M gf? < ? attltfÉÉMTMÉia ^ .. a. ^^ .-, ....- j, .. «.. A .. .... _. . . . ,.,,. ^^ - Ma are transmitted and unpacked in different packets in a frequency-based communication channeling structure of orthogonal frequency division multiplexer type, the overlapping packets are contiguous or non-contiguous in time. 13. An interference cancellation method for radio communication of propagated spectrum of stacked carrier, characterized in that it comprises the steps of: constructing in a transmitter a stacked carrier propagation gain from the complex amplitude of the phase gain of a sinusoid complex for each of a plurality of discrete frequency communication channels; propagating arbitrary narrowband baseband pre-propagated data with a vector multiplier and a reverse frequency communication channelizer at the transmitter; simultaneously transmitting from the transmitter the data after propagation over the plurality of discrete frequency communication channels with the stacked carrier propagation gain; and deproducting the plurality of discrete frequency communication channels in a receiver with a linear vector product internal combiner and the frequency communication channelizer, wherein the arbitrary narrowband baseband pre-propagated data is coated with immunity tive to the interference of the communication channel; and cancellation of the code with means of cancellation of interest according to information obtained from the depropagation stage. 14. A method of adaptable antenna array for radio communication of propagated spectrum of stacked carrier, characterized in that it comprises the steps of: constructing in a transmitter a carrier propagation gain stacked from the complex amplitude and the phase gain of a complex sinusoid for each of a plurality of discrete frequency communication channels; propagating arbitrary narrowband baseband pre-propagated data with a vector multiplier and a reverse frequency communication channelizer at the transmitter; simultaneously transmitting from the transmitter the data after propagation over the plurality of discrete frequency communication channels with the stacked carrier propagation gain; depropagate the 'plurality of discrete frequency communication channels in a receiver with a . »I« fM * »fl? M. vector internal product linear combiner and frequency communication channelizer, wherein the arbitrary narrowband baseband pre-propagated data is coated with relative immunity for interference of the communication channel; and adjusting the gains of several amplifiers connected to a set of antennas and to the transmitter according to the base de-propagated data. 15. A time division duplex method for stacked bearer propagated radio spectrum communication characterized in that it comprises the steps of: dividing time into reserved broadcast boxes for the transmission of a first plurality of discrete frequency communication channels to a remote receiver 15 and to receive a second plurality of discrete frequency communication channels from a remote transmitter; building on a near transmitter a stacked carrier propagation gain from the amplitude of complex 20 and the phase gain of a complex sinusoid of at least one of first and second plurality of discrete frequency communication channels; propagating arbitrary narrowband baseband pre-propagated data with a vector multiplier and a communication channelizer in the near transmitter '- * «« - - »-' * ..- .. - -. » . . HUKj of inverse frequency; transmit simultaneously from the near transmitter the data after propagation on the first plurality of discrete frequency communication channels with the stacked carrier propagation gain; depropagate the second plurality of discrete frequency communication channels in the near receiver with a linear combiner of vector inner product and frequency communication channelizer, wherein the arbitrary narrowband baseband pre-propagated data is coated with the relative immunity for communication channel interference; and controlling the step of separating time with precision time information obtained from a time signal source that is available for distant and near transmissions and distant and near receivers. 16. The method according to claim 15, characterized in that: the step of controlling includes receiving the system time information from the orbiting navigation satellites. 17. A radio transmitting system, characterized in that it comprises: a multi-tone transmitter assembly for the transmission of multiple spectral carrier signal according to a spectral weight calculation by a computer that distinguishes between a first plurality of individual remote receivers; and a set of antennas connected to the transmitter assembly and providing the spatial settings of the transmitted power of the multiple spectral carrier signal transmission according to the spatial weight calculation by a computer distinguishing between a second plurality and individual remote receivers. 18. A radio receiver system, characterized in that it comprises: a multi-tone receiver assembly for receiving multiple spectral carrier signal according to a spectral weight calculation by a computer that distinguishes between a first plurality of individual remote transmitters; and a set of antennas connected to the receiver assembly and providing the spatial adjustments of the received power of the multiple spectral carrier signal reception according to a spatial weight calculation by a computer that distinguishes between a second plurality of individual remote transmitters. 19. A radio communication system, characterized in that it comprises: a multi-tone transmitter assembly for the transmission of multiple spectral carrier signal according to ur spectral weight calculation by a computer that distresses between a first plurality of individual remote receivers; a first set of antennas connected to a transmitter conjugate and providing spatial adjustments of the transmitted power of the multiple spectral carrier signal transmission according to a calculation of spatial weight by a computer that distinguishes between a second plurality of individual remote receivers; a multitone receiver array for receiving multiple spectral carrier signal according to a spectral weight calculation by a computer that distresses between a first plurality of individual transmitters; and a second set of antennas connected to the receiver assembly and providing the spatial adjustments of the received power of the multiple spectral carrier signal transmission according to a spatial weight calculation by a computer that distinguishes between a second plurality of individual remote transmitters. . 20. The system according to claim 19, characterized in that it comprises: a computer connected to a transmitter assembly ma¡mí g ^^^^ üfcl - '-' - "-" a * - "'" - and to a first set of antennas that provides an individual interconnected calculation of the spectral weight and spatial weights. 21. The system according to claim 19, characterized in that it further comprises: a computer connected to the receiver set and second set of antennas that provides an individual interconnected calculation of the spectral weight and the spatial weights. 22. The system in accordance with the claim 19, characterized in that it further comprises: a computer connected to the transmitter assembly, the receiver assembly, the first set of antennas, and the second set of antennas and that provides an individual, connected calculation of the spectral weight and the spatial weights for use by the receiver assembly and the second set of antennas that repeats the spectral weight and the spatial weights for use by the transmitter assembly and the first set of antennas; wherein a particular spatial and spectral characteristic of the first and second plurality of individual remote transmitters is used to optimize a transmission back to the first and second plurality of individual remote receivers. 23. A method to recover a signal from j - '»' '•» - »' - - • • - ~ - - - ~ * '- r-tf * digital communication that was propagated and modulated on each of a plurality of stacked carrier signals using a propagation gain different for each of a plurality of stacked carrier signals, transmitted through a wireless medium and received in a receiver as a plurality of stacked carrier signals, characterized in that it comprises the steps of: channeling each of the stacked carrier signals received to identify a baseband signal for each of the received carrier signals, the received stacked carrier signals having a channel bandwidth that can be separated from the channel bandwidth of another of the plurality of received stacked carrier signals; dispropagate by applying de-propagated weights that are different from the propagation gains for each of the received baseband signals and combining the received phase-band signals to obtain a baseband signal that compensates for the interference and maximizes a signal for the noise and interference ratio; and removing at least one time distortion and frequency distortion that exists in the band-based signal to obtain a recovered digital communication signal corresponding to the digital communication signal. 24. The method in accordance with the claim 23, characterized in that the depropagation step blindly disproportions the plurality of received stacked carrier signals. 25. The method of compliance with the claim 24, characterized in that the blind despread uses a dominant mode of a generalized own equation. 26. The method of compliance with the claim 25, characterized in that the blind despreading uses dominant modes of a generalized own equation. 27. The method of compliance with the claim 26, characterized in that the proper equation is an own equation of cohesion restoration of code gates. The method according to claim 25, characterized in that a proper value of restoration of maximum code gates of the generalized equation itself is reduced by a predicted means and in scale by a predicted standard deviation during the blind depropagation stage. 29. The method of compliance with the claim 23, characterized in that the steps of channeling, depropagation, and removal each are performed repeatedly in each sequential plurality of the received stacked carrier signals to obtain a sequential plurality recovered from related digital communication signals. 30. The method according to claim 29, characterized in that the sequential plurality of received stacked carrier signals are asynchronous. The method according to claim 29, characterized in that each sequential plurality of received stacked carrier signals is received during the associated time division duplex intervals and a network clock is used to determine the time division duplex intervals. 32. The method of compliance with the claim 29, characterized in that the reception time duplex intervals are asymmetric with respect to the transmission time duplex intervals. 33. The method according to claim 31, characterized in that the reception time duplex intervals are asymmetric with respect to the transmission time duplex intervals. 34. The method of compliance with the claim 31, characterized in that the sequential plurality of received stacked carrier signals are received with a plurality of packets during a dividing duplex interval by individual time. 35. The method of compliance with the claim 31, characterized in that the sequential plurality of received stacked carrier signals is received as an individual packet during a dividing duplex interval by individual time. 36. The method according to claim 31, characterized in that the network clock is derived from universal time. 37. The method according to claim 31, characterized in that the network clock is derived from data within the digital communication signal. 38. The method according to claim 23, characterized in that the second propagation gains for a second data communication signal transmitted as a second plurality of carrier signals stacked from the receiver are determined adaptively based on the disproportionate weights so that the radiation minimum is directed at interference frequencies. 39. The method according to claim 38, characterized in that the second propagation gains are proportional together for conjugate de-propagated weights such that a gain pattern of the second plurality of stacked carrier signals is substantially the same as the gain pattern. of the plurality of stacked carrier signals. 40. The method according to claim 23, characterized in that a plurality of recovered digital communication signals are simultaneously recovered from a plurality of received stacked carrier signals, each plurality of digital communication signals having a different associated code key that it is used during the depropagation step to distinguish each plurality of received stacked carrier signals. 41. The method according to the claim 40, characterized in that each of the different code keys modulates only part of the plurality of the received stacked carrier signals. 42. The method of compliance with the claim 41, characterized in that each of the different code keys modulates one of the stacked carrier signals received even and odd from the plurality of received stacked carrier signals. 43. The method according to claim 23, characterized in that the digital communication signal is a plurality of symbols, and each of the symbols is modulated in each of the plurality of carrier signals stacked in a different discrete tone. 44. The method according to claim 23, characterized in that the digital communication signal is a plurality of bits, and each of the bits is modulated in each of the plurality of carrier signals stacked in a different discrete tone. 45. The method according to claim 23, characterized in that the time distortion is due to a Doppler frequency shift. 46. The method according to claim 23, characterized in that the frequency distortion is due to the time dispersion. 47. The method according to claim 23, characterized in that the frequency distortion is a propagation delay. 48. The method of compliance with the claim 23, characterized in that the stirring step removes the time distortion and the frequency distortion. 49. The method according to claim 48, characterized in that the time distortion is due to a Doppler frequency shift. 50. The method according to claim 48, characterized in that the frequency distortion is due to the time dispersion. 51. The method according to claim 48, characterized in that the frequency distortion is a propagation delay. 52. The method according to claim 48, characterized in that the frequency distortion is a propagation delay. 53. The method according to claim 23, characterized in that the received stacked carrier signals contain a protection time interval to compensate for the unknown propagation delay and the method does not synchronize the received stacked carrier signals until the despreading stage is complete. . 54. The method according to claim 23, characterized in that the received stacked carrier signals contain a protection frequency band to compensate for the unknown Doppler frequency shift, and the method does not synchronize formally received stacked carrier signals until the dispropagation step complete. 55. A method for recovering a digital communication signal that was propagated using propagation gains when transmitted and received in a receiver as received signals characterized in that it comprises the steps of: disprobing received signals to obtain propagated signals; and removing the Doppler time delay of the de-propagated signals to obtain a recovered digital communication signal corresponding to the transmitted digital communication signal. 56. A method "for recovering a plurality of transmitted symbols that was propagated using different propagation gains, the symbol that is received in a receiver as a plurality of discrete multiple tones having substantial frequency diversity, the method for recovering is characterized in that it comprises the steps of: dispropag- ing each of the plurality of discrete multiple tones to obtain a plurality of dispro- tened multiple tones, each of the plurality of multiple tones dispro- matted corresponds to one of the plurality of symbols, and removing the Doppler time delay of the multiple disproved tones to obtain a plurality of symbols recovered corresponding to the plurality of symbols transmitted 57. The method according to claim 56, characterized in that the transmitted symbols were propagated and modulated in each of the plurality of the stacked carrier signals. using a profit Different propagation for each of the plurality of stacked carrier signals, each of the plurality of stacked carrier signals has a channel bandwidth that is separable from the channel bandwidth of another of the plurality of stacked carrier signals. 58. The method according to claim 57, characterized in that the step of blindly dispropagates the plurality of received stacked carrier signals. 59. The method according to claim 58, characterized in that the blind depropagation uses a dominant mode of a generalized own equation. 60. The method according to claim 58, characterized in that the blind depropagation uses dominant modes of a generalized own equation. 61. The method according to claim 60, characterized in that the equation itself is an equation 10 of autocoherence restoration of code gates. 62. The method according to claim 59, characterized in that a proper value of maximum code gate restoration of the generalized equation itself is decreased by a predicted means and is scaled. 15 by a standard deviation predicted during the blind depropagation stage. 63. A method for propagating a digital communication signal, characterized in that it comprises the steps of: spectrally propagating the digital communication signal over a plurality of stacked carrier signals to obtain a plurality of spectrally propagated digital communication signals, each of the plurality of stacked carrier signals that has a 25 channel band width that can be separated from the width ^ t ^^ & ^ it sfe k of channel band of the plurality of stacked carrier signals; spatially propagating each of the plurality of spectrally propagated digital communication signals to obtain a plurality of spatially and spectrally propagated digital communication signals; and transmitting from each antenna element a plurality array of antennas, associated with one of the plurality of digital communication signals spatially and spectrally propagated through a wireless means for a receiver. 64. A method for communicating digitally characterized in that it comprises the steps of: propagating, in a motion transmitter, digital information that was propagated using different propagation gains in each of a plurality of stacked carrier signals, each of the plurality of stacked carrier signals have a channel bandwidth that can be separated from the channel bandwidth of another of the plurality of stacked carrier signals; transmitting each of the carrier signals stacked through a wireless medium from the motion transmitter to a receiver; receiving, in the receiver, the transmitted plurality of stacked carrier signals as received stacked carrier signals; channeling each of the received stacked carrier signals to identify a baseband signal for each of the received stacked carrier signals; depropagate by applying de-propagated weights that are different from the propagation gains for each of the received baseband signal and combining the received baseband signals to obtain a baseband signal that compensates for the interference and maximizes a signal for the noise and interference ratio; and processing the baseband signal to obtain the recovered digital information corresponding to the digital information transmitted. 65. The method according to claim 64, characterized in that the processing step removes the Doppler time delay from the baseband signal. 66. The method of compliance with the claim 64, characterized in that it comprises: a plurality of motion transmitters that each perform the stage of propagation and transmission of the digital information, each 'transmission of movement propagates the digital information using a non-orthogonal spread gain randomly different to propagate the digital information in each of the plurality of stacked carrier signals; the step of receiving the transmitted plurality of stacked carrier signals that receive the stacked carrier signals transmitted from each of the transmitters in a recpector; the channeling stage channels each of the received stacked carrier signals; the depropagation step combines each of the plurality channelized separately from the stacked carrier signals to obtain, for each of the plurality of transmitters, a baseband signal corresponding to the digital information transmitted by one of the plurality of transmitters; and the processing step processes each of the baseband signals to obtain the recovered digital communication signal corresponding to the digital communication signal transmitted for each of the motion transmitters. 67. The method according to claim 66, characterized in that the processing step removes the Doppler time delay that exists in each of the baseband signals. 68. The method according to claim 67, characterized in that the plurality of motion transmitters are separated geographically and each has a different transmission path for the receiver. 69. The method of compliance with the claim 67, characterized in that the set of multi-element antennas is used in the receiver, different from the elements used for the differentiation zones, and the multiple space division access is used for the differentiation differences of the transmitters. 70. A method according to claim 65, characterized in that the multiple division by frequency access is used for differentiation differences of the transmitters. 71. The method of compliance with the claim 67, characterized in that the code division multiple access is used for the differentiation differences of the transmitters. 72. The method according to claim 71, characterized in that it further includes the step of modulating a different code key in part of the plurality of the stacked carrier signals associated with each of the transmitters. 73. A method for communicating digitally characterized in that it comprises the steps of: propagating the digital information, in a first station having a set of multi-element antennas, using the different propagation gains, on each of the plurality of carrier signals stacked, each of the plurality of stacked carrier signals has a channel bandwidth that can be separated from the channel bandwidth of another of the plurality of carrier signals stacked on each of the antenna elements that is used for transmit the 10 differences of the stacked carrier signals; transmitting each of the carrier signals stacked through a wireless medium from the first station to a second station; receive, in a second station using a The multiplicity of antenna arrays of multiple elements the plurality transmitted of stacked carrier signals as received stacked carrier signals, each of the second antenna elements that are used to receive the differences of the received stacked carrier signals; 20 channeling each of the received stacked carrier signals to identify a baseband signal for each of the received stacked carrier signals; and dispropagate by applying the disproportionate weights that 25 are different from the propagation gains for each n? lWN of the received baseband signal and combining the received baseband signals to obtain a baseband signal that compensates for the interference and maximizes a signal for the noise and interference ratio. 74. The method of compliance with the claim 73, characterized in that the second propagation gains for a second data communication signal transmitted as a second plurality of stacked carrier signals from the multi-element antenna array of the second station are determined adaptively based on the disproportionate weights so that the radiation minimum is directed at interference frequencies. 75. The method according to claim 74, characterized in that the second propagation gains are proportional sets for the conjugate de-propagated weights such that a gain pattern of the second plurality of stacked carrier signals is substantially the same as the gain pattern of the the plurality of the stacked carrier signals. 76. The method of compliance with the claim 73, characterized in that the second propagation gains for a second data communication signal transmitted from the multi-element antenna array of the second station are determined adaptively so that the maximum radiation is directed to a intended station. 77. The method according to claim 76, characterized in that the second propagation gains are determined adaptively using a combined spectral and spatial direction vector. 78. The method according to claim 73, characterized in that each of the different propagation gains associated with each of the plurality of stacked carrier signals is linearly independent and is not orthogonal. 79. A method for communicating digitally characterized in that it comprises the steps of: propagating, in a first station, digital information on each of a plurality of stacked carrier signals using a different propagation gain for each stacked carrier signal, each plurality of carrier signals stacked has a channel bandwidth that can be separated from the channel bandwidth of another of the plurality of stacked carrier signals; transmitting each carrier signal stacked through a wireless medium from the first station to a second station; receiving, at the second station using a plurality array of antennas, the plurality of carrier signals stacked as received stacked carrier signals; channeling in each assembly element each received stacked carrier signal to identify a baseband signal for each received stacked carrier signal; and dispropagating by applying the disproportioned weights that are different from the propagation gains for each received baseband signal and combining the received baseband signals to obtain a baseband signal that compensates for the interference and maximizes a signal ratio of noise and interference, the stage of despropagation using a linear combiner of dimension which is composed of spectral dimensions and spatial dimensions. 80. The method according to claim 79, characterized in that the second propagation gain for a second data communication signal transmitted as a second plurality of stacked carrier signals from the multi-element antenna array of the second station is determined adaptively based in the de-propagated weights so that the minimum radiation is directed towards interference frequencies. 81. The method according to claim 80, characterized in that the second depropagation gains are proportional to the combined depropagated weights so that the gain pattern of The second plurality of stacked carrier signals is substantially the same as the gain pattern of the plurality of stacked carrier signals 82. The method according to claim 79, characterized in that the second propagation gain for a The second data communication signal transmitted from the multi-element antenna array of the second station is determined adaptively so that the maximum radiation is directed to an intended station 83. The method according to the claim 82, characterized in that the second propagation gains are determined adaptively using a combined spectral and spatial direction vector. 84. The method according to claim 79, characterized in that the spectral spatial dimensions are variable for a plurality of differences of the first stations. 85. The method according to claim 79, characterized in that each of the different propagation gains associated with each of the plurality of stacked carrier signals is linearly independent and is not octagonal. 86. A method for despreading a digital communication signal received in a receiver through a wireless means characterized in that it comprises the steps of: receiving, in each antenna element of a set of multi-element antennas, a plurality of stacked carrier signals each of the plurality of stacked carrier signals having a channel bandwidth can be separated from the channel bandwidth of the other of the plurality of stacked carrier signals; de-propagating spatially the plurality of stacked carrier signals to obtain spatially depropagated digital communication signals; and spectrally depropagating each of the plurality of spatially depropagated digital communication signals to obtain a spatially and spectrally propagated digital communication signal. SUMMARY A "stacked bearer" propagated spectrum communication system (10) based on frequency domain propagation that multiplies a 5 domain per time representation of a baseband signal by a set of stacked composite sinusoidal carrier waves or superimposed. In a preferred embodiment (10), the propagation gives power to the deposits of the large fast Fourier transform (FFT). This provides savings 10 considerable in computational complexity for moderate output FFT sizes. Point-to-multipoint and multipoint-to-multipoint network topologies (nodes) are possible. A code cancellation method is included for the cancellation of interference and separation of 15 signal increased by exploiting the spectral diversity of the various sources (11). The basic system (10) can be extended to include muting methods (26-18) of multi-element antenna array also for canceling interference and signal separation 20 increased that uses spatial separation. Such methods allow the directing and retrodirective transmission systems to adapt or adapt to the radio environment. Such systems are compatible with modulation formats of the highest order and bandwidth in g ^^? ^^ • i. t demarda and use advanced depropagator adaptation algorithms (maximum-SINR). t & amp;