JP5287916B2 - Load drive device - Google Patents

Description

  The present invention relates to a load driving device that drives a load.

  Conventionally, a gate drive circuit for driving a power switching element such as an IGBT as a load has been proposed in Patent Document 1, for example. In this Patent Document 1, the gate drive circuit includes a first on-side power supply circuit that performs an on operation of the power switching element, and the first on-side power supply circuit is a first power source dedicated to the first on-side power supply circuit. A configuration with a power supply is shown.

  In this configuration, the voltage applied to the gate of the power switching element during the ON operation of the power switching element is supplied from the first ON power supply, so that the voltage applied to the gate becomes a predetermined voltage or less. For this reason, the power switching element is not adversely affected such as characteristic variation.

  As described above, a gate drive circuit that drives a gate of a switching element such as an IGBT, that is, a driver circuit, is widely known. Also, the configuration of the gate drive circuit is not limited to the above configuration, and various configurations are known.

JP 2009-71956 A

  When the switching element is driven by the driver circuit as in the conventional technique, the rise time of the gate of the switching element is determined by the capability of the driver circuit. The shorter the gate rise time of the switching element, the faster the gate rise speed.

  Specifically, when the gate capacitance of the switching element is C, the constant current amount for charging the gate capacitance is I, and the ON voltage at which the gate is turned on is V, the gate of the switching element is turned on. The rise time T up to is expressed by T = (C × V) / I. Note that a constant current for charging the gate capacitance is supplied to the driver circuit from the outside of the driver circuit.

  According to the above formula, the rising time T of the gate is shortened by increasing the constant current I flowing to the driver circuit or by decreasing the gate capacitance C and the ON voltage V. That is, the gate of the switching element rises at a high speed. At this time, since the gate capacitance C and the ON voltage V are uniquely determined due to the size of the switching element and the manufacturing process, the gate rise time T is actually adjusted by the amount of constant current I flowing to the driver circuit. It will be.

  Therefore, it is conceivable to shorten the gate rise time T by increasing the current amount I of the constant current. However, there is a problem that an increase in the constant current amount I leads to an increase in current consumption of the driver circuit as it is. In particular, since the constant current amount I continues to be supplied to the driver circuit even after the gate of the switching element rises, current consumption in the driver circuit increases.

  An object of the present invention is to provide a load driving device that can reduce the current consumption of a driver circuit that drives a switching element while maintaining the rising speed of the switching element at a high speed.

  In order to achieve the above object, the invention described in claim 1 includes a switching element (50) connected to the load (10) and a constant current generator (30) for generating a constant current. The on-time until the switching element (50) is turned on is set to be shorter as the magnitude of the constant current increases, and is an on-time corresponding to the magnitude of the constant current flowing from the constant current generator (30). A driver circuit (40) for turning on the switching element (50) is provided.

  Then, the constant current generator (30) causes a constant current having a magnitude of the first current to flow through the driver circuit (40) until the on-time when the switching element (50) is turned on, and the switching element (50) A constant current having a second current amount smaller than the first current amount is allowed to flow through the driver circuit (40) after the on-time for turning on has elapsed.

  According to this, after the switching element (50) is turned on, the magnitude of the constant current flowing from the constant current generating unit (30) is reduced from the first current amount to the second current amount smaller than the first current amount. . For this reason, while the switching element (50) is turned on, the rising speed of the switching element (50) is maintained at a high speed by the constant current of the first current amount until the switching element (50) is turned on. The consumption current in the driver circuit (40) can be reduced by the amount of constant current.

  According to the second aspect of the present invention, the constant current generator (30) includes a switch (31) that is turned on or off in accordance with a current amount reduction signal, and a first constant current source (32) connected to the switch (31). And a second constant current source (33) connected in parallel to the series path of the switch (31) and the first constant current source (32).

  The driver circuit (40) turns on the switching element (50) in accordance with a switching signal for turning on the switching element (50).

  Then, the constant current generator (30) turns on the switch (31) in accordance with the on command of the current amount reduction signal until the on-time when the switching element (50) is turned on, whereby the first constant current source A current obtained by adding the current flowing through (32) and the current flowing through the second constant current source (33) is generated as a constant current of the first current amount.

  In addition, the constant current generator (30) is configured to turn off the switch (31) according to an off command of the current amount reduction signal after the on-time when the switching element (50) is turned on. The current flowing through the source (33) is generated as a constant current of the second current amount.

  Thus, the constant current of the first current amount can be generated by adding the current flowing through the first constant current source (32) and the current flowing through the second constant current source (33). Further, by controlling the switch (31), only the current flowing through the second constant current source (33) can be a constant current of the second current amount.

  In a third aspect of the invention, the constant current generator (30) includes a first constant current source (32) that generates a constant current having a first current amount, and a second constant current source that generates a constant current having a second current amount. And a constant current source (33).

  Further, the constant current generation unit (30) transmits the first current amount from the first constant current source (32) to the driver circuit (40) according to the current amount reduction signal until the on-time when the switching element (50) is turned on is reached. The connection is switched so that a constant current flows, and after the on-time when the switching element (50) is turned on, the second current is supplied from the second constant current source (33) to the driver circuit (40) according to the current amount reduction signal. A switch (31) for switching the connection so that a constant amount of current flows is provided. The driver circuit (40) is configured to turn on the switching element (50) in accordance with a switching signal for turning on the switching element (50).

  As described above, the switching between the driver circuit (40) and one of the first constant current source (32) and the second constant current source (33) having different current capabilities and the driver circuit (40) is performed by switching. The amount of constant current flowing through the driver circuit (40) can be adjusted before and after the on-time when the element (50) is turned on.

  In a fourth aspect of the invention, the constant current generator (30) has a variable power source (36) that can vary the voltage value, and is configured such that the amount of constant current increases as the voltage value increases. Yes. The driver circuit (40) turns on the switching element (50) in accordance with a switching signal for turning on the switching element (50).

  Then, the constant current of the first current amount is set to the driver circuit by setting the voltage value of the variable power source (36) to the first voltage value in accordance with the current amount reduction signal until the ON time when the switching element (50) is turned on is reached. (40).

  In addition, after the ON time when the switching element (50) is turned on, the voltage value of the variable power source (36) is set to the second voltage value smaller than the first voltage value in accordance with the current amount reduction signal. A constant amount of current is passed through the driver circuit (40).

  Thus, the amount of constant current flowing through the driver circuit (40) can be adjusted by adjusting the voltage value of the variable power source (36).

  In the invention according to claim 5, the constant current generator (30) has a variable resistor (34b) capable of varying the resistance value, and is configured such that the amount of constant current decreases as the resistance value increases. Yes. The driver circuit (40) turns on the switching element (50) in accordance with a switching signal for turning on the switching element (50).

  Then, the constant current of the first current amount is set to the driver circuit by setting the resistance value of the variable resistor (34b) to the first resistance value in accordance with the current amount reduction signal until the ON time when the switching element (50) is turned on is reached. (40).

  In addition, after the on-time when the switching element (50) is turned on, the resistance value of the variable resistor (34b) is set to a second resistance value larger than the first resistance value in accordance with the current amount reduction signal. A constant amount of current is passed through the driver circuit (40).

  Thus, the amount of constant current flowing through the driver circuit (40) can be adjusted by adjusting the resistance value of the variable resistor (34b).

In the invention according to claim 1 , the load (10) is a power element constituted by a semiconductor switching element. The constant current generator (30) and the driver circuit (40) are configured to be a pre-driver unit (60) for driving the power element by driving the switching element (50). The driver circuit (40) turns on the power element by driving the switching element (50) in accordance with the switching signal.

  Then, the pre-driver unit (60) drives the switching element (50) with a constant current having a magnitude of the first current amount until the on-time when the power element is turned on, and the on-time when the power element is turned on has elapsed. Then, the switching element (50) is driven by a constant current having a second current amount smaller than the first current amount.

  According to this, the constant current of the pre-driver unit (60) is reduced from the first current amount to the second current amount at the timing when the power element as the load (10) connected to the switching element (50) is turned on. The current consumption in the pre-driver unit (60) can be reduced while maintaining the rising speed of the power element at a high speed.

According to the first aspect of the present invention, when the switching element (50) is turned off, a constant current is supplied to the gate of the power element until the gate voltage of the power element reaches a predetermined voltage, thereby turning on the power element. (64). In addition, a short circuit detection signal indicating a short circuit of the power element is input. When the short circuit detection signal is input, a clamp circuit (65 that clamps the gate voltage of the power element to a clamp voltage smaller than a predetermined voltage). ). Further, a current amount reduction control circuit (70) for outputting a current amount reduction signal for allowing a constant current of the second current amount to flow at a timing when the power element is turned on after the switching signal is input to the driver circuit (40). I have.

  The constant current circuit (64) is driven by the constant current having the magnitude of the first current amount according to the current amount reduction signal input from the current amount reduction control circuit (70) until the ON time when the power element is turned on is reached. After the power element is driven at a constant current and the on-time when the power element is turned on has elapsed, the power element is driven at a constant current by a constant current having a second current amount smaller than the first current amount in accordance with the current amount reduction signal. Further, the current amount reduction control circuit (70) is configured to receive a short circuit detection signal, and from the input of the short circuit detection signal until the input of the short circuit detection signal is canceled. A signal for reducing the amount of current for flowing a constant current is output.

  According to this, when the power element is short-circuited, the current amount reduction control circuit (70) increases the current capability of the constant current circuit (64), so that the responsiveness of the constant current circuit (64) can be improved. An increase in current consumption of the current circuit (64) can be suppressed.

  In addition, the code | symbol in the bracket | parenthesis of each means described in this column and the claim shows the correspondence with the specific means as described in embodiment mentioned later.

It is a conceptual diagram of the load drive device which connected the load drive device which concerns on 1st Embodiment of this invention to load. FIG. 2 is a specific circuit diagram of the load driving device shown in FIG. 1. It is a timing chart of a gate waveform of a switching element, a switching signal, a current amount of a constant current generated by a constant current generator, and a current amount reduction signal. It is a concrete circuit diagram of the load drive device concerning a 2nd embodiment of the present invention. It is a concrete circuit diagram of the load drive device concerning a 3rd embodiment of the present invention. It is a specific circuit diagram of the constant current production | generation part which concerns on 4th Embodiment of this invention. It is a concrete circuit diagram of the load drive device concerning a 5th embodiment of the present invention. It is a specific circuit diagram of the load driving device according to the sixth embodiment of the present invention. FIG. 9 is a specific circuit diagram of the current amount reduction control circuit shown in FIG. 8. It is a timing chart for demonstrating the action | operation of the load drive device shown by FIG. It is a specific circuit diagram of a load driving device according to a seventh embodiment of the present invention. (A) is a specific circuit diagram of the delay circuit shown in FIG. 11, and (b) is a diagram showing an example in which a resistor included in the delay circuit is changed to a variable resistor. FIG. 12 is a timing chart for explaining the operation of the load driving device shown in FIG. 11. It is a specific circuit diagram of the load driving device according to the eighth embodiment of the present invention. It is a specific circuit diagram of a load driving device according to a ninth embodiment of the present invention. It is a specific circuit diagram of the load driving device according to the tenth embodiment of the present invention. It is a specific circuit diagram of a load driving device according to an eleventh embodiment of the present invention. It is a specific circuit diagram of a load driving device according to a twelfth embodiment of the present invention. FIG. 19 is a specific circuit diagram of the current amount control circuit shown in FIG. 18. It is a timing chart for demonstrating the action | operation of the load drive device shown by FIG. It is a specific circuit diagram of a load driving device according to a thirteenth embodiment of the present invention. It is a specific circuit diagram of a load driving device according to a fourteenth embodiment of the present invention. It is a specific circuit diagram of the load driving device according to the fifteenth embodiment of the present invention. It is a timing chart for demonstrating the action | operation of the load drive device shown by FIG. It is a specific circuit diagram of a load driving device according to a sixteenth embodiment of the present invention. (A) is a specific circuit diagram of the constant current circuit shown in FIG. 25, and (b) is a diagram showing a specific example of the constant current generation unit of (a). It is a timing chart for demonstrating normal operation | movement of the load drive device shown by FIG. It is a timing chart for demonstrating the action | operation of the load drive device shown by FIG. 25 when a power element short-circuits.

  Hereinafter, embodiments of the present invention will be described with reference to the drawings. In the following embodiments, the same or equivalent parts are denoted by the same reference numerals in the drawings.

(First embodiment)
Hereinafter, a first embodiment of the present invention will be described with reference to the drawings. The load driving device shown in the present embodiment is a device used for driving a load such as an IGBT, a power MOSFET, a capacitive load, and a resistance load with a constant current.

  FIG. 1 is a conceptual diagram of a load driving device in which a load driving device according to the present embodiment is connected to a load 10. As shown in this figure, the load driving device includes a constant current generation unit 30 connected to a power source 20, a driver circuit 40 connected to the constant current generation unit 30, and a switching element connected to the driver circuit 40. 50.

  The constant current generator 30 is a circuit that generates a constant current. This constant current is a current that determines the capability of the driver circuit 40, that is, the switching speed.

  The driver circuit 40 is configured to drive the switching element 50 on / off in accordance with a gate ON / OFF switching signal input from the outside. Since the ON time until the switching element 50 is turned on becomes shorter as the constant current increases, the driver circuit 40 can switch the switching element 50 in the ON time according to the constant current flowing from the constant current generating unit 30. Turn on. Hereinafter, the gate ON / OFF switching signal is simply referred to as a switching signal.

  The switching element 50 is a semiconductor switching element for driving the load 10. In the present embodiment, an Nch type MOSFET is adopted as the switching element 50. The switching element 50 has a gate connected to the driver circuit 40 and a drain connected to the load 10. Note that the load 10 may be connected to the source side of the switching element 50.

  A specific configuration of the load driving device will be described with reference to FIG. As shown in FIG. 2, the constant current generation unit 30 includes a switch 31 (SW-A in FIG. 2), a first constant current source 32, and a second constant current source 33.

  The switch 31 is connected to the first constant current source 32, and the second constant current source 33 is connected in parallel to the series path of the switch 31 and the first constant current source 32. The connection point between the switch 31 and the second constant current source 33 is connected to the power supply 20, and the connection point between the first constant current source 32 and the second constant current source 33 is connected to the driver circuit 40.

  The switch 31 is turned on / off in accordance with an on / off command of a current amount reduction signal input from the outside. The switch 31 is composed of a semiconductor element such as a MOSFET.

  When the switch 31 is turned on, a parallel circuit of the first constant current source 32 and the second constant current source 33 is formed between the power supply 20 and the driver circuit 40. Therefore, a current obtained by adding the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33 is generated as a constant current of the first current amount and supplied to the driver circuit 40. On the other hand, when the switch 31 is turned off, a circuit in which only the second constant current source 33 exists is formed between the power supply 20 and the driver circuit 40. Therefore, the current flowing through the second constant current source 33 is generated as a constant current having the second current amount and supplied to the driver circuit 40.

  As described above, the constant current generation unit 30 generates a constant current of the first current amount when the switch 31 is turned on, and a constant current of the second current amount that is smaller than the first current amount when the switch 31 is turned off. It can be said that this is a variable constant current source that generates The current capability of the first constant current source 32 and the current capability of the second constant current source 33 may be the same or different. The current capability of each of the constant current sources 32 and 33 is set depending on how the magnitude of the constant current flowing through the driver circuit 40 is designed by turning on / off the switch 31.

  The driver circuit 40 includes an amplifier 41. The amplifier 41 is a circuit that performs in-phase output with respect to the switching signal. The gate of the switching element 50 is connected to the output terminal of the amplifier 41, and the switching element 50 is driven by the output of the amplifier 41.

  The capacity of the amplifier 41 is determined by the magnitude of the constant current supplied from the constant current generator 30. Here, the capability of the amplifier 41 is a switching speed for driving the switching element 50. And the capacity | capacitance of the amplifier 41 becomes high, so that the magnitude | size of a constant current is large.

  Specifically, assuming that the capacitance of the gate of the switching element 50 is C, the current amount of a constant current for charging the capacitance of the gate is I, and the on voltage at which the gate of the switching element 50 is turned on is V, the switching element The rise time T until the 50 gates are turned on is expressed by T = (C × V) / I. Thus, the on-time until the switching element 50 is turned on is inversely proportional to the magnitude of the constant current. Therefore, the on-time until the switching element 50 is turned on becomes shorter as the magnitude of the constant current increases. The magnitude of the constant current is adjusted by turning on / off the switch 31 of the constant current generating unit 30 by a current amount reduction signal.

  The above is the circuit configuration of the load driving device according to the present embodiment. In the present embodiment, the switching signal and the current amount reduction signal are input from an ECU or the like outside the load driving device.

  Next, the operation of the load driving device shown in FIG. 2 will be described with reference to FIG. FIG. 3 is a timing chart of the gate waveform of the switching element 50, the switching signal for driving the switching element 50 on / off, the amount of constant current generated by the constant current generating unit 30, and the signal for reducing the amount of current. is there.

  First, when the switching signal is at a high level, the amplifier 41 has an in-phase output with respect to the switching signal, so that a high level is applied to the gate of the switching element 50 and the switching element 50 is turned on. Similarly, when the switching signal is at a low level, the output of the amplifier 41 is at a low level, so that the switching element 50 is turned off. As described above, the driver circuit 40 performs an operation of turning on the switching element 50 according to the high-level switching signal and turning off the switching element 50 according to the low-level switching signal.

  At time T1 shown in FIG. 3, the switching signal input to the driver circuit 40 is switched from the low level to the high level, whereby the switching element 50 is driven by the amplifier 41.

  Further, the switch 31 of the constant current generating unit 30 is turned on by an on command of the current amount reduction signal. As a result, the constant current generation unit 30 supplies the driver circuit 40 with a current obtained by adding the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33 as a constant current of the first current amount. .

  The rise time T until the gate of the switching element 50 is turned on is a time (T = (C × V) / I) according to the magnitude of the constant current supplied from the constant current generator 30 as described above. . The rise time T is an on-time when the switching element 50 is turned on.

  Therefore, the driver circuit 40 drives the gate of the switching element 50 based on the constant current of the first current amount supplied from the constant current generator 30. As a result, as shown in FIG. 3, the gate voltage of the switching element 50 rises with a slope corresponding to the first current amount of the constant current.

  Thereafter, when the ON time at which the switching element 50 is turned on at time T2 is reached, the switch 31 of the constant current generating unit 30 is turned off by an OFF command of the current amount reduction signal. Thereby, the constant current generation unit 30 supplies the current flowing through the second constant current source 33 to the driver circuit 40 as a constant current of the second current amount.

  As described above, the constant current generation unit 30 supplies a constant current having a magnitude of the first current amount to the driver circuit 40 until the on-time when the switching element 50 is turned on is reached. Thereby, until the switching element 50 is turned on, the switching element 50 can be turned on by the rise time of the gate according to the constant current having the first current amount larger than the second current amount.

  In addition, the constant current generation unit 30 causes a constant current having a second current amount smaller than the first current amount to flow through the driver circuit 40 after the ON time when the switching element 50 is turned on has elapsed. That is, the current amount of the constant current generator 30 is reduced at the timing when the switching element 50 is turned on. Thereby, after the gate of the switching element 50 rises, the amount of constant current flowing from the constant current generating unit 30 to the driver circuit 40 is reduced as compared with that before the gate of the switching element 50 rises.

  As described above, the present embodiment is characterized in that the current amount of the constant current flowing from the constant current generating unit 30 to the driver circuit 40 is reduced after the on-time when the switching element 50 is turned on.

  Thus, after the switching element 50 is turned on, the magnitude of the constant current generated by the constant current generator 30 is reduced from the first current amount to the second current amount smaller than the first current amount. Current consumption in the driver circuit 40 after the switching element 50 is turned on can be reduced.

  Further, since the driver circuit 40 is operated by a constant current having a first current amount larger than the second current amount until the switching element 50 is turned on, the rising speed of the switching element 50 is not slowed down. . For this reason, the rising speed can be maintained at a high speed according to the constant current of the first current amount.

  Therefore, current consumption can be reduced in the driver circuit 40 that drives the switching element while maintaining the rising speed of the switching element 50 at a high speed.

  In the present embodiment, the constant current generation unit 30 is configured to add the current flowing through the first constant current source 32 to the current flowing through the second constant current source 33 when the switch 31 is turned on / off. Thereby, after the ON time when the switching element 50 is turned on, only the current flowing through the second constant current source 33 can be set as the constant current of the second current amount.

(Second Embodiment)
In the present embodiment, parts different from the first embodiment will be described. The present embodiment is characterized in that the amplifier 41 of the driver circuit 40 is composed of a MOSFET.

  FIG. 4 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the amplifier 41 of the driver circuit 40 includes an inverter 41a, a switching element 41b, and a resistor 41c.

  The inverter 41a is connected to the gate of the switching element 41b, inverts the switching signal input to the driver circuit 40, and inputs the inverted signal to the gate of the switching element 41b. The switching element 41b is composed of an Nch type MOSFET, and has a drain connected to the constant current generating unit 30 and a source connected to a reference voltage line such as a ground. The resistor 41c is connected between the drain of the switching element 50 and a reference voltage line such as ground. Thus, the amplifier 41 is configured by grounding the source of the switching element 41b. 4 and FIG. 4 and subsequent figures show the ground as an example of the reference power supply line. Of course, the reference power supply line is not limited to the ground, but may be configured based on a potential other than the ground.

  Therefore, when the switching signal changes from the low level to the high level, the switching element 41b is turned off, so that the constant current (I in FIG. 4) supplied from the constant current generating unit 30 to the driver circuit 40 is It flows toward the gate. Thereby, the gate voltage of the switching element 50 rises. As described above, the amplifier 41 can also be constituted by the switching element 41b of the Nch type MOSFET.

(Third embodiment)
In the present embodiment, parts different from the first and second embodiments will be described. In each of the above embodiments, the constant current generating unit 30 is configured such that when the switch 31 is turned on, the current flowing through the first constant current source 32 is added to the current flowing through the second constant current source 33. It was. The present embodiment is characterized in that the switch 31 of the constant current generating unit 30 supplies the current flowing through one of the constant current sources 32 and 33 to the driver circuit 40 as a constant current.

  FIG. 5 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the constant current generation unit 30 includes a switch 31 (SW-B in FIG. 5), a first constant current source 32, and a second constant current source 33.

  The first constant current source 32 is configured to generate a constant current having a first current amount (I1 in FIG. 5). On the other hand, the second constant current source 33 is configured to generate a constant current (I2 in FIG. 5) having a second current amount smaller than the first current amount. Thus, in this embodiment, the current capability (I1> I2) of each of the constant current sources 32 and 33 is set in advance.

  The switch 31 has one contact point and the other contact point has two members. One power supply 20 is connected to one contact, and the first constant current source 32 and the second constant current source 33 are connected to the other two contacts.

  The driver circuit 40 and the switching element 50 are the same as the configuration shown in the first embodiment.

  In the constant current generation unit 30 as described above, the switch 31 causes the current flowing through the first constant current source 32 to flow through the driver circuit 40 in accordance with the current amount reduction signal until the ON time when the switching element 50 is turned on is reached. Switch connection. As a result, a path of the power source 20, the first constant current source 32, and the driver circuit 40 is formed, so that a constant current of the first current amount flows from the first constant current source 32 to the driver circuit 40.

  On the other hand, after the ON time when the switching element 50 is turned on, the switch 31 switches the connection so that the current flowing through the second constant current source 33 flows through the driver circuit 40 according to the current amount reduction signal. As a result, a path of the power source 20, the second constant current source 33, and the driver circuit 40 is formed. Therefore, a constant current having a second current amount smaller than the first current amount from the second constant current source 33 to the driver circuit 40. Flowing.

  As described above, the constant current generation unit 30 may be provided with a plurality of constant current sources 32 and 33 having different current amounts in advance, and the connection of the switch 31 may be switched by the current amount reduction signal.

(Fourth embodiment)
In the present embodiment, parts different from the first to third embodiments will be described. In each of the above embodiments, the constant current generator 30 is provided with a plurality of constant current sources 32 and 33 for supplying a predetermined amount of current. However, in this embodiment, the constant current generator 30 includes the constant current generator 30. It is characterized in that the magnitude of the constant current is adjusted inside the circuit.

  FIG. 6 is a specific circuit diagram of the constant current generator 30 according to the present embodiment. As shown in this figure, the constant current generator 30 includes resistors 34a and 34b and transistors 35a, 35b, and 35c to form a constant current source, and the gate input of the transistor 35a is a power source 36 (V1 in FIG. 6) and a transistor. 37 is controlled.

  The resistance value of the resistor 34b is variable. The resistance value of the resistor 34b is changed by a current amount reducing signal. For example, as an example, the resistor 34b is configured by a plurality of resistors connected in series, and any of the plurality of resistors is bypassed by a transistor, and when this transistor is turned on by a current amount reduction signal, The combined resistance value of the resistors can be changed.

  The transistor 35a is an NPN type bipolar transistor, and the transistors 35b, 35c, and 37 are PNP type bipolar transistors. The power source 36 is a power source that generates a predetermined voltage, and the voltage value of the power source 36 is variable. The voltage value of the power source 36 is changed by a current amount reduction signal. Similarly to the resistor 34b, as an example, the power source 36 is configured by a plurality of power sources, and any of the plurality of power sources is bypassed by a transistor. It can be set as the structure from which the synthetic voltage value of a power supply changes.

  The transistors 35b and 35c form a current mirror circuit, and the current flowing through the transistor 35a and the resistor 34b is transferred to the transistor 35c by the transistor 35b. The current flowing through the transistor 35c (I in FIG. 6) is supplied to the driver circuit 40 as a constant current. The PNP transistor 37 is grounded at the collector, and the voltage of the power source 36 is applied to the resistor 34b.

  Therefore, when the constant current is I, the voltage value of the power source 36 is V1, and the resistance value of the resistor 34b is R, the constant current I is expressed by I = V1 / R. Thus, the constant current is proportional to the voltage value of the power source 36 and inversely proportional to the resistance value of the resistor 34b. Therefore, the constant current increases when the voltage value of the power source 36 increases or the resistance value of the resistor 34b decreases, and the constant current decreases when the voltage value of the power source 36 decreases or the resistance value of the resistor 34b increases.

  As described above, in the constant current generation unit 30 according to the present embodiment, the amount of constant current increases as the voltage value of the power supply 36 increases, and the amount of constant current decreases as the resistance value of the resistor 34b increases. It is configured as follows.

  With the configuration of the constant current generation unit 30 as described above, the voltage value of the power source 36 is set to the first voltage value according to the current amount reduction signal and the resistance value of the resistor 34b until the ON time when the switching element 50 is turned on is reached. Is set to the first resistance value. As a result, the constant current generator 30 causes the constant current of the first current amount generated according to I = V1 / R to flow through the driver circuit 40.

  On the other hand, after the ON time when the switching element 50 is turned on, the voltage value of the power source 36 is set to the second voltage value and the resistance value of the resistor 34b is set to the second resistance value according to the current amount reduction signal. As a result, the constant current generation unit 30 passes a constant current having a second current amount smaller than the first current amount to the driver circuit 40.

  As described above, the amount of constant current flowing through the driver circuit 40 can be adjusted by adjusting the voltage value of the power supply 36 and the resistance value of the resistor 34b constituting the constant current generating unit 30.

  As for the correspondence between the description of the present embodiment and the description of the claims, the resistor 34b corresponds to the “variable resistor” in the claims, and the power source 36 corresponds to the “variable power source” in the claims. Correspond.

(Fifth embodiment)
In the present embodiment, parts different from the first to fourth embodiments will be described. In the present embodiment, when a power element is connected as the load 10 to the switching element 50, the current consumption is reduced while maintaining the rising speed of the power element at a high speed.

  FIG. 7 is a circuit diagram in which the load driving device according to the present embodiment is connected to the load 10. The load 10 is a power element composed of a semiconductor switching element. In the present embodiment, an IGBT is adopted as the power element. Hereinafter, the notation of the load 10 is referred to as a power element 10.

  The constant current generator 30 and the driver circuit 40 are configured to operate as a pre-driver unit 60 for driving the power element 10. The pre-driver unit 60 is connected to the switching element 50, and the switching element 50 is connected to the power source 20 via the resistor 61. The gate of the power element 10 is between the resistor 61 and the switching element 50. It is connected to the.

  In the present embodiment, an example in which a Pch-type MOSFET is employed as the switching element 50 is shown. Further, as the driver circuit 40, a configuration including a switching element 42 and an inverter 43 in addition to the amplifier 41 is shown. The switching element 42 is connected between the power supply 20 and the output terminal of the amplifier 41. A Pch type MOSFET is employed as the switching element 42. Therefore, the source of the switching element 42 is connected to the power supply 20, and the drain is connected to the output terminal of the amplifier 41. The inverter 43 is an element that inverts the switching signal input to the driver circuit 40 and outputs the inverted signal to the switching element 42. This inverter 43 is connected to the gate of the switching element 42.

  In the configuration as described above, the pre-driver unit 60 drives the switching element 50 with a constant current having a magnitude of the first current amount until the on-time when the power element 10 is turned on is reached. On the other hand, the pre-driver unit 60 drives the switching element 50 with a constant current having a second current amount smaller than the first current amount after the on-time when the power element 10 is turned on has elapsed. That is, the constant current of the pre-driver unit 60 is reduced from the first current amount to the second current amount at the timing when the power element 10 is turned on. The current amount of the constant current can be adjusted by controlling the switch 31 of the constant current generator 30 by the current amount reduction signal as described above.

  As described above, the constant current of the pre-driver unit 60 can be reduced based on the ON time when the power element 10 is turned on. Therefore, the current consumption in the pre-driver unit 60 can be reduced while maintaining the rising speed of the power element at a high speed.

(Sixth embodiment)
In the present embodiment, parts different from the first to fifth embodiments will be described. In each of the above embodiments, the current amount reduction signal is input from the outside to the constant current generation unit 30 at a predetermined timing based on the rise time of the gates of the switching element 50 and the power element 10. However, a circuit for generating a current amount reduction signal may be added to the load driving device by using the input timing of the switching signal. In this case, by monitoring the gate voltage of the switching element 50 or the power element 10, it is possible to improve the accuracy of the rise time, that is, the timing for adjusting the amount of constant current.

  Therefore, in this embodiment, a specific configuration of a circuit that generates a current amount reduction signal will be described. FIG. 8 is a conceptual diagram of the load driving device according to the present embodiment. As shown in this figure, the load driving device includes a current amount reduction control circuit 70 for generating a current amount reduction signal. The current amount reduction control circuit 70 is a period in which a switching signal for turning on the switching element 50 is being input to the driver circuit 40, and the timing at which the driver circuit 40 turns on the switching element 50 is set to the output of the driver circuit 40 and a predetermined value. , And outputs a current amount reduction signal at that timing.

  A specific configuration of the current amount reduction control circuit 70 will be described with reference to FIG. In the present embodiment, the constant current generator 30 includes the switch 31 (SW-A in FIG. 9), the first constant current source 32, and the second constant current source 33 shown in FIG. 2 of the first embodiment. The configuration provided will be described as an example. As illustrated in FIG. 9, the current amount reduction control circuit 70 includes a reference voltage source 71, a comparator 72, and an AND circuit 73.

  The reference voltage source 71 is a voltage source that generates a voltage having a predetermined value by, for example, dividing a 5V power source (not shown) with a plurality of resistors. This predetermined value is used as the comparator threshold value of the comparator 72. The comparator 72 is a comparison circuit that compares the output (BUFOUT) of the driver circuit 40 with a comparator threshold value and outputs the comparison result (COMP_OUT).

  Note that the comparator threshold value is input to the non-inverting input terminal of the comparator 72, and the output (BUFOUT) of the driver circuit 40 is input to the inverting input terminal of the comparator 72. The output of the driver circuit 40 is a gate voltage of the switching element 50.

  The AND circuit 73 is a logic circuit that turns on or off the switch 31 of the constant current generation unit 30 based on the switching signal (IN) and the comparison result of the comparator 72. The output (IN_CUR) of the AND circuit 73 corresponds to the current amount reduction signal. That is, when both the switching signal and the detection result of the comparator 72 are at the high level, the AND circuit 73 outputs the high level signal as an off command for the current amount reduction signal, and turns on the switch 31 of the constant current generator 30. . On the other hand, when at least one of the switching signal and the detection result of the comparator 72 is at the low level, the AND circuit 73 outputs a low level signal as an on command for the current amount reduction signal, and the switch 31 of the constant current generating unit 30 is output. Turn off.

  Thus, the current amount reduction control circuit 70 is configured to detect the ON voltage of the gate of the switching element 50 by the comparator 72 and reduce the current (I_OUT) of the constant current generation unit 30 at the timing.

  Next, the operation of the load driving device shown in FIG. 9 will be described with reference to the timing chart of FIG.

  First, in order to turn on the switching element 50, the switching signal (IN) becomes high level at time T10. However, since the output (BUFOUT) of the driver circuit 40 does not reach the comparator threshold value, the output (COMP_OUT) of the comparator 72 becomes high level, and the output (IN_CUR) of the AND circuit 73 is high level, that is, the current amount reduction signal is turned off. It becomes a command. Therefore, the constant current generator 30 that has received the off command of the current amount reduction signal turns on the switch 31. As a result, as shown in FIG. 10, the output (I_OUT) of the constant current generator 30 is the first current obtained by adding the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33 together. The constant current generator 30 supplies a constant current of the first current amount to the driver circuit 40. As a result, the output (BUFOUT) of the driver circuit 40 starts to increase according to the first current amount.

  Subsequently, at time T11, since the output (BUFOUT) of the driver circuit 40 reaches the comparator threshold value, the output (COMP_OUT) of the comparator 72 becomes low level. As a result, even if the switching signal (IN) is at a high level, the output (IN_CUR) of the AND circuit 73 is at a low level, that is, an on command for a current amount reduction signal. Therefore, the constant current generator 30 that has received the ON command for the current amount reduction signal turns off the switch 31, so that the output (I_OUT) of the constant current generator 30 uses the current flowing through the second constant current source 33 as the first current. This is supplied to the driver circuit 40 as a constant current of a second current amount smaller than the amount.

  Thereafter, when the switching signal (IN) becomes a low level, the output (BUFOUT) of the driver circuit 40 falls below the comparator threshold at time T12, and the output (COMP_OUT) of the comparator 72 becomes a high level. However, the switching signal (IN) is at a low level. For this reason, the output (IN_CUR) of the AND circuit 73 is at a low level, that is, the on command of the current amount reduction signal is continued, and the amount of current supplied to the driver circuit 40 does not increase.

  As described above, by providing the current amount reduction control circuit 70 in the load driving device, the current amount can be obtained from the switching signal (IN) and the output (BUFOUT) of the driver circuit 40 without inputting the current amount reduction signal from the outside. A reduction signal can be generated.

(Seventh embodiment)
In the present embodiment, parts different from the sixth embodiment will be described. In the present embodiment, the current amount reduction control circuit 70 is in a state where the switching signal for turning on the switching element 50 is being input to the driver circuit 40, and after the switching signal is input to the driver circuit 40, The timer time until the switching element 50 is driven is measured, and when the measured time reaches the timer time, a current amount reduction signal is output.

  FIG. 11 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the current amount reduction control circuit 70 according to this embodiment includes an inverter 74, a delay circuit 75, and an AND circuit 73.

  The inverter 74 is an inverting element that inverts the switching signal (IN) and inputs the inverted signal to the delay circuit 75. The delay circuit 75 is a timer circuit that delays and outputs a signal input from the inverter 74 by a preset timer time. The output (TIMER_OUT) of the delay circuit 75 is a high level signal until the timer time elapses, and becomes a low level signal when the timer time elapses. The timer time is set to a time until the switching element 50 is turned on.

  FIG. 12A shows a specific circuit configuration of the delay circuit 75. As shown in this figure, the delay circuit 75 includes a resistor 75a, a capacitor 75b, and an inverter 75c. That is, the delay circuit 75 is configured as a CR circuit, and is configured to delay the input signal by a time constant (timer time), invert it by the inverter 75c, and output it.

  For the resistor 75a shown in FIG. 12 (a), a variable resistor may be adopted as shown in FIG. 12 (b). Thereby, the timer time can be adjusted to the time until the switching element 50 is turned on by trimming the resistance value.

  In this embodiment, the AND circuit 73 is configured to turn on or off the switch 31 of the constant current generator 30 based on the switching signal (IN) and the output (TIMER_OUT) of the delay circuit 75. That is, when both the switching signal and the output of the delay circuit 75 are at the high level, the AND circuit 73 outputs the high level signal as an off command for the current amount reduction signal, and turns on the switch 31 of the constant current generating unit 30. . On the other hand, when at least one of the switching signal and the output of the delay circuit 75 is at a low level, the AND circuit 73 outputs a low level signal as an ON command for the current amount reduction signal, and the switch 31 of the constant current generating unit 30. Turn off.

  Thus, the current amount reduction control circuit 70 according to the present embodiment measures the timer time from when the switching signal is input to the driver circuit 40 by the delay circuit 75 until the driver circuit 40 turns on the switching element 50, At this timing, the current (I_OUT) of the constant current generator 30 is reduced.

  Next, the operation of the load driving device shown in FIGS. 11 and 12 will be described with reference to the timing chart of FIG.

  First, when the switching signal (IN) becomes high level at time T20, the output (BUFOUT) of the driver circuit 40 starts to rise. Since a low level signal is input to the delay circuit 75 via the inverter 74, the output (TIMER_OUT) of the delay circuit 75 is set to the high level, that is, the amount of current is reduced by the inverter 75c until the timer time (delay) elapses. Signal off command. For this reason, since the constant current generating unit 30 turns on the switch 31, the output (I_OUT) of the constant current generating unit 30 is the sum of the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33. The first current amount. Therefore, the constant current generation unit 30 supplies the constant current of the first current amount to the driver circuit 40.

  Subsequently, since the timer time (delay) has elapsed at time T21, the output (TIMER_OUT) of the delay circuit 75 becomes a low level, that is, an ON command for the current amount reduction signal, by the inverter 75c. For this reason, the constant current generator 30 turns off the switch 31. Therefore, the output (I_OUT) of the constant current generator 30 is a second current amount smaller than the first current amount, and the amount of current supplied to the driver circuit 40 is reduced.

  Thereafter, at time T22, the switching signal (IN) becomes low level, and the switching element 50 is turned off. Further, the output (TIMER_OUT) of the delay circuit 75 becomes a high level at a time T23 after the timer time (delay) has elapsed from the time T22, but the output (IN_CUR) of the AND circuit 73 since the switching signal (IN) is at a low level. ) Is a low level (current amount reduction signal ON command). For this reason, even if the output (TIMER_OUT) of the delay circuit 75 becomes high level, the amount of current supplied to the driver circuit 40 does not increase.

  As described above, by providing the load driving device with the current amount reduction control circuit 70 that measures the timer time by the delay circuit 75, the current amount reduction signal can be generated without inputting the current amount reduction signal from the outside. Can do.

  In the present embodiment, a CR circuit is described as an example of the delay circuit 75. However, a digital timer that counts time using a clock may be employed. As for the correspondence between the description of this embodiment and the description of the claims, the delay circuit 75 corresponds to the “timer circuit” of the claims.

(Eighth embodiment)
In the present embodiment, parts different from the sixth embodiment will be described. FIG. 14 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, it is also possible to adopt a configuration in which the power element 10 is employed as the load 10 and the current amount reduction control circuit 70 is provided in the pre-driver unit 60. Note that a Pch-type MOSFET is employed as the switching element 50 shown in FIG.

  Note that “ON of the power element 10” indicates conduction, and “OFF of the power element 10” indicates cutoff. The same applies to other embodiments.

  Thus, when the power element 10 is employed as a load, the driver circuit 40 turns off the switching element 50 to apply a voltage to the gate of the power element 10, and after the power element 10 is turned on, a constant current to the driver circuit 40 is applied. The amount will be reduced. Therefore, in the present embodiment, the current amount reduction control circuit 70 compares the gate voltage of the power element 10 with the comparator threshold when the switching signal is input to the driver circuit 40 and the power element 10 is turned on. And an ON command for the current amount reduction signal is output at the timing. That is, the comparator 72 of the current amount reduction control circuit 70 compares the gate voltage of the power element 10 with the comparator threshold value.

  With such a configuration, the current amount reduction signal can be generated without inputting the current amount reduction signal from the outside, and the current amount of the constant current generation unit 30 can be reduced.

(Ninth embodiment)
In the present embodiment, parts different from the seventh embodiment will be described. FIG. 15 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, it is also possible to adopt a configuration in which the power element 10 is employed as the load 10 and the current amount reduction control circuit 70 shown in FIG. In FIG. 15, the switching element 50 is a Pch type.

  In this case, the current amount reduction control circuit 70 delays the timer time from when the switching signal is input to the driver circuit 40 until the power element 10 is turned on while the switching signal is input to the driver circuit 40. The measurement is performed by the circuit 75, and when the measurement time reaches the timer time, an ON command for the current amount reduction signal is output. That is, the timer time according to the present embodiment is set to the time until the power element 10 is turned on.

  As described above, the current amount reduction control circuit 70 provided in the load driving device can be configured by the delay circuit 75.

(10th Embodiment)
In the present embodiment, parts different from the eighth embodiment will be described. FIG. 16 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the resistor 61 that pulls up the gate of the power element 10 may be replaced with a constant current source 62. In this case, the switching element 50 is a Pch type MOSFET.

  The constant current source 62 is a current source that supplies a constant current to the gate of the power element 10 until the gate voltage of the power element 10 reaches a predetermined voltage, that is, an ON voltage when the switching element 50 is turned off. As described above, the gate of the power element 10 may be driven by a constant current supplied from the constant current source 62.

  As for the correspondence between the description of the present embodiment and the description of the scope of claims, the constant current source 62 corresponds to the “third constant current source” of the scope of claims.

(Eleventh embodiment)
In the present embodiment, parts different from the ninth embodiment will be described. FIG. 17 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, even when the current amount reduction control circuit 70 is configured by the delay circuit 75, the resistor 61 that pulls up the gate of the power element 10 is connected to the constant current source as in the tenth embodiment. 62 can be substituted.

  As for the correspondence between the description of the present embodiment and the description of the scope of claims, the constant current source 62 corresponds to the “third constant current source” of the scope of claims.

(Twelfth embodiment)
In the present embodiment, parts different from the tenth and eleventh embodiments will be described. In the tenth and eleventh embodiments, the constant current source 62 is used to drive the switching element 50 at a constant current. Therefore, it is a feature of the load driving device according to the present embodiment that the current amount reduction signal is generated using the current flowing through the constant current source 62.

  FIG. 18 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the load driving device includes a pre-driver unit 60 composed of a constant current generating unit 30 and a driver circuit 40, a constant current source 62 that drives by driving a constant current through the gate of the power element 10, A switching element 50 that switches on / off of the power element 10 and a current amount control circuit 80 are provided. The entire circuit configuration for driving the power element 10 as a load includes a current sensor 63 that monitors the current amount of the constant current source 62.

  As in the tenth and eleventh embodiments, the constant current source 62 supplies a constant current (I_OUT_IGBT) to the switching element 50 until the gate of the power element 10 reaches the ON voltage when the switching element 50 is turned off.

  The current sensor 63 is a sensor that detects a current flowing through the constant current source 62. As the current sensor 63, a current detection sensor based on non-contact magnetic field detection such as a Hall element is employed. Further, in the present embodiment, the current sensor 63 is configured to output a high level signal when the detected current exceeds the determination threshold, and to output a low level signal when the detected current falls below the determination threshold. Has been.

  The current amount control circuit 80 is a circuit that outputs a current amount reduction signal based on the switching signal (IN) and the determination result (IGBT_CUR) of the current sensor 63. Specifically, the current amount control circuit 80 inputs the switching signal and the detection result of the current sensor 63, and the determination result input from the current sensor 63 after the switching signal for turning on the power element 10 is input is the determination threshold value. When the value is less than, an ON command for the current amount reduction signal is output.

  FIG. 19 is a diagram showing a specific circuit configuration of the current amount control circuit 80. As shown in FIG. 19, the current amount control circuit 80 includes an inverter 81, a D flip-flop 82 (DFF), an inverter 83, and an AND circuit 84.

  The inverter 81 inverts the determination result of the current sensor 63 and inputs it to the CLK terminal of the D flip-flop 82. A constant voltage is applied from the power source to the input of the D flip-flop 82. Therefore, the output (B) of the D flip-flop 82 is controlled at the timing when the output (A) of the inverter 81 changes from the low level to the high level. The inverter 83 inverts the output (B) of the D flip-flop 82 and inputs it to the AND circuit 84.

  The AND circuit 84 performs an output (IN_CUR) for turning on or off the switch 31 of the constant current generating unit 30 based on the switching signal (IN) and the output (C) of the inverter 83. When both the switching signal and the output (C) of the inverter 83 are at the high level, the AND circuit 84 outputs the high level signal as an off command for the current amount reduction signal, and turns on the switch 31 of the constant current generator 30. . On the other hand, when at least one of the switching signal and the output (C) of the inverter 83 is at low level, the AND circuit 84 outputs a low level signal as an on command for the current amount reduction signal, and the constant current generator 30 Switch 31 is turned off.

  Thus, the current amount control circuit 80 is configured to reduce the current (I_OUT) of the constant current generator 30 based on the current flowing through the constant current source 62.

  Next, the operation of the load driving device shown in FIG. 18 will be described with reference to the timing chart of FIG.

  First, at time T30, the switching signal (IN) becomes high level. In addition, since no current flows through the constant current source 62, the determination result of the current sensor 63 is a low level output (I_OUT_IGBT). For this reason, the output (A) of the inverter 81 remains at a high level, and the output (B) of the D flip-flop 82 is also at a low level. Therefore, since the output (C) of the inverter 83 is at a high level, the output (IN_CUR) of the AND circuit 84 is an off command for the current amount reduction signal. As a result, the output (I_OUT) of the constant current generation unit 30 becomes the first current amount obtained by adding the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33, and the constant current generation unit 30. Supplies a constant current of the first current amount to the driver circuit 40. As a result, the output (BUFOUT) of the driver circuit 40 starts to increase according to the first current amount.

  Subsequently, when the switching element 50 is turned off by the driver circuit 40 at time T31, the current (I_OUT_IGBT) flowing through the constant current source 62 rises and the gate voltage (IGBT_GATE) of the power element rises.

  When the current (I_OUT_IGBT) flowing through the constant current source 62 exceeds the determination threshold at time T32, the determination result (IGBT_CUR) of the current sensor 63 becomes high level, and therefore the output (A of the inverter 81 of the current amount control circuit 80) ) Goes from high to low.

  After this, the gate voltage level of the power element 10 rises, and at time T33 when it rises to the power supply voltage level of the constant current source 62, the current stops flowing from the constant current source 62. Therefore, the current flowing through the constant current source 62 (I_OUT_IGBT) Is below the determination threshold. For this reason, since the determination result (IGBT_CUR) of the current sensor 63 becomes low level, the output (A) of the inverter 81 of the current amount control circuit 80 changes from low level to high level. At this timing, the output (B) of the D flip-flop 82 becomes high level, and the output (C) of the inverter 83 becomes low level. Therefore, the output (IN_CUR) of the AND circuit 84 becomes an ON command for the current amount reduction signal. . Therefore, since the constant current generating unit 30 turns off the switch 31, the output (I_OUT) of the constant current generating unit 30 causes the current flowing through the second constant current source 33 to have a second current amount smaller than the first current amount. A constant current is supplied to the driver circuit 40.

  Thereafter, when the switching signal (IN) becomes low level at time T34, the output (IN_CUR) of the AND circuit 84 of the current amount control circuit 80 becomes low level. That is, the on-command for the current amount reduction signal is continued.

  As described above, by using the current flowing through the constant current source 62, it is possible to generate the current amount reduction signal without inputting the current amount reduction signal from the outside, and the current amount of the constant current generation unit 30 can be generated. Can be reduced.

  In the present embodiment, the current sensor 63 determines that current is flowing using the determination threshold value, and outputs the determination result. However, the current sensor 63 may simply detect the current, or the current amount control circuit 80 may determine whether or not the current exceeds the determination threshold.

(13th Embodiment)
In the present embodiment, parts different from the eighth embodiment will be described. FIG. 21 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the logic of the gate ON of the power element 10 is matched to that of the eighth embodiment by using the driver circuit 40 of the pre-driver unit 60 as an inverted output and the switching element 50 as an Nch type MOSFET. Can do.

  Further, the present embodiment is adopted when the power element 10 is turned off, and the output of the driver circuit 40 becomes high level, that is, the switching element 50 is turned on, and the gate voltage of the power element 10 becomes low level. When the current amount is reduced, the current amount reduction signal generated by the current amount reduction control circuit 70 supplies the current amount of the constant current generation unit 30 to the driver circuit 40 as a second current amount smaller than the first current amount. Even when the power element 10 is turned off, the same effect as the fifth embodiment can be obtained.

  The current amount reduction control circuit 70 includes a NOR circuit 73a that outputs a NOR logic between the switching signal (IN) and the output of the comparator 72 (COMP_OUT). The output (IN_CUR) of the NOR circuit 73a becomes a current amount reduction signal.

(14th Embodiment)
In this embodiment, parts different from the thirteenth embodiment will be described. FIG. 22 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, similarly to the tenth and eleventh embodiments, the gate of the power element 10 can be driven with a constant current by the constant current supplied from the constant current source 62.

  In the thirteenth embodiment and the present embodiment, the configuration using the comparator 72 as the current amount reduction control circuit 70 has been described as an example. However, the delay circuit 75 may be used as the current amount reduction control circuit 70 as a matter of course.

(Fifteenth embodiment)
In this embodiment, parts different from the thirteenth embodiment will be described. FIG. 23 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, a Pch type MOSFET and an Nch type MOSFET are connected from the power supply 20 side between the power supply 20 and the reference voltage line, and an inverter is constituted by these switching elements 50 and 51. ing.

  Specifically, the switching element 50 corresponds to the switching element 50 shown in the thirteenth embodiment, and in this embodiment, a Pch type switching element 51 is provided instead of the resistor 61 in the configuration according to the thirteenth embodiment. It has been configured.

  The gate of the power element 10 is connected to an intermediate point between the switching element 50 and the switching element 51. Therefore, when the output (BUFOUT) of the driver circuit 40 is at a high level, the switching element 50 is turned on and the switching element 51 is turned off, so that the gate voltage of the power element 10 decreases. On the other hand, when the output (BUFOUT) of the driver circuit 40 is at a low level, the switching element 50 is turned off and the switching element 51 is turned on, so that the gate voltage of the power element 10 is increased.

  Next, the operation of the load driving device shown in FIG. 23 will be described with reference to the timing chart of FIG.

  First, when the switching signal (IN) is at a high level, the driver circuit 40 performs an inverted output, so that the output (BUFOUT) of the driver circuit 40 is at a low level. Since the switching element 50 is turned off and the switching element 51 is turned on, the gate voltage (IGBT_GATE) of the power element 10 is at a high level, and the power element 10 is turned on.

  Further, since the switching signal (IN) is at a high level, the output (IN_CUR) of the NOR circuit 73a is at a low level, that is, an on command for a current amount reduction signal. As a result, the constant current generation unit 30 supplies the constant current of the second current amount to the driver circuit 40.

  Subsequently, when the switching signal (IN) becomes low level at time T40, the switching element 50 is turned on and the switching element 51 is turned off, so that the gate voltage (IGBT_GATE) of the power element 10 starts to drop. Immediately after time T40, the gate voltage (IGBT_GATE) of the power element 10 is at a level equal to or higher than the comparator threshold, so the output (COMP_OUT) of the comparator 72 is at a low level.

  Then, when the gate voltage (IGBT_GATE) of the power element 10 falls below the comparator threshold value at time T41, the output (COMP_OUT) of the comparator 72 becomes high level. As a result, even if the switching signal (IN) is at a low level, the output (IN_CUR) of the NOR circuit 73a becomes a low level, that is, an on command for a current amount reduction signal, and the constant current generating unit 30 has a first current amount smaller than the first current amount. A constant current of two current amounts is supplied to the driver circuit 40.

  Thereafter, when the switching signal (IN) goes to a high level to turn on the power element 10 at time T42, the output (BUFOUT) of the driver circuit 40 goes to a low level. Thereby, since the switching element 50 is turned off and the switching element 51 is turned on, the gate voltage starts to rise.

  When the gate voltage (IGBT_GATE) of the power element 10 exceeds the comparator threshold value at time T43, the output (COMP_OUT) of the comparator 72 becomes low level. At this time, since the switching signal (IN) is already at the high level, the output (IN_CUR) of the NOR circuit 73a is at the low level, that is, the on-command of the current amount reduction signal is continued, and the current supplied to the driver circuit 40 The amount will not increase.

  As described above, the switching elements 50 and 51 that drive the power element 10 can also have an inverter configuration. Regarding the correspondence between the description of the present embodiment and the description of the scope of claims, the switching element 50 and the switching element 51 correspond to “first switching element and second switching element” of the scope of claims.

(Sixteenth embodiment)
In the present embodiment, parts different from the above embodiments will be described. In general, the drive portion of the power element 10 such as an IGBT is accompanied by a short circuit and overcurrent protection function of the power element 10. In this plan, when a short circuit (overcurrent) signal is input to the protection function, the gate of the power element 10 is provided. A configuration is adopted in which the voltage is clamped to a constant voltage to determine whether or not a short circuit (overcurrent) has occurred.

  FIG. 25 is a specific circuit diagram of the load driving device according to the present embodiment. As shown in this figure, the pre-driver unit 60 includes a constant current generation unit 30, a driver circuit 40, and a current amount reduction control circuit 70. The overall configuration for driving the power element 10 is further A switching circuit 50, a constant current circuit 64, and a clamp circuit 65 are provided.

  The driver circuit 40 is configured to drive the switching element 50, which is an Nch type MOSFET, by an inverted output. In the present embodiment, the constant current generator 30 includes the switch 31 (SW-A in FIG. 2), the first constant current source 32, and the second constant current source 33 shown in FIG. 2 of the first embodiment. The provided structure is adopted.

  The constant current circuit 64 is connected between the power supply 20 and the switching element 50, and is fixed to the gate of the power element 10 until the gate of the power element 10 reaches a predetermined voltage (ON voltage) when the switching element 50 is driven. It is a circuit for passing current.

  FIG. 26A is a diagram illustrating a specific circuit configuration of the constant current circuit 64. As shown in this figure, the constant current circuit 64 includes a resistor 64a (R1 in FIG. 26A), a resistor 64b (R2 in FIG. 26A), an operational amplifier 64c, and a constant current generator 64d. , A switching element 64e, a constant current source 64f, and a switching element 64g. In the configuration of the constant current circuit 64 shown in FIG. 26A, a resistor 64b, an operational amplifier 64c, a constant current generation unit 64d, a constant current source 64f, and a pre-driver unit for driving the switching element 64e ( The range enclosed by a one-dot chain line).

  The resistor 64a is a sensing resistor through which a current corresponding to a constant current flowing through the gate of the power element 10 flows. One end of the resistor 64a is connected to the power source 20 (VB in FIG. 26A), and the other end is connected to the switching element 64e. The resistor 64b has one end connected to the power source 20 and the other end connected to the constant current source 64f.

  The operational amplifier 64c serves to adjust the magnitude of the constant current (Iout) that flows to the gate of the power element 10 by feedback controlling the current that flows to the resistor 64a based on the voltage at the other end of the resistor 64b. is there.

  The non-inverting input terminal of the operational amplifier 64c is connected to the connection point between the other end of the resistor 64b and the constant current source 64f. As a result, the first voltage corresponding to the other end of the resistor 64b is applied to the non-inverting input terminal of the operational amplifier 64c. That is, if the voltage of the power supply 20 is VB, the current flowing through the resistor 64b is I3, and the resistance value of the resistor 64b is R2, the first voltage is a voltage obtained by subtracting the reference voltage from the power supply voltage of the power supply 20 (VB-I3 XR2).

  On the other hand, the inverting input terminal of the operational amplifier 64c is connected to the other end of the resistor 64a. As a result, the second voltage corresponding to the other end of the resistor 64a is applied to the inverting input terminal of the operational amplifier 64c. That is, if the current flowing through the resistor 64a is Iout and the resistance value of the resistor 64a is R1, the second voltage is a voltage obtained by subtracting the voltage drop of the resistor 64a from the power supply voltage of the power supply 20 (VB-Iout × R1). Equivalent to.

  The constant current generator 64d is a circuit that generates a constant current that determines the capability of the operational amplifier 64c, that is, the switching speed. As shown in FIG. 26B, the constant current generator 64d includes a switch 31 (SW-A in FIG. 26B), a first constant current source 32, and a second constant current source 33. It has become. Therefore, when the switch 31 is turned on by an on command of the current amount reduction signal, the constant current of the first current amount obtained by adding the current flowing through the first constant current source 32 and the current flowing through the second constant current source 33 together. Is supplied to the operational amplifier 64c. On the other hand, when the switch 31 is turned off, only the current flowing through the second constant current source 33 is supplied to the operational amplifier 64c as a constant current of the second current amount. The configuration of the constant current generating unit 64d is the same as that of the above-described constant current generating unit 30, but other configurations shown in the third embodiment and the like may be used.

  The switching element 64e is a semiconductor element driven by the output of the operational amplifier 64c. In the present embodiment, a Pch type MOSFET is used as the switching element 64e. The gate of the switching element 64e is connected to the output terminal of the operational amplifier 64c, and the source is connected to the other end of the resistor 64a. Further, the drain of the switching element 64 e is connected to the gate of the power element 10.

  The constant current source 64f is a current source that supplies a constant current (I3) to the resistor 64b, and is connected between the other end of the resistor 64b and a reference voltage line such as a ground.

  The switching element 64g provided in the constant current circuit 64 is connected between the power supply 20 and the output terminal of the operational amplifier 64c. The switching element 64g is driven by a switching signal. In the present embodiment, a Pch-type MOSFET is employed as the switching element 64g. Therefore, the source of the switching element 64g is connected to the power supply 20, and the drain is connected to the output terminal of the operational amplifier 64c.

  In the constant current circuit 64 having the above configuration, the magnitude of the current flowing through the resistor 64a so that the first voltage corresponding to the other end of the resistor 64a and the second voltage corresponding to the other end of the resistor 64b are equal. Feedback control.

  Specifically, since the potentials of the input terminals of the operational amplifier 64c of the constant current circuit 64 are the same, the first voltage (VB-Iout × R1) corresponding to the other end of the resistor 64a and the other end of the resistor 64b. The operational amplifier 64c controls the switching element 64e so that the second voltage (VB-I3 × R2) corresponding to the side becomes equal. Therefore, the constant current Iout flowing through the resistor 64a is Iout = (R2 / R1) × I3, and the current flowing through the resistor 64a flows to the gate of the power element 10 as a constant constant current.

  As represented by the above formula (Iout = (R2 / R1) × I3), a current proportional to the magnitude of the current flowing through the resistor 64b flows through the resistor 64a. Since the current I3 of the constant current source 64f flows through the resistor 64b, a current proportional to the current I3 flows through the resistor 64a.

  The clamp circuit 65 avoids sudden fluctuations in the gate voltage by clamping the voltage applied to the gate of the power element 10 to the clamp voltage in accordance with a clamp circuit ON / OFF switching signal input from the outside. It is a circuit that plays a role of preventing destruction due to overshoot or surge at the time of short circuit. The clamp circuit 65 has a configuration in which a switch 65a and a Zener diode 65b are connected in series. The switch 65 a is connected to the gate of the power element 10.

  The clamp circuit 65 is configured to receive an IGBT short circuit detection signal indicating a short circuit of the power element 10, and when the IGBT short circuit detection signal is input, the gate voltage of the power element 10 is smaller than a predetermined voltage. A circuit for clamping to a clamp voltage. The switch 65a is turned on / off according to the IGBT short circuit detection signal. The short circuit of the power element 10 is detected by a short circuit detection circuit (not shown) or the like, and the IGBT short circuit detection signal is input to the clamp circuit 65 of the load driving device.

  The current amount reduction control circuit 70 has a current amount supplied to the constant current circuit 64 at the timing when the switching circuit 50 is turned off and the power device 10 is turned on while the switching signal is input to the driver circuit 40. This is a circuit that issues a reduction signal OFF command, issues a current amount reduction signal OFF command to the constant current generator 30 at a timing when the driver circuit 40 turns on the switching element 50 and the power element 10 turns off. Specifically, the current amount reduction control circuit 70 includes a comparator 72, an AND circuit 73, a reference voltage source 76, a reference voltage source 77, an OR circuit 78, and a NOR circuit 79.

  The reference voltage source 76 is a voltage source in which a gate H determination threshold level for determining whether or not the gate voltage (IGBT_GATE) of the power element 10 is at a high level is set. The reference voltage source 77 is a voltage source in which a gate L determination threshold level for determining whether or not the gate voltage (IGBT_GATE) of the power element 10 is at a low level is set.

  The connection of the reference voltage source 76 and the reference voltage source 77 to the non-inverting input terminal of the comparator 72 is switched by the output (COMP_OUT) of the comparator 72. When the output (COMP_OUT) of the comparator 72 is at a high level, the reference voltage source 76 in which the gate H determination threshold level is set is switched. On the other hand, when the output (COMP_OUT) of the comparator 72 is at a low level, the reference voltage source 77 is set to the gate L determination threshold level. Therefore, the comparator 72 outputs a high level signal when the gate voltage (IGBT_GATE) of the power element 10 falls below the gate L determination threshold level, and goes low when the gate voltage (IGBT_GATE) of the power element 10 exceeds the gate H determination threshold level. A level signal is output.

  The AND circuit 73 outputs a high level signal only when both the switching signal (IN) and the output of the comparator 72 (COMP_OUT) are at a high level.

  The OR circuit 78 outputs a high level signal when either the AND circuit 73 or the IGBT short circuit detection signal is at a high level. The output (IN_CUR1) of the OR circuit 78 corresponds to a current amount reduction signal for controlling the current amount (Pre_Iout1) of the constant current circuit 64. In the present embodiment, the OR circuit 78 receives a low level signal as an IGBT short circuit detection signal after the high level signal is input as an IGBT short circuit detection signal from the outside until the input of the IGBT short circuit detection signal is cancelled. Until this time, the command to turn off the current amount reduction signal is issued.

  The NOR circuit 79 outputs a high level signal only when both the switching signal (IN) and the output of the comparator 72 (COMP_OUT) are at a low level. The output (IN_CUR2) of the NOR circuit 79 corresponds to a current amount reduction signal for controlling the current amount (Pre_Iout2) of the constant current generating unit 30.

  In the OR circuit 78 and the NOR circuit 79, when the output is low level, it corresponds to the on command of the current amount reduction signal, and when the output is high level, it corresponds to the off command of the current amount reduction signal.

  According to the configuration of the load driving apparatus as described above, the current amount reduction control circuit 70 determines the amount of current to be supplied to the driver circuit 40 in accordance with the ON command or the OFF command of the current amount reduction signal that is the output (IN_CUR2) of the NOR circuit 79. Control.

  The constant current circuit 64 determines the magnitude of the first current amount in accordance with the current amount reduction signal OFF command that is the output (IN_CUR1) of the current amount reduction control circuit 70 until the ON time when the power element is turned on is reached. The gate of the power element 10 is driven with a constant current by the current. After the on-time when the power element 10 is turned on, the constant current circuit 64 is smaller than the first current amount according to the on-command of the current amount reduction signal that is the output (IN_CUR1) of the current amount reduction control circuit 70. The switching element 64e is driven by the constant current of the second current amount.

  Specifically, the operation of the load driving device will be described with reference to the flowchart of FIG. First, the power element 10 is on until time T50. At this time, the constant current generation unit 30 that supplies current to the driver circuit 40 supplies a constant current of the second current amount in accordance with an ON command of the current amount reduction signal from the current amount reduction control circuit 70.

  When the switching signal (IN) becomes low level at time T50 to turn off the power element 10, the NOR circuit 79 of the current amount reduction control circuit 70 receives the low level signal of the switching signal (IN) and the comparator 72. A low level signal is input. For this reason, the output (IN_CUR2) of the NOR circuit 79 becomes an off command for the current amount reduction signal, and the current amount (Pre_Iout2) of the first current amount is supplied from the constant current generation unit 30 to the driver circuit 40. Since the output (COMP_OUT) of the comparator 72 is at a low level, the threshold value of the comparator 72 is set to the gate L determination threshold level.

  Subsequently, when the gate voltage (IGBT_GATE) of the power element 10 decreases after time T50 and the gate voltage (IGBT_GATE) of the power element 10 falls below the gate L determination threshold level at time T51, the output (COMP_OUT) of the comparator 72 becomes high. Become a level. For this reason, the output (IN_CUR2) of the NOR circuit 79 becomes an ON command for the current amount reduction signal, and the current (Pre_Iout2) having a second current amount smaller than the first current amount is supplied from the constant current generating unit 30 to the driver circuit 40. Is done.

  As described above, at the time T50 to T51, the gate of the power element 10 is quickly lowered by increasing the amount of current supplied to the driver circuit 40 and quickly turning on the Nch type switching element 50. . Further, since the low level signal of the comparator 72 is input to the AND circuit 73 of the current amount reduction control circuit 70, the output to the OR circuit 78 is also low level, and the IGBT short circuit detection signal input to the OR circuit 78 is also low. Is a level. For this reason, the output command (IN_CUR1) of the current amount reduction control circuit 70 for the constant current circuit 64 is continuously commanded to turn on the current amount reduction signal.

  Subsequently, when the switching signal (IN) becomes a high level at time T52 to turn on the power element 10, the AND circuit 73 of the current amount reduction control circuit 70 receives the high level signal of the switching signal (IN) and the comparator 72. The high level signal is input. For this reason, since the output of the AND circuit 73 is at a high level, the output (IN_CUR1) of the OR circuit 78 to the constant current generator 64d of the constant current circuit 64 is an off command for the current amount reduction signal. Therefore, the amount of current (Pre_Iout1) supplied to the operational amplifier 64c increases to the first amount of current. For this reason, since the amount of current (Iout) flowing from the constant current circuit 64 to the switching element 50 increases at time T53, the gate voltage of the power element 10 quickly rises according to the amount of current (Iout) of the constant current circuit 64. Since the output (COMP_OUT) of the comparator 72 is at a high level, the threshold value of the comparator 72 is set to the gate H determination threshold level.

  Thereafter, when the gate voltage (IGBT_GATE) of the power element 10 exceeds the gate H determination threshold level at time T53, the output (COMP_OUT) of the comparator 72 becomes low level. For this reason, since the output of the AND circuit 73 is at a low level, the output (IN_CUR1) of the OR circuit 78 is an ON command for the current amount reduction signal, and is smaller than the first current amount from the constant current generator 64d to the operational amplifier 64c. A second amount of current (Pre_Iout1) is supplied.

  As described above, at the time points T52 to T54 described above, the amount of current supplied from the constant current circuit 64 to the gate of the power element 10 is increased by increasing the amount of current supplied to the operational amplifier 64c of the constant current circuit 64. The gate of the element 10 is quickly started up. Further, since a high level signal is input as the switching signal (IN) to the NOR circuit 79 of the current amount reduction control circuit 70, the output (IN_CUR2) of the NOR circuit 79 becomes a low level. For this reason, the output command (IN_CUR2) of the current amount reduction control circuit 70 for the constant current generation unit 30 is continuously commanded to turn on the current amount reduction signal.

  Here, the gate voltage of the power element 10 passes through the mirror period and the clamp voltage holding period from time T52 to T54, and becomes a full-on period after time T54. The gate voltage in the mirror section is a mirror voltage determined by characteristics such as the amplification factor of the IGBT that is the power element 10, and is a voltage that first becomes a constant voltage after time T52. A section where the gate voltage becomes a constant voltage again after the mirror section is a clamp voltage holding section. In this clamp voltage holding section, the switch 65a is turned on in accordance with the clamp circuit ON / OFF switching signal input to the clamp circuit 65, and the gate voltage is held at the clamp voltage. Thereby, the surge destruction at the time of the short circuit of the power element 10 at the time of start-up is prevented. When the switch 65a is turned off by the clamp circuit ON / OFF switching signal, the gate voltage rises, and the power element 10 is fully turned on at time T54.

  Next, an operation when a short circuit of the power element 10 is detected while the power element 10 is turned on will be described with reference to FIG. In FIG. 28, the operation is the same as that described above until time T54. A broken line waveform shown in FIG. 28 indicates a normal operation when the power element 10 is not short-circuited.

  When a short circuit of the power element 10 is detected at time T55, the clamp circuit ON / OFF switching signal for turning on the switch 65a of the clamp circuit 65 and the high level of the IGBT short circuit detection signal are input to the load driving device at this timing. The As a result, the clamp circuit 65 tries to hold the gate voltage at the clamp voltage, so that the gate voltage falls from the full-on state to the clamp voltage.

  Further, since the high level of the IGBT short circuit detection signal is input to the OR circuit of the current amount reduction control circuit 70, the output (IN_CUR1) of the OR circuit 78 serves as an off command for the current amount reduction signal. Along with this, since the amount of current (Pre_Iout1) of the constant current generating unit 64d of the constant current circuit 64 increases, the output (AMP_OUT) of the operational amplifier 64c also increases. That is, the current reduction of the constant current generator 64d is canceled at the timing when the short-circuit of the power element 10 is detected, and the current capability of the operational amplifier 64c that has been lowered is restored. As a result, as shown by the portion surrounded by the dotted line in FIG. 28, it does not take time to reach the output stable level of the operational amplifier 64c at the time of clamping. Thus, since the current capability of the operational amplifier 64c is restored, the responsiveness of the circuit for controlling the constant current is improved, and the overshoot of the current (Iout) after the time T55 is reduced.

  On the other hand, when the current capability of the operational amplifier 64c of the constant current circuit 64 is not recovered, the slew rate of the operational amplifier 64c remains low, the control of the gate of the switching element 64e is delayed, and the system constituting the constant current circuit 64 The overall responsiveness deteriorates. For this reason, it takes time until the output (AMP_OUT) is stabilized, as indicated by the one-dot chain line in the portion surrounded by the dotted line in FIG. For this reason, the overshoot of the driving constant current (Iout) is large and the period becomes long, leading to an increase in current consumption and heat generation.

  Therefore, as described above, when the power element 10 is short-circuited, by increasing the current capability of the constant current circuit 64, the responsiveness of the constant current circuit 64 is improved, overshoot is reduced, and current consumption is suppressed.

  Since the power element 10 is turned off after the time T56, the same operation as the above-described time T50 to T51 is performed. As the power element 10 is turned off, the high level of the IGBT short circuit detection signal becomes low level (that is, the input of the IGBT short circuit detection signal is canceled), and the clamp circuit ON / OFF switching signal also becomes low level.

  As described above, when the power element is short-circuited, the current amount reduction control circuit 70 increases the current capability of the constant current circuit 64, thereby suppressing an increase in current consumption of the constant current circuit 64 and the gate of the power element 10. The voltage can be increased quickly.

  In this embodiment, the configuration in which the comparator 72 monitors the gate level of the power element 10 as the current amount reduction control circuit 70 has been described as an example, but the configuration using the delay circuit 75 shown in the seventh embodiment. Alternatively, a configuration using the current amount control circuit 80 shown in the twelfth embodiment may be adopted.

(Other embodiments)
The configuration of the load driving device shown in each of the above embodiments is an example, and the configuration is not limited to the configuration shown above, and other configurations including the features of the present invention may be adopted. For example, the configuration of the constant current generation unit 30 shown in the first embodiment or the third embodiment is an example, and other configurations may be used. Similarly, the configuration of the driver circuit 40 is not limited to that shown in the above embodiments, and other configurations may be used.

  In the first to fourth embodiments, an Nch type MOSFET is employed as the switching element 50, but a Pch type MOSFET may be employed. Even when a Pch-type MOSFET is used as the switching element 50, the principle of reducing the constant current is the same when the output of the driver circuit 40 is at a high level, that is, when the gate potential of the switching element 50 is at a high level. It is. Of course, an Nch type MOSFET may be employed as the switching element 50 in the fifth embodiment. In that case, the pre-driver unit 60 may be configured to correspond to the Nch type switching element 50.

  Further, in the fourth embodiment, the magnitude of the constant current is adjusted by adjusting both the voltage value of the power source 36 and the resistance value of the resistor 34b. The amount of current may be adjusted.

  For example, when the resistance value of the resistor 34b is fixed and the voltage value of the power source 36 is adjusted, the voltage value of the power source 36 is set to the first voltage value according to the current amount reduction signal until the ON time when the switching element 50 is turned on is reached. The constant current of the first current amount is caused to flow through the driver circuit 40. In addition, after the on-time when the switching element 50 is turned on, the voltage value of the power source 36 is set to a second voltage value smaller than the first voltage value in accordance with the current amount reduction signal, whereby the constant current of the second current amount is set. Is supplied to the driver circuit 40. As described above, the amount of constant current flowing through the driver circuit 40 may be adjusted by adjusting only the voltage value of the power source 36.

  On the other hand, when the voltage value of the power source 36 is fixed and the resistance value of the resistor 34b is adjusted, the resistance value of the resistor 34b is set to the first resistance value according to the current amount reduction signal until the ON time when the switching element 50 is turned on is reached. The constant current of the first current amount is caused to flow through the driver circuit 40. In addition, after the on-time when the switching element 50 is turned on, the resistance value of the resistor 34b is set to a second resistance value larger than the first resistance value in accordance with the current amount reduction signal, thereby making the constant current of the second current amount. Is supplied to the driver circuit 40. As described above, the amount of constant current flowing through the driver circuit 40 may be adjusted by adjusting the resistance value of the resistor 34b.

  In the sixth to sixteenth embodiments, the constant current generating unit 30 has been described by taking the example shown in the first embodiment as an example, but of course, other configurations described above may be used.

DESCRIPTION OF SYMBOLS 10 Load 30 Constant current generation part 31 Switch 32 1st constant current source 33 2nd constant current source 34b Resistance 36 Power supply 40 Driver circuit 50 Switching element 60 Pre-driver part

Claims (5)

A switching element (50) connected to a load (10);
A constant current generator (30) for generating a constant current;
The ON time until the switching element (50) is turned on is set to be shorter as the magnitude of the constant current increases, and the ON time corresponding to the magnitude of the constant current flowing from the constant current generator (30) is set. A driver circuit (40) for turning on the switching element (50) in time,
The constant current generator (30) causes a constant current having a first current amount to flow through the driver circuit (40) until an on time is reached when the switching element (50) is turned on. ) Is turned on, a constant current having a second current amount smaller than the first current amount is allowed to flow through the driver circuit (40) after the on-time has elapsed ,
The load (10) is a power element composed of a semiconductor switching element,
The constant current generator (30) and the driver circuit (40) are configured to be a pre-driver unit (60) for driving the power element by driving the switching element (50). And
The driver circuit (40) is adapted to turn on the power element by driving the switching element (50) according to the switching signal.
The pre-driver unit (60) drives the switching element (50) with a constant current having a magnitude of the first current amount until the on-time when the power element is turned on, and turns on the power element. A load driving device configured to drive the switching element (50) with a constant current having a second current amount smaller than the first current amount after time has elapsed,
A constant current circuit (64) for turning on the power element by passing a constant current to the gate of the power element until the gate voltage of the power element reaches a predetermined voltage when the switching element (50) is turned off;
A short circuit detection signal indicating a short circuit of the power element is input, and when the short circuit detection signal is input, a clamp circuit that clamps the gate voltage of the power element to a clamp voltage smaller than the predetermined voltage ( 65)
A current amount reduction control circuit (70) that outputs a current amount reduction signal for causing the constant current of the second current amount to flow at a timing when the power element is turned on after the switching signal is input to the driver circuit (40). ) And
The constant current circuit (64) has a magnitude of the first current amount according to the current amount reduction signal input from the current amount reduction control circuit (70) until an ON time when the power element is turned on is reached. The power element is driven with a constant current by a constant current, and after the on-time when the power element is turned on, the power is driven by a constant current having a second current amount smaller than the first current amount according to the current amount reducing signal. Drive the element at a constant current,
The current amount reduction control circuit (70) is configured to receive the short-circuit detection signal, and from the input of the short-circuit detection signal until the input of the short-circuit detection signal is canceled. A load driving device that outputs a current amount reduction signal for flowing a constant amount of current . The constant current generator (30)
A switch (31) that is turned on or off in accordance with a signal for reducing the amount of current;
A first constant current source (32) connected to the switch (31);
A second constant current source (33) connected in parallel to a series path of the switch (31) and the first constant current source (32),
The driver circuit (40) is configured to turn on the switching element (50) in accordance with a switching signal for turning on the switching element (50).
The switch (31) is turned on in accordance with the on command of the current amount reduction signal until the on time when the switching element (50) is turned on, whereby the current flowing through the first constant current source (32) A current summed with a current flowing through the second constant current source (33) is generated as a constant current of the first current amount;
After the on-time when the switching element (50) is turned on, the switch (31) is turned off in accordance with the turn-off command of the current amount reduction signal, so that the current flowing through the second constant current source (33) is reduced. The load driving device according to claim 1, wherein the load driving device is generated as a constant current of the second current amount. The constant current generator (30)
A first constant current source (32) for generating a constant current of the first current amount;
A second constant current source (33) for generating a constant current of the second current amount;
The constant current of the first current amount flows from the first constant current source (32) to the driver circuit (40) according to the current amount reduction signal until the ON time when the switching element (50) is turned on is reached. After the connection is switched and the on-time when the switching element (50) is turned on has elapsed, the second current amount is fixed from the second constant current source (33) to the driver circuit (40) according to a current amount reduction signal. A switch (31) for switching the connection so that a current flows,
The load driving device according to claim 1, wherein the driver circuit (40) is configured to turn on the switching element (50) in accordance with a switching signal for turning on the switching element (50). . The constant current generator (30) includes a variable power source (36) capable of varying a voltage value, and is configured such that the amount of the constant current increases as the voltage value increases.
The driver circuit (40) is configured to turn on the switching element (50) in accordance with a switching signal for turning on the switching element (50).
The constant current of the first current amount is set to the first voltage value by setting the voltage value of the variable power source (36) to the first voltage value in accordance with the current amount reduction signal until the ON time when the switching element (50) is turned on is reached. Flow to the driver circuit (40),
After the ON time when the switching element (50) is turned on, the voltage value of the variable power source (36) is set to a second voltage value smaller than the first voltage value according to a current amount reduction signal. 2. The load driving device according to claim 1, wherein a constant current having a second current amount is passed through the driver circuit. The constant current generator (30) includes a variable resistor (34b) capable of varying a resistance value, and is configured such that the amount of the constant current decreases as the resistance value increases.
The driver circuit (40) is configured to turn on the switching element (50) in accordance with a switching signal for turning on the switching element (50).
The constant current of the first current amount is set to the first resistance value by setting the resistance value of the variable resistor (34b) to the first resistance value according to the current amount reduction signal until the on-time when the switching element (50) is turned on. Flow to the driver circuit (40),
After the ON time when the switching element (50) is turned on, the resistance value of the variable resistor (34b) is set to a second resistance value larger than the first resistance value in accordance with a current amount reduction signal. 5. The load driving device according to claim 1, wherein a constant current having a second current amount is passed through the driver circuit.

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