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EP0361353B1 - Circuit de contrôle alimenté en courant continu pour une électrovanne - Google Patents

Circuit de contrôle alimenté en courant continu pour une électrovanne Download PDF

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Publication number
EP0361353B1
EP0361353B1 EP89117647A EP89117647A EP0361353B1 EP 0361353 B1 EP0361353 B1 EP 0361353B1 EP 89117647 A EP89117647 A EP 89117647A EP 89117647 A EP89117647 A EP 89117647A EP 0361353 B1 EP0361353 B1 EP 0361353B1
Authority
EP
European Patent Office
Prior art keywords
resistor
voltage
comparator
control circuit
capacitor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP89117647A
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German (de)
English (en)
Other versions
EP0361353A1 (fr
Inventor
Derk Vegter
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Honeywell BV
Original Assignee
Honeywell BV
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Filing date
Publication date
Application filed by Honeywell BV filed Critical Honeywell BV
Publication of EP0361353A1 publication Critical patent/EP0361353A1/fr
Application granted granted Critical
Publication of EP0361353B1 publication Critical patent/EP0361353B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/22—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for supplying energising current for relay coil
    • H01H47/32—Energising current supplied by semiconductor device
    • H01H47/325—Energising current supplied by semiconductor device by switching regulator
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings

Definitions

  • the invention relates to a direct current-fed control circuit for a modulating gas solenoid valve of a burner system according to the preamble of claim 1.
  • a pulse width modulator converts the DC supply voltage into a pulse train that alternately charges a capacitor located in the excitation circuit of the solenoid valve and discharges it via the excitation winding of the solenoid valve.
  • the object of the invention is to construct such a control circuit in such a way that errors in the circuit arrangement due to component failure or short circuits cannot lead to an increase in the excitation current and thus also in the gas pressure.
  • the control circuit should therefore be intrinsically safe.
  • the control circuit is supplied between the supply terminals 1 and 2 with a DC voltage U V of, for example, + 30V.
  • a control voltage U S at the input terminal 3 specifies the target value for the current flowing through the coil 4 of the solenoid valve.
  • a constant current generator of conventional design turned on, which consists of a Zener diode Z1, a diode D1, two resistors R1 and R2 and a transistor T1. It feeds a potentiometer consisting of a variable resistor P1 and a fixed resistor R3.
  • the connection point F between adjusting resistor P1 and transistor T1 is connected via a resistor R5 of, for example, 22 kOhm to the non-inverting input of a first comparator CM1 working as an integrating amplifier.
  • the voltage generated at the series resistor R16 by the excitation current through the winding 4 is also fed to this via a resistor R11 of, for example, also 22 kOhm.
  • the voltage U E at the non-inverting input of the comparator CM1 corresponds to half the sum of the voltages U F and U G.
  • the control voltage U S is fed from the input terminal 3 to the inverting input of the comparator CM1.
  • the pulse width modulator II comprises an oscillator which has a third comparator CM3 with feedback resistor R10 between the output and non-inverting input, a second resistor R9 between the output and node B and a charging capacitor C3 which is connected to the DC supply terminal via a resistor R7 1 is connected.
  • the non-inverting input is also connected via a high-resistance resistor R4 to the connection point of diode D1 and resistor R1 in the constant current source.
  • the inventory input is connected to circuit point B via a high-resistance resistor R8.
  • This relaxation oscillator generates a sawtooth voltage that changes, for example, between a minimum value of 10V and a maximum value of 24V with a frequency of 25kHz.
  • This sawtooth voltage U B passes through the resistor R8 to the inventory input of the comparator CM3 and at the same time to the non-inverting input of the second comparator CM2, whose inverting input is at the output C of the amplifier CM1.
  • This output C is also connected to the supply terminal 1 via a high-resistance resistor R6, and a storage capacitor C2 of, for example, 10 ⁇ F lies between the switching point C and ground.
  • a power stage III controlled by the second comparator CM2 comprises three transistors T2, T3 and T4 in addition to three resistors R12, R13 and R14.
  • the input of this power stage is connected to the output D of the comparator CM2, while its output A forms a charging current connection for charging the capacitor C6.
  • This is in series with a low-resistance resistor R15, the field winding 4 and the series resistor R16 between the charging current connection A and ground, a diode D2 of the series connection of the field winding 4 and resistor R16 being connected in parallel in a current-permeable manner in the direction of the ground connection.
  • a switching transistor T5 is also switched on, which is controlled by the output signal of the second comparator CM2 in such a way that either the switching transistor T5 is switched through and at the same time the power stage T2 to T4 is blocked, or conversely the power stage is switched on and the Charging current connection A connects to the supply terminal 1 and at the same time the switching transistor T5 is blocked.
  • the capacitor C6 is charged via the power stage and the diode D2, while in the former case the capacitor C6 is discharged via the excitation winding 4 and the switching transistor T5 and an excitation current thus flows through the excitation winding 4 of the solenoid valve.
  • the frequency and duration of these excitation current pulses determine the degree of opening of the solenoid valve.
  • the capacitor C6 In order to provide sufficient excitation energy for the solenoid valve 4, the capacitor C6 must have a sufficient capacitance of, for example, 47 ⁇ F.
  • capacitors C2 and C3 are discharged before the control circuit is switched on. If voltage is applied to terminals 1 and 2 and the open collector outputs of comparators CM1 and CM2 are initially open, capacitor C3 charges faster than capacitor C2 because it has a lower capacitance of, for example, 390pF than capacitor C2 (10 ⁇ F ).
  • the capacitor C2 is charged via the resistor R6 and the capacitor C3 is charged via the resistor R7, both resistors having a value of, for example, 100 kOhm.
  • the relaxation oscillator therefore begins to oscillate quickly and generates a sawtooth voltage U B at its output B in a voltage range between 10 and 24 V.
  • the non-inverting input of the comparator CM2 therefore receives a positive voltage, while the inverting input is initially still at the potential 0. This results in a positive output signal U D at the output D of the comparator CM2. This blocks the switching transistor T5 and switches through the power stage T2 to T4. The capacitor C6 is consequently charged from the supply voltage between the terminals 1 and 2 via the transistor T4 and the diode D2.
  • the constant current source with the transistor T1 generates a voltage U F of a maximum of 1.5 V at the circuit point F, that is to say at the series connection of the adjusting resistor P1 and the fixed resistor R10. This is determined by a current of approximately 1 mA from the constant current source and by the series connection consisting of potentiometer P1 of, for example, 1KOhm and resistor R3 of, for example, 560 Ohm. Between the circuit points F and G there is a voltage divider consisting of the two resistors R5 and R11 of the same size, so that at the tap E and thus at the non-inverting input of the first comparator CM1 half the sum of these two voltages U F and U G is present.
  • the voltage U C at the output of the comparator CM1 rises until it reaches the value of the sawtooth voltage U B at the non-inverting input of the comparator CM2.
  • the output D of the comparator CM2 switches to a low potential. This has the consequence that the power stage T2 to T4 blocks and the switching transistor T5 turns on.
  • the capacitor C6 is now discharged via the excitation coil 4 of the solenoid valve in a circuit which is formed by the resistor R16, the switching transistor T5 and the resistor R15.
  • the excitation current derived from this charging voltage is linearly dependent on the ratio of the discharge time to the total period of the pulse-shaped voltage at the charging current connection A. This period is for example 40 ⁇ s, which corresponds to a frequency of 25kHz.
  • the pulse / pause ratio changes depending on the voltage U C.
  • the comparator CM1 works as an integrating operational amplifier, so that its output voltage U C corresponds to the time integral of the differential voltage at its two inputs. This difference is regulated by changing the output voltage U C and the pulse / pause ratio and the excitation current through the winding 4 and thus by changing the voltage U G across the series resistor R16 to zero.
  • circuit interruptions and short circuits in individual components either lead to the excitation current being switched off or to a current limitation to a value below the maximum current.
  • the capacitor C6 is short-circuited or its supply line is interrupted, no charge can be stored on it and no current will flow through the excitation winding 4.
  • An interruption of the diode D2 prevents charging as well as a short circuit of the diode D2 prevents current flow through the excitation winding 4.
  • the upper peak value of the sawtooth voltage U B of the oscillator is 24V lower than the supply voltage of 30V.
  • the lower peak value of the sawtooth voltage U B is higher than the ground potential. It is determined by the voltage at the non-inverting input of the comparator CM3 when the open collector output of the comparator CM3 is connected through to the ground line 2. The minimum value of the voltage U B is determined by the voltage divider R4, R10 and the voltage across the resistor R1.
  • the control circuit proves to be intrinsically safe in both directions.
  • the output signal of the comparator CM1 can be worst In this case, the value of the supply voltage U V of, for example, + 30V can be reached and thus safely exceed the upper peak value of the sawtooth voltage.
  • the effect of the comparator CM1 as an integrating operational amplifier leads to the fact that in this case the current through the excitation winding is reduced to zero. The same applies in the event of a short circuit in the Zener diode Z1 or the transistor T1 or in the event of an interruption in the feedback resistor R2.
  • the value of the resistor R15 is selected so that when the supply voltage U V drops to 27V, just enough current flows through the excitation winding 4.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Feedback Control In General (AREA)
  • Magnetically Actuated Valves (AREA)

Claims (8)

  1. Circuit de commande alimenté en courant continu pour une électrovanne à gaz d'une installation de brûleur, qui fonctionne d'une manière modulée et dont l'enroulement d'excitation (4) est branché en série avec un condensateur (C6) et une résistance (R16) entre une borne (A) d'alimentation en courant de charge et un potentiel de référence (2), une diode (D2) passante en direction du potentiel de référence étant branchée en parallèle avec le circuit série formé de I'enroulement (4) et de la résistance (R16), caractérisé par
    a) un premier comparateur (CM1), à une entrée (-) duquel est envoyé un signal de commande à courant continu (US) et dont la seconde entrée (+) est raccordée d'une part par l'intermédiaire d'une première résistance (R5) à une source de courant constant (T1,Z1,D1,R1,R2) et d'autre part par l'intermédiaire d'une seconde résistance (R11) au point de jonction (G) de l'enroulement d'excitation (4) et de la résistance en série (R16);
    b) un circuit série branché entre la source de courant continu (UV) et le potentiel de référence (2) et constitué par une résistance (R6) et un condensateur (C2), dont la prise (C) est raccordée d'une part à la sortie du premier comparateur (CM1) et d'autre part à une entrée (-) d'un second comparateur (CM2);
    c) un oscillateur (R4,R7-R10,C3,CM3), qui produit une tension en dents de scie ayant une fréquence et une amplitude prédéterminées et dont la sortie (B) est raccordée à l'autre entrée (+) du second comparateur (CM2);
    d) un étage de puissance (T2,T3,T4,R13,R14), commandé par le signal de sortie (UD) du second comparateur (CM2) et servant à alimenter la borne (A) d'alimentation du courant de charge pour le condensateur série (C6);
    e) un interrupteur électronique (T5), branché entre la borne (A) d'alimentation en courant de charge et le potentiel de référence et commandé par le signal de sortie (UD) du second comparateur (CM2) et qui réalise un blocage lorsque l'étage de puissance est passant, et est passant lorsque l'étage de puissance est bloqué.
  2. Circuit de commande selon la revendication 1, caractérisé en ce qu'une résistance (R15) de faible valeur ohmique est branchée entre le condensateur en série (C6) et la borne (A) d'alimentation en courant de charge.
  3. Circuit de commande selon la revendication 1, caractérisé en ce que la source de courant constant (T1,Z1,D1,R1,R2) est raccordée, en série avec au moins une résistance (P1,R3).à la source de courant continu d'alimentation (1).
  4. Circuit de commande selon la revendication 3, caractérisé en ce que la résistance (P1) est réglable.
  5. Circuit de commande selon l'une des revendications 1 à 4, caractérisé par un dimensionnement tel de l'oscillateur (R4,R7-R10, C3,CM3) que, lors du fonctionnement normal, la valeur maximale de la tension en dents de scie est inférieure à la tension continue d'alimentation (Uv) et que sa valeur minimale est supérieure au potentiel de masse.
  6. Circuit de commande selon la revendication 5, caractérisé en ce que l'oscillateur contient un troisième comparateur (CM3), dont la sortie est raccordée d'une part par l'intermédiaire d'une première résistance de réaction (R10) à l'entrée non inverseuse (+) et d'autre part par l'intermédiaire d'une seconde résistance (R9) à un condensateur de charge (C3), tandis qu'entre le condensateur de charge (C3) et l'entrée inverseuse (-) est branchée une résistance de forte valeur ohmique (R8), et que l'entrée non inverseuse (+) est raccordée à une tension de référence stabilisée par l'intermédiaire d'une autre résistance de forte valeur ohmique (R4).
  7. Circuit de commande selon la revendication 6, caractérisé en ce que la tension de référence est formée par la tension présente au niveau d'un diviseur de tension (R1,Z1,D1) dans la source de courant constant (Z1,D1,R1,R1,R2,T1).
  8. Circuit de commande selon l'une des revendications 5 à 7, caractérisé en ce que le condensateur de charge (C3) et l'oscillateur (CM3,C3,R7-R10) est raccordé par l'intermédiaire d'une résistance (R7) à la tension continue d'alimentation (Uv).
EP89117647A 1988-09-28 1989-09-25 Circuit de contrôle alimenté en courant continu pour une électrovanne Expired - Lifetime EP0361353B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3832817 1988-09-28
DE3832817A DE3832817A1 (de) 1988-09-28 1988-09-28 Gleichstromgespeiste steuerschaltung fuer ein magnetventil

Publications (2)

Publication Number Publication Date
EP0361353A1 EP0361353A1 (fr) 1990-04-04
EP0361353B1 true EP0361353B1 (fr) 1993-04-28

Family

ID=6363831

Family Applications (1)

Application Number Title Priority Date Filing Date
EP89117647A Expired - Lifetime EP0361353B1 (fr) 1988-09-28 1989-09-25 Circuit de contrôle alimenté en courant continu pour une électrovanne

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EP (1) EP0361353B1 (fr)
DE (2) DE3832817A1 (fr)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2777384B1 (fr) * 1998-04-10 2000-06-23 Europ Equip Menager Dispositif de controle d'une electrovanne pulsee pour circuit de fluide
DE10244522B4 (de) * 2002-09-25 2005-06-30 Karl Dungs Gmbh & Co. Kg Ansteuereinrichtung für eine Magnetspule
CN104595552B (zh) * 2015-01-28 2017-04-05 玉环联帮洁具制造有限公司 一种触控水龙头

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS57121703A (en) * 1981-01-22 1982-07-29 Nippon Denso Co Ltd Driving circuit of electromagnetic operating device
DE3233536A1 (de) * 1982-09-10 1984-04-05 Robert Bosch Gmbh, 7000 Stuttgart Einrichtung zum getakteten regeln eines eine spule durchfliessenden stromes
DE3440885A1 (de) * 1984-11-09 1986-05-15 Robert Bosch Gmbh, 7000 Stuttgart Schaltungsanordnung zum einschalten von magnetventilen
GB8616965D0 (en) * 1986-07-11 1986-08-20 Lucas Ind Plc Drive circuit
DE3701985A1 (de) * 1987-01-23 1988-08-04 Knorr Bremse Ag Vorschaltelektronik fuer ein gleichspannungserregbares geraet

Also Published As

Publication number Publication date
DE58904194D1 (de) 1993-06-03
DE3832817A1 (de) 1990-03-29
EP0361353A1 (fr) 1990-04-04

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