[go: up one dir, main page]

CN118748635A - A frequency deviation estimation method and system for WIFI6 system - Google Patents

A frequency deviation estimation method and system for WIFI6 system Download PDF

Info

Publication number
CN118748635A
CN118748635A CN202411005032.0A CN202411005032A CN118748635A CN 118748635 A CN118748635 A CN 118748635A CN 202411005032 A CN202411005032 A CN 202411005032A CN 118748635 A CN118748635 A CN 118748635A
Authority
CN
China
Prior art keywords
frequency offset
data symbol
offset estimation
frequency domain
wifi6
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN202411005032.0A
Other languages
Chinese (zh)
Other versions
CN118748635B (en
Inventor
韩洁
乐磊
张熠
牛冠群
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Suzhou Saimai Measurement And Control Technology Co ltd
Original Assignee
Suzhou Saimai Measurement And Control Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Suzhou Saimai Measurement And Control Technology Co ltd filed Critical Suzhou Saimai Measurement And Control Technology Co ltd
Priority to CN202411005032.0A priority Critical patent/CN118748635B/en
Publication of CN118748635A publication Critical patent/CN118748635A/en
Application granted granted Critical
Publication of CN118748635B publication Critical patent/CN118748635B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H04L27/2663—Coarse synchronisation, e.g. by correlation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H04L27/2665—Fine synchronisation, e.g. by positioning the FFT window
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W84/00—Network topologies
    • H04W84/02—Hierarchically pre-organised networks, e.g. paging networks, cellular networks, WLAN [Wireless Local Area Network] or WLL [Wireless Local Loop]
    • H04W84/10—Small scale networks; Flat hierarchical networks
    • H04W84/12—WLAN [Wireless Local Area Networks]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0024—Carrier regulation at the receiver end
    • H04L2027/0026—Correction of carrier offset

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Measuring Frequencies, Analyzing Spectra (AREA)

Abstract

The invention discloses a frequency offset estimation method and a system for a WIFI6 system, and belongs to the technical field of frequency offset estimation. The invention constructs a new sequence with the length more than or equal to the preset length L based on the short training sequence, carries out coarse frequency offset estimation based on the constructed new sequence, and obtains a coarse frequency offset estimation value only through one-time angle calculation. Compared with the prior art, on the basis of unchanged frequency offset estimation range, the method has the advantage that the estimation accuracy and the estimation speed are obviously improved because the sequence with higher resolution is utilized.

Description

一种用于WIFI6系统的频偏估计方法及系统A frequency deviation estimation method and system for WIFI6 system

技术领域Technical Field

本发明属频偏估计技术领域，具体涉及一种用于WIFI6系统的频偏估计方法及系统。The present invention belongs to the technical field of frequency deviation estimation, and specifically relates to a frequency deviation estimation method and system for a WIFI6 system.

背景技术Background Art

由于OFDM技术对频率偏差非常敏感，所以接收端在完成定时同步之后必须进行频偏估计和相位补偿。基于OFDM通信的WIFI6标准中，前导码中插入了特定的训练序列，如短训练序列和长训练序列等用于完成接收端的定时同步、频率同步、信道估计等。同时WIFI6为了达到帧容量的提升，其数据字段相对于前导部分采用了更窄的子载波间隔，其具有更高的频率分辨率。Since OFDM technology is very sensitive to frequency deviation, the receiver must perform frequency deviation estimation and phase compensation after completing timing synchronization. In the WIFI6 standard based on OFDM communication, specific training sequences are inserted into the preamble, such as short training sequences and long training sequences, which are used to complete the timing synchronization, frequency synchronization, channel estimation, etc. of the receiver. At the same time, in order to achieve an increase in frame capacity, the data field of WIFI6 uses a narrower subcarrier spacing than the preamble part, which has a higher frequency resolution.

通常接收端进行频偏估计和补偿的方法，采用短训练序列LSTF进行粗频偏估计和补偿，如在中国专利申请文献CN 112866163 B中一种用于WiFi业务残余频偏估计的方法，包括以下步骤：步骤S1，通过短训练序列实现粗频偏估计和补偿；步骤S2，通过长训练序列实现精频偏估计和补偿；步骤3，对符号循环前缀部分的残余频偏进行估计和补偿；步骤S4，对补偿完符号循环前缀部分的残余频偏后的接收数据进行信道估计；步骤5，对每一个数据符号进行符号内的相位差补偿，直到处理完所有的数据符号。其粗频偏估计是直接利用短训练序列，即直接采用长度较短的前导码进行估计，估计精度低，且存在多次复杂的求角度操作和平均操作，耗时长，效率低。Usually, the method for frequency offset estimation and compensation at the receiving end uses a short training sequence LSTF for rough frequency offset estimation and compensation. For example, in Chinese patent application document CN 112866163 B, a method for residual frequency offset estimation for WiFi services includes the following steps: step S1, rough frequency offset estimation and compensation is achieved through a short training sequence; step S2, fine frequency offset estimation and compensation is achieved through a long training sequence; step 3, residual frequency offset estimation and compensation is performed on the cyclic prefix part of the symbol; step S4, channel estimation is performed on the received data after the residual frequency offset of the cyclic prefix part of the symbol is compensated; step 5, phase difference compensation is performed on each data symbol until all data symbols are processed. The rough frequency offset estimation directly uses a short training sequence, that is, a short preamble code is directly used for estimation, the estimation accuracy is low, and there are multiple complex angle calculation operations and averaging operations, which is time-consuming and inefficient.

发明内容Summary of the invention

本发明旨在针对现有技术中存在的技术问题，提供了一种用于WIFI6系统的频偏估计方法及系统，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计，仅通过一次求角度的计算来得到粗频偏估计值。相比于现有技术，在频偏估计范围不变的基础上，由于构建长度更长的新序列以及更巧妙快速的求取方式，因此估计精度和估计速度方都得到显著的提高。The present invention aims to solve the technical problems existing in the prior art, and provides a frequency offset estimation method and system for a WIFI6 system. A new sequence with a length greater than or equal to a preset length L is constructed based on a short training sequence, and a rough frequency offset estimation is performed based on the constructed new sequence, and a rough frequency offset estimation value is obtained by only one angle calculation. Compared with the prior art, on the basis of the unchanged frequency offset estimation range, due to the construction of a new sequence with a longer length and a more clever and fast method of obtaining, both the estimation accuracy and the estimation speed are significantly improved.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

优选地，步骤1中，基于短训练序列在时域上构建长度大于等于预设长度L的新序列进行粗频偏估计。Preferably, in step 1, a new sequence with a length greater than or equal to a preset length L is constructed in the time domain based on the short training sequence to perform coarse frequency offset estimation.

优选地，步骤1中，基于短训练序列，在时域上构建相邻的两个长度均大于等于预设长度L的重复新序列段，通过求角度得到粗频偏估计值，新序列段长度大于短训练序列码元长度。Preferably, in step 1, based on the short training sequence, two adjacent repeated new sequence segments with lengths greater than or equal to a preset length L are constructed in the time domain, and a coarse frequency offset estimation value is obtained by calculating the angle, and the length of the new sequence segment is greater than the short training sequence symbol length.

优选地，步骤1中，在短训练序列LSTF序列中，根据短码元的采样点数D确定新序列的长度。Preferably, in step 1, in the short training sequence LSTF sequence, the length of the new sequence is determined according to the number of sampling points D of the short codewords.

优选地，选取长度为L＝9D的两段重复的新序列段，且保证两段新序列段之间的间隔为短码元的长度。Preferably, two repeated new sequence segments with a length of L=9D are selected, and the interval between the two new sequence segments is ensured to be the length of a short code element.

优选地，粗频偏估计采用如下公式计算：Preferably, the coarse frequency offset estimation is calculated using the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；如果采样率是20M，则FS＝20e6；Fs represents the sampling rate; if the sampling rate is 20M, then F S = 20e 6 ;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

优选地，在步骤4之后还包括步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Preferably, step 5 is further included after step 4, estimating and compensating for the residual phase deviation of each data symbol in the frequency domain.

优选地，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，求出每个符号的残余相位偏差估计值。Preferably, in step 5, a residual phase deviation estimation value of each symbol is obtained in the frequency domain based on a received signal on a pilot subcarrier of each symbol and a known reference signal.

优选地，采用如下公式计算第l个符号的残余相位偏差估计值：Preferably, the residual phase deviation estimate of the lth symbol is calculated using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

优选地，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：Preferably, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

优选地，步骤3中，采用长训练序列LLTF进行细频偏估计。Preferably, in step 3, a long training sequence LLTF is used to perform fine frequency offset estimation.

优选地，步骤3中，采用长训练序列LLTF，利用时域上相邻的两个重复的长训练序列的长码元通过求角度得到细频偏估计值。Preferably, in step 3, a long training sequence LLTF is used, and a fine frequency offset estimation value is obtained by calculating an angle using long symbols of two adjacent repeated long training sequences in the time domain.

优选地，步骤3中，采用长训练序列LLTF，利用时域上相邻的两个重复的长训练序列的长码元通过求角度得到细频偏估计值，细频偏估计具体采用如下公式计算：Preferably, in step 3, a long training sequence LLTF is used, and a fine frequency offset estimation value is obtained by calculating an angle using long code elements of two adjacent repeated long training sequences in the time domain. The fine frequency offset estimation is specifically calculated using the following formula:

其中in

flts为细频偏估计值；f lts is the fine frequency deviation estimate;

Fs代表采样率，单位为Hz；如果采样率是20M，则FS＝20e6；Fs represents the sampling rate, in Hz; if the sampling rate is 20M, then F S = 20e 6 ;

DD代表长训练序列码元的采样点数，DD＝3.2×1e-6×FS；DD represents the number of sampling points of the long training sequence codeword, DD = 3.2 × 1e -6 × F S ;

j代表长训练序列码元中采样点数的索引；j represents the index of the sampling point number in the long training sequence codeword;

dd(j)代表第一个长训练序列码元中第j个采样点的数据；dd(j) represents the data of the jth sampling point in the first long training sequence codeword;

dd(j+DD)代表第二个长训练序列码元中第j个采样点的数据，第二个长训练序列码元也可以理解为与第一个长训练序列码元相隔长码元采样点数DD的码元；dd(j+DD) represents the data of the jth sampling point in the second long training sequence codeword. The second long training sequence codeword can also be understood as the codeword separated from the first long training sequence codeword by the number of long codeword sampling points DD;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

优选地，步骤3中，数据字段构建导频子载波的信道系数子集进行细频偏估计。Preferably, in step 3, the data field constructs a channel coefficient subset of the pilot subcarriers to perform fine frequency offset estimation.

优选地，步骤3中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计。Preferably, in step 3, the data field constructs a channel coefficient subset of the pilot subcarrier in the frequency domain to perform fine frequency offset estimation.

优选地，步骤3中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计包括：求出数据字段每个数据符号频域中的P个导频子载波的信道系数，数据字段在频域上所有符号的导频子载波的信道系数组成数据字段的导频信道系数集H，从该导频信道系数集中分别选取有M个系数的H1子集和H2子集，使用这两个子集来进行细频偏估计。Preferably, in step 3, the data field constructs a channel coefficient subset of pilot subcarriers in the frequency domain for fine frequency offset estimation, including: calculating the channel coefficients of P pilot subcarriers in the frequency domain of each data symbol of the data field, the channel coefficients of the pilot subcarriers of all symbols of the data field in the frequency domain constitute a pilot channel coefficient set H of the data field, and from the pilot channel coefficient set, respectively select an H1 subset and an H2 subset with M coefficients, and use these two subsets to perform fine frequency offset estimation.

优选地，采用如下公式计算细频偏估计值：Preferably, the following formula is used to calculate the fine frequency offset estimate:

其中，in,

Fs代表采样率，单位为Hz，如采样率是20M，则FS＝20e6；Fs represents the sampling rate, in Hz. If the sampling rate is 20M, then F S = 20e 6 ;

Ncp代表时域上数据字段每个数据符号的保护间隔GI的采样点数，Ncp＝GI×FS，其中数据符号的保护间隔GI为0.8us，1.6us，3.2us三种配置的其中一种；Ncp represents the number of sampling points of the guard interval GI of each data symbol in the data field in the time domain, Ncp = GI × Fs , where the guard interval GI of the data symbol is one of the three configurations of 0.8us, 1.6us, and 3.2us;

Nfft代表时域上数据字段每个数据符号的有效数据符号的采样点数，Nfft＝SYM×FS，其中时域上每个数据符号的有效数据符号SYM固定为12.8us；Nfft represents the number of sampling points of the effective data symbol of each data symbol in the data field in the time domain, N fft =SYM× FS , wherein the effective data symbol SYM of each data symbol in the time domain is fixed to 12.8us;

M代表从导频信道系数集中选取的系数个数，M取值为P×(Num-1)；其中Num代表数据字段中所包含的数据符号的个数，P代表每个数据符号频域中导频子载波的个数；M represents the number of coefficients selected from the pilot channel coefficient set, and the value of M is P×(Num-1); wherein Num represents the number of data symbols contained in the data field, and P represents the number of pilot subcarriers in the frequency domain of each data symbol;

H1代表子集1，表示从导频信道系数集H第1个系数开始选取的子集；H 1 represents subset 1, which indicates the subset selected from the first coefficient of the pilot channel coefficient set H;

H2代表子集2，表示从导频信道系数集H第P+1个系数开始选取的子集；H 2 represents subset 2, which indicates the subset selected from the P+1th coefficient of the pilot channel coefficient set H;

j代表子集中系数序号的索引；j represents the index of the coefficient number in the subset;

H代表数据字段的所有符号的频域导频子载波的信道系数组成数据字段的导频信道系数集；导频信道系数集中的第j个子载波信道系数的求取公式为Yj表示频域上第j个子载波的接收信号，REFj表示频域上第j个子载波的已知参考信号。H represents the channel coefficients of the frequency domain pilot subcarriers of all symbols of the data field, which constitute the pilot channel coefficient set of the data field; the formula for obtaining the j-th subcarrier channel coefficient in the pilot channel coefficient set is: Y j represents the received signal of the j-th subcarrier in the frequency domain, and REF j represents the known reference signal of the j-th subcarrier in the frequency domain.

优选地，在时域上对粗频偏补偿后的信号进行细频偏补偿，细频偏补偿公式如下：Preferably, fine frequency offset compensation is performed on the signal after coarse frequency offset compensation in the time domain, and the fine frequency offset compensation formula is as follows:

其中，x1(t)是实现粗频偏补偿后的信号，x2(t)是实现细频偏补偿后的接收信号，fdata是细频偏估计值，t为时间序号。Wherein, x 1 (t) is the signal after coarse frequency offset compensation is achieved, x 2 (t) is the received signal after fine frequency offset compensation is achieved, f data is the estimated value of fine frequency offset, and t is the time sequence number.

本发明还提供了一种用于WIFI6系统的频偏估计系统，包括处理器，所述处理器执行上述的用于WIFI6系统的频偏估计方法。The present invention also provides a frequency offset estimation system for a WIFI6 system, comprising a processor, which executes the above-mentioned frequency offset estimation method for a WIFI6 system.

与现有技术相比，本发明所产生的有益效果是：Compared with the prior art, the beneficial effects of the present invention are:

1、本发明使用短训练序列在时域上构建长度远大于短训练序列码元长度的新序列进行粗频偏估计，仅通过一次求角度的计算来得到粗频偏估计值，也不需要进行平均操作，相比于现有技术，在频偏估计范围不变的基础上，估计精度和估计速度方都得到显著的提高。1. The present invention uses a short training sequence to construct a new sequence in the time domain whose length is much larger than the symbol length of the short training sequence for coarse frequency offset estimation. The coarse frequency offset estimation value is obtained by only one angle calculation, and no averaging operation is required. Compared with the prior art, the estimation accuracy and estimation speed are significantly improved on the basis of the unchanged frequency offset estimation range.

2、本发明对每个数据符号在频域上进行残余相位偏差估计及补偿，使用该补偿后的信号进行后续的解调，可提高接收机后续解调的性能。2. The present invention estimates and compensates for the residual phase deviation of each data symbol in the frequency domain, and uses the compensated signal for subsequent demodulation, which can improve the performance of subsequent demodulation of the receiver.

附图说明BRIEF DESCRIPTION OF THE DRAWINGS

图1为本发明的一个实施例的用于WIFI6系统的频偏估计方法流程图；FIG1 is a flow chart of a frequency offset estimation method for a WIFI6 system according to an embodiment of the present invention;

图2为本发明的又一个实施例的用于WIFI6系统的频偏估计方法流程图；FIG2 is a flow chart of a frequency offset estimation method for a WIFI6 system according to another embodiment of the present invention;

图3为本发明的又一个实施例的用于WIFI6系统的频偏估计方法流程图；FIG3 is a flow chart of a frequency offset estimation method for a WIFI6 system according to another embodiment of the present invention;

图4为本发明的又一个实施例的用于WIFI6系统的频偏估计方法流程图。FIG4 is a flow chart of a frequency offset estimation method for a WIFI6 system according to another embodiment of the present invention.

具体实施方式DETAILED DESCRIPTION

下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，所描述的实施例仅仅是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。The following will be combined with the drawings in the embodiments of the present invention to clearly and completely describe the technical solutions in the embodiments of the present invention. The described embodiments are only part of the embodiments of the present invention, not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；使得新序列长度远大于短训练序列码元的长度；Step 1, constructing a new sequence with a length greater than or equal to a preset length L based on the short training sequence, and performing coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value; so that the length of the new sequence is much greater than the symbol length of the short training sequence;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

在本发明的某些具体实施例中，步骤1中，基于短训练序列在时域上构建长度为L的新序列进行粗频偏估计。In some specific embodiments of the present invention, in step 1, a new sequence with a length of L is constructed in the time domain based on the short training sequence to perform coarse frequency offset estimation.

在本发明的某些具体实施例中，步骤1中，基于短训练序列，在时域上构建相邻的两个长度均大于等于预设长度L的重复新序列段，通过求角度得到粗频偏估计值。In some specific embodiments of the present invention, in step 1, two adjacent repeated new sequence segments with lengths greater than or equal to a preset length L are constructed in the time domain based on the short training sequence, and a coarse frequency offset estimation value is obtained by calculating the angle.

在本发明的某些具体实施例中，步骤1中，在短训练序列LSTF序列中，根据短码元的采样点数D确定新序列的长度。In some specific embodiments of the present invention, in step 1, in the short training sequence LSTF sequence, the length of the new sequence is determined according to the number of sampling points D of the short codewords.

在本发明的某些具体实施例中，选取长度为L＝9D的两段重复的新序列段，且保证两段新序列段之间的间隔为短码元的长度。In some specific embodiments of the present invention, two repeated new sequence segments with a length of L=9D are selected, and the interval between the two new sequence segments is ensured to be the length of a short code element.

在本发明的某些具体实施例中，粗频偏估计采用如下公式计算：In some specific embodiments of the present invention, the coarse frequency offset estimation is calculated using the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；如果采样率是20M，则FS＝20e6；Fs represents the sampling rate; if the sampling rate is 20M, then F S = 20e 6 ;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

在本发明的某些具体实施例中，在步骤4之后还包括步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。In some specific embodiments of the present invention, step 5 is further included after step 4, performing residual phase deviation estimation and compensation on each data symbol in the frequency domain.

在本发明的某些具体实施例中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，求出每个符号的残余相位偏差估计值。In some specific embodiments of the present invention, in step 5, a residual phase deviation estimation value of each symbol is obtained in the frequency domain based on a received signal on a pilot subcarrier of each symbol and a known reference signal.

在本发明的某些具体实施例中，采用如下公式计算第l个符号的残余相位偏差估计值：In some specific embodiments of the present invention, the residual phase deviation estimate of the lth symbol is calculated using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

在本发明的某些具体实施例中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In some specific embodiments of the present invention, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

在本发明的某些具体实施例中，步骤3中，采用长训练序列LLTF进行细频偏估计。In some specific embodiments of the present invention, in step 3, a long training sequence LLTF is used to perform fine frequency offset estimation.

在本发明的某些具体实施例中，步骤3中，采用长训练序列LLTF，利用时域上相邻的两个重复长训练序列的长码元通过求角度得到细频偏估计值。In some specific embodiments of the present invention, in step 3, a long training sequence LLTF is used, and a fine frequency offset estimation value is obtained by calculating the angle using long code elements of two adjacent long training sequences in the time domain.

在本发明的某些具体实施例中，步骤3中，采用长训练序列LLTF，利用时域上相邻的两个重复长训练序列的长码元通过求角度得到细频偏估计值，细频偏估计具体采用如下公式计算：In some specific embodiments of the present invention, in step 3, a long training sequence LLTF is used, and a fine frequency offset estimation value is obtained by calculating the angle using the long code elements of two adjacent repeated long training sequences in the time domain. The fine frequency offset estimation is specifically calculated using the following formula:

其中in

flts为细频偏估计值；f lts is the fine frequency deviation estimate;

Fs代表采样率，单位为Hz；如果采样率是20M，则FS＝20e6；Fs represents the sampling rate, in Hz; if the sampling rate is 20M, then F S = 20e 6 ;

DD代表长训练序列码元的采样点数，DD＝3.2×1e-6×FS；DD represents the number of sampling points of the long training sequence codeword, DD = 3.2 × 1e -6 × F S ;

j代表长训练序列码元中采样点数的索引；j represents the index of the sampling point number in the long training sequence codeword;

dd(j)代表第一个长训练序列码元中第j个采样点的数据；dd(j) represents the data of the jth sampling point in the first long training sequence codeword;

dd(j+DD)代表第二个长训练序列码元中第j个采样点的数据，第二个长训练序列码元也可以理解为与第一个长训练序列码元相隔长码元采样点数DD的码元；dd(j+DD) represents the data of the jth sampling point in the second long training sequence codeword. The second long training sequence codeword can also be understood as the codeword separated from the first long training sequence codeword by the number of long codeword sampling points DD;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

在本发明的某些具体实施例中，数据字段构建导频子载波的信道系数子集进行细频偏估计。In some specific embodiments of the present invention, the data field constructs a channel coefficient subset of the pilot subcarriers for fine frequency offset estimation.

在本发明的某些具体实施例中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计。In some specific embodiments of the present invention, the data field constructs a channel coefficient subset of the pilot subcarrier in the frequency domain to perform fine frequency offset estimation.

在本发明的某些具体实施例中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计包括：求出数据字段每个数据符号频域中的P个导频子载波的信道系数，数据字段在频域上所有符号的导频子载波的信道系数组成数据字段的导频信道系数集H，从该导频信道系数集中分别选取有M个系数的H1子集和H2子集，使用这两个子集来进行细频偏估计。In certain specific embodiments of the present invention, constructing a channel coefficient subset of pilot subcarriers in the frequency domain for the data field to perform fine frequency offset estimation includes: calculating the channel coefficients of P pilot subcarriers in the frequency domain for each data symbol of the data field, the channel coefficients of the pilot subcarriers of all symbols of the data field in the frequency domain constitute a pilot channel coefficient set H for the data field, and selecting an H1 subset and an H2 subset with M coefficients from the pilot channel coefficient set, and using these two subsets to perform fine frequency offset estimation.

在本发明的某些具体实施例中，采用如下公式计算细频偏估计值：In some specific embodiments of the present invention, the following formula is used to calculate the fine frequency offset estimate:

其中，in,

Fs代表采样率，如采样率是20M，则FS＝20e6；Fs represents the sampling rate. If the sampling rate is 20M, then F S = 20e 6 ;

Ncp代表时域上数据字段每个数据符号的保护间隔GI的采样点数，Ncp＝GI×FS，其中数据符号的保护间隔GI为0.8us，1.6us，3.2us三种配置的其中一种；Ncp represents the number of sampling points of the guard interval GI of each data symbol in the data field in the time domain, Ncp = GI × Fs , where the guard interval GI of the data symbol is one of the three configurations of 0.8us, 1.6us, and 3.2us;

Nfft代表时域上数据字段每个数据符号的有效数据符号的采样点数，Nfft＝SYM×FS，其中时域上每个数据符号的有效数据符号SYM固定为12.8us；Nfft represents the number of sampling points of the effective data symbol of each data symbol in the data field in the time domain, N fft =SYM× FS , wherein the effective data symbol SYM of each data symbol in the time domain is fixed to 12.8us;

M代表从导频信道系数集中选取的系数个数，M取值为P×(Num-1)；其中Num代表数据字段中所包含的数据符号的个数，P代表每个数据符号频域中导频子载波的个数；M represents the number of coefficients selected from the pilot channel coefficient set, and the value of M is P×(Num-1); wherein Num represents the number of data symbols contained in the data field, and P represents the number of pilot subcarriers in the frequency domain of each data symbol;

H1代表子集1，表示从导频信道系数集H第1个系数开始选取的子集；H 1 represents subset 1, which indicates the subset selected from the first coefficient of the pilot channel coefficient set H;

H2代表子集2，表示从导频信道系数集H第P+1个系数开始选取的子集；H 2 represents subset 2, which indicates the subset selected from the P+1th coefficient of the pilot channel coefficient set H;

j代表子集中系数序号的索引；j represents the index of the coefficient number in the subset;

H代表数据字段的所有符号的频域导频子载波的信道系数组成数据字段的导频信道系数集；导频信道系数集中的第j个子载波信道系数的求取公式为Yj表示频域上第j个子载波的接收信号，REFj表示频域上第j个子载波的已知参考信号；H represents the channel coefficients of the frequency domain pilot subcarriers of all symbols of the data field, which constitute the pilot channel coefficient set of the data field; the formula for obtaining the j-th subcarrier channel coefficient in the pilot channel coefficient set is: Y j represents the received signal of the j-th subcarrier in the frequency domain, REF j represents the known reference signal of the j-th subcarrier in the frequency domain;

在本发明的某些具体实施例中，在时域上对粗频偏补偿后的信号进行细频偏补偿，细频偏补偿公式如下：In some specific embodiments of the present invention, fine frequency offset compensation is performed on the signal after coarse frequency offset compensation in the time domain, and the fine frequency offset compensation formula is as follows:

其中，x1(t)是实现粗频偏补偿后的信号，x2(t)是实现细频偏补偿后的接收信号，fdata是细频偏估计值，t为时间序号。Wherein, x 1 (t) is the signal after coarse frequency offset compensation is achieved, x 2 (t) is the received signal after fine frequency offset compensation is achieved, f data is the estimated value of fine frequency offset, and t is the time sequence number.

本发明还提供了一种用于WIFI6系统的频偏估计系统，包括处理器，所述处理器上述的用于WIFI6系统的频偏估计方法。The present invention also provides a frequency offset estimation system for a WIFI6 system, comprising a processor, and the processor implements the above-mentioned frequency offset estimation method for a WIFI6 system.

实施例1Example 1

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

实施例2Example 2

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

其中，基于短训练序列，在时域上构建相邻的两个长度均大于等于预设长度L的重复新序列段，通过求角度得到粗频偏估计值。Based on the short training sequence, two adjacent repeated new sequence segments whose lengths are both greater than or equal to a preset length L are constructed in the time domain, and a coarse frequency offset estimation value is obtained by calculating the angle.

实施例3Example 3

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过求角度得到粗频偏估计值，D为短码元的采样点数。Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is guaranteed to be the length of the short code element. The coarse frequency offset estimation value is obtained by calculating the angle, and D is the number of sampling points of the short code element.

实施例4Example 4

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element, and the coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency offset estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

实施例5Example 5

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿；Step 4, based on the fine frequency offset estimation, performing fine frequency offset compensation on the signal after the coarse frequency offset compensation;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element, and the coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

其中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，采用如下公式计算第l个符号的残余相位偏差估计值：In step 5, the residual phase deviation estimation value of the lth symbol is calculated in the frequency domain according to the received signal on each symbol pilot subcarrier and the known reference signal using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

其中，步骤5中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In step 5, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

实施例6Example 6

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，采用长训练序列LLTF进行细频偏估计；Step 3, use the long training sequence LLTF to perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation.

实施例7Example 7

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，采用长训练序列LLTF进行细频偏估计；Step 3, use the long training sequence LLTF to perform fine frequency offset estimation;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿；Step 4, based on the fine frequency offset estimation, performing fine frequency offset compensation on the signal after the coarse frequency offset compensation;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element, and the coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

其中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，采用如下公式计算第l个符号的残余相位偏差估计值：In step 5, the residual phase deviation estimation value of the lth symbol is calculated in the frequency domain according to the received signal on each symbol pilot subcarrier and the known reference signal using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

其中，步骤5中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In step 5, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

实施例8Example 8

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，采用长训练序列LLTF，利用时域上相邻的两个重复长训练序列的长码元通过求角度得到细频偏估计值；Step 3, using the long training sequence LLTF, using the long code elements of two adjacent repeated long training sequences in the time domain to obtain a fine frequency offset estimate by calculating the angle;

步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿；Step 4, based on the fine frequency offset estimation, performing fine frequency offset compensation on the signal after the coarse frequency offset compensation;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的、分辨率高于前导码的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D and a resolution higher than the preamble code are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element. The coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

其中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，采用如下公式计算第l个符号的残余相位偏差估计值：In step 5, the residual phase deviation estimation value of the lth symbol is calculated in the frequency domain according to the received signal on each symbol pilot subcarrier and the known reference signal using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

其中，步骤5中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In step 5, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

其中，步骤3中，采用长训练序列LLTF，利用时域上相邻的两个重复长训练序列的长码元通过求角度得到细频偏估计值，细频偏估计具体采用如下公式计算：In step 3, a long training sequence LLTF is used, and a fine frequency offset estimation value is obtained by calculating the angle using the long code elements of two adjacent repeated long training sequences in the time domain. The fine frequency offset estimation is specifically calculated using the following formula:

其中in

flts为细频偏估计值；f lts is the fine frequency deviation estimate;

Fs代表采样率，单位为Hz；如果采样率是20M，则FS＝20e6；Fs represents the sampling rate, in Hz; if the sampling rate is 20M, then F S = 20e 6 ;

DD代表长训练序列码元的采样点数，DD＝3.2×1e-6×FS；DD represents the number of sampling points of the long training sequence codeword, DD = 3.2 × 1e -6 × F S ;

j代表长训练序列码元中采样点数的索引；j represents the index of the sampling point number in the long training sequence codeword;

dd(j)代表第一个长训练序列码元中第j个采样点的数据；dd(j) represents the data of the jth sampling point in the first long training sequence codeword;

dd(j+DD)代表第二个长训练序列码元中第j个采样点的数据，第二个长训练序列码元也可以理解为与第一个长训练序列码元相隔长码元采样点数DD的码元；dd(j+DD) represents the data of the jth sampling point in the second long training sequence codeword. The second long training sequence codeword can also be understood as the codeword separated from the first long training sequence codeword by the number of long codeword sampling points DD;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

实施例9Example 9

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，数据字段构建导频子载波的信道系数子集进行细频偏估计；Step 3: The data field constructs a channel coefficient subset of the pilot subcarrier to perform fine frequency offset estimation;

步骤4，基于细频偏估计值，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Perform fine frequency offset compensation on the signal after coarse frequency offset compensation based on the fine frequency offset estimation value.

实施例10Example 10

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，数据字段构建导频子载波的信道系数子集进行细频偏估计；Step 3: The data field constructs a channel coefficient subset of the pilot subcarrier to perform fine frequency offset estimation;

步骤4，基于细频偏估计值，对粗频偏补偿后的信号进行细频偏补偿；Step 4, performing fine frequency offset compensation on the signal after coarse frequency offset compensation based on the fine frequency offset estimation value;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

实施例11Embodiment 11

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；Step 1, constructing a new sequence with a length greater than or equal to a preset length L based on the short training sequence, and performing a coarse frequency offset estimation based on the constructed new sequence;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，数据字段构建导频子载波的信道系数子集进行细频偏估计；Step 3: The data field constructs a channel coefficient subset of the pilot subcarrier to perform fine frequency offset estimation;

步骤4，基于细频偏估计值，对粗频偏补偿后的信号进行细频偏补偿；Step 4, performing fine frequency offset compensation on the signal after coarse frequency offset compensation based on the fine frequency offset estimation value;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element, and the coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

其中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，采用如下公式计算第l个符号的残余相位偏差估计值：In step 5, the residual phase deviation estimation value of the lth symbol is calculated in the frequency domain according to the received signal on each symbol pilot subcarrier and the known reference signal using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

其中，步骤5中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In step 5, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

其中，步骤3中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计包括：求出数据字段每个数据符号频域中的P个导频子载波的信道系数，数据字段在频域上所有符号的导频子载波的信道系数组成数据字段的导频信道系数集H，从该导频信道系数集中分别选取有M个系数的H1子集和H2子集，使用这两个子集来进行细频偏估计。Among them, in step 3, the data field constructs a channel coefficient subset of the pilot subcarrier in the frequency domain for fine frequency offset estimation, including: calculating the channel coefficients of P pilot subcarriers in the frequency domain of each data symbol of the data field, the channel coefficients of the pilot subcarriers of all symbols of the data field in the frequency domain constitute the pilot channel coefficient set H of the data field, and the H1 subset and H2 subset with M coefficients are selected from the pilot channel coefficient set, and these two subsets are used to perform fine frequency offset estimation.

实施例12Example 12

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计方法进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation method for a WIFI6 system of the present invention is described in detail below.

本发明提供了一种用于WIFI6系统的频偏估计方法，包括如下步骤：The present invention provides a frequency deviation estimation method for a WIFI6 system, comprising the following steps:

步骤1，基于短训练序列构建长度大于等于预设长度L、分辨率高于前导码的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L and a resolution higher than the preamble code based on the short training sequence, and perform coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value;

步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal;

步骤3，数据字段构建导频子载波的信道系数子集进行细频偏估计；Step 3: The data field constructs a channel coefficient subset of the pilot subcarrier to perform fine frequency offset estimation;

步骤4，基于细频偏估计值，对粗频偏补偿后的信号进行细频偏补偿；Step 4, performing fine frequency offset compensation on the signal after coarse frequency offset compensation based on the fine frequency offset estimation value;

步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。Step 5: perform residual phase deviation estimation and compensation on each data symbol in the frequency domain.

其中，基于短训练序列LSTF序列中，在时域上构建相邻的两个长度L＝9D的两段重复新序列段，且保证两段新序列段之间的间隔为短码元的长度，通过下式进行粗频偏估计值计算：Among them, based on the short training sequence LSTF sequence, two adjacent repeated new sequence segments with a length of L=9D are constructed in the time domain, and the interval between the two new sequence segments is ensured to be the length of the short code element, and the coarse frequency offset estimation value is calculated by the following formula:

其中，in,

fsts为粗频偏估计值；f sts is the coarse frequency offset estimate;

Fs代表采样率；Fs represents the sampling rate;

D代表短码元的采样点数，D＝0.8×1e-6×FS；D represents the number of sampling points of the short code element, D = 0.8 × 1e -6 × F S ;

n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment;

s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed;

s(n+D)代表构建的第二段新序列段中第n个采样点的数据，第二段新序列段也可以理解为与第一段新序列段相隔短码元采样点数D的序列段；s(n+D) represents the data of the nth sampling point in the constructed second new sequence segment. The second new sequence segment can also be understood as a sequence segment separated from the first new sequence segment by the number of short code element sampling points D;

L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D;

conj()代表取共轭操作；conj() represents the conjugate operation;

arctan()代表求角度操作。arctan() represents the angle operation.

其中，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，采用如下公式计算第l个符号的残余相位偏差估计值：In step 5, the residual phase deviation estimation value of the lth symbol is calculated in the frequency domain according to the received signal on each symbol pilot subcarrier and the known reference signal using the following formula:

其中，in,

k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain;

P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain;

l为数据字段的数据符号的索引；l is the index of the data symbol of the data field;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation;

REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol;

φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol.

其中，步骤5中，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：In step 5, each data symbol is compensated for residual phase deviation in the frequency domain using the following formula:

其中，in,

k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol;

l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field;

φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol;

Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol;

Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol.

其中，步骤3中，数据字段在频域上构建导频子载波的信道系数子集进行细频偏估计包括：求出数据字段每个数据符号频域中的P个导频子载波的信道系数，数据字段在频域上所有符号的导频子载波的信道系数组成数据字段的导频信道系数集H，从该导频信道系数集中分别选取有M个系数的H1子集和H2子集，使用这两个子集来进行细频偏估计。Among them, in step 3, the data field constructs a channel coefficient subset of the pilot subcarrier in the frequency domain for fine frequency offset estimation, including: calculating the channel coefficients of P pilot subcarriers in the frequency domain of each data symbol of the data field, the channel coefficients of the pilot subcarriers of all symbols of the data field in the frequency domain constitute the pilot channel coefficient set H of the data field, and the H1 subset and H2 subset with M coefficients are selected from the pilot channel coefficient set, and these two subsets are used to perform fine frequency offset estimation.

采用如下公式计算细频偏估计值：The fine frequency offset estimate is calculated using the following formula:

其中，in,

Fs代表采样率，如采样率是20M，则FS＝20e6；Fs represents the sampling rate. If the sampling rate is 20M, then F S = 20e 6 ;

Ncp代表时域上数据字段每个数据符号的保护间隔GI的采样点数，Ncp＝GI×FS，其中数据符号的保护间隔GI为0.8us，1.6us，3.2us三种配置的其中一种；Ncp represents the number of sampling points of the guard interval GI of each data symbol in the data field in the time domain, Ncp = GI × Fs , where the guard interval GI of the data symbol is one of the three configurations of 0.8us, 1.6us, and 3.2us;

Nfft代表时域上数据字段每个数据符号的有效数据符号的采样点数，Nfft＝SYM×FS，其中时域上每个数据符号的有效数据符号SYM固定为12.8us；Nfft represents the number of sampling points of the effective data symbol of each data symbol in the data field in the time domain, N fft =SYM× FS , wherein the effective data symbol SYM of each data symbol in the time domain is fixed to 12.8us;

M代表从导频信道系数集中选取的系数个数，M取值为P×(Num-1)；其中Num代表数据字段中所包含的数据符号的个数，P代表每个数据符号频域中导频子载波的个数；M represents the number of coefficients selected from the pilot channel coefficient set, and the value of M is P×(Num-1); wherein Num represents the number of data symbols contained in the data field, and P represents the number of pilot subcarriers in the frequency domain of each data symbol;

H1代表子集1，表示从导频信道系数集H第1个系数开始选取的子集；H 1 represents subset 1, which indicates the subset selected from the first coefficient of the pilot channel coefficient set H;

H2代表子集2，表示从导频信道系数集H第P+1个系数开始选取的子集；H 2 represents subset 2, which indicates the subset selected from the P+1th coefficient of the pilot channel coefficient set H;

j代表子集中系数序号的索引；j represents the index of the coefficient number in the subset;

H代表数据字段的所有符号的频域导频子载波的信道系数组成数据字段的导频信道系数集；导频信道系数集中的第j个子载波信道系数的求取公式为Yj表示频域上第j个子载波的接收信号，REFj表示频域上第j个子载波的已知参考信号；H represents the channel coefficients of the frequency domain pilot subcarriers of all symbols of the data field, which constitute the pilot channel coefficient set of the data field; the formula for obtaining the j-th subcarrier channel coefficient in the pilot channel coefficient set is: Y j represents the received signal of the j-th subcarrier in the frequency domain, REF j represents the known reference signal of the j-th subcarrier in the frequency domain;

在时域上对粗频偏补偿后的信号进行细频偏补偿，细频偏补偿公式如下：In the time domain, fine frequency offset compensation is performed on the signal after coarse frequency offset compensation. The fine frequency offset compensation formula is as follows:

其中，x1(t)是实现粗频偏补偿后的信号，x2(t)是实现细频偏补偿后的接收信号，fdata是细频偏估计值，t为时间序号。Wherein, x 1 (t) is the signal after coarse frequency offset compensation is achieved, x 2 (t) is the received signal after fine frequency offset compensation is achieved, f data is the estimated value of fine frequency offset, and t is the time sequence number.

实施例13Example 13

根据本发明的一个具体实施方案，下面对本发明的用于WIFI6系统的频偏估计系统进行详细说明。According to a specific implementation scheme of the present invention, the frequency offset estimation system for the WIFI6 system of the present invention is described in detail below.

本发明还提供了一种用于WIFI6系统的频偏估计系统，包括处理器，所述处理器执行上述的用于WIFI6系统的频偏估计方法。The present invention also provides a frequency offset estimation system for a WIFI6 system, comprising a processor, which executes the above-mentioned frequency offset estimation method for a WIFI6 system.

以上所述仅为本发明的优选实施例而已，并不用于限制本发明，对于本领域的技术人员来说，本发明可以有各种更改和变化。凡在本发明的精神和原则之内，所作的任何修改、等同替换、改进等，均包含在本发明的保护范围之内。The above description is only a preferred embodiment of the present invention and is not intended to limit the present invention. For those skilled in the art, the present invention may have various modifications and variations. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present invention are included in the protection scope of the present invention.

Claims (11)

1.一种用于WIFI6系统的频偏估计方法，其特征在于，包括如下步骤：1. A frequency deviation estimation method for a WIFI6 system, comprising the following steps: 步骤1，基于短训练序列构建长度大于等于预设长度L的新序列，基于构建的新序列进行粗频偏估计；L与短训练序列码元长度的差大于预设门限值；Step 1: construct a new sequence with a length greater than or equal to a preset length L based on a short training sequence, and perform a coarse frequency offset estimation based on the constructed new sequence; the difference between L and the symbol length of the short training sequence is greater than a preset threshold value; 步骤2，基于粗频偏估计，对接收信号进行粗频偏补偿；Step 2, based on the coarse frequency offset estimation, performing coarse frequency offset compensation on the received signal; 步骤3，进行细频偏估计；Step 3, perform fine frequency offset estimation; 步骤4，基于细频偏估计，对粗频偏补偿后的信号进行细频偏补偿。Step 4: Based on the fine frequency offset estimation, perform fine frequency offset compensation on the signal after the coarse frequency offset compensation. 2.根据权利要求1所述的用于WIFI6系统的频偏估计方法，其特征在于，步骤1中，基于短训练序列在时域上构建长度大于等于预设长度L的新序列进行粗频偏估计。2. According to the frequency offset estimation method for WIFI6 system according to claim 1, it is characterized in that in step 1, a new sequence with a length greater than or equal to a preset length L is constructed in the time domain based on the short training sequence to perform coarse frequency offset estimation. 3.根据权利要求2所述的用于WIFI6系统的频偏估计方法，其特征在于，步骤1中，基于短训练序列，在时域上构建相邻的两个长度均大于等于预设长度L的重复新序列段，通过求角度得到粗频偏估计值。3. According to the frequency deviation estimation method for WIFI6 system according to claim 2, it is characterized in that in step 1, based on the short training sequence, two adjacent repeated new sequence segments with lengths greater than or equal to a preset length L are constructed in the time domain, and a coarse frequency deviation estimation value is obtained by calculating the angle. 4.根据权利要求3所述的用于WIFI6系统的频偏估计方法，其特征在于，步骤1中，在短训练序列LSTF序列中，根据短码元的采样点数D确定新序列的长度。4. The frequency offset estimation method for a WIFI6 system according to claim 3 is characterized in that, in step 1, in a short training sequence LSTF sequence, the length of the new sequence is determined according to the number of sampling points D of the short codewords. 5.根据权利要求4所述的用于WIFI6系统的频偏估计方法，其特征在于，选取长度为L＝9D的两段重复的新序列段，且保证两段新序列段之间的间隔为短码元的长度。5. According to the frequency offset estimation method for WIFI6 system described in claim 4, it is characterized in that two repeated new sequence segments with a length of L=9D are selected, and the interval between the two new sequence segments is ensured to be the length of a short code element. 6.根据权利要求5所述的用于WIFI6系统的频偏估计方法，其特征在于，粗频偏估计采用如下公式计算：6. According to the frequency offset estimation method for the WIFI6 system of claim 5, it is characterized in that the coarse frequency offset estimation is calculated using the following formula: 其中，in, fsts为粗频偏估计值；f sts is the coarse frequency deviation estimate; Fs代表采样率，单位为Hz；Fs represents the sampling rate in Hz; D代表短码元的采样点数，D＝0.8×1e-6×Fs；D represents the number of sampling points of the short codeword, D = 0.8 × 1e -6 × F s ; n代表选取序列段中采样点数的索引；n represents the index of the number of sampling points in the selected sequence segment; s(n)代表构建的第一段新序列段中第n个采样点的数据；s(n) represents the data of the nth sampling point in the first new sequence segment constructed; s(n+D)代表构建的第二段新序列段中第n个采样点的数据；s(n+D) represents the data of the nth sampling point in the second new sequence segment constructed; L为构建新序列段的采样点数的长度，取L＝9D；L is the length of the sampling points for constructing a new sequence segment, and L=9D; conj()代表取共轭操作；conj() represents the conjugate operation; arctan()代表求角度操作。arctan() represents the angle operation. 7.根据权利要求1-6任一项所述的用于WIFI6系统的频偏估计方法，其特征在于，在步骤4之后还包括步骤5，对每个数据符号在频域上进行残余相位偏差估计和补偿。7. The frequency deviation estimation method for a WIFI6 system according to any one of claims 1-6 is characterized in that, after step 4, it also includes step 5, performing residual phase deviation estimation and compensation in the frequency domain for each data symbol. 8.根据权利要求7所述的用于WIFI6系统的频偏估计方法，其特征在于，步骤5中，在频域上根据每个符号导频子载波上的接收信号和已知的参考信号，求出每个符号的残余相位偏差估计值。8. According to the frequency deviation estimation method for WIFI6 system according to claim 7, it is characterized in that in step 5, the residual phase deviation estimation value of each symbol is calculated in the frequency domain based on the received signal on each symbol pilot subcarrier and the known reference signal. 9.根据权利要求8所述的用于WIFI6系统的频偏估计方法，其特征在于，采用如下公式计算第l个符号的残余相位偏差估计值：9. The frequency deviation estimation method for a WIFI6 system according to claim 8, characterized in that the residual phase deviation estimation value of the lth symbol is calculated using the following formula: 其中，in, k为当前数据符号在频域上导频子载波的索引；k is the index of the pilot subcarrier of the current data symbol in the frequency domain; P为当前数据符号在频域上所包含的导频子载波的总个数；P is the total number of pilot subcarriers contained in the current data symbol in the frequency domain; l为数据字段的数据符号的索引；l is the index of the data symbol of the data field; Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上的接收信号；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation; REFl(k)表示第l个数据符号在频域子载波上的已知参考信号，其对应的位置为第l个数据符号的频域上第k个导频子载波；REF l (k) represents the known reference signal of the l-th data symbol on the frequency domain subcarrier, and its corresponding position is the k-th pilot subcarrier on the frequency domain of the l-th data symbol; φl表示第l个数据符号所估计出的残余相位偏差。φ l represents the residual phase deviation estimated for the lth data symbol. 10.根据权利要求8所述的用于WIFI6系统的频偏估计方法，其特征在于，每个数据符号在频域上进行残余相位偏差的补偿，采用如下公式：10. The frequency offset estimation method for a WIFI6 system according to claim 8, characterized in that each data symbol is compensated for residual phase deviation in the frequency domain using the following formula: 其中，in, k为每个数据符号的频域上子载波的索引；k is the index of the subcarrier in the frequency domain of each data symbol; l为数据字段每个数据符号的索引；l is the index of each data symbol in the data field; φl表示第l个数据符号所估计出的残余相位偏差；φ l represents the estimated residual phase deviation of the lth data symbol; Yl(k)表示细频偏补偿后的第l个数据符号在频域子载波上接收信号，其对应的位置为第l个数据符号的频域上第k个子载波；Y l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after fine frequency offset compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol; Y1,l(k)表示残余相位偏差补偿后第l个数据符号在频域子载波上的接收信号，其对应的位置为第l个数据符号的频域上第k个子载波。Y 1,l (k) represents the received signal of the lth data symbol on the frequency domain subcarrier after residual phase deviation compensation, and its corresponding position is the kth subcarrier on the frequency domain of the lth data symbol. 11.一种用于WIFI6系统的频偏估计系统，其特征在于，包括处理器，所述处理器执行权利要权利要求书求1-10任一项所述的用于WIFI6系统的频偏估计方法。11. A frequency offset estimation system for a WIFI6 system, characterized in that it comprises a processor, and the processor executes the frequency offset estimation method for a WIFI6 system as described in any one of claims 1-10.
CN202411005032.0A 2024-07-25 2024-07-25 A frequency deviation estimation method and system for WIFI6 system Active CN118748635B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202411005032.0A CN118748635B (en) 2024-07-25 2024-07-25 A frequency deviation estimation method and system for WIFI6 system

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202411005032.0A CN118748635B (en) 2024-07-25 2024-07-25 A frequency deviation estimation method and system for WIFI6 system

Publications (2)

Publication Number Publication Date
CN118748635A true CN118748635A (en) 2024-10-08
CN118748635B CN118748635B (en) 2025-03-28

Family

ID=92923670

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202411005032.0A Active CN118748635B (en) 2024-07-25 2024-07-25 A frequency deviation estimation method and system for WIFI6 system

Country Status (1)

Country Link
CN (1) CN118748635B (en)

Citations (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR20050034116A (en) * 2003-10-08 2005-04-14 한국전자통신연구원 Apparatus and method for synchronization channel and compensating frequency offset of wireless local area network system
US7218691B1 (en) * 2001-03-05 2007-05-15 Marvell International Ltd. Method and apparatus for estimation of orthogonal frequency division multiplexing symbol timing and carrier frequency offset
CN101394391A (en) * 2008-11-03 2009-03-25 华北电力大学 OFDM Synchronization Method Based on Four-dimensional Chaotic System
CN101494634A (en) * 2009-01-06 2009-07-29 北京交通大学 Improved method based on Schmidl & Cox synchronization
CN101977175A (en) * 2010-11-18 2011-02-16 北京航空航天大学 Novel two-dimensional spread spectrum system synchronization method
US20130114453A1 (en) * 2011-11-08 2013-05-09 Mstar Semiconductor, Inc. Method Applied to Receiver of Wireless Network for Frequency Offset and Associated Apparatus
CN103220252A (en) * 2013-04-10 2013-07-24 安徽华东光电技术研究所 Coding orthogonal frequency division multiplexing wireless signal receiving and processing device and processing method thereof
CN104168224A (en) * 2013-05-20 2014-11-26 普天信息技术研究院有限公司 Frequency offset estimation and compensation method
CN104168227A (en) * 2014-08-04 2014-11-26 东南大学 Carrier synchronization method applied to orthogonal frequency division multiplexing system
CN104253782A (en) * 2014-09-02 2014-12-31 深圳市力合微电子股份有限公司 Residual carrier deviation and sampling deviation estimation method and compensation method
CN105847211A (en) * 2016-03-15 2016-08-10 东南大学 Carrier frequency offset estimation method suitable for MIMO-OFDM (Multiple Input Multiple Output-Orthogonal Frequency Division Multiplexing) system
CN106559370A (en) * 2016-11-05 2017-04-05 上海大学 A kind of method of low complexity OFDM PON system sample clock frequency deviation compensation
CN106789791A (en) * 2017-02-28 2017-05-31 北京科技大学 GSM carrier frequency bias estimation based on conjugation symmetric training sequence
CN108199994A (en) * 2017-12-29 2018-06-22 深圳市极致汇仪科技有限公司 A kind of wireless comprehensive test instrument ofdm signal frequency deviation estimating method and system
CN108365872A (en) * 2017-12-29 2018-08-03 中国电子科技集团公司第五十四研究所 A kind of signal synthesis method suitable for strange land multiple antennas group battle array
CN110113276A (en) * 2018-02-01 2019-08-09 珠海全志科技股份有限公司 OFDM frequency deviation estimating method, system and device based on IEEE802.11
CN112866163A (en) * 2021-01-06 2021-05-28 深圳市极致汇仪科技有限公司 Method and system for estimating residual frequency offset of WiFi service
CN113949608A (en) * 2021-10-27 2022-01-18 东南大学 Decision feedback demodulation system and method for VDES system
CN114079604A (en) * 2020-08-10 2022-02-22 广州海格通信集团股份有限公司 Communication signal receiving method, communication signal receiving device, computer equipment and storage medium
US20220123851A1 (en) * 2021-09-14 2022-04-21 Hangzhou Vango Technologies, Inc. Robust method and device for estimating frequency offset in orthogonal frequency division multiplexing communication
CN114745775A (en) * 2022-06-13 2022-07-12 为准（北京）电子科技有限公司 Frequency offset estimation method and device in wireless communication system
CN115242587A (en) * 2022-07-27 2022-10-25 西安电子科技大学 A data-aided carrier frequency offset estimation method in low signal-to-noise ratio environment
US20220407746A1 (en) * 2019-11-15 2022-12-22 Telefonaktiebolaget Lm Ericsson (Publ) Method and receiver for frequency offset estimation
CN116208457A (en) * 2023-01-30 2023-06-02 鹏城实验室 Signal frequency offset compensation method, terminal equipment and computer readable storage medium
CN116915565A (en) * 2023-05-11 2023-10-20 电子科技大学 An integrated system for terahertz communication and sensing under Doppler frequency deviation

Patent Citations (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7218691B1 (en) * 2001-03-05 2007-05-15 Marvell International Ltd. Method and apparatus for estimation of orthogonal frequency division multiplexing symbol timing and carrier frequency offset
KR20050034116A (en) * 2003-10-08 2005-04-14 한국전자통신연구원 Apparatus and method for synchronization channel and compensating frequency offset of wireless local area network system
CN101394391A (en) * 2008-11-03 2009-03-25 华北电力大学 OFDM Synchronization Method Based on Four-dimensional Chaotic System
CN101494634A (en) * 2009-01-06 2009-07-29 北京交通大学 Improved method based on Schmidl & Cox synchronization
CN101977175A (en) * 2010-11-18 2011-02-16 北京航空航天大学 Novel two-dimensional spread spectrum system synchronization method
US20130114453A1 (en) * 2011-11-08 2013-05-09 Mstar Semiconductor, Inc. Method Applied to Receiver of Wireless Network for Frequency Offset and Associated Apparatus
CN103220252A (en) * 2013-04-10 2013-07-24 安徽华东光电技术研究所 Coding orthogonal frequency division multiplexing wireless signal receiving and processing device and processing method thereof
CN104168224A (en) * 2013-05-20 2014-11-26 普天信息技术研究院有限公司 Frequency offset estimation and compensation method
CN104168227A (en) * 2014-08-04 2014-11-26 东南大学 Carrier synchronization method applied to orthogonal frequency division multiplexing system
CN104253782A (en) * 2014-09-02 2014-12-31 深圳市力合微电子股份有限公司 Residual carrier deviation and sampling deviation estimation method and compensation method
CN105847211A (en) * 2016-03-15 2016-08-10 东南大学 Carrier frequency offset estimation method suitable for MIMO-OFDM (Multiple Input Multiple Output-Orthogonal Frequency Division Multiplexing) system
CN106559370A (en) * 2016-11-05 2017-04-05 上海大学 A kind of method of low complexity OFDM PON system sample clock frequency deviation compensation
CN106789791A (en) * 2017-02-28 2017-05-31 北京科技大学 GSM carrier frequency bias estimation based on conjugation symmetric training sequence
CN108199994A (en) * 2017-12-29 2018-06-22 深圳市极致汇仪科技有限公司 A kind of wireless comprehensive test instrument ofdm signal frequency deviation estimating method and system
CN108365872A (en) * 2017-12-29 2018-08-03 中国电子科技集团公司第五十四研究所 A kind of signal synthesis method suitable for strange land multiple antennas group battle array
CN110113276A (en) * 2018-02-01 2019-08-09 珠海全志科技股份有限公司 OFDM frequency deviation estimating method, system and device based on IEEE802.11
US20220407746A1 (en) * 2019-11-15 2022-12-22 Telefonaktiebolaget Lm Ericsson (Publ) Method and receiver for frequency offset estimation
CN114079604A (en) * 2020-08-10 2022-02-22 广州海格通信集团股份有限公司 Communication signal receiving method, communication signal receiving device, computer equipment and storage medium
CN112866163A (en) * 2021-01-06 2021-05-28 深圳市极致汇仪科技有限公司 Method and system for estimating residual frequency offset of WiFi service
US20220123851A1 (en) * 2021-09-14 2022-04-21 Hangzhou Vango Technologies, Inc. Robust method and device for estimating frequency offset in orthogonal frequency division multiplexing communication
CN113949608A (en) * 2021-10-27 2022-01-18 东南大学 Decision feedback demodulation system and method for VDES system
CN114745775A (en) * 2022-06-13 2022-07-12 为准（北京）电子科技有限公司 Frequency offset estimation method and device in wireless communication system
CN115242587A (en) * 2022-07-27 2022-10-25 西安电子科技大学 A data-aided carrier frequency offset estimation method in low signal-to-noise ratio environment
CN116208457A (en) * 2023-01-30 2023-06-02 鹏城实验室 Signal frequency offset compensation method, terminal equipment and computer readable storage medium
CN116915565A (en) * 2023-05-11 2023-10-20 电子科技大学 An integrated system for terahertz communication and sensing under Doppler frequency deviation

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
袁声: "多模式MIMO-OFDM通信系统的设计与实现", CNKI硕士电子期刊, 15 May 2024 (2024-05-15), pages 3 *

Also Published As

Publication number Publication date
CN118748635B (en) 2025-03-28

Similar Documents

Publication Publication Date Title
KR101066712B1 (en) Methods and apparatuses for time tracking using assistance from TMD pilots in a communication network
JP2002518880A (en) OFDM bus, carrier frequency synchronization and repetition frequency domain frame synchronization
CN101421948B (en) Channel estimation method and apparatus using linear interpolation scheme in orthogonal frequency division multiplexing system
WO2006111843A1 (en) Time domain windowing and inter-carrier interference cancellation
CN101924723A (en) OFDM signal demodulation method and device
CN101394381A (en) An Adaptive Equalizer for Phase Noise Compensation
JPWO2007020943A1 (en) OFDM communication method
Wu et al. A preamble-aided symbol and frequency synchronization scheme for OFDM systems
Geng et al. Dual-diagonal LMMSE channel estimation for OFDM systems
US8817918B2 (en) Cyclic prefix and precursor joint estimation
CN103873397A (en) Novel estimation method for orthogonal frequency-division multiplexing receiving channel combining time domain and frequency domain
CN110460550B (en) An interference cancellation detection method suitable for short cyclic prefix OFDM
CN107770110A (en) A kind of sending method of discontinuous frame, channel compensating method
JP2000165341A (en) OFDM demodulation circuit
EP1535404A1 (en) Channel estimation for communication systems
CN108650199B (en) Method and device for IQ imbalance and channel joint estimation at wireless communication receiver
CN118748635A (en) A frequency deviation estimation method and system for WIFI6 system
CN106059967A (en) Single carrier channel estimating method
WO2008109267A1 (en) System and method for performing channel estimation using interpolation
CN105991489B (en) The method of channel equalization is realized using frequency domain over-sampling
Abhayawardhana et al. Residual frequency offset correction for coherently modulated OFDM systems in wireless communication
CN113099427B (en) Sparsity self-adaptive in-band deployment NB-IoT signal recovery method
Gunther et al. A new approach for symbol frame synchronization and carrier frequency estimation in OFDM communications
CN107835141B (en) Self-correlation and cross-correlation combined multi-segment repeated sequence OFDM synchronization algorithm
CN115514606B (en) High-precision timing estimation method based on mutual quality sampling

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant