CN112910435B - Duplexer device and network implementation method thereof - Google Patents
Duplexer device and network implementation method thereof Download PDFInfo
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- CN112910435B CN112910435B CN202110099554.1A CN202110099554A CN112910435B CN 112910435 B CN112910435 B CN 112910435B CN 202110099554 A CN202110099554 A CN 202110099554A CN 112910435 B CN112910435 B CN 112910435B
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H9/00—Networks comprising electromechanical or electro-acoustic elements; Electromechanical resonators
- H03H9/46—Filters
- H03H9/64—Filters using surface acoustic waves
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H9/00—Networks comprising electromechanical or electro-acoustic elements; Electromechanical resonators
- H03H9/70—Multiple-port networks for connecting several sources or loads, working on different frequencies or frequency bands, to a common load or source
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
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Abstract
The invention discloses a duplexer device which comprises an A part structure, a B part structure and a C part structure, wherein the A part structure and the B part structure are the same and are in axial symmetry arrangement relative to the C part structure, and the A part structure comprises loads Z arranged in sequence LA Characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 Characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 Characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 Said transmission line A 0 And a transmission line A 2 Between them through T-shaped joints T A And a characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 The C part structure comprises a load Z Lc A transmission line C 0 And T-shaped joint T C Said T-shaped joint T C The invention also discloses a corresponding network implementation method. The invention combines the quarter-wave line and the filter in the traditional duplex network, so that the functional structure is more compact; the passive three-port duplex network with small size, no additional device and common port DC bias is realized.
Description
Technical Field
The embodiment of the invention belongs to the field of radio frequency microwaves for laser equipment, and particularly relates to a duplexer device and a network implementation method thereof.
Background
In the radio communication equipment, a great deal of duplexers are needed, which are different-frequency duplex radio stations and are used for isolating the transmitted and received signals and ensuring that both the receiving and transmitting can work normally. The band elimination filter is composed of two groups of band elimination filters with different frequencies, and prevents a signal transmitted by a local transmitter from being transmitted to a receiver; the traditional duplex network is realized by connecting a T-shaped joint with two quarter-wavelength lines with respective central wavelengths and then connecting a filter, and because the quarter-wavelength lines and the filter independently exist, the overall size is related to the sum of the two parts, and the size is often larger; secondly, at least one filter in the duplex network is usually a band pass or a high pass, and the direct current bias voltage cannot be shared.
Disclosure of Invention
In view of the above-mentioned drawbacks and needs of the prior art, the present invention is directed to a passive three-port duplex network with a more compact functional structure and no additional devices while providing common port dc bias.
To achieve the above object, the present invention relates to: a duplexer device comprises an A part structure, a B part structure and a C part structure, wherein the A part structure and the B part structure are the same and are in axial symmetry arrangement relative to the C part structure, and the A part structure comprises a load Z sequentially arranged LA Characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 Characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 Characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 Said transmission line A 0 And a transmission line A 2 Between them through T-shaped joints T A And a characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 The C part structure comprises a load Z Lc A transmission line C 0 And T-shaped joint T C Said T-shaped joint T C Is connected with the A part structure and the B part structure.
Further, the part A structure and the part B structure are arranged in an axial symmetry mode relative to the part C structure.
Furthermore, transition units are arranged among the transmission lines.
Further, the transition unit is composed of a short transmission line with linearly-graded characteristic impedance.
In general, compared with the prior art, the above technical solution contemplated by the present invention can achieve the following beneficial effects:
(1) The duplexer device of the invention has the advantages that the plurality of sections of microstrip lines and each section of microstrip line in the minor matters play the role of impedance conversion and the role of a resonant network, which is equivalent to combining a quarter-wavelength line and a filter in the traditional duplex network, thereby leading the functional structure to be more compact.
(2) The duplexer device of the invention does not need any additional device and is communicated under direct current because the microstrip lines are connected with each other, and can directly and simultaneously share direct current bias. Therefore, the passive three-port duplex network with small size and no additional device and with common port DC bias can be realized.
Drawings
FIG. 1 is a schematic overall structure of a preferred embodiment of the present invention;
fig. 2 is a schematic element-labeled diagram of fig. 1.
FIG. 3 is a schematic overall structure (with transition unit) of the preferred embodiment of the present invention;
fig. 4 is a microstrip line implementation diagram according to a preferred embodiment of the invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the invention. In addition, the technical features involved in the respective embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.
Example 1:
referring to fig. 1-2, a duplexer device includes an a-portion structure, a B-portion structure and a C-portion structure, the a-portion structure and the B-portion structure are the same and are arranged in axial symmetry with respect to the C-portion structure, the a-portion junction is disposed on the C-portion structureThe structure comprising loads Z arranged in sequence LA Characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 Characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 Characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 Said transmission line A 0 And a transmission line A 2 Between them through T-shaped joints T A And characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 The C part structure comprises a load Z Lc A transmission line C 0 And T-shaped joint T C Said T-shaped joint T C Is connected with the A part structure and the B part structure.
Example 2:
referring to fig. 3, the difference from embodiment 1 is that, in order to achieve the purpose of further optimization, an impedance transition unit is disposed between the transmission lines, and the impedance transition unit is formed by short transmission lines with linearly gradually changing characteristic impedances, and performs impedance linear transition on the front and rear transmission lines with different characteristic impedances, so that the reflection coefficient at the connection point of the two transmission lines is reduced, and the original input impedance value is optimized.
The network implementation method of the duplexer device specifically comprises the following steps:
port (1) of part A configuration from load Z LA Initially, through a characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 At this time Z in1 At an input impedance of
Then is compared with the characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 Are connected with each other, and the open-circuit branch is at Z in2 At an input impedance of
After slave combination in Z in3 At an input impedance of
Then passes through a characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 When Z is in4 At an input impedance of
Then passes through a characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 At this time Z in5 At an input impedance of
The topology structure of the part B is the same as that of the part A which is just analyzed from the port (2), and according to the required duplex frequency band, the characteristic impedance, the phase coefficient and the length of each transmission line are optimized by adopting a quasi-Newton method (other optimization algorithms such as a gradient descent algorithm or a genetic algorithm can also be adopted) according to the following targets; the quasi-Newton method is one of the most effective methods for solving the nonlinear optimization problem, has the advantage of high convergence rate, and mainly uses an approximate matrix of a sea plug matrix to replace the original plug-returning matrix, so that the complexity of operation is reduced by the method. The main process is to derive the conditions to be met by the sea plug matrix, namely the quasi-Newton condition. And then constructing an approximate matrix meeting the quasi-Newton condition to replace the original sea plug matrix.
Goal 1-part A is brought closer to Z for duplex band 1 in5 →Z L Approach to Z for frequency band 2 in5 →∞；
The suppression of the conduction band 2 of the band 1 is realized in the part a structure, the conduction of the suppression band 2 of the band 1 is realized in the part B structure, and then Z is performed in5 And Z in5 B After combination, at Z in6 Therein is provided with
I.e. to port (3) Z in6 Z for both frequency band 1 and frequency band 2 in6 →Z L Thus, the duplex effect is formed between the ports (1), (2) and (3) finally; based on the optimized transmission line values, the microstrip lines are used for realizing concrete implementation, the matching of the two links at the corresponding pass bands at the interfaces is realized, the equivalent of the stop bands is an open circuit, and meanwhile, the corresponding frequency matching of the ports (1), (2) and (3) is realized integrally and simultaneously; finally, a direct-current communicated duplex network is realized; in the above formulas → approach is indicated by j, which represents an imaginary unit, and the symbol with B superscript indicates that the B-part structure corresponds to the input impedance.
Referring to fig. 4, as shown in fig. 4, an implementation manner on a microstrip line is provided, where the dual-port network includes one or more sections of transmission lines with specific impedance and length and open-circuit branches, the input of the port (1) is divided into two paths by a T-junction, and the two paths are respectively connected to the port (2) and the port (3) through the sections of transmission lines with specific impedance and specific length and through branches. The middle bottom plate part is a medium part of the PCB, and the routing part is a microstrip line.
Because the quarter-wave line and the filter are integrated into a whole and are formed by the transmission line and the branch knot which are directly connected, the size of the duplex network is smaller than that of the duplex network formed by the traditional function separation mode, and simultaneously, the direct current path of each port is reserved and the duplex network is realized by the full transmission line, thereby obtaining the duplex network which has smaller size than that of the traditional duplex network, does not have additional elements and simultaneously shares direct current bias.
The scheme of the invention realizes a three-port duplex network which has small size and no additional devices, and the ports can share the DC bias. The S12 and S13 in the corresponding pass band are within-0.5 dB, the S12 and S13 in the stop band are below-10 dB, and the port standing-wave ratio is within 1.5. In addition, the frequency band and the index can be adjusted by optimizing the number, the impedance and the length of the transmission lines.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.
Claims (5)
1. A network implementation method of a duplexer device is characterized by comprising the following steps:
the method comprises the following steps: performing input impedance calculations: port (1) of part A configuration from load Z LA Initially, through a characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 At this time Z in1 At an input impedance of
Then is compared with the characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 Are connected with each other, and the open-circuit branch is at Z in2 At an input impedance of
After slave combination in Z in3 At an input impedance of
Then passes through a characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 At this time Z in4 At an input impedance of
Then passes through a characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 At this time Z in5 At an input impedance of
The topology and input impedance calculation of the B part structure from the port (2) is the same as that of the A part which is just analyzed;
step two: optimizing the characteristic impedance, the phase coefficient and the length of each transmission line:
optimizing the characteristic impedance, phase coefficient and length of each section of transmission line according to the required duplex frequency band by adopting an optimization algorithm according to the following targets;
goal 1-part A is brought closer to Z for duplex band 1 in5 →Z L Approach to Z for frequency band 2 in5 →∞；
Target 2. Bringing part B towards the duplex band 1 to Z in5 B → infinity, approaches Z to band 2 in5 B →Z L ；
In the above formulae → represents approach, j represents an imaginary unit; the symbol with B superscript represents the corresponding input impedance of the B part structure;
the suppression of the conduction band 2 of the band 1 is realized in the part a structure, the conduction of the suppression band 2 of the band 1 is realized in the part B structure, and then Z is performed in5 And Z in5 B After combination, at Z in6 Input impedance of
I.e. to port (3) Z in6 Z for both frequency band 1 and frequency band 2 in6 →Z L Thus, the duplex effect is formed between the ports (1), (2) and (3); based on the optimized transmission line values, the microstrip lines are used for realizing concrete implementation, the matching of the two links at the corresponding pass bands at the interfaces is realized, the equivalent of the stop bands is an open circuit, and meanwhile, the corresponding frequency matching of the ports (1), (2) and (3) is realized integrally and simultaneously; finally, a direct-current communicated duplex network is realized; wherein Z in1 Transmission line Ao and T-shaped connector T with characteristic impedance Zo phase coefficient beta o length lo A A joint; z in2 Is a characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 Transmission line A of 1 With T-shaped joints T A A joint; z in3 Is a characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 With T-shaped joints T A A joint; z in4 Is a characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 And a characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 The connection of the transmission line of (1); z is a linear or branched member in5 Is a characteristic impedance Z 3 Phase positionCoefficient beta 3 Length l 5 Transmission line and T-shaped connector T C A joint; z in6 Is provided with a transmission line C 0 With T-shaped joints T C A joint; z L Is a load Z LA The impedance of (a);
the network implementation method of the duplexer device uses the device comprising:
the part A structure, the part B structure and the part C structure are the same, and the part A structure comprises loads Z arranged in sequence LA Characteristic impedance Z 0 Phase coefficient beta 0 Length l 0 Transmission line A of 0 Characteristic impedance Z 2 Phase coefficient beta 2 Length l 2 Transmission line A of 2 Characteristic impedance Z 3 Phase coefficient beta 3 Length l 3 +l 4 +l 5 Transmission line A of 3 Said transmission line A 0 And a transmission line A 2 Between them through T-shaped joints T A And characteristic impedance Z 1 Phase coefficient beta 1 Length l 1 The open circuit branches are connected; the C-section structure includes a load Z Lc、 Transmission line C 0 And T-shaped joint T C Said T-shaped joint T C Is connected with the part A structure and the part B structure.
2. The method of claim 1, wherein the A-part structure and the B-part structure are arranged in axial symmetry with respect to the C-part structure.
3. The method of claim 1, wherein an impedance transition unit is disposed between the transmission lines of the A-part structure and the B-part structure.
4. The method of claim 3, wherein the impedance transition unit is formed of a short transmission line having a linearly gradually changing characteristic impedance.
5. The method of claim 1, wherein the optimization algorithm is a quasi-Newton method, a gradient descent algorithm, or a genetic algorithm.
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| DE69426283T2 (en) * | 1993-08-24 | 2001-03-15 | Matsushita Electric Industrial Co., Ltd. | Layered antenna switch and dielectric filter |
| CN203690451U (en) * | 2013-11-27 | 2014-07-02 | 成都九洲迪飞科技有限责任公司 | Duplexer |
| CN104143672B (en) * | 2014-07-21 | 2016-08-24 | 华南理工大学 | A kind of two-frequency duplex device using racemosus nodel line to load matching network |
| CN106207323A (en) * | 2016-08-26 | 2016-12-07 | 成都九洲迪飞科技有限责任公司 | Micro-strip and the duplexer of substrate integration wave-guide mixed structure |
| CN106413259B (en) * | 2016-08-31 | 2019-08-02 | 宇龙计算机通信科技(深圳)有限公司 | The mismatch compensation method and mismatch compensation device of radio-frequency transmission line |
| CN107171044A (en) * | 2017-05-03 | 2017-09-15 | 南京航空航天大学 | A kind of hybrid coupled micro-strip duplexer |
| CN108183293A (en) * | 2017-12-11 | 2018-06-19 | 南京理工大学 | Plane micro-strip duplexer |
| CN212517462U (en) * | 2020-09-29 | 2021-02-09 | 深圳市共进电子股份有限公司 | Tuning duplexer, radio frequency circuit and communication equipment |
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