CN111261989A - Non-reciprocal power divider and electromagnetic wave transmission device - Google Patents

Abstract

The invention provides a non-reciprocal power divider and an electromagnetic wave transmission device. The non-reciprocal power divider comprises: a dielectric substrate, at least one Wilkinson power divider; the port of the Wilkinson power divider serves as a non-reciprocal power divider. The radio frequency port of the changeable power divider; the Wilkinson power divider is arranged on the top surface of the dielectric substrate, each branch of the Wilkinson power divider includes a filter, and the filter is composed of at least two resonators; The back is provided with a plurality of varactor diodes, a plurality of signal feeding circuits, a plurality of metallized through holes and a plurality of modulation ports; the modulation ports are used to receive modulation signals, and each modulation port is respectively connected to a metal through a signal feeding circuit One end of each varactor diode is connected to one end of a resonator through a metallized through hole, and the other end of each varactor diode is grounded. The present invention realizes the non-reciprocal power divider without any magnetic material bias, and can integrate with the circuit and the like.

Description

Non-reciprocal power divider and electromagnetic wave transmission device

technical field

The invention relates to semiconductor technology, in particular to a non-reciprocal power divider and an electromagnetic wave transmission device.

Background technique

In mobile communication systems, radio frequency non-reciprocal devices are essential system components. Non-reciprocity means that when electromagnetic waves propagate in two opposite directions in a medium, they will exhibit different electromagnetic wave transmission characteristics.

Common RF non-reciprocal devices include isolators and circulators. Isolators protect signal sources from high-power reflected signals, and circulators direct electromagnetic waves. Non-reciprocal devices in the prior art usually use magnetic materials and an external magnetic field bias to break the time-reversal symmetry to achieve non-reciprocity in electromagnetic wave transmission. These non-reciprocal devices often exist due to the use of magnetic materials. Disadvantages such as high loss, large size, high cost and inability to integrate with circuits.

With the rapid development of 5G communication, the frequency spectrum used in mobile communication is getting higher and higher, and the requirements for miniaturization and integration of devices are getting higher and higher. Almost all non-reciprocal radio frequency devices in the prior art need to use magnetic materials such as ferrite to break the time-reversal symmetry, and the lattice of magnetic materials is different from the processing technology of CMOS (complementary metal-oxide-semiconductor) integrated circuits. Compatibility makes it difficult for these radio frequency devices to be integrated with the system circuit, which is not conducive to realizing the miniaturization of the equipment.

SUMMARY OF THE INVENTION

The present invention provides a non-reciprocal power divider that can be integrated with a circuit without biasing a magnetic material. The non-reciprocal power divider provided by the present invention includes: a dielectric substrate, and at least one Wilkinson power divider; a port of the Wilkinson power divider serves as a radio frequency port of the non-reciprocal power divider; wherein ,

The Wilkinson power divider is arranged on the top surface of the dielectric substrate, and each branch of the Wilkinson power divider includes a filter, and the filter is composed of at least two resonators;

The back of the dielectric substrate is provided with a plurality of varactor diodes, a plurality of signal feeding circuits, a plurality of metallized through holes and a plurality of modulation ports; the modulation ports are used for receiving modulation signals, and each modulation port passes a signal The feeding circuit is connected to a metallized through hole, one end of each varactor diode is respectively connected to one end of a resonator through a metallized through hole, and the other end of each varicap diode is grounded.

In the embodiment of the present invention, the resonators of the filters are arranged in a staggered manner.

In the embodiment of the present invention, the Wilkinson power divider is a Wilkinson power divider with a microstrip structure.

In the embodiment of the present invention, the backside of the dielectric substrate is further provided with a plurality of inductors, and each signal feeding circuit is respectively connected to the metallized through hole through an inductor.

In the embodiment of the present invention, each of the signal feeding circuits is a circuit of a coplanar waveguide structure.

In this embodiment of the present invention, the modulation signal includes: a DC bias voltage signal and/or a low-frequency modulation signal.

In the embodiment of the present invention, the resonator is a microstrip resonator.

At the same time, the present invention also provides a non-reciprocal electromagnetic wave transmission device, the non-reciprocal power divider, DC voltage source and low-frequency signal source mentioned above in the device;

The DC voltage source and the low-frequency signal source provide modulation signals for the non-reciprocal power divider through the modulation port.

The non-reciprocal power divider of the present invention does not need any magnetic material bias, adopts the control of time-space control to break the time reversal symmetry, realizes the non-reciprocal power divider, and can control the value of the DC bias voltage. A non-reciprocal power divider with adjustable operating frequency is realized. It does not need any magnetic material bias and is integrated with the filter. It has the advantages of low cost, miniaturization, and the ability to integrate with circuits. In addition to the function of power divider energy distribution, it also has the ability to filter and suppress out-of-band interference signals.

In order to make the above-mentioned and other objects, features and advantages of the present invention more obvious and easy to understand, the preferred embodiments are exemplified below, and are described in detail as follows in conjunction with the accompanying drawings.

Description of drawings

In order to explain the embodiments of the present invention or the technical solutions in the prior art more clearly, the following briefly introduces the accompanying drawings that need to be used in the description of the embodiments or the prior art. Obviously, the accompanying drawings in the following description are only These are some embodiments of the present invention. For those of ordinary skill in the art, other drawings can also be obtained according to these drawings without creative efforts.

FIG. 1 is a top view of the structure diagram of the non-reciprocal power divider of the present invention.

Fig. 2 is the bottom view of the structure diagram of the non-reciprocal power divider of the present invention;

3 is a partial enlarged view of a metallized through hole in a non-reciprocal power divider according to an embodiment of the present invention;

Fig. 4 is the test curve of the power divider scattering parameter test when the low-frequency modulation signal is not loaded and only the DC bias voltage signal is loaded in the embodiment of the present invention;

FIG. 5 is an experimental test curve of the scattering parameters of the non-reciprocal power divider after the modulation signal is loaded in the embodiment of the present invention;

6 is an experimental test curve of the scattering parameters of the non-reciprocal power divider after changing the phase relationship of the modulated signal in the embodiment of the present invention;

7 is an experimental test curve of the scattering parameters of the non-reciprocal power divider after reducing the DC bias voltage in the embodiment of the present invention;

FIG. 8 is an experimental test curve of the scattering parameters of the non-reciprocal power divider after increasing the DC bias voltage in the embodiment of the present invention.

Detailed ways

The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention. Obviously, the described embodiments are only a part of the embodiments of the present invention, but not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those of ordinary skill in the art without creative efforts shall fall within the protection scope of the present invention.

The present invention provides a non-reciprocal power divider, comprising: a dielectric substrate, at least one Wilkinson power divider; a port of the Wilkinson power divider serves as a radio frequency port of the non-reciprocal power divider; wherein,

The Wilkinson power divider is arranged on the top surface of the dielectric substrate, and each branch of the Wilkinson power divider includes a filter, and the filter is composed of at least two resonators;

The back of the dielectric substrate is provided with a plurality of varactor diodes, a plurality of signal feeding circuits, a plurality of metallized through holes and a plurality of modulation ports; the modulation ports are used for receiving modulation signals, and each modulation port passes a signal The feeding circuit is connected to a metallized through hole, one end of each varactor diode is respectively connected to one end of a resonator through a metallized through hole, and the other end of each varicap diode is grounded.

The invention relates to a non-reciprocal power divider based on time-space regulation, which does not require any magnetic material bias to realize the non-reciprocity of electromagnetic wave transmission. The transmission direction of the electromagnetic wave can be controlled by controlling the phase relationship of each low-frequency modulation signal; and the reconfigurable characteristic of the working frequency can be realized by adjusting the DC bias voltage loaded by the varactor diode.

The non-reciprocal power divider provided by the present invention can break the symmetry of time inversion by applying a modulation signal to the modulation port, and realize the method of using time-space modulation, and can realize a non-reciprocal radio frequency device without any magnetic material. In the embodiment of the present invention, the general implementation method of the time-space modulation is: discretely loading the time-varying modulation signal, and controlling the frequency, amplitude and initial phase of each modulation signal to realize the non-reciprocal propagation of electromagnetic waves.

With the gradual large-scale commercial deployment of 5G and the in-depth research on B5G/6G mobile communication, mobile communication systems are constantly developing in the direction of integration, and the requirements for the integration of radio frequency devices are getting higher and higher. The non-reciprocal devices controlled by time and space do not need magnetic material bias, have the characteristics of compatibility with CMOS process, and can be integrated with system circuits. Therefore, they have great application prospects in circuit miniaturization and integration.

The technical solution of the present invention will be described in further detail below with reference to a specific embodiment.

The non-reciprocal power divider based on the time-space control provided in this embodiment is implemented by the integrated integration of the Wilkinson power divider and the filter. In the embodiment of the present invention, the non-reciprocal power divider includes: a dielectric substrate, several microstrip resonators, several radio frequency ports, several modulation signal input terminals, several inductors, and several varactor diodes.

FIG. 1 is a top view of the structure diagram of the non-reciprocal power divider provided in this embodiment. The power divider provided in this embodiment is a one-to-two-level power divider.

The top surface of the dielectric substrate includes: three radio frequency ports, a Wilkinson power divider 102 divided into two parts, and each branch of the power divider includes a filter. In the embodiment of FIG. 1 , the filter is a third-order filter, and the third-order filter is composed of three interleaved resonators 1031 .

In this embodiment, the Wilkinson power divider 102 is implemented by a microstrip structure, which is composed of a microstrip line structure 1021 with a characteristic impedance of 50 ohms and a microstrip line structure 1022 with a length of a quarter wavelength and a characteristic impedance of 70.7 ohms , a microstrip line structure 1023 with a characteristic impedance of 50 ohms and a resistor 1024 with a resistance value of 100 ohms.

A third-order microstrip filter is cascaded behind the microstrip line structure 1023 in the two branches of the Wilkinson power divider, and the coupling output end of the third-order filter is a microstrip line structure 1025 with a characteristic impedance of 50 ohms, respectively. For RF port 2 and RF port 3.

The radio frequency port 1, the radio frequency port 2, and the radio frequency port 3 are the input and output ports of the radio frequency signal. If the RF signal is fed from the RF port 1, then the RF port 2 and the RF port 3 are the RF signal output ports; if the RF signal is fed from the RF port 2 and the RF port 3, then the RF port 1 is the RF signal output port.

Each third-order filter described is composed of three microstrip resonators, the first branch includes resonator 1031, resonator 1032 and resonator 1033, and the second branch includes resonator 1034, resonator 1035 and resonator 1036, The three microstrip resonators of each branch are staggered in turn, and the coupling strength can be effectively controlled by controlling the distance between the microstrip resonators. connect.

As shown in FIG. 2 , it is a schematic diagram of the bottom of the dielectric substrate in the embodiment of the present invention. The bottom of the dielectric substrate in this embodiment includes: six modulated signal feed circuits, six modulated signal terminals, six inductors and six varactor diodes.

On the back copper clad plate of the dielectric board, six modulated signals are fed into the circuit 20, and each modulated low frequency signal and the DC bias voltage signal are fed into the modulated signal feeding circuit from the modulating port.

The six-channel modulation signal feeding circuit adopts the structure of a coplanar waveguide to transmit the low frequency modulation signal and the DC bias voltage signal. In this embodiment, the characteristic impedance of the coplanar waveguide is designed to be 50 ohms. The end of each modulation signal feeding circuit and the metallized through hole 30 are connected by inductance to increase the isolation between the RF signal port and the modulation signal port.

One end of the varactor diode is connected to the microstrip resonator through a metallized through hole, and the other end of the varactor diode is connected to the metal ground. The varactor diode works in a reverse biased state and functions as a capacitor. As shown in FIG. 3 , it is a schematic diagram of the connection between the metallized through hole 30 , the inductor 40 and the varactor diode 50 in the embodiment of the present invention.

After the modulation port 301 is fed with a low-frequency modulation signal with a DC bias voltage, the microstrip resonator 1 connected to the varactor diode also becomes a time-varying resonator. Similarly, after the modulation port 302 is fed with a low-frequency modulation signal with a DC bias voltage, the microstrip resonator 1032 connected to the varactor diode also becomes a time-varying resonator; the modulation port 303 is fed with a DC bias voltage After the low-frequency modulation signal of the voltage, the microstrip resonator 1033 connected with the varactor diode also becomes a time-varying resonator; after the modulation port 304 is fed with a low-frequency modulation signal with a DC bias voltage, it is in phase with the varactor diode. The connected microstrip resonator 1034 also becomes a time-varying resonator; after the modulation port 305 is fed with a low-frequency modulation signal with a DC bias voltage, the microstrip resonator 1035 connected to the varactor diode also becomes a time-varying resonator. After the modulation port 306 is fed with a low-frequency modulation signal with a DC bias voltage, the microstrip resonator 1036 connected with the varactor diode also becomes a time-varying resonator.

The non-reciprocal power divider in the embodiment of the present invention is symmetrical, and the two branches are exactly the same. The time-space control implementation method is as follows: the modulation port 301, the modulation port 302, and the modulation port 303 are sequentially fed into the time with DC bias. Variable low frequency modulation signal;

The frequency of the low frequency modulation signal is:

ω _m = 2πf _m

(i对应于调制端口序号为301、302、303)。Phase is

(i corresponds to the modulation port serial numbers 301, 302, 303).

At this time, the variation formula of the capacitance value of each varactor diode with time near the static point is:

In the formula, C ₀ is the static capacitance value, which is determined by the DC bias voltage. This static capacitance value will affect the resonant frequency of the resonator, thereby affecting the operating frequency of the non-reciprocal power divider;

In the actual use of the project, the varactor diode will have a capacitance value-voltage value curve, that is, the relationship (curve) of the capacitance value with the change of the bias voltage. This relationship curve is usually provided by the selected varactor diode data sheet;

Secondly, static means that the low-frequency time-varying modulation signal (dynamic signal) is not loaded on the varactor diode, but only the DC bias voltage is loaded. Because there is only a DC bias voltage (which does not change with time, we call it static), the change at this time is The capacitance value presented by the capacitor diode is called the static capacitance value (which does not change with time), and this capacitance value can be determined by the relationship curve of the capacitance value with the change of the bias voltage, that is, refer to the product data manual of the selected varactor diode. Therefore, according to the DC bias voltage, the static capacitance value can be determined.

Δ _m =Δ _C /C ₀ , is the modulation coefficient (0<Δ _m <1), and Δ _C is the capacitance fluctuation amplitude, which is controlled by the amplitude of the modulation signal.

At the same time, the modulation port 304 and the modulation port 301, the modulation port 305 and the modulation port 302, and the modulation port 306 and the modulation port 303 are fed with exactly the same time-varying low-frequency modulation signal with DC bias, including the same DC bias voltage value, The same low frequency modulation signal frequency, amplitude and initial phase.

The DC bias voltage fed into the modulation port is controlled by a DC voltage source external to the modulation port; the low-frequency modulation signal fed into the modulation port is controlled by a low-frequency signal source external to the modulation port. The DC bias voltage acts on the varactor diode, the magnitude of the bias voltage directly affects the operating frequency of the power divider, and its initial value needs to be determined according to the data sheet of the selected type of varactor diode; the frequency of the low-frequency modulation signal should be less than The passband bandwidth of the integrated filter; the amplitude of the low-frequency modulation signal will affect the modulation coefficient Δ _m , and the initial value of the modulation coefficient can be set to 0.1; the initial value of the phase of the low-frequency modulation signal can be between 30 degrees and 120 degrees.

When the present invention is implemented, according to the specific operating frequency requirements of the required non-reciprocal power divider, after comprehensively adjusting the DC bias voltage, the frequency of the low-frequency modulation signal, the amplitude of the low-frequency modulation signal and the phase of the low-frequency modulation signal, the non-reciprocal power divider The device can get the best response. The control of the RF signal transmission is realized by adjusting the phase of the low-frequency modulation signal fed into the adjustment port.

时，其中

为步进相位，那么射频信号可以从射频端口1平均的分配传输到射频端口2和射频端口3，而射频信号却不能够有效的从射频端口2和射频端口3传输到射频端口1；When the phases of the low-frequency modulation signals fed into the modulation port 301, modulation port 302 and modulation port 303 are controlled to satisfy the

when, of which

In order to step the phase, the RF signal can be equally distributed from RF port 1 to RF port 2 and RF port 3, but the RF signal cannot be effectively transmitted from RF port 2 and RF port 3 to RF port 1;

时，射频信号可以从射频端口2和射频端口3传输到射频端口1，而射频信号却不能够有效的从射频端口1传输到射频端口2和射频端口3，实现了电磁波的非互易性传输。On the contrary, when the phases of the low-frequency modulation signals fed into the modulation port 301, modulation port 302 and modulation port 303 are controlled to satisfy the

When the RF signal is transmitted from the RF port 2 and the RF port 3 to the RF port 1, the RF signal cannot be effectively transmitted from the RF port 1 to the RF port 2 and the RF port 3, which realizes the non-reciprocal transmission of electromagnetic waves. .

和

中，i为计数用，i＝1,2…n；n为滤波器阶数；abovementioned

and

Among them, i is for counting, i=1,2...n; n is the filter order;

In a specific embodiment, if the filter integrated in each branch of the power divider is a third-order, that is, three modulated signals need to be loaded, then i=1, 2, and 3.

If the filter integrated in each branch of the power divider is second-order, then i=1,2.

If the filter integrated in each branch of the power divider is fifth-order, then i=1,2,3,4,5.

In short, the value of i starts from 1, and the maximum value is the integrated filter order.

Changing the value of the DC bias voltage fed into the modulation port also changes the static capacitance value of the varactor diode, so that the operating frequency of the non-reciprocal power divider can be controlled. When the value of the DC bias voltage fed into the modulation port is decreased, the static capacitance of the varactor diode increases, so that the operating frequency of the non-reciprocal power divider decreases; when the DC bias fed into the modulation port is increased When the value of the voltage is increased, the static capacitance value of the varactor diode decreases, so that the operating frequency of the non-reciprocal power divider increases.

In addition, in the nonvolatile power divider provided by the embodiment of the present invention, the modulation signal port 301 , the modulation signal port 302 , the modulation signal port 303 , the modulation signal port 304 , the modulation signal port 305 , and the modulation signal port 306 remove low-frequency modulation After the signal is transmitted, the electromagnetic wave transmission in the power divider provided by the embodiment of the present invention is completely reciprocal.

FIG. 1 and FIG. 2 of the embodiment of the present invention only take a one-to-two Wilkinson power divider and a third-order filter as examples for description. With the technical solution of the present invention, according to actual engineering needs, any one-to-two power divider can be divided into more than one. The required non-reciprocal power divider can be realized by integrating the Wilkinson power divider with any filter of two or more orders, that is, the implementation manner mentioned in the embodiments of the present invention is not limited.

The non-reciprocal power divider provided by the embodiment of the present invention does not require any magnetic material bias, adopts the time-space control method to break the symmetry of time reversal, realizes the non-reciprocal power divider, and controls the DC The value of the bias voltage can realize a non-reciprocal power divider with adjustable operating frequency.

The non-reciprocal power divider provided by the embodiment of the present invention does not require any magnetic material bias and is integrated with the filter, and has the advantages of low cost, miniaturization, and integration with circuits. In addition to the function, it also has the ability to filter and suppress out-of-band interference signals.

In the embodiment of the present invention, the adopted dielectric substrate is an F4B substrate with a relative dielectric constant of 2.55, a loss tangent value of 0.0015, a thickness of 1.27 mm, a size of l ₁ =114 mm, and w ₁ =69.4 mm. As shown in the top view of FIG. 1 , the non-reciprocal power divider according to the present invention is symmetrical in structure.

The parameters of the integrated Wilkinson power divider in the embodiment of the present invention are as follows:

The characteristic impedance of the first part 1021 of the microstrip structure of the Wilkinson power divider is 50 ohms, the length l ₂ =15mm, and the width is 3.4mm;

The characteristic impedance of the transition band 1022 of the Wilkinson power divider is 70.7 ohms, the length l ₃ =20.4mm, the width is 1.85mm, and the spacing g ₃ =1.65mm;

The characteristic impedance of the third part 1023 of the microstrip structure of the Wilkinson power divider is 50 ohms, the length l ₄ =43.7mm, l ₅ =6.7mm, and the width is 3.4mm;

The resistance value of the resistor 1024 welded between the two branches of the Wilkinson power divider is 100 ohms.

The resonator 1031 and the resonator 1033 of the microstrip structure in the integrated third-order filter structure of the present invention have the same length of l ₈ =25mm, the length of the resonator 1032 is l ₉ =24.4mm, and the width of the microstrip resonator is equal to is 1.6mm.

When optimizing the design of the microstrip line filter, attention should be paid to adjusting the spacing between the resonators to achieve good impedance matching. In this preferred example, the spacing g ₁ =0.5mm, g ₂ =2.4mm.

The metallized vias at the ends of the microstrip resonators are 0.5 mm in diameter.

The radio frequency port 2 and the radio frequency port 3 adopt a microstrip line structure with a characteristic impedance of 50 ohms, that is, w ₂ =3.4mm, and the length dimensions of the microstrip line structure l ₆ =28.3mm and l ₇ =16.7mm.

In the embodiment of the present invention, the model of the varactor diode is SMV1232, and the inductance is a chip inductance value of 52nH. The characteristic impedance of the coplanar waveguide is 50 ohms, that is, g ₄ =0.22mm, w ₃ =3mm, and the length dimensions of the coplanar waveguide are l ₁₀ =10.3mm and l ₁₁ =8mm.

As shown in FIG. 3 , a circular surface with a diameter of Φ ₁ =2mm is removed from the metal base plate, and a metal circular surface with a diameter of Φ ₂ =1mm is placed to fix and weld the varactor diode and the inductor.

The RF signal is fed from RF port 1 or RF ports 2 and 3, and the DC bias voltage and low-frequency modulation signal are fed in by modulation port 301, modulation port 302, and modulation port 303 in turn, and ensure that modulation port 304 and modulation port 301, modulation The DC bias voltage and the low-frequency modulation signal fed into the port 305 and the modulation port 302 and the modulation port 306 and the modulation port 303 are exactly the same. The non-reciprocity of electromagnetic wave transmission is achieved by controlling the frequency, amplitude and phase relationship of the low-frequency modulated signal.

When the modulation port 301, the modulation port 302, the modulation port 303, the modulation port 304, the modulation port 305 and the modulation port 306 only load the DC bias voltage signal without loading the low-frequency modulation signal, the designed power divider is reciprocal, The experimental test data is shown in Figure 4. The return loss _S11 of the power divider is less than -10dB near the in-band operating frequency band of 2.4GHz, which has good return loss characteristics. Good filter suppression.

As can be seen from Figure 4, at this time, the radio frequency signal is transmitted from the radio frequency port 1 to the radio frequency port 2 and the radio frequency port 3, and the radio frequency signal can also be transmitted from the radio frequency port 2 and the radio frequency port 3 to the radio frequency port 1, that is, S ₂₁ =S ₁₂ , S ₃₁ =S ₁₃ , since it is equal power division, so S ₂₁ =S ₃₁ . There is an additional 2.5dB insertion loss due to energy losses in lumped devices such as varactors and inductors.

步进相位

度，同时确保调制端口304与调制端口301、调制端口305与调制端口302、调制端口306与调制端口303馈入的直流偏置电压和低频调制信号完全相同，非互易性功分器响应如图5所示，试验测试中直流偏置电压为1.9V，低频调制信号频率f_m＝70MHz，调制系数Δ_m＝0.08。When the modulation port 301, the modulation port 302 and the modulation port 303 are sequentially fed with a low-frequency modulation signal with a DC offset, and the phases of the three-way modulation signals are sequentially satisfied

step phase

At the same time, ensure that modulation port 304 and modulation port 301, modulation port 305 and modulation port 302, modulation port 306 and modulation port 303 feed the same DC bias voltage and low-frequency modulation signal. The non-reciprocal power divider responds as follows As shown in FIG. 5 , in the test, the DC bias voltage is 1.9V, the frequency of the low-frequency modulation signal is f _m =70MHz, and the modulation coefficient Δ _m =0.08.

It can be seen from Figure 5 that the return loss _S11 of the non-reciprocal power divider is less than -10dB near the in-band operating frequency band of 2.4 GHz, which has good return loss characteristics, and at the same time has good filtering and suppression of out-of-band interference signals. effect. In addition, it can be seen from Fig. 3 that S ₂₁ ≠S ₁₂ , S ₃₁ ≠S ₁₃ , the electromagnetic wave propagation has a non-reciprocity of about 10dB, the electromagnetic wave can be transmitted from the RF port 1 to the RF port 2 and the RF port 3, but the electromagnetic wave cannot RF port 2 and RF port 3 transmit to RF port 1. The invented non-reciprocal power divider has good port isolation S ₃₂ better than 30dB.

步进相位

度，同时确保调制端口304与调制端口301、调制端口305与调制端口302、调制端口306与调制端口303馈入的直流偏置电压和低频调制信号完全相同，非互易性功分器响应。如图6所示，试验测试中直流偏置电压为1.9V，低频调制信号频率f_m＝70MHz，调制系数Δ_m＝0.08。When the modulation port 301, the modulation port 302 and the modulation port 303 are sequentially fed with a low-frequency modulation signal with a DC offset, and the phases of the three-way modulation signals are adjusted to satisfy the requirements in sequence

step phase

At the same time, ensure that the modulation port 304 and modulation port 301, modulation port 305 and modulation port 302, modulation port 306 and modulation port 303 feed the same DC bias voltage and low-frequency modulation signal, and the non-reciprocal power divider responds. As shown in FIG. 6 , in the test, the DC bias voltage is 1.9V, the frequency of the low-frequency modulation signal is f _m =70MHz, and the modulation coefficient Δ _m =0.08.

It can be seen from Figure 6 that the return loss _S11 of the non-reciprocal power divider is less than -10dB near the in-band operating frequency band of 2.4 GHz, which has good return loss characteristics, and at the same time has good filtering and suppression of out-of-band interference signals. effect. In addition, it can be seen from Fig. 4 that S ₁₂ ≠S ₂₁ , S ₁₃ ≠S ₃₁ , the electromagnetic wave propagation has a non-reciprocity of about 10dB. At this time, the electromagnetic wave can be transmitted from the radio frequency port 2 and the radio frequency port 3 to the radio frequency port 1, while the electromagnetic wave is not reciprocal. It is not possible to transmit from RF port 1 to RF port 2 and RF port 3.

步进相位

度，同时确保调制端口304与调制端口301、调制端口305与调制端口302、调制端口306与调制端口303馈入的直流偏置电压和低频调制信号完全相同，并控制直流偏置电压为0.4V，此时非互易性功分器响应如图7所示，试验测试中低频调制信号频率f_m＝70MHz，调制系数Δ_m＝0.08。When the modulation port 301, the modulation port 302 and the modulation port 303 are sequentially fed with a low-frequency modulation signal with a DC offset, and the phases of the three-way modulation signals are sequentially satisfied

step phase

At the same time, ensure that the modulation port 304 and modulation port 301, modulation port 305 and modulation port 302, modulation port 306 and modulation port 303 feed the same DC bias voltage and low-frequency modulation signal, and control the DC bias voltage to 0.4V , and the response of the non-reciprocal power divider is shown in Figure 7. In the test, the frequency of the low-frequency modulation signal is f _m =70MHz, and the modulation coefficient Δ _m =0.08.

It can be seen from Figure 7 that the return loss _S11 of the non-reciprocal power divider is less than -10dB near the in-band operating frequency band of 2.2 GHz, which has good return loss characteristics, and at the same time has good filtering and suppression of out-of-band interference signals. effect. In addition, it can be seen from Figure 5 that S ₂₁ ≠S ₁₂ , S ₃₁ ≠S ₁₃ , the electromagnetic wave propagation has a non-reciprocity of about 10dB, and electromagnetic waves can be transmitted from RF port 1 to RF port 2 and RF port 3, but electromagnetic waves cannot RF port 2 and RF port 3 transmit to RF port 1. It can be seen that when the value of the DC bias voltage fed into the modulation port is reduced, the operating frequency of the non-reciprocal power divider is reduced, and the adjustable characteristic of the operating frequency is realized.

步进相位

度，同时确保调制端口304与调制端口301、调制端口305与调制端口302、调制端口306与调制端口303馈入的直流偏置电压和低频调制信号完全相同，并控制直流偏置电压为3.5V，此时非互易性功分器响应如图8所示，试验测试中低频调制信号频率f_m＝70MHz，调制系数Δ_m＝0.08。When the modulation port 301, the modulation port 302 and the modulation port 303 are sequentially fed with a low-frequency modulation signal with a DC offset, and the phases of the three-way modulation signals are sequentially satisfied

step phase

At the same time, ensure that the modulation port 304 and modulation port 301, modulation port 305 and modulation port 302, modulation port 306 and modulation port 303 feed the same DC bias voltage and low-frequency modulation signal, and control the DC bias voltage to 3.5V , and the response of the non-reciprocal power divider is shown in Figure 8. In the test, the frequency of the low-frequency modulation signal is f _m =70MHz, and the modulation coefficient Δ _m =0.08.

It can be seen from Figure 8 that the return loss _S11 of the non-reciprocal power divider is less than -10dB near the in-band operating frequency band of 2.6 GHz, which has good return loss characteristics, and at the same time has good filtering and suppression of out-of-band interference signals. effect. In addition, it can be seen from Figure 8 that S ₂₁ ≠S ₁₂ , S ₃₁ ≠S ₁₃ , the electromagnetic wave propagation has a non-reciprocity of about 10dB, the electromagnetic wave can be transmitted from the RF port 1 to the RF port 2 and the RF port 3, but the electromagnetic wave cannot RF port 2 and RF port 3 transmit to RF port 1. It can be seen that when the value of the DC bias voltage fed into the modulation port increases, the operating frequency of the non-reciprocal power divider increases, and the adjustable characteristic of the operating frequency is realized.

In addition, it can be found from Figure 4 to Figure 8 that due to the use of lumped devices such as varactor diodes and inductors, as well as part of the energy coupling between the modulation resonators is converted to high-order harmonics

It can be seen from the above embodiments that, unlike the existing radio frequency non-reciprocal devices that rely on magnetic materials such as ferrite for biasing, the non-reciprocal power divider provided by the present invention can adopt a time-space control method, that is, The non-reciprocal transmission of electromagnetic waves is achieved by discretely loading a low-frequency modulation signal with a DC bias voltage on the resonator and controlling the phase relationship of the modulation signal to break the time-reversal symmetry. The non-reciprocal power divider provided by the present invention no longer needs to be biased by magnetic materials such as ferrite, so there is no problem of incompatibility between the magnetic material lattice and the CMOS integrated circuit processing technology.

The preferred embodiments of the present invention have been described above with reference to the accompanying drawings. The many features and advantages of these embodiments are apparent from this detailed description, and the appended claims are therefore intended to cover all such features and advantages of these embodiments as fall within their true spirit and scope. Furthermore, since many modifications and changes will readily occur to those skilled in the art, the embodiments of the present invention are not intended to be limited to the precise construction and operation illustrated and described, but are intended to cover all suitable modifications and equivalents falling within the scope thereof thing.

In the present invention, the principles and implementations of the present invention are described by using specific embodiments, and the descriptions of the above embodiments are only used to help understand the method and the core idea of the present invention; The idea of the invention will have changes in the specific implementation and application scope. To sum up, the content of this specification should not be construed as a limitation to the present invention.

Claims (8)

1. A non-reciprocal power divider, wherein the non-reciprocal power divider comprises: a dielectric substrate, at least one Wilkinson power divider; a port of the Wilkinson power divider as the radio frequency port of the non-reciprocal power divider; wherein, The Wilkinson power divider is arranged on the top surface of the dielectric substrate, and each branch of the Wilkinson power divider includes a filter, and the filter is composed of at least two resonators; The back of the dielectric substrate is provided with a plurality of varactor diodes, a plurality of signal feeding circuits, a plurality of metallized through holes and a plurality of modulation ports; the modulation ports are used for receiving modulation signals, and each modulation port passes a signal The feeding circuit is connected to a metallized through hole, one end of each varactor diode is respectively connected to one end of a resonator through a metallized through hole, and the other end of each varicap diode is grounded. 2 . The non-reciprocal power divider according to claim 1 , wherein the resonators of the filters are staggered. 3 . 3. The non-reciprocal power divider according to claim 1, wherein the Wilkinson power divider is a Wilkinson power divider with a microstrip structure. 4 . The non-reciprocal power divider according to claim 1 , wherein a plurality of inductors are further provided on the back of the dielectric substrate, and each signal feeding circuit is connected to the metallized through hole through an inductor respectively. 5 . . 5. The non-reciprocal power divider according to claim 1, wherein the signal feeding circuit is a circuit of a coplanar waveguide structure. 6. The non-reciprocal power divider according to claim 1, wherein the modulation signal comprises: a DC bias voltage signal and/or a low frequency modulation signal. 7. The non-reciprocal power divider of claim 3, wherein the resonator is a microstrip resonator. 8. A non-reciprocal electromagnetic wave transmission device, the device comprising the non-reciprocal power divider, a DC voltage source and a low-frequency signal source according to any one of claims 1-6; The DC voltage source and the low-frequency signal source provide modulation signals for the non-reciprocal power divider through the modulation port.

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