CN101106335A - A resonant converter - Google Patents
A resonant converter Download PDFInfo
- Publication number
- CN101106335A CN101106335A CNA2007100750296A CN200710075029A CN101106335A CN 101106335 A CN101106335 A CN 101106335A CN A2007100750296 A CNA2007100750296 A CN A2007100750296A CN 200710075029 A CN200710075029 A CN 200710075029A CN 101106335 A CN101106335 A CN 101106335A
- Authority
- CN
- China
- Prior art keywords
- resonant
- square wave
- inductor
- output
- capacitor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Landscapes
- Dc-Dc Converters (AREA)
Abstract
本发明公开了一种谐振变换器，包括变压器、方波生成器、谐振电路、输出整流电路和输出滤波电路，输出整流电路连在变压器副边绕组与输出滤波电路之间，方波生成器输入端接有直流电源，方波生成器用于将输入的直流电压变换为交流方波电压并输出，谐振电路包括第一电感、谐振电容、第二电感，谐振电容和第一电感串联形成谐振支路，第二电感与变压器原边绕组并联形成并联支路，谐振支路一端与并联支路一端相连，谐振支路与并联支路的另一端分别与方波生成器的两个输出端相连；方波生成器输出的交流方波电压为固定频率、可调占空比的交流方波电压。从而避免变换器的工作频率在一个很宽的范围内，从而可以优化输出滤波电路的设计。
The invention discloses a resonant converter, which comprises a transformer, a square wave generator, a resonant circuit, an output rectifier circuit and an output filter circuit, the output rectifier circuit is connected between the transformer secondary winding and the output filter circuit, and the square wave generator inputs The terminal is connected with a DC power supply, and the square wave generator is used to convert the input DC voltage into an AC square wave voltage and output it. The resonant circuit includes a first inductor, a resonant capacitor, and a second inductor. The resonant capacitor and the first inductor are connected in series to form a resonant branch. , the second inductor is connected in parallel with the primary winding of the transformer to form a parallel branch, one end of the resonant branch is connected to one end of the parallel branch, and the other end of the resonant branch and the parallel branch are respectively connected to the two output ends of the square wave generator; The AC square wave voltage output by the wave generator is an AC square wave voltage with a fixed frequency and an adjustable duty cycle. Thereby avoiding the operating frequency of the converter in a very wide range, so that the design of the output filter circuit can be optimized.
Description
Technical Field
The present invention relates to a resonant converter.
Background
As shown in fig. 1, the LLC resonant converter with a symmetric half-bridge structure includes a transformer, a square-wave generator, a resonant circuit, an output rectifying circuit, and an output filter circuit, where the output rectifying circuit is connected between the secondary winding of the transformer and the output filter circuit, the input end of the square-wave generator is connected with a dc power supply, and the square-wave generator is used to convert an input dc voltage Vin into an ac square-wave voltage and output the ac square-wave voltage. The transformer comprises a primary winding N1, a first secondary winding N21 and a second secondary winding N22. The square wave generator comprises a first capacitor Cd1, a second capacitor Cd2, a first switch tube Q1 and a second switch tube Q2. The first capacitor Cd1 and the second capacitor Cd2 have large capacities, and equally divide the input voltage Vin, and the upper voltage of the input voltage Vin is half of the input voltage Vin. The first switch tube Q1 and the second switch tube Q2 form a half-bridge structure, driving signals of the half-bridge structure are complementary signals with fixed 50% duty ratio, and the first switch tube Q1 and the second switch tube Q both adopt frequency conversion modulation to adjust output voltage. The resonant circuit comprises a first inductor Lr, a resonant capacitor Cr and a second inductor Lm. The resonant circuit is connected between the midpoint of the half bridge and the first capacitor Cd1 and the second capacitor Cd2, so that the resonant capacitor Cr also plays a role in blocking the direct current. On the output side, the output rectifying circuit comprises a first rectifying diode D3 and a second rectifying diode D4, the output filter circuit comprises an output capacitor Co, the first rectifying diode D3 and the second rectifying diode D4 form a rectifying circuit with a center tap, and the first rectifying diode D3 and the second rectifying diode D4 are respectively and directly connected to the output capacitor Co.
Fig. 2 is a characteristic curve diagram of the output voltage Vo and the switching frequency f of the switching tube of the conventional resonant converter with a symmetrical half-bridge structure. In general, since the switching frequency is selected in a frequency range after the output voltage Vo has the maximum value in fig. 2, the frequency increases and the output voltage decreases. As can be seen from fig. 2, when the frequency rises to a certain extent, the characteristic curve becomes very flat, and even there may be a case where the counter-rise does not fall, and the frequency adjusting capability becomes very weak. When the converter is in light load or no load, the switching frequency needs to be increased in order to reduce the output voltage, and the switching frequency needs to be increased very high in order to reduce the voltage because the characteristic curve becomes very flat when the frequency is increased to a certain value, so that the working frequency range of the converter is very wide. If the electromagnetic compatibility requirement index is very high, and the output filter circuit of the converter is a simple capacitor filter, the electromagnetic compatibility requirement cannot be met, and the output filter circuit needs to be changed into a pi-type filter circuit or a multi-stage filter circuit. If the working frequency range of the converter is very wide, the index of the output filter circuit must meet the parameter index when the lowest switching frequency is reached, so that the capacitance and inductance parameters in the filter are very large due to the low frequency of the output filter, and therefore the filter with a very large size needs to be selected. In addition, when the operating frequency is too high, the rectifier diode loses the zero current turn-off characteristic, so that the voltage spikes at two ends of the output rectifier diode are very high, a diode with high voltage resistance must be selected, the conduction voltage drop of the diode with high voltage resistance is high, the loss is multiplied, the reliability of the converter is reduced, and the efficiency is reduced.
For other LLC series resonant converters, such as asymmetric half-bridge LLC resonant converters, there is a problem that the control frequency of the converter is wide.
In summary, the conventional resonant converter has the following disadvantages: when the converter is in light load or no load, the switching frequency needs to be increased in order to reduce the output voltage, and the switching frequency needs to be increased very high in order to reduce the voltage because the characteristic curve becomes very flat when the frequency is increased to a certain value, so that the working frequency range of the converter is very wide. The wide variation range of the switching frequency of the converter causes that an output filter circuit is difficult to optimize, and the output filter circuit must meet the requirement of the lowest frequency, so that the capacitance and inductance parameters in the output filter circuit are large, and the volume of the output filter circuit is large. In addition, when the working frequency is too high, the rectifier diode loses the zero current turn-off characteristic, so that the voltage peak at two ends of the output rectifier diode is very high, a diode with high voltage resistance must be selected, and the conduction voltage drop of the diode with high voltage resistance is higher, so that the loss is multiplied, the reliability of the converter is reduced, and the efficiency is reduced.
Disclosure of Invention
The invention provides a resonant converter for overcoming the defects, and is beneficial to optimization of an output filter.
The technical problem of the invention is solved by the following technical scheme:
a resonant converter comprises a transformer, a square wave generator, a resonant circuit, an output rectifying circuit and an output filter circuit, wherein the output rectifying circuit is connected between a secondary winding of the transformer and the output filter circuit, the input end of the square wave generator is connected with a direct current power supply, the square wave generator is used for converting input direct current voltage into alternating current square wave voltage and outputting the alternating current square wave voltage, the resonant circuit comprises a first inductor, a resonant capacitor and a second inductor, the resonant capacitor and the first inductor are connected in series to form a resonant branch circuit, the second inductor and a primary winding of the transformer are connected in parallel to form a parallel branch circuit, one end of the resonant branch circuit is connected with one end of the parallel branch circuit, and the resonant branch circuit and the other end of the parallel branch circuit are respectively connected with two output ends of the square wave generator; the method is characterized in that: the alternating-current square wave voltage output by the square wave generator is an alternating-current square wave voltage with fixed frequency and adjustable duty ratio, and the fixed frequency meets the following formula:
f m ＜f＜f r ，
wherein f is the fixed frequency, cr is the capacitance of the resonant capacitor, lr is the inductance of the first inductor,
lm is the inductance of the second inductor.
The technical problem of the invention is further solved by the following technical scheme:
the fixed frequency also satisfies the following equation: (fr-f) < (f-fm).
The first inductor and the second inductor are respectively external independent inductors.
The square wave generator comprises a first capacitor, a second capacitor, a first switching tube and a second switching tube, wherein the first capacitor and the second capacitor are connected in series and then bridged at two ends of a direct current power supply, and the first switching tube and the second switching tube are connected in series and then bridged at two ends of the direct current power supply; one end of the first inductor is connected between the first switching tube and the second switching tube, the other end of the first inductor is connected with one end of the second inductor and one end of the primary winding of the transformer through the resonant capacitor, and the other end of the second inductor and the other end of the primary winding of the transformer are connected between the first capacitor and the second capacitor.
The square wave generator comprises a first switching tube, a second switching tube, a third switching tube and a fourth switching tube, the first switching tube and the second switching tube are connected in series and then bridged at two ends of the direct current power supply, and the third switching tube and the fourth switching tube are connected in series and then bridged at two ends of the direct current power supply; one end of the first inductor is connected between the first switch tube and the second switch tube, the other end of the first inductor is connected with one end of the second inductor and one end of the primary winding of the transformer through the resonant capacitor, and the other ends of the second inductor and the primary winding of the transformer are connected between the third switch tube and the fourth switch tube.
The first inductor is a leakage inductor of a primary winding of the transformer, and the second inductor is an excitation inductor of the primary winding of the transformer.
The transformer comprises a first transformer and a second transformer, the square wave generator comprises a first square wave generator and a second square wave generator, the resonant circuit comprises a first resonant circuit and a second resonant circuit, and the output rectifying circuit comprises a first output rectifying circuit and a second output rectifying circuit; the first output rectifying circuit is connected between a secondary winding of the first transformer and the output filter circuit, the input end of the first square wave generator is connected with a direct-current power supply, the first square wave generator is used for converting the input direct-current voltage into alternating-current square wave voltage and outputting the alternating-current square wave voltage, the first resonant circuit comprises a first inductor, a first resonant capacitor and a second inductor, the first resonant capacitor and the first inductor are connected in series to form a first resonant branch, the second inductor is connected with a primary winding of the first transformer in parallel to form a first parallel branch, one end of the first resonant branch is connected with one end of the first parallel branch, and the other ends of the first resonant branch and the first parallel branch are respectively connected with two output ends of the first square wave generator; the second output rectifying circuit is connected between a secondary winding of the second transformer and the output filter circuit, the input end of the second square wave generator is connected with a direct current power supply, the second square wave generator is used for converting input direct current voltage into alternating current square wave voltage and outputting the alternating current square wave voltage, the second resonant circuit comprises a third inductor, a second resonant capacitor and a fourth inductor, the second resonant capacitor and the third inductor are connected in series to form a first resonant branch, the fourth inductor and a primary winding of the second transformer are connected in parallel to form a second parallel branch, one end of the second resonant branch is connected with one end of the second parallel branch, the other end of the second resonant branch and the other end of the second parallel branch are respectively connected with two output ends of the second square wave generator, and the phase difference of the alternating current square wave voltages output by the first square wave generator and the second square wave generator is 90 degrees.
Compared with the prior art, the invention has the advantages that:
the square wave generator of the resonant converter outputs alternating-current square wave voltage with fixed frequency and adjustable duty ratio, and the working frequency of the converter is prevented from being in a wide range due to the adoption of PWM control with fixed frequency, so that the design of an output filter circuit can be optimized. The invention is beneficial to the optimal design of the main power transformer and the optimal design of the filter circuit, thereby being beneficial to the optimal design of the converter.
The working frequency of the switching tube of the square wave generator is located between two characteristic resonant frequencies of the resonant circuit, so that the switching tube of the square wave generator can realize zero-voltage switching in a full-load range, the rectifier diode can realize zero-current turn-off, the switching loss of the switching tube can be reduced, and the rectifier diode is turned off at zero current, so that high voltage spikes at two ends of the rectifier diode are avoided, and a low-voltage-withstanding diode can be selected. The rectifier diode adopts a low-voltage-withstanding diode, so that on one hand, the switching loss can be reduced, and the efficiency and the reliability of the resonant converter are improved; on the other hand, the cost of the resonant converter can be reduced.
The off-frequency of the switching tube of the square-wave generator is between the two characteristic resonance frequencies of the resonant circuit and as close as possible to the higher resonance frequency. The higher switching frequency of the converter switching tube can reduce the volume of the transformer and the volume of the output filter.
Drawings
Fig. 1 is a schematic diagram of a symmetrical half-bridge structure LLC resonant converter;
FIG. 2 is a graph of the output voltage and switching frequency characteristics of FIG. 1;
FIG. 3 is a schematic view of the mode of operation of the present invention;
FIG. 4 is a schematic structural diagram of a second embodiment of the present invention;
FIG. 5 is a schematic structural diagram of a third embodiment of the present invention;
fig. 6 is a schematic structural diagram of a fourth embodiment of the present invention.
Detailed Description
The present invention will be described in further detail below with reference to specific embodiments and accompanying drawings.
Detailed description of the invention
The invention improves the existing control method of the LLC resonant converter with the symmetrical half-bridge structure as shown in figure 1, which is characterized in that: the control square wave generator converts the input direct-current voltage into alternating-current square wave voltage with fixed frequency f and adjustable duty ratio, and outputs the alternating-current square wave voltage to the resonance circuit, wherein the fixed frequency satisfies the following formula:
f m ＜f＜f r ，
wherein f is the fixed frequency, fr is a first characteristic resonance frequency of the resonance circuit, fm is a second characteristic resonance frequency of the resonance circuit, cr is a capacitance value of the resonance capacitor, lr is an inductance of the first inductor, and Lm is an inductance of the second inductor. That is, the first switching tube Q1 and the second switching tube Q2 of the inverter are respectively controlled by PWM, and the switching frequency f of the first switching tube Q1 and the second switching tube Q2 is between the first characteristic resonant frequency fr and the second characteristic resonant frequency fm of the resonant circuit, and the PWM signals input by the first switching tube Q1 and the second switching tube Q2 are complementary. The resonant converter is controlled by Pulse-width modulation (PWM), so that the design of an input filter is facilitated. And zero-voltage switching (ZVS) of the main switching tubes (the first switching tube Q1 and the second switching tube Q2) can be realized in a full-load range, and the secondary side rectifier diodes (the first rectifier diode D3 and the second rectifier diode D4) are switched off (ZCS) in a zero current mode.
The switching frequency f of the converter is close to fr as much as possible, and the volume of the main power transformer and the volume of the filter can be reduced by increasing the working frequency of the converter, so that the volume of the whole resonant converter can be reduced, and the power density of the converter is improved. In addition, the primary winding of the transformer receives input power in the whole switching period and transmits power to a load through the secondary winding of the transformer, so that the utilization rate of the transformer is high.
The first inductor Lr can utilize the leakage inductance of the primary winding N1 of the transformer, or can adopt an external independent series inductor; the second inductor Lm can use the exciting inductance of the primary winding N1 of the transformer, and can also use an external independent parallel inductor. After the first inductor Lr and the second inductor Lm are integrated into the transformer, the whole resonant converter only needs one magnetic core, so that the cost can be saved and the interference can be reduced.
The invention provides a PWM controlled symmetrical half-bridge LLC resonant converter, the primary side is a symmetrical half-bridge structure, the secondary side is a full-wave rectifier circuit of a transformer center tap, and the output of the invention can adopt other rectifier circuits such as a bridge rectifier circuit and the like.
The working principle of the invention will be described below by taking as an example the resonant converter shown in fig. 1. To facilitate circuit principle analysis, the following assumptions are made: the capacities of the first capacitor Cd1 and the second capacitor Cd2 are large, and the upper voltage of the first capacitor Cd1 and the upper voltage of the second capacitor Cd2 are half of the input voltage Vin; the output capacitance Co is very large and is equivalent to a voltage source.
As shown in fig. 3, the resonant converter has a total of 6 operating modes in one switching cycle. In the figure id3 is a first rectifying diode D 3 A current flowing therethrough, id4 is a second rectifying diode D 4 The upper current Vcr is the voltage on the resonant capacitor Cr. The working principle of the 6 working modes is described as follows:
1) Modal 1 (t 0-t 1)
At time t0, the second switching tube Q 2 Off, resonant current i r For the first switch tube Q 1 Discharging the output junction capacitance at both ends, and simultaneously, discharging the second switch tube Q 2 The output junction capacitance at both ends charges. Up to the first switching tube Q 1 The voltage drop at both ends is zero, the first switch tube Q 1 Body diode D of 1 And naturally conducting.
2) Modal 2 (t 1. About.t 2)
First switch tube Q at time t1 1 On due to its body diode D 1 Has been conducted, so the first switch tube Q 1 Turn on for Zero Voltage (ZVS). Excitation current i Lm Linearly increasing, resonant current i r Flows through the first switch tube Q 1 And rises in a sinusoidal fashion due to the first switching tube Q 1 Is smaller than the resonance period of the first inductance Lr and the resonance capacitance Cr (i.e. the first characteristic resonance frequency of the resonance circuit). Thus, at the resonant current i r After half a period of resonance, Q 1 Still in the on state. When the resonant current i r Down to and from the excitation current i Lm When equal, the first rectifier diode D 3 The current is naturally turned off when passing zero, and zero current turn-off (ZCS) is realized. The present mode of operation ends.
3) Modal 3 (t 2. About.t 3)
At the time t2, the first rectifier diode D 3 Due to the flow of currentZero crossing and naturally off (ZCS). The second inductance Lm is no longer limited by the output voltage. At this time, the first inductor Lr, the second inductor Lm and the resonant capacitor Cr resonate with each other. Generally, the second inductance Lm is much larger than the inductance of the first inductance Lr, so the resonant period formed by the first inductance Lr, the second inductance Lm and the resonant capacitor Cr is relatively long, the modal time is generally short, and it can be considered that the resonant current i is r Remains substantially constant.
4) Modal 4 (t 3-t 4)
At time t3, the first switch tube Q 1 Off, at which time the resonant current i r For the second switch tube Q 2 The output junction capacitors at both ends discharge and simultaneously discharge the first switch tube Q 1 The output junction capacitance at both ends charges. Up to the second switching tube Q 2 The voltage drop at both ends is zero, and a second switch tube Q 2 Body diode D of 2 And naturally conducting.
5) Modal 5 (t 4-t 5)
At time t4, the second switch tube Q 2 On due to its body diode D 2 Has been conducted, so the second switch tube Q 2 Turn on for Zero Voltage (ZVS). Excitation current i Lm Linearly increasing, resonant current i r Flow through Q 2 And rises in a sinusoidal fashion since the switching frequency is less than the resonant period of Lr and Cr. Therefore, when the resonant current is resonated through a half cycle, the second switching tube Q 2 But is in an on state. When the resonant current i r Down to and from the excitation current i Lm When equal, the first rectifier diode D 4 The current is naturally turned off by passing through zero, and zero current turn-off (ZCS) is realized. The present mode of operation ends.
6) Modal 6 (t 5-t 6)
At time t5, the second rectifier diode D 4 Naturally switched off due to current Zero Crossing (ZCS). The second inductor Lm is no longer limited by the output voltage, and at this time, the first inductor Lr, the resonant capacitor Cr, and the second inductor Lm resonate. Generally, the second inductance Lm is much larger than the inductance of the first inductance Lr, so the resonant period is longer, and this mode is oneThe time is generally short, and the excitation current can be considered as a constant current.
Detailed description of the invention
As shown in fig. 4, the present invention may also improve a control method of a full-bridge LLC resonant converter, which is different from the half-bridge LLC resonant converter shown in fig. 1 in that: the square wave generator comprises a first switching tube Q1, a second switching tube Q2, a third switching tube Q3 and a fourth switching tube Q4, the first switching tube Q1 and the second switching tube Q2 are connected in series and then bridged at two ends of a direct current power supply, and the third switching tube Q3 and the fourth switching tube Q4 are connected in series and then bridged at two ends of the direct current power supply; one end of the first inductor Lr is connected between the first switching tube Q1 and the second switching tube Q2, the other end of the first inductor Lr is connected with one end of the second inductor Lm and one end of the primary winding N1 of the transformer through the resonant capacitor Cr, and the other ends of the second inductor Lm and the primary winding N1 of the transformer are connected between the third switching tube Q3 and the fourth switching tube Q4. The first switch tube Q1 and the fourth switch tube are the same drive signal, the second switch tube Q2 and the third switch tube Q3 are the same drive signal, the two drive signals are complementary, the conduction time of the first switch tube Q1 and the conduction time of the second switch tube Q2 are equal, and the output voltage of the converter is adjusted by adjusting the duty ratio.
The operation principle of the full-bridge converter is similar to that of the symmetrical half-bridge, and is briefly described here. Compared with a symmetrical half-bridge converter, the amplitude of the voltage applied to the resonant circuit in the full-bridge converter is the input voltage, and the amplitude of the voltage applied to the resonant circuit in the symmetrical half-bridge converter is half of the input voltage, so that the transformation ratio of the main power transformer is different. Although some voltage and current stresses may differ, the basic operating principle is similar and will not be described in detail here, and it can be analyzed with particular reference to the operating principle of a symmetrical half bridge.
Detailed description of the invention
Fig. 5 is a schematic structural diagram of a PWM-controlled interleaved parallel-symmetric half-bridge LLC resonant converter in this embodiment, which is different from the first embodiment in that: two symmetrical half-bridge LLC resonant converters are adopted and are connected in parallel in a staggered mode.
The resonant converter shown in fig. 5 includes a first transformer, a second transformer, a first square wave generator, a second square wave generator, a first resonant circuit, a second resonant circuit, a first output rectifying circuit and a second output rectifying circuit; the first output rectifying circuit is connected between secondary windings N21 and N22 of the first transformer and the output filter circuit, the input end of the first square wave generator is connected with a direct-current power Vin, the first square wave generator is used for converting input direct-current voltage into alternating-current square wave voltage and outputting the alternating-current square wave voltage, the first resonant circuit comprises a first inductor Lr1, a first resonant capacitor Cr1 and a second inductor Lm1, the first resonant capacitor Cr1 and the first inductor Lr1 are connected in series to form a first resonant branch, the second inductor Lm1 and the primary winding N1 of the first transformer are connected in parallel to form a first parallel branch, one end of the first resonant branch is connected with one end of the first parallel branch, and the other ends of the first resonant branch and the first parallel branch are respectively connected with two output ends of the first square wave generator; the second output rectifying circuit is connected between secondary windings N31 and N32 of the second transformer and the output filter circuit, the input end of the second square wave generator is connected with a direct current power supply, the second square wave generator is used for converting the input direct current voltage into alternating current square wave voltage and outputting the alternating current square wave voltage, the second resonant circuit comprises a third inductor Lr2, a second resonant capacitor Cr2 and a fourth inductor Lm2, the second resonant capacitor Cr2 and the third inductor Lr2 are connected in series to form a first resonant branch, the fourth inductor Lm2 and a primary winding N3 of the second transformer are connected in parallel to form a second parallel branch, one end of the second resonant branch is connected with one end of the second parallel branch, the other ends of the second resonant branch and the second parallel branch are respectively connected with two output ends of the second square wave generator, and the phase difference between the alternating current voltages output by the first square wave generator and the second square wave generator is 90 degrees. The output filter circuit is composed of an output capacitor Co.
The first square wave generator comprises a first capacitor Cd1, a second capacitor Cd2, a first switching tube Q1 and a second switching tube Q2, wherein the first capacitor Cd1 and the second capacitor Cd2 are connected in series and then bridged at two ends of a direct current power supply, and the first switching tube Q1 and the second switching tube Q2 are connected in series and then bridged at two ends of the direct current power supply; one end of the first inductor Lr1 is connected between the first switching tube Q1 and the second switching tube Q2, the other end of the first inductor Lr1 is connected with one end of the second inductor Lm1 and one end of the first transformer primary winding N1 through the first resonant capacitor Cr1, and the other end of the second inductor Lm1 and the transformer primary winding N1 are connected between the first capacitor Cd1 and the second capacitor Cd 2.
The second square wave generator comprises a third capacitor Cd3, a fourth capacitor Cd4, a third switching tube Q3 and a fourth switching tube Q4, the third capacitor Cd3 and the fourth capacitor Cd4 are connected in series and then bridged at two ends of the direct current power supply, and the third switching tube Q3 and the fourth switching tube Q4 are connected in series and then bridged at two ends of the direct current power supply; one end of a third inductor Lr2 is connected between the third switching tube Q3 and the fourth switching tube Q4, the other end of the third inductor Lr2 is connected with one end of a fourth inductor Lm2 and one end of a primary winding N3 of the second transformer through a second resonant capacitor Cr2, and the other end of the fourth inductor Lm2 and the other end of the primary winding N3 of the second transformer are connected between the third capacitor Cd3 and the fourth capacitor Cd 4.
The phase difference of the alternating-current square wave voltages output by the first square wave generator and the second square wave generator is 90 degrees, and the phase difference can be realized by the following modes: the phase of the driving signal of the second switch tube Q2 lags behind the phase of the driving signal of the first switch tube Q1 by 180 degrees, the phase of the driving signal of the third switch tube Q2 lags behind the phase of the driving signal of the first switch tube Q1 by 90 degrees, and the phase of the driving signal of the fourth switch tube Q4 lags behind the phase of the driving signal of the first switch tube Q1 by 270 degrees. The switching tubes of the present embodiment are all PWM controlled. The specific implementation mode can increase the output power of the circuit and reduce the voltage ripple on the output filter capacitor.
Detailed description of the invention
Fig. 6 is a schematic structural diagram of a PWM-controlled interleaved parallel full-bridge LLC resonant converter in the present embodiment, which is different from the third embodiment in that: the first and second square wave generators have different structures, and the square wave generator of the present embodiment has the same structure as the square wave generator of the second embodiment. The phase difference between the ac square wave voltages output by the first and second square wave generators of the present embodiment is also 90 degrees. The switching tubes of the present embodiment are all PWM controlled. The specific implementation mode can increase the output power of the circuit and reduce the voltage ripple on the output filter capacitor.
The invention adopts PWM control to the switch tube of the resonant converter. Because the PWM control with fixed frequency is adopted, the problem that the design of a converter is difficult to optimize due to the wider working frequency range of the frequency conversion control is solved, and the design of an input filter circuit is facilitated.
The volume of the main power transformer and the volume of the filter can be reduced by improving the working frequency of the resonant converter, so that the volume of the converter is reduced, and the power density of the converter is improved. However, since the operating frequency of the switching tube is increased, if the switching tube is operated in a hard switching state, the loss is multiplied, and the efficiency of the converter is reduced, so that the high-frequency switching power supply is difficult to be practically applied if soft switching cannot be realized. The resonant converter can realize zero-voltage switching of the main switching tube and zero-current switching-off of the rectifier diode, so that the switching loss of the main switching tube can be reduced, and the rectifier diode is switched off at zero current, so that high voltage peaks at two ends of the rectifier diode are avoided, and a low-voltage-resistant diode can be selected. On one hand, the rectifier diode adopts a low-voltage-withstanding diode, so that the switching loss can be reduced, and the efficiency and the reliability of the resonant converter are improved; another aspect may reduce the cost of the resonant converter.
The switching frequency of the switching tube of the resonant converter according to the invention lies between the two characteristic resonant frequencies of the resonant circuit and is as close as possible to the higher characteristic resonant frequency. Higher switching frequency of the converter switch tube can reduce the volume of the transformer and the volume of the output filter.
The foregoing is a more detailed description of the invention in connection with specific preferred embodiments and it is not intended that the invention be limited to these specific details. For those skilled in the art to which the invention pertains, several simple deductions or substitutions can be made without departing from the spirit of the invention, and all should be considered as belonging to the protection scope of the present invention.
Claims (7)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2007100750296A CN100521492C (en) | 2007-06-13 | 2007-06-13 | A harmonic vibration converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2007100750296A CN100521492C (en) | 2007-06-13 | 2007-06-13 | A harmonic vibration converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101106335A true CN101106335A (en) | 2008-01-16 |
| CN100521492C CN100521492C (en) | 2009-07-29 |
Family
ID=39000073
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB2007100750296A Active CN100521492C (en) | 2007-06-13 | 2007-06-13 | A harmonic vibration converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN100521492C (en) |
Cited By (33)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101500364A (en) * | 2008-01-30 | 2009-08-05 | 杭州茂力半导体技术有限公司 | Discharge lamp driving apparatus and driving method |
| CN101488715B (en) * | 2009-02-19 | 2011-04-20 | 普天信息技术研究院有限公司 | DC/DC resonance converter |
| CN102047544A (en) * | 2008-12-19 | 2011-05-04 | 德克萨斯仪器股份有限公司 | Fixed-frequency LLC resonant power regulator |
| CN102684499A (en) * | 2011-03-08 | 2012-09-19 | 登丰微电子股份有限公司 | Full-bridge conversion circuit and full-bridge drive control circuit |
| US8717782B2 (en) | 2009-01-07 | 2014-05-06 | Texas Instruments Incorporated | Sweeping frequency LLC resonant power regulator |
| CN103997217A (en) * | 2014-06-09 | 2014-08-20 | 西安电子科技大学 | Fixed-frequency series resonant converter based on flat inductor |
| WO2014169821A1 (en) * | 2013-04-16 | 2014-10-23 | Huawei Technologies Co., Ltd. | Apparatus and method for resonant converters |
| WO2015070740A1 (en) * | 2013-11-12 | 2015-05-21 | Huawei Technologies Co., Ltd. | Gate drive apparatus for resonant converters |
| CN105099197A (en) * | 2014-05-20 | 2015-11-25 | 艾默生网络能源有限公司 | Resonance circuit, charger and uninterruptible power supply |
| CN105099157A (en) * | 2015-08-12 | 2015-11-25 | 阳光电源股份有限公司 | LLC resonant converter and soft starting method thereof |
| CN105281576A (en) * | 2014-06-30 | 2016-01-27 | 光宝科技股份有限公司 | Quasi-resonant half-bridge converter and control method thereof |
| EP3098956A1 (en) * | 2015-05-26 | 2016-11-30 | Hitachi, Ltd. | Power conversion device and power conversion control method for the same |
| EP3099153A1 (en) * | 2015-05-26 | 2016-11-30 | Hitachi, Ltd. | Power supply apparatus |
| CN106230268A (en) * | 2016-08-31 | 2016-12-14 | 中天昱品科技有限公司 | A kind of crisscross parallel LLC resonance DC/DC power inverter |
| CN106329931A (en) * | 2015-07-03 | 2017-01-11 | 艾默生网络能源有限公司 | A control method and device for a symmetrical half-bridge LLC resonant converter |
| CN106877671A (en) * | 2017-03-06 | 2017-06-20 | 郭志邦 | A kind of inductance capacitance connection in series-parallel combinational circuit and Switching Power Supply |
| CN107134910A (en) * | 2016-02-25 | 2017-09-05 | 株式会社村田制作所 | Switch drive unit, DC/DC conversion equipments and its control method |
| CN107276190A (en) * | 2017-05-27 | 2017-10-20 | 华为技术有限公司 | The Wave method and device, equipment of a kind of underloading ripple |
| CN107431437A (en) * | 2015-03-09 | 2017-12-01 | 弗罗纽斯国际有限公司 | With the controlled resonant converter with centre tapped transformer |
| CN108616215A (en) * | 2016-12-13 | 2018-10-02 | 深圳职业技术学院 | a kind of resonance circuit |
| CN110048496A (en) * | 2019-04-23 | 2019-07-23 | 甘肃南洋新能源科技发展有限公司 | A kind of low-cost wireless method of electric energy transfer and device |
| CN110086348A (en) * | 2019-05-16 | 2019-08-02 | 中国地质大学（武汉） | It is a kind of to determine frequency resonant mode DC converter and its control method |
| CN110907680A (en) * | 2018-09-14 | 2020-03-24 | 台达电子工业股份有限公司 | Current detection device, method and system |
| CN111525807A (en) * | 2020-04-13 | 2020-08-11 | 哈尔滨工业大学 | Harmonic optimization-based high-order LCLCL direct current converter and parameter design method |
| CN112421953A (en) * | 2019-08-22 | 2021-02-26 | 圣邦微电子（北京）股份有限公司 | Multiphase converter and control circuit and control method thereof |
| CN112910266A (en) * | 2021-02-01 | 2021-06-04 | 南京航空航天大学 | Low-voltage ripple control method under power distribution change of multi-port converter and multi-port converter |
| CN113162420A (en) * | 2021-03-30 | 2021-07-23 | 国网河北省电力有限公司雄安新区供电公司 | A resonant DC-DC converter |
| CN113725984A (en) * | 2021-07-27 | 2021-11-30 | 华为数字能源技术有限公司 | Multi-pulse-wave rectifying circuit and charging device |
| CN114094814A (en) * | 2021-10-19 | 2022-02-25 | 许继电源有限公司 | A kind of LLC topology small gain ripple control method and device |
| CN114244157A (en) * | 2021-12-18 | 2022-03-25 | 北京动力源科技股份有限公司 | Staggered high-power large-current isolation DC-DC circuit |
| WO2022078126A1 (en) * | 2020-10-13 | 2022-04-21 | 比亚迪股份有限公司 | Charging apparatus, method for controlling charging of charging apparatus, and vehicle |
| CN115603588A (en) * | 2022-10-27 | 2023-01-13 | 北京智芯微电子科技有限公司（Cn） | Bridge conversion circuit, circuit working method and electronic device |
| CN115995980A (en) * | 2022-12-06 | 2023-04-21 | 北京索英电气技术股份有限公司 | Power supply circuit of high-insulation soft switch |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP4381493B2 (en) * | 1998-03-17 | 2009-12-09 | ソニー株式会社 | Current resonant switching power supply |
| JPH11299232A (en) * | 1998-04-16 | 1999-10-29 | Sony Corp | Current resonant-type switching power supply unit |
| US6169683B1 (en) * | 1999-10-07 | 2001-01-02 | Ericsson Inc. | Resonant gate drive for synchronous rectifiers |
| EP1120896B1 (en) * | 2000-01-28 | 2005-03-23 | Densei-Lambda K.K. | Resonant power converter |
| WO2004068929A2 (en) * | 2003-02-04 | 2004-08-19 | Celetron Usa, Inc. | Improved fixed frequency resonant converter |
-
2007
- 2007-06-13 CN CNB2007100750296A patent/CN100521492C/en active Active
Cited By (53)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101500364A (en) * | 2008-01-30 | 2009-08-05 | 杭州茂力半导体技术有限公司 | Discharge lamp driving apparatus and driving method |
| CN102047544A (en) * | 2008-12-19 | 2011-05-04 | 德克萨斯仪器股份有限公司 | Fixed-frequency LLC resonant power regulator |
| US8717782B2 (en) | 2009-01-07 | 2014-05-06 | Texas Instruments Incorporated | Sweeping frequency LLC resonant power regulator |
| CN101488715B (en) * | 2009-02-19 | 2011-04-20 | 普天信息技术研究院有限公司 | DC/DC resonance converter |
| CN102684499A (en) * | 2011-03-08 | 2012-09-19 | 登丰微电子股份有限公司 | Full-bridge conversion circuit and full-bridge drive control circuit |
| WO2014169821A1 (en) * | 2013-04-16 | 2014-10-23 | Huawei Technologies Co., Ltd. | Apparatus and method for resonant converters |
| US9178440B2 (en) | 2013-04-16 | 2015-11-03 | Futurewei Technologies, Inc. | Apparatus and method for resonant converters |
| EP2939337A1 (en) * | 2013-04-16 | 2015-11-04 | Huawei Technologies Co., Ltd. | Apparatus and method for resonant converters |
| EP2939337A4 (en) * | 2013-04-16 | 2016-07-20 | Huawei Tech Co Ltd | Apparatus and method for resonant converters |
| US9876435B2 (en) | 2013-11-12 | 2018-01-23 | Futurewei Technologies, Inc. | Gate drive apparatus for resonant converters |
| WO2015070740A1 (en) * | 2013-11-12 | 2015-05-21 | Huawei Technologies Co., Ltd. | Gate drive apparatus for resonant converters |
| US10340807B2 (en) | 2013-11-12 | 2019-07-02 | Futurewei Technologies, Inc. | Gate drive apparatus for resonant converters |
| US9479073B2 (en) | 2013-11-12 | 2016-10-25 | Futurewei Technologies, Inc. | Gate drive apparatus for resonant converters |
| CN105099197A (en) * | 2014-05-20 | 2015-11-25 | 艾默生网络能源有限公司 | Resonance circuit, charger and uninterruptible power supply |
| CN103997217A (en) * | 2014-06-09 | 2014-08-20 | 西安电子科技大学 | Fixed-frequency series resonant converter based on flat inductor |
| CN105281576B (en) * | 2014-06-30 | 2018-06-19 | 光宝科技股份有限公司 | Quasi-resonant half-bridge converter and control method thereof |
| CN105281576A (en) * | 2014-06-30 | 2016-01-27 | 光宝科技股份有限公司 | Quasi-resonant half-bridge converter and control method thereof |
| CN107431437A (en) * | 2015-03-09 | 2017-12-01 | 弗罗纽斯国际有限公司 | With the controlled resonant converter with centre tapped transformer |
| CN107431437B (en) * | 2015-03-09 | 2020-07-07 | 弗罗纽斯国际有限公司 | Resonant converter with center tapped transformer |
| US9750125B2 (en) | 2015-05-26 | 2017-08-29 | Hitachi, Ltd. | Power supply apparatus |
| EP3098956A1 (en) * | 2015-05-26 | 2016-11-30 | Hitachi, Ltd. | Power conversion device and power conversion control method for the same |
| EP3099153A1 (en) * | 2015-05-26 | 2016-11-30 | Hitachi, Ltd. | Power supply apparatus |
| US9806622B2 (en) | 2015-05-26 | 2017-10-31 | Hitachi, Ltd. | Power conversion device and power conversion control method for the same |
| CN106329931B (en) * | 2015-07-03 | 2018-08-07 | 维谛技术有限公司 | A kind of control method and device of symmetrical half bridge LLC resonant converter |
| CN106329931A (en) * | 2015-07-03 | 2017-01-11 | 艾默生网络能源有限公司 | A control method and device for a symmetrical half-bridge LLC resonant converter |
| CN105099157B (en) * | 2015-08-12 | 2018-02-23 | 阳光电源股份有限公司 | A kind of LLC resonant converter and its soft-start method |
| CN105099157A (en) * | 2015-08-12 | 2015-11-25 | 阳光电源股份有限公司 | LLC resonant converter and soft starting method thereof |
| CN107134910A (en) * | 2016-02-25 | 2017-09-05 | 株式会社村田制作所 | Switch drive unit, DC/DC conversion equipments and its control method |
| CN106230268A (en) * | 2016-08-31 | 2016-12-14 | 中天昱品科技有限公司 | A kind of crisscross parallel LLC resonance DC/DC power inverter |
| CN108616215A (en) * | 2016-12-13 | 2018-10-02 | 深圳职业技术学院 | a kind of resonance circuit |
| CN106877671A (en) * | 2017-03-06 | 2017-06-20 | 郭志邦 | A kind of inductance capacitance connection in series-parallel combinational circuit and Switching Power Supply |
| CN107276190B (en) * | 2017-05-27 | 2020-02-21 | 华为技术有限公司 | Light-load ripple wave sending method, device and equipment |
| CN107276190A (en) * | 2017-05-27 | 2017-10-20 | 华为技术有限公司 | The Wave method and device, equipment of a kind of underloading ripple |
| CN110907680A (en) * | 2018-09-14 | 2020-03-24 | 台达电子工业股份有限公司 | Current detection device, method and system |
| CN110907680B (en) * | 2018-09-14 | 2022-03-01 | 台达电子工业股份有限公司 | Current detection device, method and system |
| US11187728B2 (en) | 2018-09-14 | 2021-11-30 | Delta Electronics, Inc. | Current sensing device, method and system |
| CN110048496A (en) * | 2019-04-23 | 2019-07-23 | 甘肃南洋新能源科技发展有限公司 | A kind of low-cost wireless method of electric energy transfer and device |
| CN110086348A (en) * | 2019-05-16 | 2019-08-02 | 中国地质大学（武汉） | It is a kind of to determine frequency resonant mode DC converter and its control method |
| CN110086348B (en) * | 2019-05-16 | 2023-12-01 | 中国地质大学（武汉） | Fixed-frequency resonant direct-current conversion device and control method thereof |
| CN112421953A (en) * | 2019-08-22 | 2021-02-26 | 圣邦微电子（北京）股份有限公司 | Multiphase converter and control circuit and control method thereof |
| CN112421953B (en) * | 2019-08-22 | 2022-02-15 | 圣邦微电子（北京）股份有限公司 | Multiphase converter and control circuit and control method thereof |
| CN111525807A (en) * | 2020-04-13 | 2020-08-11 | 哈尔滨工业大学 | Harmonic optimization-based high-order LCLCL direct current converter and parameter design method |
| WO2022078126A1 (en) * | 2020-10-13 | 2022-04-21 | 比亚迪股份有限公司 | Charging apparatus, method for controlling charging of charging apparatus, and vehicle |
| CN112910266A (en) * | 2021-02-01 | 2021-06-04 | 南京航空航天大学 | Low-voltage ripple control method under power distribution change of multi-port converter and multi-port converter |
| CN112910266B (en) * | 2021-02-01 | 2022-04-08 | 南京航空航天大学 | Low-voltage ripple control method under power distribution change of multi-port converter |
| CN113162420B (en) * | 2021-03-30 | 2022-10-21 | 国网河北省电力有限公司雄安新区供电公司 | A resonant DC-DC converter |
| CN113162420A (en) * | 2021-03-30 | 2021-07-23 | 国网河北省电力有限公司雄安新区供电公司 | A resonant DC-DC converter |
| CN113725984A (en) * | 2021-07-27 | 2021-11-30 | 华为数字能源技术有限公司 | Multi-pulse-wave rectifying circuit and charging device |
| CN114094814A (en) * | 2021-10-19 | 2022-02-25 | 许继电源有限公司 | A kind of LLC topology small gain ripple control method and device |
| CN114244157A (en) * | 2021-12-18 | 2022-03-25 | 北京动力源科技股份有限公司 | Staggered high-power large-current isolation DC-DC circuit |
| CN115603588A (en) * | 2022-10-27 | 2023-01-13 | 北京智芯微电子科技有限公司（Cn） | Bridge conversion circuit, circuit working method and electronic device |
| CN115603588B (en) * | 2022-10-27 | 2024-03-19 | 北京智芯微电子科技有限公司 | Bridge conversion circuit, circuit working method and electronic device |
| CN115995980A (en) * | 2022-12-06 | 2023-04-21 | 北京索英电气技术股份有限公司 | Power supply circuit of high-insulation soft switch |
Also Published As
| Publication number | Publication date |
|---|---|
| CN100521492C (en) | 2009-07-29 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN101106335A (en) | A resonant converter | |
| CN110768535B (en) | Wide gain control method of variable topology LLC resonant converter | |
| CN101309049B (en) | Dc-dc converter | |
| US8842450B2 (en) | Power converter using multiple phase-shifting quasi-resonant converters | |
| US8923018B2 (en) | DC/DC converter, power converter and control method thereof | |
| CN101615840B (en) | Resonant circuit and resonant power converter with narrow operating frequency band | |
| CN101488715B (en) | DC/DC resonance converter | |
| JP4232845B1 (en) | DC converter | |
| JP5591666B2 (en) | DC-DC converter | |
| CN109861543A (en) | An Interleaved Parallel LCLC Resonant Converter with Wide Load and Wide Gain | |
| CN114337344B (en) | Control method based on self-adaptive hybrid rectification multi-switch resonance LLC converter | |
| JP2007020391A (en) | Highly efficient half-bridge dc/dc converter and its control method | |
| CN109302078B (en) | DC-DC switching power supply based on synchronous rectification mode | |
| KR20180004675A (en) | Bidirectional Converter with Auxiliary LC Resonant Circuit and Operating Method thereof | |
| KR102009351B1 (en) | High Efficiency LLC Resonant Converter with Balanced Secondary Currents using the Two Transformer Structure | |
| CN103138580B (en) | DC-to-DC converter, power converter and control method thereof | |
| Sun et al. | Optimization of high-efficiency half-bridge LLC resonant converter | |
| Cao et al. | Fixed frequency phase shift modulated LLC resonant converter adapted to ultra wide output voltage range | |
| CN112636605B (en) | A DC conversion circuit and its mode switching control method in a wide voltage range | |
| Lu et al. | Solving three key problems of wavelet transform processor using surface acoustic wave devices | |
| CN110868071A (en) | Conversion device | |
| Oeder | Analysis and design of a low-profile LLC converter | |
| US20110058392A1 (en) | Current-sharing power supply apparatus | |
| CN111404415A (en) | Urban rail vehicle auxiliary converter considering switching loss and operation strategy optimization method | |
| Das et al. | Optimal design of a dual active bridge based single-stage dc-ac converter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| ASS | Succession or assignment of patent right |
Owner name: YADA POWER SUPPLY PRODUCTS (SHENZHEN) CO., LTD. Free format text: FORMER OWNER: AIMOSHENG NETWORK ENERGY SOURCE CO LTD Effective date: 20140911 |
|
| C41 | Transfer of patent application or patent right or utility model | ||
| COR | Change of bibliographic data |
Free format text: CORRECT: ADDRESS; FROM: 518057 SHENZHEN, GUANGDONG PROVINCE TO: 518101 SHENZHEN, GUANGDONG PROVINCE |
|
| TR01 | Transfer of patent right |
Effective date of registration: 20140911 Address after: 518101 Guangdong city of Shenzhen province Baoan District Xin'an road two North 68 Street office Honglang District Industrial Park plant Patentee after: Astec power supply (Shenzhen) Co., Ltd. Address before: 518057 Nanshan District science and Technology Industrial Park, Guangdong, Shenzhen Branch Road, No. Patentee before: Aimosheng Network Energy Source Co., Ltd. |