CN100521492C - A harmonic vibration converter - Google Patents
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- CN100521492C CN100521492C CNB2007100750296A CN200710075029A CN100521492C CN 100521492 C CN100521492 C CN 100521492C CN B2007100750296 A CNB2007100750296 A CN B2007100750296A CN 200710075029 A CN200710075029 A CN 200710075029A CN 100521492 C CN100521492 C CN 100521492C
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Abstract
本发明公开了一种谐振变换器，包括变压器、方波生成器、谐振电路、输出整流电路和输出滤波电路，输出整流电路连在变压器副边绕组与输出滤波电路之间，方波生成器输入端接有直流电源，方波生成器用于将输入的直流电压变换为交流方波电压并输出，谐振电路包括第一电感、谐振电容、第二电感，谐振电容和第一电感串联形成谐振支路，第二电感与变压器原边绕组并联形成并联支路，谐振支路一端与并联支路一端相连，谐振支路与并联支路的另一端分别与方波生成器的两个输出端相连；方波生成器输出的交流方波电压为固定频率、可调占空比的交流方波电压。从而避免变换器的工作频率在一个很宽的范围内，从而可以优化输出滤波电路的设计。
The invention discloses a resonant converter, which comprises a transformer, a square wave generator, a resonant circuit, an output rectifier circuit and an output filter circuit, the output rectifier circuit is connected between the transformer secondary winding and the output filter circuit, and the square wave generator inputs The terminal is connected with a DC power supply, and the square wave generator is used to convert the input DC voltage into an AC square wave voltage and output it. The resonant circuit includes a first inductor, a resonant capacitor, and a second inductor. The resonant capacitor and the first inductor are connected in series to form a resonant branch. , the second inductor is connected in parallel with the primary winding of the transformer to form a parallel branch, one end of the resonant branch is connected to one end of the parallel branch, and the other end of the resonant branch and the parallel branch are respectively connected to the two output ends of the square wave generator; The AC square wave voltage output by the wave generator is an AC square wave voltage with a fixed frequency and an adjustable duty cycle. Thereby avoiding the operating frequency of the converter in a very wide range, so that the design of the output filter circuit can be optimized.
Description
Technical field
The present invention relates to a kind of controlled resonant converter.
Background technology
As shown in Figure 1, a kind of symmetrical half bridge structure LLC controlled resonant converter, comprise transformer, square wave maker, resonant circuit, output rectification circuit and output filter circuit, described output rectification circuit is connected between transformer secondary winding and the output filter circuit, described square wave maker input is connected to DC power supply, and described square wave maker is used for the direct voltage Vin of input is transformed to ac square-wave voltage and output.Described transformer comprises former limit winding N1, the first secondary winding N21, the second secondary winding N22.Described square wave maker comprises the first capacitor C d1, the second capacitor C d2, the first switching tube Q1 and second switch pipe Q2.The capacity of the first capacitor C d1 and the second capacitor C d2 is very big, divides equally input voltage vin, and voltage is half of input voltage vin on it.The first switching tube Q1, second switch pipe Q2 constitute a half-bridge structure, and its drive signal is to fix the complementary signal of 50% duty ratio, and the described first switching tube Q1, second switch pipe Q adopt Frequency-variable Modulation to regulate output voltage.Resonant circuit comprises the first inductance L r, resonant capacitance Cr, the second inductance L m.This resonant circuit is connected between the mid point and the first capacitor C d1 and the second capacitor C d2 of half-bridge, so resonant capacitance Cr also plays every straight effect.At outlet side, described output rectification circuit comprises the first rectifier diode D3, the second rectifier diode D4, described output filter circuit comprises output capacitance Co, the first rectifier diode D3, the second rectifier diode D4 constitute centre tapped rectification circuit, and the first rectifier diode D3, the second rectifier diode D4 are directly connected to respectively on the output capacitance Co.
Fig. 2 is the characteristic curve schematic diagram of the switching frequency f of the output voltage V o of controlled resonant converter of existing symmetrical half bridge structure and switching tube.General switching frequency can be chosen in output voltage V o among Fig. 2 and obtain frequency band after the maximum, so frequency raises, output voltage descends.As can be seen from Figure 2, when frequency is elevated to a certain degree, it is very smooth that characteristic curve becomes, even the situation that may occur going up not down, and it is very weak that frequency regulation capability becomes.When underloading or zero load, in order to reduce the output voltage switching frequency that need raise, because characteristic curve became very smooth when frequency was elevated to certain value, reduce very high that voltage need rise switching frequency, cause the operating frequency range of converter very wide.If Electro Magnetic Compatibility requires index very high, when being simple capacitive filter, then can not satisfy the output filter circuit of converter this Electro Magnetic Compatibility index request, then need to change output filter circuit into π type filter circuit or multi-stage filter circuit.If the converter operating frequency range is very wide, parameter index when the index of output filter circuit must satisfy the lowermost switch frequency, output filter causes electric capacity and inductance parameters in the filter very big because frequency is low like this, thereby needs to select the very big filter of volume.In addition, can make when operating frequency is too high that rectifier diode loses the zero-current switching characteristic, it is very high to cause exporting rectifier diode both end voltage spike, must select high withstand voltage diode, and the conduction voltage drop of high withstand voltage diode is higher, thereby loss is multiplied, and causes transducer reliability to reduce decrease in efficiency.
Such as asymmetrical half-bridge LLC controlled resonant converter, the very wide problem of control frequency of converter is arranged all for other LLC series resonant converter.
To sum up, existing controlled resonant converter has following deficiency: when underloading or zero load, in order to reduce the output voltage switching frequency that need raise, because characteristic curve became very smooth when frequency was elevated to certain value, reduce very high that voltage need rise switching frequency, cause the operating frequency range of converter very wide.The very wide output filter circuit that causes of converter switches frequency range is difficult to optimize, and the requirement of output filter circuit must satisfy low-limit frequency the time, cause electric capacity and inductance parameters in the output filter circuit very big, thereby cause the volume of output filter circuit very big.Can make when operating frequency is too high in addition that rectifier diode loses the zero-current switching characteristic, it is very high to cause exporting rectifier diode both end voltage spike, must select high withstand voltage diode, and the conduction voltage drop of high withstand voltage diode is higher, thereby loss is multiplied, cause transducer reliability to reduce decrease in efficiency.
Summary of the invention
The present invention is exactly in order to overcome above deficiency, to have proposed a kind of controlled resonant converter, helping the optimization of output filter.
Technical problem of the present invention is solved by following technical scheme:
A kind of controlled resonant converter, comprise transformer, the square wave maker, resonant circuit, output rectification circuit and output filter circuit, described output rectification circuit is connected between transformer secondary winding and the output filter circuit, described square wave maker input is connected to DC power supply, the dc voltage conversion that described square wave maker is used for input is ac square-wave voltage and output, described resonant circuit comprises first inductance, resonant capacitance, second inductance, described resonant capacitance and the series connection of first inductance form the resonance branch road, described second inductance and the former limit of transformer winding formation in parallel parallel branch, described resonance branch road one end links to each other with parallel branch one end, and described resonance branch road links to each other with two outputs of square wave maker respectively with the other end of parallel branch; It is characterized in that: the ac square-wave voltage of described square wave maker output is the ac square-wave voltage of fixed frequency, adjustable duty ratio, and described fixed frequency satisfies following formula:
f
m<f<f
r，
Wherein f is described fixed frequency, and Cr is the appearance value of resonant capacitance, and Lr is the inductance value of first inductance, and Lm is the inductance value of second inductance.
Technical problem of the present invention is further solved by following technical scheme:
Described fixed frequency also satisfies following formula: (fr-f)＜(f-fm).
Described first inductance and second inductance are respectively external independent inductance.
Described square wave maker comprises first electric capacity, second electric capacity, first switching tube and second switch pipe, be connected across the DC power supply two ends after described first electric capacity and second capacitances in series, be connected across the DC power supply two ends after described first switching tube and the series connection of second switch pipe; Described first inductance, one end is connected between described first switching tube and the second switch pipe, the described first inductance other end links to each other through the end of resonant capacitance with the former limit of second inductance and transformer winding, and the other end of described second inductance and the former limit of transformer winding is connected between first electric capacity and second electric capacity.
Described square wave maker comprises first switching tube, second switch pipe, the 3rd switching tube and the 4th switching tube, be connected across the DC power supply two ends after described first switching tube and the series connection of second switch pipe, be connected across the DC power supply two ends after described the 3rd switching tube and the series connection of the 4th switching tube; Described first inductance, one end is connected to be stated between first switching tube and the second switch pipe, the described first inductance other end links to each other through the end of resonant capacitance with the former limit of second inductance and transformer winding, and the other end of described second inductance and the former limit of transformer winding is connected between the 3rd switching tube and the 4th switching tube.
Described first inductance is the leakage inductance of the former limit of transformer winding, and described second inductance is the magnetizing inductance of the former limit of transformer winding.
A kind of controlled resonant converter, being connected in parallel by two above-mentioned controlled resonant converters that one of have in above-mentioned two kinds of square wave makers forms.
The beneficial effect that the present invention is compared with the prior art is:
What the square wave maker of controlled resonant converter of the present invention was exported is the ac square-wave voltage of fixed frequency, adjustable duty ratio, owing to adopt the PWM control of fixed-frequency, the operating frequency of avoiding converter in a very wide scope, thereby can optimize the design of output filter circuit.The present invention helps the optimal design of main power transformer and the optimal design of filter circuit, thereby helps the optimal design of converter.
The operating frequency of the switching tube of square wave maker is between two characteristic resonant frequencies of resonant circuit, therefore the switching tube of square wave maker can be realized zero voltage switch in full-load range, rectifier diode can be realized zero-current switching, can reduce the switching loss of switching tube, and rectifier diode is owing to be zero-current switching, avoided very high due to voltage spikes occurring, so can select the withstand voltage diode of low-voltage for use at the rectifier diode two ends.And rectifier diode adopts the withstand voltage diode of low-voltage can reduce switching loss on the one hand, improves the efficient and the reliability of controlled resonant converter; Can reduce the cost of controlled resonant converter on the other hand.
The switching frequency of the switching tube of square wave maker is between two characteristic resonant frequencies of resonant circuit, and as far as possible close upper resonance frequency.The switching frequency of higher converter switches pipe can reduce the volume of transformer and the volume of output filter.
Description of drawings
Fig. 1 is the structural representation of symmetrical half bridge structure LLC controlled resonant converter;
Fig. 2 is the output voltage of Fig. 1 and the characteristic curve schematic diagram of switching frequency;
Fig. 3 is an operation mode schematic diagram of the present invention;
Fig. 4 is the structural representation of the specific embodiment of the invention two;
Fig. 5 is the structural representation of the specific embodiment of the invention three;
Fig. 6 is the structural representation of the specific embodiment of the invention four.
Embodiment
Also in conjunction with the accompanying drawings the present invention is described in further details below by concrete execution mode.
Embodiment one
The present invention improves control method existing, as shown in Figure 1 symmetrical half bridge structure LLC controlled resonant converter, be in particular in: control square wave maker is the ac square-wave voltage of fixed frequency f, adjustable duty ratio and exports resonant circuit to that with the dc voltage conversion of input described fixed frequency satisfies following formula:
f
m<f<f
r，
Wherein f is described fixed frequency, and fr is first characteristic resonant frequency of resonant circuit, and fm is second characteristic resonant frequency of resonant circuit, and Cr is the appearance value of resonant capacitance, and Lr is the inductance value of first inductance, and Lm is the inductance value of second inductance.The first switching tube Q1 and the second switch pipe Q2 that are converter adopt PWM control respectively, and the switching frequency f that makes the first switching tube Q1 and second switch pipe Q2 is between the first characteristic resonant frequency fr and the second characteristic resonant frequency fm of resonant circuit, and the pwm signal of the first switching tube Q1 and second switch pipe Q2 input be complementation.Controlled resonant converter of the present invention helps the input filter design by adopting pulse-width modulation (Pulse-width modulation is called for short PWM) control.And can in full-load range, realize the zero voltage switch (ZVS) of main switch (the first switching tube Q1 and second switch pipe Q2), secondary rectifier diode (the first rectifier diode D3, the second rectifier diode D4) is zero-current switching (ZCS).
The converter switches frequency f should be tried one's best near fr, can reduce the volume of main power transformer and the volume of filter by rising converter operating frequency, thereby can reduce the volume of whole controlled resonant converter, improves power density of transform.And the present invention's former limit of transformer winding in whole switch periods all receives input power, and by depressor secondary winding to the load through-put power, the transformer utilization factor height.
The above-mentioned first inductance L r can utilize the leakage inductance of the former limit of transformer winding N1, also can adopt external independent series inductance; The second inductance L m can utilize the magnetizing inductance of the former limit of transformer winding N1, also can adopt external independent shunt inductance.After the first inductance L r and the second inductance L m were integrated in the transformer, whole controlled resonant converter only needed a magnetic core, thereby can save cost, reduce and disturb.
What propose above is a kind of symmetrical half bridge LLC controlled resonant converter of PWM control, and former limit is the symmetrical half bridge structure, and secondary is the centre tapped full-wave rectifying circuit of transformer, and the output among the present invention can be adopted other rectification circuits such as bridge rectifier equally.
Be that example is introduced operation principle of the present invention with controlled resonant converter shown in Figure 1 below.For the ease of the circuit theory analysis, make the following assumptions: the capacity of the first capacitor C d1 and the second capacitor C d2 is very big, and voltage is half of input voltage vin on it; Output capacitance capacity C o is very big, and equivalence is a voltage source.
As shown in Figure 3, this controlled resonant converter one has 6 operation modes in a switch periods.Id3 is the first rectifier diode D among the figure
3On the electric current that flows through, id4 is the second rectifier diode D
4On the electric current that flows through, Vcr is the voltage on the resonant capacitance Cr.The following description of the operation principle of 6 operation modes:
1) mode 1 (t0～t1)
At t0 moment second switch pipe Q
2Turn-off resonance current i
rTo the first switching tube Q
1The output junction capacitance discharge at two ends, simultaneously, to second switch pipe Q
2The output junction capacitance charging at two ends.Up to the first switching tube Q
1Both end voltage reduces to zero, the first switching tube Q
1Body diode D
1The nature conducting.
2) mode 2 (t1～t2)
T1 is the first switching tube Q constantly
1Open-minded, because its body diode D
1So conducting is the first switching tube Q
1For no-voltage is opened (ZVS).Exciting current i
LmLinear increase, resonance current i
rFlow through the first switching tube Q
1And rising, because the first switching tube Q with sinusoidal form
1Switching frequency less than the harmonic period (being first characteristic resonant frequency of resonant circuit) of the first inductance L r and resonant capacitance Cr.Therefore, at resonance current i
rThrough behind the resonance of half period, Q
1Still be in opening state.As resonance current i
rDrop to and exciting current i
LmWhen equating, the first rectifier diode D
3Current over-zero and turn-offing is naturally realized zero-current switching (ZCS).This operation mode finishes.
3) mode 3 (t2～t3)
At the t2 moment first rectifier diode D
3Naturally turn-off owing to current over-zero (ZCS).The second inductance L m no longer is subjected to the restriction of output voltage.At this moment, resonance takes place in the first inductance L r, the second inductance L m and resonant capacitance Cr.Generally, the second inductance L m is much larger than the inductance value of the first inductance L r, so this moment, the first inductance L r, the second inductance L m were long with the harmonic period of resonant capacitance Cr formation, this mode time is generally very short, can think resonance current i
rBasic maintenance is constant.
4) mode 4 (t3～t4)
At t3 constantly, the first switching tube Q
1Turn-off, at this moment resonance current i
rTo second switch pipe Q
2The output junction capacitance discharge at two ends, simultaneously, to the first switching tube Q
1The output junction capacitance charging at two ends.Up to second switch pipe Q
2Both end voltage reduces to zero, second switch pipe Q
2Body diode D
2The nature conducting.
5) mode 5 (t4～t5)
At t4 constantly, second switch pipe Q
2Open-minded, because its body diode D
2So conducting is second switch pipe Q
2For no-voltage is opened (ZVS).Exciting current i
LmLinear increase, resonance current i
rFlow through Q
2And rise with sinusoidal form, because switching frequency is less than the harmonic period of Lr and Cr.Therefore, at the resonance of resonance current through half period, second switch pipe Q
2So be in opening state.As resonance current i
rDrop to and exciting current i
LmWhen equating, the first rectifier diode D
4Current over-zero and turn-offing is naturally realized zero-current switching (ZCS).This operation mode finishes.
6) mode 6 (t5～t6)
At t5 constantly, the second rectifier diode D
4Naturally turn-off owing to current over-zero (ZCS).The second inductance L m no longer is subjected to the restriction of output voltage, and at this moment, resonance takes place for the first inductance L r, resonant capacitance Cr and the second inductance L m.Generally, the second inductance L m is much larger than the inductance value of the first inductance L r, so harmonic period is long, the general time of this mode is very short, can think that exciting curent is a constant current.
Embodiment two
As Fig. 4, the present invention also can improve the control method of full bridge structure LLC controlled resonant converter, the difference of this full bridge structure LLC controlled resonant converter and half-bridge structure LLC controlled resonant converter shown in Figure 1 is: described square wave maker comprises the first switching tube Q1, second switch pipe Q2, the 3rd switching tube Q3 and the 4th switching tube Q4, be connected across the DC power supply two ends after described first switching tube Q1 and the second switch pipe Q2 series connection, be connected across the DC power supply two ends after described the 3rd switching tube Q3 and the 4th switching tube Q4 series connection; The described first inductance L r, one end is connected to be stated between the first switching tube Q1 and the second switch pipe Q2, the described first inductance L r other end links to each other with the end of the former limit of transformer winding N1 with the second inductance L m through resonant capacitance Cr, and the other end of described second inductance L m and the former limit of transformer winding N1 is connected between the 3rd switching tube Q3 and the 4th switching tube Q4.The first switching tube Q1 and the 4th switching tube are same drive signal, second switch pipe Q2 and the 3rd switching tube Q3 are same drive signal, these two drive signal complementations, the first switching tube Q1 equates with the ON time of second switch pipe Q2, recently regulates the output voltage of converter by regulating duty.
The operation principle of above-mentioned full-bridge converter and the operation principle of symmetrical half bridge are similar, do simple the description here.With respect to the symmetrical half bridge converter, the voltage magnitude that is added in the full-bridge converter on the resonant circuit is an input voltage, and be added in voltage magnitude on the resonant circuit in the symmetrical half bridge converter is half of input voltage, thereby makes the no-load voltage ratio of winner's power transformer also different.Though some electric current and voltage stress can be different, basic operation principle is similarly, is not described in detail here, specifically can analyze with reference to the operation principle of symmetrical half bridge.
Embodiment three
Fig. 5 is the structural representation of crisscross parallel symmetrical half bridge LLC controlled resonant converter of the PWM control of this embodiment, and this embodiment is with the difference of embodiment one: adopt two symmetrical half bridge LLC controlled resonant converter crisscross parallels.
Controlled resonant converter as shown in Figure 5 comprises first and second transformer, first and second square wave maker, first and second resonant circuit, first and second output rectification circuit; Described first output rectification circuit is connected in the first transformer secondary winding N21, between N22 and the output filter circuit, the described first square wave maker input is connected to DC power supply Vin, the dc voltage conversion that the described first square wave maker is used for input is ac square-wave voltage and output, described first resonant circuit comprises the first inductance L r1, the first resonant capacitance Cr1, the second inductance L m1, described first resonant capacitance Cr1 and first inductance L r1 series connection form the first resonance branch road, described second inductance L m1 and the former limit of first transformer winding N1 formation first parallel branch in parallel, the described first resonance branch road, one end links to each other with first parallel branch, one end, and the described first resonance branch road links to each other with two outputs of the first square wave maker respectively with the other end of first parallel branch; Described second output rectification circuit is connected in the second transformer secondary winding N31, between N32 and the output filter circuit, the described second square wave maker input is connected to DC power supply, the dc voltage conversion that the described second square wave maker is used for input is ac square-wave voltage and output, described second resonant circuit comprises the 3rd inductance L r2, the second resonant capacitance Cr2, the 4th inductance L m2, described second resonant capacitance Cr2 and the 3rd inductance L r2 series connection form the first resonance branch road, described the 4th inductance L m2 and the former limit of second transformer winding N3 formation second parallel branch in parallel, the described second resonance branch road, one end links to each other with second parallel branch, one end, the described second resonance branch road links to each other described first with two outputs of the second square wave maker respectively with the other end of second parallel branch, the phase difference of the ac square-wave voltage of two square wave makers output is 90 degree.Described output filter circuit is made of output capacitance Co.
The described first square wave maker comprises the first capacitor C d1, the second capacitor C d2, the first switching tube Q1 and second switch pipe Q2, be connected across the DC power supply two ends after the described first capacitor C d1, the second capacitor C d2 series connection, be connected across the DC power supply two ends after described first switching tube Q1 and the second switch pipe Q2 series connection; The described first inductance L r1, one end is connected between described first switching tube Q1 and the second switch pipe Q2, the described first inductance L r1 other end links to each other with the end of the former limit of first transformer winding N1 with the second inductance L m1 through the first resonant capacitance Cr1, and described second inductance L m1's and the former limit of transformer winding N1's the other end is connected between the first capacitor C d1, the second capacitor C d2.
The described second square wave maker comprises the 3rd capacitor C d3, the 4th capacitor C d4, the 3rd switching tube Q3 and the 4th switching tube Q4, be connected across the DC power supply two ends after described the 3rd capacitor C d3, the 4th capacitor C d4 series connection, be connected across the DC power supply two ends after described the 3rd switching tube Q3 and the 4th switching tube Q4 series connection; Described the 3rd inductance L r2 one end is connected between described the 3rd switching tube Q3 and the 4th switching tube Q4, described the 3rd inductance L r2 other end links to each other with the end of the former limit of second transformer winding N3 with the 4th inductance L m2 through the second resonant capacitance Cr2, and described the 4th inductance L m2's and the former limit of second transformer winding N3's the other end is connected between the 3rd capacitor C d3, the 4th capacitor C d4.
The phase difference of the ac square-wave voltage of described first and second square wave maker output is that 90 degree can be realized in the following way: the drive signal of second switch pipe Q2 is than phase lag 180 degree of the drive signal of the first switching tube Q1, the drive signal of the 3rd switching tube Q2 is than phase lag 90 degree of the drive signal of the first switching tube Q1, and the drive signal of the 4th switching tube Q4 realizes than phase lag 270 degree of the drive signal of the first switching tube Q1.The switching tube of this embodiment all adopts PWM control.This embodiment can increase the power output of circuit, reduces the voltage ripple on the output filter capacitor.
Embodiment four
Fig. 6 is the structural representation of crisscross parallel full-bridge LLC controlled resonant converter of the PWM control of this embodiment, this embodiment is with the difference of embodiment three: the structure of described first and second square wave maker is different, and the square wave maker of this embodiment is identical with the structure of the square wave maker of embodiment two.The phase difference of the ac square-wave voltage of first and second square wave maker output of this embodiment also is 90 degree.The switching tube of this embodiment all adopts PWM control.This embodiment can increase the power output of circuit, reduces the voltage ripple on the output filter capacitor.
The present invention adopts PWM control to the switching tube of controlled resonant converter.Owing to adopt the PWM control of fixed-frequency, so the problem of bringing with regard to the broad operating frequency range that has not had variable frequency control that is difficult to optimize converter design helps the input filter circuit design.
The operating frequency that improves controlled resonant converter can reduce the volume of main power transformer and the volume of filter, thereby reduces the converter volume, helps improving power density of transform.But because the switching tube operating frequency improves, if switching tube works in the hard switching state, will cause loss to be multiplied, transducer effciency descends, so be difficult to practical application if high frequency switch power can not be realized soft switch.Controlled resonant converter of the present invention can be realized the zero voltage switch of main switch and the zero-current switching of rectifier diode, so can reduce the switching loss of main switch, and rectifier diode is owing to be zero-current switching, avoided very high due to voltage spikes occurring, so can select the withstand voltage diode of low-voltage for use at the rectifier diode two ends.And rectifier diode adopts the withstand voltage diode of low-voltage can reduce switching loss on the one hand, improves the efficient and the reliability of controlled resonant converter; Can reduce the cost of controlled resonant converter on the other hand.
The switching frequency of the switching tube of controlled resonant converter of the present invention is between two characteristic resonant frequencies of resonant circuit, and as far as possible close higher characteristic resonant frequency.The switching frequency of higher converter switches pipe can reduce the volume of transformer and the volume of output filter.
Above content be in conjunction with concrete preferred implementation to further describing that the present invention did, can not assert that concrete enforcement of the present invention is confined to these explanations.For the general technical staff of the technical field of the invention, without departing from the inventive concept of the premise, can also make some simple deduction or replace, all should be considered as belonging to protection scope of the present invention.
Claims (7)
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| CNB2007100750296A CN100521492C (en) | 2007-06-13 | 2007-06-13 | A harmonic vibration converter |
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| CNB2007100750296A CN100521492C (en) | 2007-06-13 | 2007-06-13 | A harmonic vibration converter |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110907680A (en) * | 2018-09-14 | 2020-03-24 | 台达电子工业股份有限公司 | Current detection device, method and system |
Families Citing this family (32)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101500364A (en) * | 2008-01-30 | 2009-08-05 | 杭州茂力半导体技术有限公司 | Discharge lamp driving apparatus and driving method |
| WO2010069096A1 (en) * | 2008-12-19 | 2010-06-24 | Texas Instruments Incorporated | Fixed-frequency llc resonant power regulator |
| US8717782B2 (en) | 2009-01-07 | 2014-05-06 | Texas Instruments Incorporated | Sweeping frequency LLC resonant power regulator |
| CN101488715B (en) * | 2009-02-19 | 2011-04-20 | 普天信息技术研究院有限公司 | DC/DC resonance converter |
| TWI452809B (en) * | 2011-03-08 | 2014-09-11 | Green Solution Tech Co Ltd | Full-bridge driving controller and full-bridge converting circuit |
| US9178440B2 (en) * | 2013-04-16 | 2015-11-03 | Futurewei Technologies, Inc. | Apparatus and method for resonant converters |
| US9479073B2 (en) | 2013-11-12 | 2016-10-25 | Futurewei Technologies, Inc. | Gate drive apparatus for resonant converters |
| CN105099197A (en) * | 2014-05-20 | 2015-11-25 | 艾默生网络能源有限公司 | Resonance circuit, charger and uninterruptible power supply |
| CN103997217A (en) * | 2014-06-09 | 2014-08-20 | 西安电子科技大学 | Fixed-frequency series resonant converter based on flat inductor |
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6072701A (en) * | 1998-04-16 | 2000-06-06 | Sony Corporation | Current resonance type switching power source |
| US6130825A (en) * | 1998-03-17 | 2000-10-10 | Sony Corporation | Current-resonant switching power supply |
| US6169683B1 (en) * | 1999-10-07 | 2001-01-02 | Ericsson Inc. | Resonant gate drive for synchronous rectifiers |
| US6483721B2 (en) * | 2000-01-28 | 2002-11-19 | Densei-Lambda K.K. | Resonant power converter |
| WO2004068929A2 (en) * | 2003-02-04 | 2004-08-19 | Celetron Usa, Inc. | Improved fixed frequency resonant converter |
-
2007
- 2007-06-13 CN CNB2007100750296A patent/CN100521492C/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6130825A (en) * | 1998-03-17 | 2000-10-10 | Sony Corporation | Current-resonant switching power supply |
| US6072701A (en) * | 1998-04-16 | 2000-06-06 | Sony Corporation | Current resonance type switching power source |
| US6169683B1 (en) * | 1999-10-07 | 2001-01-02 | Ericsson Inc. | Resonant gate drive for synchronous rectifiers |
| US6483721B2 (en) * | 2000-01-28 | 2002-11-19 | Densei-Lambda K.K. | Resonant power converter |
| WO2004068929A2 (en) * | 2003-02-04 | 2004-08-19 | Celetron Usa, Inc. | Improved fixed frequency resonant converter |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110907680A (en) * | 2018-09-14 | 2020-03-24 | 台达电子工业股份有限公司 | Current detection device, method and system |
| US11187728B2 (en) | 2018-09-14 | 2021-11-30 | Delta Electronics, Inc. | Current sensing device, method and system |
| CN110907680B (en) * | 2018-09-14 | 2022-03-01 | 台达电子工业股份有限公司 | Current detection device, method and system |
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