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WO2024160168A1 - 平面透镜天线、波束相位调节方法、天线设备及介质 - Google Patents

平面透镜天线、波束相位调节方法、天线设备及介质 Download PDF

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Publication number
WO2024160168A1
WO2024160168A1 PCT/CN2024/074444 CN2024074444W WO2024160168A1 WO 2024160168 A1 WO2024160168 A1 WO 2024160168A1 CN 2024074444 W CN2024074444 W CN 2024074444W WO 2024160168 A1 WO2024160168 A1 WO 2024160168A1
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WO
WIPO (PCT)
Prior art keywords
antenna
metamaterial
beam phase
lens
planar lens
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2024/074444
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English (en)
French (fr)
Inventor
张金玲
钟坤静
彭琳
朱雄志
贾立飞
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ZTE Corp
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ZTE Corp
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Publication of WO2024160168A1 publication Critical patent/WO2024160168A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/02—Refracting or diffracting devices, e.g. lens, prism
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters

Definitions

  • the present application relates to the field of antenna technology, and in particular to a planar lens antenna, a beam phase adjustment method, an antenna device and a medium.
  • 5G fifth generation mobile communication
  • the reception and reconnaissance of 5G signals in a specific environment is of great significance to the current information system capacity building in my country.
  • millimeter wave frequency bands e.g., 60GHz bands
  • the radiation coverage and radiation gain of radio waves are limited.
  • base station antennas generally use large-scale or extremely large-scale phased antenna arrays.
  • the phased antenna array requires that each antenna unit be connected to a phase shifting device with a phase shifting function at the back end, which means that the number of phase shifting devices required to be configured in the phased antenna array is huge.
  • the large number of phase shifting devices brings extremely high complexity to the antenna equipment, resulting in a significant increase in the cost and power consumption of the antenna equipment.
  • the main purpose of the present application is to provide a planar lens antenna, a beam phase adjustment method, an antenna device and a medium, aiming to reduce the cost and power consumption of the antenna device while improving the radiation coverage and radiation gain of radio waves.
  • planar lens antenna comprising:
  • a feed antenna wherein the feed antenna comprises a plurality of antenna arrays, each of the antenna arrays is arranged at intervals along a first direction, the antenna array is composed of a plurality of antenna units distributed in an array, and the antenna units are used to radiate radio waves;
  • a metamaterial plane lens wherein the metamaterial plane lens is arranged opposite to the feed antenna, and the refractive index of the metamaterial plane lens for radio waves is consistent in a first direction and gradually changes in a second direction, so that the metamaterial plane lens can compensate and shape the beam phase of the radio waves radiated by the feed antenna in the second direction, wherein the first direction is perpendicular to the second direction.
  • the present application also provides a beam phase adjustment method, which is applied to the planar lens antenna as described above, comprising:
  • the refractive index of the metamaterial plane lens in the second direction is calibrated according to the beam phase compensation information, so that the beam phases of the radio waves transmitted by the metamaterial plane lens are equal in the second direction.
  • the present application also provides an antenna device, including the planar lens antenna as described above.
  • the present application also provides a medium, which is a computer-readable storage medium, on which a beam phase adjustment program is stored.
  • a beam phase adjustment program is executed by a processor, the processor runs the steps of the beam phase adjustment method as described above.
  • FIG1 is a schematic diagram of a scenario in which a planar lens antenna performs beam scanning according to an embodiment of the present application
  • FIG2 is a schematic diagram of the structure of a planar lens antenna according to an embodiment of the present application.
  • FIG3 is a schematic diagram of the structure of a feed antenna according to an embodiment of the present application.
  • FIG4 is a geometric diagram of calculating beam phase compensation information in an embodiment of the present application.
  • FIG5 is a schematic structural diagram of a feed antenna according to a specific embodiment of the present application.
  • FIG6 is a schematic diagram of the structure of a metamaterial planar lens according to a specific embodiment of the present application.
  • FIG7 is a top view of a feed antenna in one embodiment of the present application.
  • FIG8 is a top view of a feed antenna in another embodiment of the present application.
  • FIG9 is a top view of a metamaterial unit according to a specific embodiment of the present application.
  • FIG10 is a top view of a metamaterial planar lens according to a specific embodiment of the present application.
  • FIG11 is a diagram of simulation experimental data when the array spacing of the antenna array in the vertical direction is 6 mm;
  • FIG12 is a simulation experiment data diagram of the antenna array when the array spacing in the vertical direction is 10 mm;
  • FIG13 is a beam phase diagram of the antenna array when the array spacing in the vertical direction is 10 mm;
  • FIG14 is a schematic diagram of a flow chart of a beam phase adjustment method according to an embodiment of the present application.
  • FIG. 15 is a schematic diagram of the hardware structure of the antenna device according to an embodiment of the present application.
  • connection can be a fixed connection, a detachable connection, or an integral connection; it can be a mechanical connection or an electrical connection; it can be a direct connection or an indirect connection through an intermediate medium, it can be the internal connection of two elements or the interaction relationship between two elements, unless otherwise clearly defined.
  • fixation can be a fixed connection, a detachable connection, or an integral connection; it can be a mechanical connection or an electrical connection; it can be a direct connection or an indirect connection through an intermediate medium, it can be the internal connection of two elements or the interaction relationship between two elements, unless otherwise clearly defined.
  • base station antennas especially those in the millimeter wave frequency band, require high gain to offset space loss.
  • base station antennas are required to have wide coverage.
  • base station antennas In order to achieve high gain and wide coverage, base station antennas generally use large-scale or extremely large-scale phased antenna arrays.
  • the phased antenna array requires that each antenna unit be connected to a phase shifting device with a phase shifting function at the back end, which means that the number of phase shifting devices that need to be configured in the phased antenna array is huge.
  • the large number of phase shifting devices brings extremely high complexity to the antenna equipment, resulting in a significant increase in the cost and power consumption of the antenna equipment.
  • planar lens antenna 100 includes:
  • a feed antenna 1 the feed antenna 1 comprises a plurality of antenna arrays 11, each antenna array 11 is arranged at intervals along a first direction, the antenna array 11 is composed of a plurality of antenna units 111 distributed in an array, and the antenna unit 111 is used to radiate radio waves;
  • Metamaterial plane lens 2 metamaterial plane lens 2 is arranged opposite to feed antenna 1, and the refractive index of metamaterial plane lens 2 for radio waves is consistent in the first direction, and gradually changes in the second direction, so that metamaterial plane lens 2 can compensate and shape the beam phase of radio waves radiated by feed antenna 1 in the second direction, wherein the first direction is perpendicular to the second direction.
  • the refractive index of metamaterial plane lens 2 for radio waves being consistent in the first direction means that the refractive index is consistent as a whole. Even if the refractive index of a few antenna units 111 of metamaterial plane lens 2 is different in the first direction, it only leads to inconsistent refractive index of a few beams, and its local subtle beam inconsistency.
  • the first direction is perpendicular to the second direction.
  • the first direction is a horizontal direction and the second direction is a vertical direction.
  • the first direction is a vertical direction and the second direction is a horizontal direction.
  • the above examples are only used to assist in understanding the embodiments of the present application and do not constitute a limitation on the first direction and the second direction.
  • the metamaterial plane lens 2 is arranged opposite to the feed antenna 1, and the feed antenna 1 includes a plurality of antenna arrays 11, and each antenna array 11 is arranged at intervals along the first direction. That is to say, the orthographic projection of the metamaterial plane lens 2 on the plane where the feed antenna 1 is located covers at least two antenna arrays 11, so that the electromagnetic waves radiated by the at least two antenna arrays 11 are beam scanned through the metamaterial plane lens 2.
  • the at least two antenna arrays 11 arranged at intervals in the first direction are directly opposite to the metamaterial plane lens 2, and since the refractive index of the metamaterial plane lens 2 for radio waves is consistent in the first direction and gradually changes in the second direction, the at least two antenna arrays 11 are radiated to the metamaterial plane lens 2 in the form of spherical waves a in their respective spatial dimensions, and the spherical waves a are converted into plane waves A by the metamaterial plane lens 2. Since the plurality of antenna arrays 11 radiate electromagnetic waves in the first direction toward different positions of the metamaterial plane lens 2, the feed antenna 1 is facilitated to realize beam scanning in multiple different spatial dimensions.
  • the metamaterial planar lens 2 and the feed antenna 1 are disposed opposite to and in parallel.
  • the metamaterial planar lens 2 includes a dielectric substrate 21, and a plurality of metamaterial units 22 covered on the surface of the dielectric substrate 21, wherein the unit response phases of the metamaterial units 22 covered along a first direction of the dielectric substrate 21 are consistent, and the unit response phases of the metamaterial units 22 covered along a second direction of the dielectric substrate 21 are gradually changed.
  • the material of the dielectric substrate 21 may include one or more of PET, COP, glass, polytetrafluoroethylene, PMMA, PC and carbon compounds.
  • the metamaterial unit 22 may be a three-dimensional object having a unit area and a height. Although the metamaterial units 22 have the same unit area, the unit response phase between the metamaterial units 22 may vary according to the material and height of the dielectric material constituting the metamaterial unit 22. For example, when the metamaterial unit 22 has a dielectric material with the same unit area and material, the unit response phase may vary according to the height between the metamaterial units 22. When the metamaterial units 22 included in the metamaterial planar lens 2 have the same unit area and height, the metamaterial unit 22 may have different unit response phases according to the material of the dielectric material.
  • the unit response phase can be different according to the height of the metamaterial unit 22 of the same dielectric material with the same unit area, in the metamaterial plane lens 2, by arranging the metamaterial units 22 of the same height in the first direction and arranging the metamaterial units 22 of different heights in the second direction, when the radio wave radiated from the antenna array 11 passes through the first direction, the phase of the radio wave is the same as the phase of the radio wave incident on the metamaterial plane lens 2, so that the coverage of the output radio wave can be enlarged.
  • the phase of the radio wave in the second direction is compensated, so that the beam phase of the radio wave transmitted by the metamaterial plane lens 2 can be kept consistent in the second direction, thereby enhancing the radiation gain of the output radio wave.
  • the unit response phase can be different according to the dielectric material of the metamaterial unit 22 of the same height with the same unit area, in the metamaterial plane lens 2, by arranging the metamaterial unit 22 with the same unit response phase in the first direction and arranging the metamaterial unit 22 with different unit response phases in the second direction, when the radio waves radiated by the antenna array 11 pass through the second direction, all the radio waves output to the metamaterial plane lens 2 have the same phase, so the gain of the output radio waves can be increased.
  • the radio waves in the second direction are phase compensated, so that the beam phase of the radio waves transmitted by the metamaterial plane lens 2 can be kept consistent in the second direction, thereby enhancing the radiation gain of the output radio waves.
  • the metamaterial plane lens 2 is provided with a dielectric substrate 21, and a plurality of metamaterial units 22 covered on the surface of the dielectric substrate 21, wherein the unit response phases of the metamaterial units 22 covered along the first direction of the dielectric substrate 21 are consistent, and the unit response phases of the metamaterial units 22 covered along the second direction of the dielectric substrate 21 are gradually changed, thereby effectively achieving that the refractive index of the metamaterial plane lens 2 for radio waves is consistent in the first direction and gradually changes in the second direction, thereby achieving the compensation shaping of the beam phase of the radio waves radiated by the feed antenna 1 by the metamaterial plane lens 2 in the second direction.
  • the refractive index of the metamaterial plane lens 2 for radio waves gradually decreases from the central axis position toward both sides along the second direction, and the refractive indices on both sides of the central axis position are symmetrically distributed about the central axis position, wherein the central axis position is the center position of the positive projection of the feed antenna 1 on the metamaterial plane lens 2.
  • the central axis position is the center position of the orthographic projection of the feed antenna 1 on the metamaterial plane lens 2.
  • the refractive index of the metamaterial plane lens 2 for radio waves is set to gradually decrease from the central axis position to both sides along the second direction, and the refractive indexes on both sides of the central axis position are symmetrically distributed about the central axis position.
  • the part with a large refractive index can perform phase compensation on radio waves that arrive at the metamaterial plane lens 2 relatively close to the central axis, and the part with a small refractive index can perform phase compensation on radio waves that arrive at the relatively edge of the metamaterial plane lens 2.
  • the phases of the electromagnetic waves emitted from the metamaterial plane lens 2 are equal, thereby forming a beam with good directivity, realizing the concentration of electromagnetic wave energy, and improving the antenna gain.
  • the metamaterial planar lens 2 has a first surface 23 and a second surface 24 that are relatively arranged, and a plurality of through holes (not shown) arranged in an array that penetrate the first surface 23 and the second surface 24, the first surface 23 is opposite to the feed antenna 1, the aperture of the through holes gradually increases from the central axis position to both sides along the second direction, and/or the arrangement density of the through holes gradually increases from the central axis position to both sides along the second direction.
  • the unit response phase of the metamaterial plane lens 2 can be changed by changing the aperture of the through hole on the metamaterial plane lens 2.
  • the aperture of the through hole gradually increases from the central axis position to both sides along the second direction, and the refractive index of the metamaterial plane lens 2 to radio waves gradually decreases from the central axis position to both sides.
  • the unit response phase of the metamaterial plane lens 2 gradually changes from the central axis position to both sides.
  • the aperture of the through hole on the metamaterial plane lens 2 gradually increases from the central axis position to both sides along the second direction, so that the phase compensation of the metamaterial plane lens 2 to the electromagnetic wave can be gradually reduced from the central axis position of the metamaterial plane lens 2 to both sides along the second direction, thereby compensating the phase of the electromagnetic wave emitted by the antenna array 11, making the phase of the electromagnetic wave emitted from the metamaterial plane lens 2 equal, thereby forming a beam with good directivity, realizing the concentration of electromagnetic wave energy, and improving the antenna gain.
  • the metamaterial plane lens 2 prepared in this embodiment can realize the gradual change of the refractive index of the metamaterial plane lens 2 to the radio wave by adjusting the spacing between the through holes, so that the adjustable range of the refractive index is large, and the refractive index of different positions of the metamaterial plane lens 2 can be flexibly set.
  • This embodiment does not limit the shape of the through hole, and the shape of the through hole includes but is not limited to circular, square, triangular, etc.
  • the arrangement density of the through holes gradually increases from the central axis position to both sides along the second direction.
  • the refractive index of the metamaterial plane lens 2 can be changed by changing the arrangement density of the through holes on the metamaterial plane lens 2.
  • the arrangement density of the through holes gradually increases from the central axis position to both sides along the second direction, and at this time, the refractive index of the metamaterial plane lens 2 gradually decreases from the central axis position to both sides.
  • the arrangement density of the through holes on the metamaterial plane lens 2 gradually increases from the central axis position to both sides along the second direction, so that the phase compensation of the metamaterial plane lens 2 to the electromagnetic wave can be gradually reduced from the central axis position of the metamaterial plane lens 2 to both sides along the second direction, thereby compensating the phase of the electromagnetic wave emitted by the antenna array 11, making the phase of the electromagnetic wave emitted from the metamaterial plane lens 2 equal, thereby forming a beam with good directivity, realizing electromagnetic wave energy concentration, and improving antenna gain.
  • the process of preparing the metamaterial plane lens 2 in this embodiment is simple, and only the same through hole size needs to be set, and the refractive index of the metamaterial plane lens 2 to the electromagnetic wave can be gradually changed by adjusting the spacing between the through holes.
  • the metamaterial planar lens 2 includes a laminated dielectric substrate 21 and a metal functional layer (not shown), the metal functional layer includes a plurality of metal resonance units (not shown), and the refractive index of the metal resonance units in the metal functional layer gradually decreases from the central axis position to both sides along the second direction.
  • the metamaterial planar lens 2 includes a laminated dielectric substrate 21 and a metal functional layer, wherein the metal functional layer includes a plurality of metal resonance units.
  • the metamaterial planar lens 2 can arrange metal resonance units having the same refractive index (i.e., the same unit response phase) in a first direction of the dielectric substrate 21, and the refractive index (or unit response phase) in a second direction is symmetrical about the central axis.
  • the metamaterial planar lens 2 includes a dielectric substrate 21 and a plurality of metamaterial units 22 covering the surface of the dielectric substrate 21, wherein the refractive index of the metamaterial units 22 covering the surface of the dielectric substrate 21 gradually decreases from the central axis position to both sides along the second direction.
  • the metamaterial plane lens 2 includes a dielectric substrate 21 and a plurality of metamaterial units 22 covering the surface of the dielectric substrate 21.
  • the metamaterial plane lens 2 can arrange metamaterial units 22 having the same refractive index in a first direction of the dielectric substrate 21 and having refractive indexes symmetrical about the central axis along a second direction.
  • the phase compensation of the electromagnetic wave by the metamaterial plane lens 2 can be gradually reduced from the central axis position of the metamaterial plane lens 2 to both sides along the second direction, thereby compensating the phase of the electromagnetic wave emitted by the antenna array 11, making the phase of the electromagnetic wave emitted from the metamaterial plane lens 2 equal, thereby forming a beam with good directivity, realizing electromagnetic wave energy concentration, and improving antenna gain.
  • the process of preparing the metamaterial plane lens 2 in this embodiment is simple, no drilling is required, and the thickness is consistent, which reduces the manufacturing difficulty and cost.
  • each antenna array 11 is composed of a plurality of antenna units 111 distributed in an array.
  • the types of the antenna array 11 include, but are not limited to, a phased array antenna array, a lens antenna array, and the like.
  • the orthographic projection of the metamaterial planar lens 2 on the plane where the feed antenna 1 is located covers the multiple antenna arrays 11 , so that the electromagnetic wave signals radiated by the multiple antenna arrays 11 can all be radiated to the metamaterial planar lens 2 .
  • the refractive index of the metamaterial plane lens 2 for radio waves changes gradually in the second direction.
  • the refractive index of the lens 2 for the electromagnetic wave in the second direction changes gradually according to the gradient, so that the phase compensation of the electromagnetic wave in the metamaterial plane lens 2 changes gradually according to the gradient, thereby making the phases of the electromagnetic waves emitted from the metamaterial plane lens 2 equal, enhancing the directivity of the electromagnetic wave radiation, so that the radio waves radiated by the multiple antenna arrays 11 are compensated and shaped in the second direction for the beam phase, so that the energy of the radio waves (or electromagnetic waves) is concentrated, and the gain of the radio waves is improved.
  • the antenna unit 111 may be a primary radiator, and the type of the primary radiator may be a horn antenna, a waveguide slot antenna, or a microstrip antenna.
  • This embodiment does not limit the number of antenna units 111 provided in the antenna array 11.
  • An antenna array 11 is formed by providing a plurality of antenna units 111 distributed in an array, so that the beam pointing ranges radiated by each antenna unit 111 in each antenna array 11 are different.
  • the beam pointing ranges of different antenna units 111 may overlap.
  • the beam pointing ranges of different antenna units 111 may overlap to cover the transmission and reception of electromagnetic wave signals on one side, for example, the coverage angle of the electromagnetic wave signal of an antenna array 11 is greater than 180 degrees.
  • the antenna array 11 also includes a phase shifting unit (not shown), which is connected to the antenna unit 111.
  • the phase shifting unit is used to periodically change the beam direction of the radio waves to be radiated by the antenna unit 111 so that the radio waves radiated by the antenna unit 111 can be periodically beam scanned in a first direction.
  • the antenna array 11 further includes a phase shifting unit, which is connected to the antenna unit 111. All antenna units 111 in the same antenna array 11 may share a phase shifting unit, or each antenna unit 111 in the same antenna array 11 may be independently connected to a phase shifting unit, which is not specifically limited in this embodiment.
  • the phase shift unit may be a radio frequency circuit composed of a phase shifter and an amplifier.
  • the phase shift unit adjusts the phase value of the antenna unit 111 in the antenna array 11 so that the antenna array 11 has a beam scanning capability in a first direction.
  • a metamaterial plane lens 2 is arranged relative to a feed antenna 1, and the refractive index of the metamaterial plane lens 2 for radio waves is consistent in a first direction and gradually changes in a second direction, wherein the first direction is perpendicular to the second direction, so that the metamaterial plane lens 2 can compensate and shape the beam phase of the radio waves radiated by the feed antenna 1 in the second direction, thereby making the beam phases of the radio waves transmitted by the metamaterial plane lens 2 equal in the second direction. Due to the focusing effect of the radio waves in the second direction, the radiation gain of the radio waves is enhanced.
  • a planar lens antenna 100 is arranged to include a feed antenna 1 and a metamaterial plane lens 2, wherein the feed antenna 1 includes a plurality of antenna arrays 11, each antenna array 11 is arranged at intervals along the first direction, and the antenna array 11 is composed of a plurality of antenna units 1 distributed in an array.
  • the antenna unit 111 is used to radiate radio waves, and the radio waves are radiated toward different positions of the planar lens by controlling different antenna arrays 11 to make each antenna array 11 have different focusing directions, so that the radiation range of the radio waves is improved, so that the embodiment of the present application not only improves the gain of the feed antenna 1 by configuring the positions of different antenna arrays 11 in the feed antenna 1 and the phase distribution in the metamaterial planar lens 2, but also realizes the beam scanning capability in the second direction (such as the horizontal direction) and the combined wide beam in the first direction (such as the vertical direction), thereby achieving high-gain and wide-coverage base station antenna performance with only a few phase shifting devices, reducing the cost and power consumption of the antenna device, and then achieving the improvement of the radiation coverage and radiation gain of the radio waves while reducing the cost and power consumption of the antenna device.
  • planar lens antenna 100 of a specific embodiment is listed below:
  • the embodiment of the present application is applied to the base station antenna scene to achieve high gain and wide coverage.
  • the hardware framework of the planar lens antenna 100 is composed of a feed antenna 1 and a metamaterial planar lens 2.
  • the feed antenna 1 is composed of several groups of small linear arrays (i.e., antenna arrays 11) arranged in a certain direction.
  • the antenna units 111 in the small linear arrays are all connected to phase shifters (i.e., phase shifting units).
  • the antenna unit 111 can be a half-wave array or a patch antenna as long as it meets the frequency band performance, preferably a patch antenna.
  • the number of antenna units 111 in the linear array can be set according to the scanning capability and gain, preferably 4 to 8.
  • the spacing of the antenna units 111 in the linear array i.e., the antenna array 11
  • the number of linear arrays of the feed antenna 1 can be determined according to the coverage requirements, preferably 3 to 6 groups.
  • the metamaterial planar lens 2 is composed of a substrate and a plurality of phase shift units formed by a metal functional layer covering the substrate.
  • the substrate may be a dielectric substrate 21, and the material of the dielectric substrate 21 may include one or more materials such as PET, COP, glass, polytetrafluoroethylene, PMMA, PC, carbon compounds, etc.
  • the metal functional layer may be formed on the substrate by etching, photolithography, chemical plating or electroplating.
  • the metal functional layer in the phase shift unit may be multiple layers, preferably 2 to 4 layers.
  • the present application provides a beam phase adjustment method.
  • the beam phase adjustment method is applied to the planar lens antenna as described above, and includes the following steps:
  • Step S10 determining actual beam phase distribution information of the radio wave reaching the surface of the metamaterial planar lens
  • the actual beam phase distribution information input by the user through human-computer interaction can be obtained.
  • the actual beam phase distribution information of the radio waves reaching the surface of the metamaterial planar lens can be determined according to the law of radio wave transmission of each antenna array of the feed antenna.
  • Step S20 obtaining theoretical beam phase distribution information required by the current antenna application scenario, and calculating beam phase compensation information in the second direction according to the actual beam phase distribution information and the theoretical beam phase distribution information;
  • Step S30 calibrate the refractive index of the metamaterial plane lens in the second direction according to the beam phase compensation information, so that the beam phase of the radio wave transmitted by the metamaterial plane lens is equal in the second direction.
  • the method before the step of obtaining theoretical beam phase distribution information required by the current antenna application scenario, the method further includes:
  • Step S40 obtaining a pre-calibrated radiation performance mapping table, wherein the radiation performance mapping table includes a plurality of beam phase distribution information, and a radiation coverage value and a radiation gain value mapped by each beam phase distribution information;
  • Step S50 obtaining a target radiation coverage value and a target radiation gain value required by the current antenna application scenario, and querying from the radiation performance mapping table to obtain beam phase distribution information mapped to the target radiation coverage value and the target radiation gain value;
  • Step S60 Using the beam phase distribution information mapped by the target radiation coverage value and the target radiation gain value as the theoretical beam phase distribution information required by the current antenna application scenario.
  • each antenna array of the feed antenna changes the beam phase through the phase shifting unit to perform beam scanning
  • the change of the beam phase is periodic, that is, the beam phase of the radio waves emitted by each antenna array of the feed antenna is regular, so the actual beam phase distribution information of the radio waves reaching the surface of the metamaterial planar lens can be determined according to the law of the radio waves emitted by each antenna array of the feed antenna.
  • the actual beam phase distribution information of the radio waves reaching the surface of the metamaterial planar lens can be determined. It is easy to understand that the actual beam phase distribution information refers to the actual beam phase corresponding to different positions of the radio waves emitted by the feed antenna reaching the surface of the metamaterial planar lens (not yet through the metamaterial planar lens).
  • the required radiation coverage range value and/or radiation gain value are often different.
  • the beam phases corresponding to the radio waves radiated by the feed antenna at different positions on the surface of the metamaterial planar lens are often different. That is, for different antenna application scenarios, the required theoretical beam phase distribution information is often different.
  • the theoretical beam phase distribution information refers to the theoretical beam phases corresponding to different positions of the radio waves emitted by the feed antenna after passing through the surface of the metamaterial planar lens in the face of the required radiation coverage range value and/or radiation gain value.
  • the beam phase compensation information in the second direction can be accurately calculated based on the actual beam phase distribution information and the theoretical beam phase distribution information, so as to facilitate the subsequent calculation of the unit response at each position on the metamaterial plane lens based on the beam phase compensation information.
  • the phase is calibrated (for example, the relative position of each antenna array of the feed antenna and the metamaterial plane lens is adjusted, and for example, the unit response phase of the metamaterial unit at different positions on the surface of the dielectric substrate of the metamaterial plane lens is calibrated, and for example, the unit response phase of the metal resonance unit at different positions on the surface of the dielectric substrate of the metamaterial plane lens is calibrated, and for example, the aperture size of the through hole on the metamaterial plane lens or the arrangement density of the through hole is calibrated), so as to calibrate the refractive index of the metamaterial plane lens in the second direction, thereby ensuring that the beam phase of the radio wave transmitted by the metamaterial plane lens is equal in the second direction.
  • the metamaterial plane lens will maintain the horizontal scanning capability of the feed line array (i.e., the feed antenna), so the refractive index of the metamaterial plane lens for radio waves in the horizontal direction is basically the same, and phase compensation is performed in the vertical direction so that beam focusing and specific pointing can be performed (it can also be designed to maintain the vertical scanning capability and perform phase compensation in the horizontal direction so that beam focusing and specific pointing can be performed).
  • the metamaterial plane lens including two line arrays (i.e., antenna arrays) as an example, the phase compensation value of the metamaterial plane lens in the vertical direction is calculated.
  • points a and b are the positions of the line arrays in the vertical direction, specifically a ( xa , ya , fa ) and b ( xb , yb , fb ).
  • the position response phases of them to point i in the metamaterial plane can be calculated as: ⁇ a_i and ⁇ b_i respectively.
  • ⁇ 0 is the wavelength of the electromagnetic wave in free space
  • fa and fb are the focal lengths of the line array a and line array b respectively.
  • xa , xb , xi are the projection coordinates of a, b, i on the X-axis.
  • ya , yb , yi are the projection coordinates of a, b, i on the X-axis.
  • the ideal response phase of point i in the metamaterial plane lens can be derived by using the array antenna beam synthesis principle. Then the compensation phase for beam a at point i is The response phase of the b array at point i is
  • the phase value can be used to obtain the focusing direction of the b-array in the vertical plane.
  • the positions of the a-array and b-array and the response codebook of the metamaterial plane lens can be optimized (for example, the unit response phase of the metamaterial plane lens at different positions can be calibrated).
  • this embodiment is based on a planar lens antenna framework composed of a feed antenna 1 and a metamaterial planar lens.
  • the feed antenna 1 is composed of several groups (3a, 3b, 3c, 3d) of small linear arrays (i.e., antenna arrays) arranged in a first direction (e.g., horizontal direction).
  • the antenna units 111 in the small linear arrays are all connected to phase shifters (i.e., phase shifting units).
  • the metamaterial planar lens 2 is composed of a plurality of metamaterial units 22 having different fixed phase shifting capabilities.
  • the structure of the feed antenna used in this specific embodiment may be as shown in Figure 7 or Figure 8.
  • the spacing between the two groups of feed antennas in the vertical direction is 6mm and 10mm respectively.
  • the feed antenna uses a patch antenna solution and adopts a polytetrafluoroethylene medium with a dielectric constant of 2.7 and a loss tangent of 0.0023.
  • the 4 ⁇ 4 feed antenna array can be regarded as a combination of four groups of 1 ⁇ 4 linear arrays in the horizontal direction.
  • the spacing between each antenna array in the horizontal direction is 6mm, and the spacing between each antenna array in the vertical direction is also 6mm.
  • the spacing between each antenna array in the horizontal direction is 6mm, and the spacing between each antenna array in the vertical direction is 10mm.
  • the metamaterial unit structure of the metamaterial plane lens is shown in FIG9 .
  • the size of the phase shift unit is L ⁇ L, and the unit side length L is selected as 4.6 mm, which is slightly less than half of the resonant frequency air wavelength.
  • the side length l of the square metal frame is 4 mm, and the lengths l1 and l2 of the two rectangular metal strips constituting the T-shaped metal strip are 1.6 mm and 0.4 mm respectively.
  • the width w of all metal strips is consistent, all of which are 0.2 mm.
  • the dielectric sheet is Rogers 4003, with a relative dielectric constant of 3.55, a loss tangent of 0.0027, and a thickness of 0.203 mm.
  • the metamaterial unit of the metamaterial plane lens can be double-layered.
  • the schematic diagram of the array structure of the metamaterial planar lens is shown in Figure 10.
  • the spacing p between the metamaterial units is 4.6 mm.
  • the arm length of the phase shift unit of the metamaterial planar lens in the vertical direction is selected according to the phase adjustment curve of the metamaterial lens unit, and remains consistent in the horizontal direction.
  • the focal length f of the antenna array of the metamaterial planar lens is 44 mm, the phase shift and corresponding l1 parameters required to be provided by each phase shift unit of the planar lens antenna are shown in Table 1 below:
  • corresponding arm lengths are set at different positions of the array (ie, the antenna array) according to the need for phase compensation, and the overall gain of the metamaterial lens antenna is improved by adjusting the phase.
  • the 26 GHz frequency point is selected for simulation, and linear array 1, linear array 2, linear array 3, and linear array 4 are selected for separate excitation.
  • Figure 11 shows the corresponding simulation results when the array spacing of the antenna array in the vertical direction is 6 mm.
  • the gain of a single linear array can be increased by about 9 dBi, and the vertical plane coverage range is -16 degrees to 16 degrees.
  • the combined gain is further increased by 1.7 dBi.
  • Figure 12 shows the corresponding simulation results when the array spacing of the antenna array in the vertical direction is 10 mm.
  • the gain of a single linear array can be increased by about 9 dBi, and the vertical plane coverage range is -22.75 degrees to 23 degrees.
  • planar lens antenna has guaranteed horizontal scanning capability and the overall antenna gain is equivalent to that of a full 5*5 scale phased array antenna, reducing the number of phase shifter devices (i.e. phase shifting units) by 36%. At the same time, it maintains the horizontal scanning capability and vertical combined wide beam coverage.
  • the antenna array of the feed antenna used in this embodiment is a traditional microstrip antenna to verify the corresponding method and array mode.
  • Antenna arrays using different feed antennas such as an array composed of slot-coupled antenna units, a horn antenna array, etc., can also achieve the corresponding effect.
  • the gain of the lens antenna is further improved by using two groups of antenna arrays with a smaller vertical spacing, and the beam width of the lens antenna is further improved by selecting two groups of antenna arrays with a larger vertical spacing.
  • the embodiment of the present application also provides an antenna device, referring to FIG. 15, which is a schematic diagram of the hardware structure of an antenna device provided by the embodiment of the present application.
  • the antenna device may include: a processor 1001, such as a central processing unit (CPU), a communication bus 1002, a user interface 1003, a network interface 1004, and a memory 1005.
  • the communication bus 1002 is used to realize the connection and communication between these components.
  • the user interface 1003 may include a display screen (Display), an input unit such as a keyboard (Keyboard), and the user interface 1003 may also include a standard wired interface and a wireless interface.
  • the network interface 1004 may include a standard wired interface and a wireless interface (such as a wireless fidelity (Wireless-Fidelity, WI-FI) interface).
  • the memory 1005 may be a high-speed random access memory (Random Access Memory, RAM) memory, or a stable non-volatile memory (Non-Volatile Memory, NVM), such as a disk memory.
  • RAM Random Access Memory
  • NVM Non-Volatile Memory
  • the memory 1005 may also be a storage device independent of the aforementioned processor 1001 .
  • the structure shown in FIG15 does not limit the antenna device, and may include more or fewer components than shown, or combine certain components, or arrange components differently.
  • the memory 1005 as a storage medium may include an operating system, a data storage module, a network communication module, a user interface module, and a beam phase adjustment program.
  • the network interface 1004 is mainly used for data communication with other devices; the user interface 1003 is mainly used for data interaction with the user; the processor 1001 and the memory 1005 in this embodiment can be set in the communication device, and the communication device calls the beam phase adjustment program stored in the memory 1005 through the processor 1001, and executes the beam phase adjustment method provided in any of the above embodiments.
  • the terminal proposed in this embodiment and the beam phase adjustment method proposed in the above embodiment belong to the same inventive concept.
  • the technical details not described in detail in this embodiment can be referred to any of the above embodiments, and this embodiment has the same beneficial effects as executing the beam phase adjustment method.
  • the present application also provides an antenna device, including the planar lens antenna as described above.
  • the present application also provides a medium, which is a computer-readable storage medium, and the computer-readable storage medium stores a beam phase adjustment program.
  • the processor runs the steps of the beam phase adjustment method as described above.
  • the technical solution of the present application is essentially or the part that contributes to the prior art can be embodied in the form of a software product, which is stored in a storage medium (such as ROM/RAM, magnetic disk, optical disk) as described above, and includes a number of instructions for a terminal device (which can be a mobile phone, computer, server, air conditioner, or network device, etc.) to execute the methods described in each embodiment of the present application.
  • a storage medium such as ROM/RAM, magnetic disk, optical disk
  • a terminal device which can be a mobile phone, computer, server, air conditioner, or network device, etc.

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Abstract

本申请公开了一种平面透镜天线、波束相位调节方法、天线设备及介质，其中，平面透镜天线包括馈源天线和超材料平面透镜，馈源天线包括多个天线阵列，各天线阵列沿第一方向间距设置，天线阵列由阵列分布的多个天线单元构成，天线单元用于辐射无线电波；超材料平面透镜，超材料平面透镜与馈源天线相对设置，超材料平面透镜对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，以供超材料平面透镜对馈源天线辐射的无线电波在第二方向上进行波束相位的补偿赋形。

Description

平面透镜天线、波束相位调节方法、天线设备及介质
相关申请
本申请要求于2023年2月1号申请的、申请号为202310050607.X的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及天线技术领域，尤其涉及平面透镜天线、波束相位调节方法、天线设备及介质。
背景技术
随着通信业务的快速增长，第五代移动通信(5G)技术成为国内外研究和发展的热点。特定环境中5G信号的接收侦察作为一种重要的监测手段，对我国当前的信息系统能力建设具有重要意义。为了实现高数据传输速率，正在考虑毫米波频段(例如，60GHz频段)中实现5G通信系统。而在5G通信系统中，由于毫米波频段具有强方向性的特性，使得无线电波的辐射覆盖范围和辐射增益受到了限制。
目前，基站天线要实现高增益和广覆盖性能，一般都采用大规模或极大规模的相控天线阵列。该相控天线阵列要求每个天线单元后端都要连接具有移相功能的移相器件，使得相控天线阵列需要配置的移相器件数量庞大，而数量庞大的移相器件给天线设备带来了极高复杂度，导致天线设备的成本和功耗极大上升。
发明内容
本申请的主要目的在于提供一种平面透镜天线、波束相位调节方法、天线设备及介质，旨在降低天线设备的成本和功耗的同时，提升无线电波的辐射覆盖范围和辐射增益。
为实现上述目的，本申请提供一种平面透镜天线，包括：
馈源天线，所述馈源天线包括多个天线阵列，各所述天线阵列沿第一方向间距设置，所述天线阵列由阵列分布的多个天线单元构成，所述天线单元用于辐射无线电波；
超材料平面透镜，所述超材料平面透镜与所述馈源天线相对设置，所述超材料平面透镜对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，以供所述超材料平面透镜对所述馈源天线辐射的无线电波在所述第二方向上进行波束相位的补偿赋形，其中，所述第一方向与所述第二方向垂直。
为实现上述目的，本申请还提供一种波束相位调节方法，所述波束相位调节方法应用于如上述的平面透镜天线，包括：
确定无线电波到达超材料平面透镜表面的实际波束相位分布信息；
获取当前天线应用场景需求的理论波束相位分布信息，根据所述实际波束相位分布信息和所述理论波束相位分布信息，计算得到在第二方向上的波束相位补偿信息；
根据所述波束相位补偿信息，对所述超材料平面透镜在所述第二方向上的折射率进行校准，以供所述超材料平面透镜透射出的无线电波的波束相位在所述第二方向上相等。
此外，为实现上述目的，本申请还提供一种天线设备，包括如上述的平面透镜天线。
本申请还提供一种介质，所述介质为计算机可读存储介质，所述计算机可读存储介质上存储有波束相位调节程序，所述波束相位调节程序被处理器执行时，由所述处理器运行如上述的波束相位调节方法的步骤。
附图说明
图1为本申请实施例平面透镜天线进行波束扫描的场景示意图；
图2为本申请实施例平面透镜天线的结构示意图；
图3为本申请实施例馈源天线的结构示意图；
图4为本申请实施例中计算波束相位补偿信息的几何示意图；
图5为本申请一具体实施例的馈源天线的结构示意图；
图6为本申请一具体实施例的超材料平面透镜的结构示意图；
图7为本申请一实施例中馈源天线的俯视图；
图8为本申请另一实施例中馈源天线的俯视图；
图9为本申请一具体实施例的超材料单元的俯视图；
图10为本申请一具体实施例的超材料平面透镜的俯视图；
图11为天线阵列在垂直方向的阵列间距为6mm时的仿真实验数据图；
图12为天线阵列在垂直方向的阵列间距为10mm时的仿真实验数据图；
图13为天线阵列在垂直方向的阵列间距为10mm时的波束相位图；
图14为本申请实施例的波束相位调节方法的流程示意图；
图15为本申请实施例的天线设备的硬件结构示意图。
附图标号说明：
本申请目的实现、功能特点及优点将结合实施例，参照附图做进一步说明。
具体实施方式
应当理解，此处所描述的具体实施例仅仅用以解释本申请，并不用于限定本申请。
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例仅仅是本申请的一部分实施例，而不是全部的实施例。基于本申请中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本申请保护的范围。
需要说明，本申请实施例中所有方向性指示(诸如上、下、左、右、前、后……)仅用于解释在某一特定姿态(如附图所示)下各部件之间的相对位置关系、运动情况等，如果该特定姿态发生改变时，则该方向性指示也相应地随之改变。
在本申请中，除非另有明确的规定和限定，术语“连接”、“固定”等应做广义理解，例如，“固定”可以是固定连接，也可以是可拆卸连接，或成一体；可以是机械连接，也可以是电连接；可以是直接相连，也可以通过中间媒介间接相连，可以是两个元件内部的连通或两个元件的相互作用关系，除非另有明确的限定。对于本领域的普通技术人员而言，可以根据具体情况理解上述术语在本申请中的具体含义。
另外，在本申请中如涉及“第一”、“第二”等的描述仅用于描述目的，而不能理解为指示或暗示其相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括至少一个该特征。另外，各个实施例之间的技术方案可以相互结合，但是必须是以本领域普通技术人员能够实现为基础，当技术方案的结合出现相互矛盾或无法实现时应当认为这种技术方案的结合不存在，也不在本申请要求的保护范围之内。
目前，基站天线尤其是毫米波频段基站，为了抵消空间损耗，都是要求高增益；同时为减少基站数量，就要求基站天线能广覆盖。而基站天线要实现高增益和广覆盖性能，一般都采用大规模或极大规模的相控天线阵列。该相控天线阵列要求每个天线单元后端都要连接具有移相功能的移相器件，使得相控天线阵列需要配置的移相器件数量庞大，而数量庞大的移相器件给天线设备带来了极高复杂度，导致天线设备的成本和功耗极大上升。
基于此，本申请实施例提出一种平面透镜天线100，请参照图1至图3，在本实施例中，该平面透镜天线100包括：
馈源天线1，馈源天线1包括多个天线阵列11，各天线阵列11沿第一方向间距设置，天线阵列11由阵列分布的多个天线单元111构成，天线单元111用于辐射无线电波；
超材料平面透镜2，超材料平面透镜2与馈源天线1相对设置，超材料平面透镜2对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，以供超材料平面透镜2对馈源天线1辐射的无线电波在第二方向上进行波束相位的补偿赋形，其中，第一方向与第二方向垂直。超材料平面透镜2对无线电波的折射率在第一方向上一致指的是：在整体上的折射率一致。即使超材料平面透镜2的少数天线单元111在第一方向上的折射率存在差别，也仅导致少数波束的折射率不一致，其局部细微的波束不一致， 并不影响超材料平面透镜2对无线电波的折射率在第一方向上的整体一致性。因此，即使超材料平面透镜2存在少数天线单元111在第一方向上的折射率存在差别，也仍然在本申请实施例的保护范围内。
在本实施例中，第一方向与第二方向垂直。为了助于理解，列举出两示例，在一示例中，第一方向为水平方向，第二方向为垂直方向。在另一示例中，第一方向为垂直方向，第二方向为水平方向。上述示例仅助于辅助理解本申请实施例，并不构成对第一方向和第二方向的限定。
在本实施例中，超材料平面透镜2与馈源天线1相对设置，馈源天线1包括多个天线阵列11，各天线阵列11沿第一方向间距设置。也就是说，超材料平面透镜2在馈源天线1所在平面上的正投影覆盖至少两个天线阵列11，以使至少两个天线阵列11辐射的电磁波经过超材料平面透镜2进行波束扫描。在第一方向间距设置的至少两个天线阵列11正对于超材料平面透镜2，而由于超材料平面透镜2对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，从而使得至少两个天线阵列11在各自所在的空间维度以球面波a形式辐射到超材料平面透镜2，并且经超材料平面透镜2将球面波a转化为平面波A，由于多个天线阵列11在第一方向上朝向超材料平面透镜2的不同位置辐射电磁波，因此促进馈源天线1实现了在多个不同的空间维度进行波束扫描。
在一实施方式中，超材料平面透镜2与馈源天线1为相对且平行设置。
在一种可实施的方式中，超材料平面透镜2包括介质基板21，以及覆盖于介质基板21的表面上的多个超材料单元22，其中，沿介质基板21的第一方向覆盖的超材料单元22的单元响应相位一致，沿介质基板21的第二方向覆盖的超材料单元22的单元响应相位渐变。
在本实施例中，该介质基板21的材料可包含PET、COP、玻璃、聚四氟乙烯、PMMA、PC和碳化合物等材料中的一种或多种。该超材料单元22可以为具有单元面积和高度的三维物体。尽管超材料单元22具有相同的单元面积，但是超材料单元22之间的单元响应相位可以根据组成超材料单元22的电介质材料的材料和高度而变化。例如，当超材料单元22具有相同单元面积和材料的电介质材料时，单元响应相位可以根据超材料单元22之间的高度而变化。当超材料平面透镜2中包括的超材料单元22具有相同的单元面积和高度时，超材料单元22可以根据电介质材料的材料而具有不同的单元响应相位。
作为一种示例，由于单元响应相位可以根据具有相同单元面积的相同电介质材料的超材料单元22的高度而不同，因此在超材料平面透镜2中，可通过在第一方向上布置相同高度的超材料单元22和在第二方向上布置不同高度的超材料单元22，当从天线阵列11辐射的无线电波穿过第一方向时，该无线电波的相位与入射在超材料平面透镜2上的无线电波的相位相同，因此可以放大输出的无线电波的覆盖范围。而在天线阵列11辐射的无线电波穿过第二方向时，对第二方向上的无线电波进行相位补偿，使得超材料平面透镜2透射出的无线电波的波束相位在第二方向上能够保持一致，因此加强了输出的无线电波的辐射增益。
作为另一种示例，由于单元响应相位可以根据具有相同单元面积的相同高度的超材料单元22的电介质材料而不同，因此在超材料平面透镜2中，可通过在第一方向上布置具有相同单元响应相位的超材料单元22和在第二方向上布置具有不同单元响应相位的超材料单元22，当在天线阵列11辐射的无线电波穿过第二方向时，输出到超材料平面透镜2的所有无线电波具有相同的相位，因此可以增加输出无线电波的增益。而在天线阵列11辐射的无线电波穿过第二方向时，对第二方向上的无线电波进行相位补偿，使得超材料平面透镜2透射出的无线电波的波束相位在第二方向上能够保持一致，因此加强了输出的无线电波的辐射增益。
本实施例通过将超材料平面透镜2设置包括介质基板21，以及覆盖于该介质基板21的表面上的多个超材料单元22，其中，沿该介质基板21的第一方向覆盖的超材料单元22的单元响应相位一致，沿该介质基板21的第二方向覆盖的超材料单元22的单元响应相位渐变，从而使得有效地实现了超材料平面透镜2对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，进而实现了超材料平面透镜2对馈源天线1辐射的无线电波在第二方向上进行波束相位的补偿赋形。
在一种可能的实施方式中，超材料平面透镜2对无线电波的折射率沿第二方向由中轴位置向两侧逐渐减小，且中轴位置的两侧的折射率以中轴位置对称分布，其中，中轴位置为馈源天线1在超材料平面透镜2的正投影中心位置。
在本实施例中，中轴位置为馈源天线1在超材料平面透镜2的正投影中心位置。当馈源天线1发射的无线电波传输至超材料平面透镜2的过程中，由于馈源天线1发射的无线电波传输至超材料平面透镜2的中轴位置的路径短，传输至超材料平面透镜2的相对边缘位置的路径长，无线电波的相位随着传输路径的改变而改变，所以到达超材料平面透镜2的无线电波的相位由中轴位置向两侧逐渐增大，使得到达超材料平面透镜2的表面无线电波的相位相差较大，导致电磁波的发散，进而电磁波的增益小。
因此，本实施例通过设置超材料平面透镜2对无线电波的折射率沿第二方向由中轴位置向两侧逐渐减小，且中轴位置的两侧的折射率以中轴位置对称分布。由于超材料平面透镜2对电磁波的折射率越大， 超材料平面透镜2对无线电波的相位补偿量越大，超材料平面透镜2对无线电波的相位补偿为由中间向两侧依次减小。折射率大的部分可以对到达超材料平面透镜2的相对靠近中轴位置的无线电波进行相位补偿，折射率小的部分可以对到达超材料平面透镜2的相对边缘位置的无线电波进行相位补偿，无线电波经超材料平面透镜2的差异化的相位补偿之后，使得从超材料平面透镜2射出的电磁波的相位相等，进而形成指向性好的波束，实现了电磁波能量集中，提高了天线增益。
作为一种示例，超材料平面透镜2具有相对设置的第一表面23和第二表面24，以及贯穿第一表面23与第二表面24的阵列排布的多个通孔(未图示)，第一表面23与馈源天线1相对，通孔的孔径沿第二方向由中轴位置向两侧逐渐增大，和/或通孔的排布密度沿第二方向由中轴位置向两侧逐渐增大。
在本实施例中，通过改变超材料平面透镜2上通孔的孔径可以改变超材料平面透镜2的单元响应相位。该通孔的孔径沿第二方向由中轴位置向两侧逐渐增大，超材料平面透镜2对无线电波的折射率由中轴位置向两侧逐渐减小，根据超材料平面透镜2的单元响应相位与超材料平面透镜2对电磁波的折射率的对应关系，此时超材料平面透镜2的单元响应相位由中轴位置向两侧渐变。
超材料平面透镜2上通孔的孔径沿第二方向由中轴位置向两侧逐渐增大，可以使得超材料平面透镜2对电磁波的相位补偿从超材料平面透镜2的中轴位置沿第二方向向两侧逐渐减小，从而补偿天线阵列11发出的电磁波的相位，使得从超材料平面透镜2射出的电磁波的相位相等，进而形成指向性好的波束，实现了电磁波能量集中，提高了天线增益。此外，本实施方式制备的超材料平面透镜2通过调节通孔之间的间距，即可实现超材料平面透镜2对无线电波的折射率的渐变，以使折射率的可调范围较大，可灵活设置超材料平面透镜2的不同位置的折射率。
本实施例对于该通孔的形状不做限定，该通孔的形状包括但不限于圆形、方形、三角形等。
在本实施例中，该通孔的排布密度沿第二方向由中轴位置向两侧呈逐渐增大。通过改变超材料平面透镜2上的通孔的排布密度可以改变超材料平面透镜2的折射率。该通孔的排布密度沿第二方向由中轴位置向两侧逐渐增大，此时超材料平面透镜2的折射率由中轴位置向两侧逐渐减小。
超材料平面透镜2上通孔的排布密度沿第二方向由中轴位置向两侧逐渐增大，可以使得超材料平面透镜2对电磁波的相位补偿从超材料平面透镜2的中轴位置沿第二方向向两侧逐渐减小，从而补偿天线阵列11发出的电磁波的相位，使得从超材料平面透镜2射出的电磁波的相位相等，进而形成指向性好的波束，实现了电磁波能量集中，提高了天线增益。此外，本实施方式制备的超材料平面透镜2的工艺简单，只需设置同一个通孔尺寸，通过调节通孔之间的间距即可实现超材料平面透镜2对电磁波的折射率的渐变。
作为另一种示例，超材料平面透镜2包括叠层设置的介质基板21和金属功能层(未图示)，金属功能层包括多个金属谐振单元(未图示)，金属功能层中的金属谐振单元的折射率沿第二方向由中轴位置向两侧逐渐减小。
其中，超材料平面透镜2包括叠层设置的介质基板21和金属功能层，属功能层包括多个金属谐振单元，该超材料平面透镜2可以在介质基板21的第一方向上布置具有相同的折射率(即具有相同的单元响应相位)，以及沿第二方向的折射率(或者单元响应相位)关于中轴位置对称的金属谐振单元。
作为又一种示例，超材料平面透镜2包括介质基板21，以及覆盖于介质基板21表面上的多个超材料单元22，覆盖于介质基板21表面上的超材料单元22的折射率沿第二方向由中轴位置向两侧逐渐减小。
其中，超材料平面透镜2包括介质基板21，以及覆盖于介质基板21表面上的多个超材料单元22。该超材料平面透镜2可以在介质基板21的第一方向上布置具有相同折射率，以及沿第二方向的折射率关于中轴位置对称的超材料单元22。
本实施例通过设置超材料平面透镜2由多种折射率不同的材质形成折射率由中轴位置向两侧逐渐减小的透镜，可以使得超材料平面透镜2对电磁波的相位补偿从超材料平面透镜2的中轴位置沿第二方向上向两侧逐渐减小，从而补偿天线阵列11发出的电磁波的相位，使得从超材料平面透镜2射出的电磁波的相位相等，进而形成指向性好的波束，实现了电磁波能量集中，提高了天线增益。此外，本实施制备的超材料平面透镜2的工艺简单，无需打孔，且厚度一致，降低制造难度和成本。
以上的几种实施方式可以相互结合，以实现超材料平面透镜2对无线电波的折射率沿第二方向由中轴位置向两侧逐渐减小。
在本实施例中，每个天线阵列11由阵列分布的多个天线单元111构成。该天线阵列11的种类包括但不限于相控阵天线阵列、透镜天线阵列等。
超材料平面透镜2在馈源天线1所在平面上的正投影覆盖多个天线阵列11，以使多个天线阵列11辐射的电磁波信号皆能够辐射至超材料平面透镜2上。
在本实施例中，超材料平面透镜2在第二方向上对无线电波的折射率渐变。通过设置超材料平面 透镜2在第二方向上对电磁波的折射率按照梯度逐渐变化，从而使得电磁波在超材料平面透镜2对电磁波的相位补偿按照梯度逐渐变化，进而使得从超材料平面透镜2射出的电磁波的相位相等，增强电磁波辐射的定向性，以使多个天线阵列11辐射的无线电波在第二方向上进行波束相位的补偿赋形，使得无线电波(或者称为电磁波)的能量集中，提高无线电波的增益。
在一实施方式中，该天线单元111可为初级辐射器，初级辐射器的种类可为喇叭天线、波导缝隙天线或者微带天线等。
本实施例对于天线阵列11中设置的天线单元111的数量不做限定，通过设置阵列分布的多个天线单元111构成一个天线阵列11，以使每个天线阵列11中各个天线单元111辐射的波束指向范围不同。不同的天线单元111的波束指向范围可以有重叠。通过合理设计天线单元111的数量，以使不同的天线单元111的波束指向范围相叠加可以覆盖一侧的电磁波信号的收发，例如一个天线阵列11的电磁波信号的覆盖角度大于180度。
在一实施方式中，天线阵列11还包括移相单元(未图示)，移相单元与天线单元111连接，移相单元用于周期性地改变天线单元111待辐射的无线电波的波束指向，以供天线单元111辐射的无线电波在第一方向上进行周期性地波束扫描。
在本实施例中，天线阵列11还包括移相单元，该移相单元与天线单元111连接。同一个天线阵列11中的所有天线单元111可以共用一个移相单元，也可以同一个天线阵列11中的每个天线单元111均独立连接一个移相单元，本实施例对此不作具体的限定。
该移相单元可为由移相器、放大器构成的射频电路。移相单元通过调节天线阵列11中的天线单元111相位值从而使得天线阵列11在第一方向上具有波束扫描能力。
本申请实施例通过将超材料平面透镜2与馈源天线1相对设置，该超材料平面透镜2对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，其中，第一方向与第二方向垂直，以供超材料平面透镜2对馈源天线1辐射的无线电波在第二方向上进行波束相位的补偿赋形，从而使得超材料平面透镜2透射出的无线电波的波束相位在第二方向上相等，由于第二方向上无线电波的聚焦作用，使得无线电波的辐射增益进行了加强，本申请实施例还通过将平面透镜天线100设置包括馈源天线1和超材料平面透镜2，该馈源天线1包括多个天线阵列11，各天线阵列11沿第一方向间距设置，且天线阵列11由阵列分布的多个天线单元111构成，该天线单元111用于辐射无线电波，通过控制不同的天线阵列11朝向平面透镜的不同位置辐射无线电波，使得每个天线阵列11的不同聚焦指向，使得无线电波的辐射范围得到了提高，从而使得本申请实施例通过配置馈源天线1中不同天线阵列11的位置及超材料平面透镜2中的相位分布，既提高了馈源天线1增益的同时，还实现了第二方向上(如水平方向)的波束扫描能力及第一方向上(如垂直方向)的组合宽波束，从而达到了只采用较少的移相器件就能实现了高增益、广覆盖的基站天线性能，降低了天线设备的成本及功耗，进而实现在降低天线设备的成本和功耗的同时，提升了无线电波的辐射覆盖范围和辐射增益。
为了助于理解本申请实施例的技术构思或技术原理，列举一具体实施例的平面透镜天线100：
本申请实施例应用于基站天线场景，实现高增益，广覆盖。平面透镜天线100的硬件框架由馈源天线1和超材料平面透镜2组成。馈源天线1由几组沿某一方向排布的小线阵(即天线阵列11)组成。小线阵列中的天线单元111后都后接移相器(即移相单元)。
在本实施例中，天线单元111为满足频段性能即可，可为半波阵子或贴片天线，优选为贴片天线。线阵中的天线单元111数可根据扫描能力及增益设定，优选4至8个。线阵(即天线阵列11)中天线单元111的间距可根据目标扫描能力确定，优选为0.3至0.7波长。馈源天线1的线阵数目可根据覆盖要求确定，优选为3至6组。
超材料平面透镜2由基板，以及基板上覆盖金属功能层形成的众多相移单元组成。基板可为介质基板21，介质基板21的材料可包含PET、COP、玻璃、聚四氟乙烯、PMMA、PC、碳化合物等材料中的一种或多种。金属功能层可通过刻蚀、光刻、化镀或电镀等方式形成在基板上。相移单元中的金属功能层可为多层，优选2至4层。
上述具体实施例仅用于帮助理解本申请实施例的技术原理或技术构思，并不构成对本申请的限定，基于该技术构思进行更多形式的简单变换，均应在本申请的保护范围内。
参照图14，本申请提供一种波束相位调节方法，在波束相位调节方法的第一实施例中，波束相位调节方法应用于如上述的平面透镜天线，包括以下步骤：
步骤S10，确定无线电波到达超材料平面透镜表面的实际波束相位分布信息；
在一实施例中，可通过获取用户通过人机交互而输入的该实际波束相位分布信息。在另一实施例中， 可根据馈源天线的各天线阵列发射无线电波的规律，确定无线电波到达超材料平面透镜表面的实际波束相位分布信息。
步骤S20，获取当前天线应用场景需求的理论波束相位分布信息，根据所述实际波束相位分布信息和所述理论波束相位分布信息，计算得到在第二方向上的波束相位补偿信息；
步骤S30，根据所述波束相位补偿信息，对所述超材料平面透镜在所述第二方向上的折射率进行校准，以供所述超材料平面透镜透射出的无线电波的波束相位在所述第二方向上相等。
在一种可能的实施方式中，在获取当前天线应用场景需求的理论波束相位分布信息的步骤之前，所述方法还包括：
步骤S40，获取预先标定的辐射性能映射表，其中，所述辐射性能映射表包括多个波束相位分布信息，以及各波束相位分布信息映射的辐射覆盖范围值和辐射增益值；
步骤S50，获取当前天线应用场景需求的目标辐射覆盖范围值和目标辐射增益值，并从所述辐射性能映射表中查询得到所述目标辐射覆盖范围值和所述目标辐射增益值映射的波束相位分布信息；
步骤S60，将所述目标辐射覆盖范围值和所述目标辐射增益值映射的波束相位分布信息，作为当前天线应用场景需求的理论波束相位分布信息。
在本实施例中，由于馈源天线的各天线阵列与超材料平面透镜的相对位置是固定的，因此即使馈源天线的各天线阵列通过移相单元改变波束相位进行波束扫描，但该波束相位的变化是呈周期性的，也即馈源天线的各天线阵列发射无线电波的波束相位是具有规律的，因此可根据馈源天线的各天线阵列发射无线电波的规律，来确定无线电波到达超材料平面透镜表面的实际波束相位分布信息。可根据馈源天线的各天线阵列发射无线电波的规律，结合当前扫描周期的扫描进度(即在当前扫描周期中的扫描累积时刻)，来确定出无线电波到达超材料平面透镜表面的实际波束相位分布信息。容易理解的是，该实际波束相位分布信息是指馈源天线所发射的无线电波到达超材料平面透镜表面(还未透过超材料平面透镜)的不同位置对应的实际波束相位。
对于不同的天线应用场景，其所要求的辐射覆盖范围值和/或辐射增益值往往不同。而在馈源天线的各天线阵列与超材料平面透镜的相对位置是固定的情况下，为营造出每个不同的辐射覆盖范围值和/或辐射增益值的辐射性能，需求馈源天线所对应辐射的无线电波到达超材料平面透镜的表面不同位置对应的波束相位往往不相同。也即，对于不同的天线应用场景，往往需求的理论波束相位分布信息不同。该理论波束相位分布信息是指在面对所要求的辐射覆盖范围值和/或辐射增益值的辐射性能，需求馈源天线所发射的无线电波透过超材料平面透镜表面后的不同位置对应的理论波束相位。
由于本实施例获知了馈源天线所发射的无线电波到达超材料平面透镜表面(还未透过超材料平面透镜)的不同位置对应的实际波束相位(即实际波束相位分布信息)，以及需求馈源天线所发射的无线电波透过超材料平面透镜表面后的不同位置对应的理论波束相位(即理论波束相位分布信息)，因此可以根据该实际波束相位分布信息和理论波束相位分布信息，准确地计算得到在第二方向上的波束相位补偿信息，从而便于后续根据该波束相位补偿信息，对超材料平面透镜上各位置的单元响应相位进行校准(例如对馈源天线的各天线阵列与超材料平面透镜的相对位置进行调节，又例如对超材料平面透镜的介质基板表面不同位置处的超材料单元的单元响应相位进行校准，还例如对超材料平面透镜的介质基板表面不同位置处的金属谐振单元的单元响应相位进行校准，再例如对超材料平面透镜上的通孔的孔径大小或者通孔的排布密度进行校准)，从而实现对超材料平面透镜在第二方向上的折射率进行校准，进而确保超材料平面透镜透射出的无线电波的波束相位在第二方向上相等。
为了进一步辅助理解本申请实施例的技术构思或技术原理，列举一具体实施例：
在该具体实施例中，超材料平面透镜将保持馈源线阵(即馈源天线)在水平方向扫描能力，则超材料平面透镜在水平方向对无线电波的折射率基本保持一致，而在垂直方向则进行相位补偿从而可以进行波束聚焦及特定的指向(也可设计成保持垂直扫描能力，在水平方向进行相位补偿从而可以进行波束聚焦及特定的指向)。以超材料平面透镜包括两个线阵(即天线阵列)为例，计算超材料平面透镜在垂直方向上相位补偿值。如图4所示，a、b两点为线阵在垂直方向的位置，具体如下a(xa，ya，fa)、b(xb，yb，fb)。根据a、b的位置信息可以计算它们到超材料平面中i点的位置响应相位分别为：φa_i和φb_i。
在本实施例中，


其中，λ0为自由空间电磁波波长，fa、fb分别为a线阵、b线阵对应的焦距。xa、xb、xi为a、b、i在X轴上的投影坐标。ya、yb、yi为a、b、i在X轴上的投影坐标。
在本实施例中，已知a线阵在垂直面波束指向时，利用阵列天线波束综合原理则可推导出超材料平面透镜中i点的理想的响应相位则针对a波束在i点的补偿相位为b线阵在i点的响应相位为

利用阵列天线波束综合原理综合超材料平面透镜中所有点的相位值则可得出b线阵在垂直面聚焦指向，当不符合设计要求时，优化调整a线阵、b线阵位置及超材料平面透镜的响应码本(例如对超材料平面透镜在不同位置的单元响应相位进行校准)即可。
在本实施例中，如图5所示，本实施例基于平面透镜天线框架由馈源天线1和超材料平面透镜组成。馈源天线1由几组(3a、3b、3c、3d)沿第一方向排布(如水平方向)的小线阵(即天线阵列)组成。小线阵列中的天线单元111后都后接移相器(即移相单元)。
如图6所示，超材料平面透镜2由许多具有不同固定移相能力的超材料单元22组成。
本具体实施例所采用的馈源天线，其结构可如图7或如图8所示。两组馈源天线在垂直方向的间距分别为6mm及10mm，该馈源天线使用贴片天线方案，采用聚四氟乙烯介质，介电常数为2.7，损耗正切角为0.0023。如图7所示，4×4馈源天线阵列可看作为四组水平方向1×4线性阵列组合而成，各天线阵列在水平方向的间距为6mm，在垂直方向上各天线阵列的间距同样为6mm。对应地，如图8所示，各天线阵列在水平方向间距为6mm，而在垂直方向上各天线阵列的间距为10mm。
超材料平面透镜的超材料单元结构如图9所示，移相单元的尺寸为L×L，单元边长L值选取为4.6mm，略小于谐振频率空气波长的二分之一。正方形金属框边长l为4mm，构成T型金属条带的两个矩形金属条的长度l1和l2分别为1.6mm和0.4mm。所有金属条带宽度w保持一致，均为0.2mm。介质板材为Rogers 4003，相对介电常数3.55，损耗角正切0.0027，厚度0.203mm。超材料平面透镜的超材料单元可为双层的。
超材料平面透镜的阵列结构示意图如图10所示，超材料单元之间的间距p为4.6mm，超材料平面透镜的相移单元在垂直方向的臂长根据超材料透镜单元相位调整曲线进行选取，而在水平方向上保持一致。超材料平面透镜的天线阵列的焦距f为44mm时，平面透镜天线各相移单元所需提供相移及对应的l1参数如下的表1所示：
表1
在本实施例中，通过在阵列(即天线阵列)不同位置根据补偿相位的需求，设置相应的臂长长度，通过相位的调整提高超材料透镜天线的整体增益。
在本实施例中，选定26GHz频点进行仿真，分别选通线阵1、线阵2、线阵3、线阵4单独激励，图11为天线阵列在垂直方向的阵列间距为6mm时对应仿真结果，可以单组线阵增益提高约9dbi，同时垂直面覆盖范围为-16度至16度。相邻两者的天线阵列同时激励时，组合增益再提高1.7dbi。图12为天线阵列在垂直方向的阵列间距为10mm时对应仿真结果，可以单组线阵增益提高约9dbi，同时垂直面覆盖范围为-22.75度至23度。相邻两者的天线阵列同时激励时，组合增益不提升，但垂直波束宽度变大。另外，还可结合参照图13，图13为天线阵列在垂直方向的阵列间距为10mm时对应的波束相位图。在本实施例中，该平面透镜天线各天线阵列在垂直方向不同间距排布下增益及波束宽度如下的表2所示：
表2
由上述实验数据可以明确，平面透镜天线在保证水平扫描能力，以及整体天线增益与采用全5*5规模相控阵天线增益相当，降低了36％的移相器器件(即移相单元)数量。同时保持了水平面的扫描能力及垂直面组合宽波束覆盖。
本实施例所采用馈源天线的天线阵列是以传统的微带天线来验证相应的方法与布阵方式，此处使用不同馈源天线的天线阵列，如缝隙耦合天线单元组成的阵列、喇叭天线阵列等也可以实现相应的效果，通过垂直方向间距较小的两组天线阵列以进一步提升透镜天线增益，通过选通垂直方向间距较大的两组天线阵列以进一步提升透镜天线波束宽度。
以上所揭露的仅为本申请一种较佳实施例而已，当然不能以此来限定本申请的保护范围，本领域普通技术人员可以理解实现上述实施例的全部或部分流程，并依本申请实施例所做的等同变化，仍属于本申请所涵盖的范围。
也就是说，上述具体实施例仅用于帮助理解本申请实施例的技术原理或技术构思，并不构成对本申请的限定，基于该技术构思进行更多形式的简单变换，均应在本申请的保护范围内。
此外，本申请实施例还提供一种天线设备，参照图15，图15为本申请实施例提供的一种天线设备的硬件结构示意图。如图15所示，天线设备可以包括：处理器1001，例如中央处理器(Central Processing Unit，CPU)，通信总线1002、用户接口1003，网络接口1004，存储器1005。其中，通信总线1002用于实现这些组件之间的连接通信。用户接口1003可以包括显示屏(Display)、输入单元比如键盘(Keyboard)，用户接口1003还可以包括标准的有线接口、无线接口。网络接口1004可以包括标准的有线接口、无线接口(如无线保真(Wireless-Fidelity，WI-FI)接口)。存储器1005可以是高速的随机存取存储器(Random Access Memory，RAM)存储器，也可以是稳定的非易失性存储器(Non-Volatile Memory，NVM)，例如磁盘存储器。存储器1005还可以是独立于前述处理器1001的存储设备。
本领域技术人员可以理解，图15中示出的结构并不构成对天线设备的限定，可以包括比图示更多或更少的部件，或者组合某些部件，或者不同的部件布置。如图15所示，作为一种存储介质的存储器1005中可以包括操作系统、数据存储模块、网络通信模块、用户接口模块以及波束相位调节程序。
在图15所示的天线设备中，网络接口1004主要用于与其他设备进行数据通信；用户接口1003主要用于与用户进行数据交互；本实施例中的处理器1001、存储器1005可以设置在通信设备中，通信设备通过处理器1001调用存储器1005中存储的波束相位调节程序，并执行上述任一实施例提供的应用于波束相位调节方法。
本实施例提出的终端与上述实施例提出的应用于波束相位调节方法属于同一发明构思，未在本实施例中详尽描述的技术细节可参见上述任意实施例，并且本实施例具备与执行波束相位调节方法相同的有益效果。
此外，本申请还提供一种天线设备，包括如上述的平面透镜天线。
本申请还提供了一种介质，所述介质为计算机可读存储介质，所述计算机可读存储介质存储有波束相位调节程序，所述波束相位调节程序被处理器执行时，由所述处理器运行如上述的波束相位调节方法的步骤。
本申请计算机可读存储介质具体实施方式与上述波束相位调节方法各实施例基本相同，在此不再赘述。
需要说明的是，在本文中，术语“包括”、“包含”或者其任何其他变体意在涵盖非排他性的包含，从而使得包括一系列要素的过程、方法、物品或者系统不仅包括那些要素，而且还包括没有明确列出的其他要素，或者是还包括为这种过程、方法、物品或者系统所固有的要素。在没有更多限制的情况下，由语句“包括一个……”限定的要素，并不排除在包括该要素的过程、方法、物品或者系统中还存在另外的相同要素。
上述本申请实施例序号仅仅为了描述，不代表实施例的优劣。
通过以上的实施方式的描述，本领域的技术人员可以清楚地了解到上述实施例方法可借助软件加必需的通用硬件平台的方式来实现，当然也可以通过硬件，但很多情况下前者是更佳的实施方式。基于这样的理解，本申请的技术方案本质上或者说对现有技术做出贡献的部分可以以软件产品的形式体现出来，该计算机软件产品存储在如上所述的一个存储介质(如ROM/RAM、磁碟、光盘)中，包括若干指令用以使得一台终端设备(可以是手机，计算机，服务器，空调器，或者网络设备等)执行本申请各个实施例所述的方法。
以上仅为本申请的可选实施例，并非因此限制本申请的专利范围，凡是利用本申请说明书及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本申请的专利保护范围内。

Claims (11)

  1. 一种平面透镜天线，其中，所述天线包括：
    馈源天线，所述馈源天线包括多个天线阵列，各所述天线阵列沿第一方向间距设置，所述天线阵列由阵列分布的多个天线单元构成，所述天线单元用于辐射无线电波；
    超材料平面透镜，所述超材料平面透镜与所述馈源天线相对设置，所述超材料平面透镜对无线电波的折射率在第一方向上一致，以及在第二方向上渐变，以供所述超材料平面透镜对所述馈源天线辐射的无线电波在所述第二方向上进行波束相位的补偿赋形，其中，所述第一方向与所述第二方向垂直。
  2. 如权利要求1所述的平面透镜天线，其中，所述天线阵列还包括移相单元，所述移相单元与所述天线单元连接，所述移相单元用于周期性地改变所述天线单元待辐射的无线电波的波束指向，以供所述天线单元辐射的无线电波在第一方向上进行周期性地波束扫描。
  3. 如权利要求1所述的平面透镜天线，其中，所述超材料平面透镜包括介质基板，以及覆盖于所述介质基板的表面上的多个超材料单元，其中，沿所述介质基板的所述第一方向覆盖的超材料单元的单元响应相位一致，沿所述介质基板的所述第二方向覆盖的超材料单元的单元响应相位渐变。
  4. 如权利要求1所述的平面透镜天线，其中，所述超材料平面透镜对所述无线电波的折射率沿所述第二方向由中轴位置向两侧逐渐减小，且所述中轴位置的两侧的折射率以所述中轴位置对称分布，其中，所述中轴位置为所述馈源天线在所述超材料平面透镜的正投影中心位置。
  5. 如权利要求4所述的平面透镜天线，其中，所述超材料平面透镜具有相对设置的第一表面和第二表面，以及贯穿所述第一表面与所述第二表面的阵列排布的多个通孔，所述第一表面与所述馈源天线相对，所述通孔的孔径沿所述第二方向由中轴位置向两侧逐渐增大，和/或所述通孔的排布密度沿所述第二方向由中轴位置向两侧逐渐增大。
  6. 如权利要求4所述的平面透镜天线，其中，所述超材料平面透镜包括叠层设置的介质基板和金属功能层，所述金属功能层包括多个金属谐振单元，所述金属功能层中的金属谐振单元的折射率沿所述第二方向由中轴位置向两侧逐渐减小。
  7. 如权利要求4所述的平面透镜天线，其中，所述超材料平面透镜包括介质基板，以及覆盖于所述介质基板表面上的多个超材料单元，覆盖于所述介质基板表面上的超材料单元的折射率沿所述第二方向由中轴位置向两侧逐渐减小。
  8. 一种波束相位调节方法，所述波束相位调节方法应用于如权利要求1至7中任一项所述的平面透镜天线，其中，所述方法包括：
    确定无线电波到达超材料平面透镜表面的实际波束相位分布信息；
    获取当前天线应用场景需求的理论波束相位分布信息，根据所述实际波束相位分布信息和所述理论波束相位分布信息，计算得到在第二方向上的波束相位补偿信息；
    根据所述波束相位补偿信息，对所述超材料平面透镜在所述第二方向上的折射率进行校准，以供所述超材料平面透镜透射出的无线电波的波束相位在所述第二方向上相等。
  9. 如权利要求8所述的波束相位调节方法，其中，在获取当前天线应用场景需求的理论波束相位分布信息的步骤之前，所述方法还包括：
    获取预先标定的辐射性能映射表，其中，所述辐射性能映射表包括多个波束相位分布信息，以及各波束相位分布信息映射的辐射覆盖范围值和辐射增益值；
    获取当前天线应用场景需求的目标辐射覆盖范围值和目标辐射增益值，并从所述辐射性能映射表中查询得到所述目标辐射覆盖范围值和所述目标辐射增益值映射的波束相位分布信息；
    将所述目标辐射覆盖范围值和所述目标辐射增益值映射的波束相位分布信息，作为当前天线应用场景需求的理论波束相位分布信息。
  10. 一种天线设备，包括如上权利要求1至7中任一项所述的平面透镜天线。
  11. 一种介质，其中，所述介质为计算机可读存储介质，所述计算机可读存储介质上存储有波束相位调节程序，所述波束相位调节程序被处理器执行时，由所述处理器运行如权利要求8或9所述的波束相位调节方法。
PCT/CN2024/074444 2023-02-01 2024-01-29 平面透镜天线、波束相位调节方法、天线设备及介质 Ceased WO2024160168A1 (zh)

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