TWI806609B - Boost converter with high output stability - Google Patents

Abstract

A boost converter includes a bridge rectifier, a boost inductor, a power switch element, a PWM (Pulse Width Modulation) IC (Integrated Circuit), an output stage circuit, a feedback compensation circuit, and a detection and control circuit. The bridge rectifier generates a rectified voltage according to a first input voltage and a second input voltage. The boost inductor receives the rectified voltage. The output stage circuit is coupled to the boost inductor, and generates an output voltage. The feedback compensation circuit generates a feedback voltage according to the output voltage. The feedback compensation circuit includes a first linear optical coupler and a second linear optical coupler. The detection and control circuit monitors an operational temperature of the first linear optical coupler. The detection and control circuit selectively enables or disables the second linear optical coupler according to the operational temperature.

Description

Boost Converter with High Output Regulation

The present invention relates to a boost converter, in particular to a boost converter with high output stability.

Due to the large power required by notebook computers used in gaming, it often causes the temperature of the corresponding power supply to rise. However, an excessively high operating temperature will easily reduce the conversion efficiency of the internal components of the power supply, and result in insufficient overall output stability. In view of this, it is necessary to propose a new solution to overcome the difficulties faced by the previous technology.

In a preferred embodiment, the present invention provides a boost converter, comprising: a bridge rectifier, which generates a rectified potential according to a first input potential and a second input potential; a boost inductor, which receives the rectified potential ; a power switch selectively couples the boost inductor to a ground potential according to a pulse width modulation potential; a pulse width modulation integrated circuit generates the boost inductor according to a feedback potential Pulse width modulation potential; an output stage circuit, coupled to the boost inductor, and generating an output potential; a feedback compensation circuit, generating the feedback potential according to the output potential, wherein the feedback compensation The circuit includes a first linear optocoupler and a second linear optocoupler; and a detection and control circuit for monitoring an operating temperature of the first linear optocoupler, wherein the detection and control circuit is further based on The operating temperature is used to selectively enable or disable the second linear optocoupler.

In order to make the purpose, features and advantages of the present invention more comprehensible, specific embodiments of the present invention are listed below, together with the accompanying drawings, for detailed description as follows.

Certain terms are used in the specification and claims to refer to particular elements. Those skilled in the art should understand that hardware manufacturers may use different terms to refer to the same component. This description and the scope of the patent application do not use the difference in name as a way to distinguish components, but use the difference in function of components as a criterion for distinguishing. The words "comprising" and "comprising" mentioned throughout the specification and scope of patent application are open-ended terms, so they should be interpreted as "including but not limited to". The term "approximately" means that within an acceptable error range, those skilled in the art can solve the technical problem within a certain error range and achieve the basic technical effect. In addition, the term "coupled" in this specification includes any direct and indirect electrical connection means. Therefore, if it is described that a first device is coupled to a second device, it means that the first device can be directly electrically connected to the second device, or indirectly electrically connected to the second device through other devices or connection means. Two devices.

FIG. 1 is a schematic diagram of a boost converter 100 according to an embodiment of the present invention. For example, the boost converter 100 can be applied to a desktop computer, a notebook computer, or an all-in-one computer. As shown in Figure 1, the boost converter 100 includes: a bridge rectifier 110, a boost inductor LU, a power switch 120, a pulse width modulation integrated circuit (Pulse Width Modulation Integrated Circuit, PWM IC ) 130, an output stage circuit 140, a feedback compensation circuit 150, and a detection and control circuit 160. It should be noted that although not shown in FIG. 1 , the boost converter 100 may further include other components, such as a voltage regulator and/or a negative feedback circuit.

The bridge rectifier 110 can generate a rectified potential VR according to a first input potential VIN1 and a second input potential VIN2, wherein one of any frequency and any amplitude can be formed between the first input potential VIN1 and the second input potential VIN2 AC voltage. For example, the frequency of the AC voltage can be about 50Hz or 60Hz, and the root mean square value of the AC voltage can be about 90V to 264V, but it is not limited thereto. The boost inductor LU can receive the rectified potential VR. The power switch 120 can selectively couple the boost inductor LU to a ground potential VSS (eg, 0V) according to a pulse width modulation potential VM. For example, if the pulse width modulation potential VM is a high logic level (ie, logic “1”), the power switch 120 can couple the boost inductor LU to the ground potential VSS (ie, power switch 120 can be approximated as a short-circuit path); conversely, if the pulse width modulation potential VM is a low logic level (ie, logic "0"), the power switch 120 will not switch the boost inductor LU is coupled to the ground potential VSS (ie, the power switch 120 can be approximated as an open path). The PWM IC 130 can generate the PWM potential VM according to a feedback potential VF. The output stage circuit 140 is coupled to the boost inductor LU and can generate an output potential VOUT. For example, the output potential VOUT can be a DC potential, and its potential level can be about 400V, but it is not limited thereto. The feedback compensation circuit 150 can generate a feedback potential VF according to the output potential VOUT, wherein the feedback compensation circuit 150 includes a first linear optocoupler 152 and a second linear optocoupler 154 . The detection and control circuit 160 can monitor the operating temperature of the first linear optocoupler 152 . Then, the detection and control circuit 160 can selectively enable or disable the second linear optocoupler 154 according to the operating temperature. In some embodiments, if the operating temperature of the first linear optocoupler 152 is too high (for example: higher than or equal to a critical temperature), the detection and control circuit 160 will enable the second linear optocoupler 154 Conversely, if the operating temperature of the first linear optocoupler 152 is normal (for example: lower than the aforementioned critical temperature), the detection and control circuit 160 will disable the second linear optocoupler 154 . Under this design, even if the conversion efficiency of the first linear optocoupler 152 declines due to its high operating temperature, the second linear optocoupler 154 can still be used to compensate part of the first linear optocoupler 152 function, so that the overall output stability of the boost converter 100 can be maintained.

The following embodiments will introduce the detailed structure and operation of the boost converter 100 . It must be understood that these drawings and descriptions are examples only and are not intended to limit the scope of the present invention.

FIG. 2 shows a circuit diagram of a boost converter 200 according to an embodiment of the present invention. In the embodiment of FIG. 2, the boost converter 200 has a first input node NIN1, a second input node NIN2, and an output node NOUT, and includes a bridge rectifier 210, a boost inductor LU, a A power switch 220 , a PWM integrated circuit 230 , an output stage circuit 240 , a feedback compensation circuit 250 , and a detection and control circuit 260 . The first input node NIN1 and the second input node NIN2 of the boost converter 200 can be used to receive a first input potential VIN1 and a second input potential VIN2 . The output node NOUT of the boost converter 200 can be used to output an output potential VOUT.

The bridge rectifier 210 includes a first diode D1, a second diode D2, a third diode D3, and a fourth diode D4. The first diode D1 has an anode and a cathode, wherein the anode of the first diode D1 is coupled to the first input node NIN1, and the cathode of the first diode D1 is coupled to a first node N1 To output a rectified potential VR. The second diode D2 has an anode and a cathode, wherein the anode of the second diode D2 is coupled to the second input node NIN2 , and the cathode of the second diode D2 is coupled to the first node N1 . The third diode D3 has an anode and a cathode, wherein the anode of the third diode D3 is coupled to a ground potential VSS, and the cathode of the third diode D3 is coupled to the first input node NIN1 . The fourth diode D4 has an anode and a cathode, wherein the anode of the fourth diode D4 is coupled to the ground potential VSS, and the cathode of the fourth diode D4 is coupled to the second input node NIN2.

The boost inductor LU has a first end and a second end, wherein the first end of the boost inductor LU is coupled to the first node N1 to receive the rectified potential VR, and the second end of the boost inductor LU is coupled to a second node N2.

The power switch 220 includes a first transistor M1. For example, the first transistor M1 can be an N-type metal oxide semiconductor field effect transistor. The first transistor M1 has a control end (for example: a gate), a first end (for example: a source), and a second end (for example: a drain), wherein the control of the first transistor M1 The terminal is used to receive a pulse width modulation potential VM, the first terminal of the first transistor M1 is coupled to the ground potential VSS, and the second terminal of the first transistor M1 is coupled to the second node N2 . For example, if the pulse width modulation potential VM is at a high logic level, the first transistor M1 will be turned on; otherwise, if the pulse width modulation potential VM is at a low logic level, then the first transistor M1 will be closed.

The PWM IC 230 includes at least a comparator 235 . For example, comparator 235 can be implemented with an operational amplifier. The comparator 235 has a positive input terminal, a negative input terminal, and an output terminal, wherein the positive input terminal of the comparator 235 is used to receive a feedback potential VF, and the negative input terminal of the comparator 235 is used to receive a triangular wave The potential VT, and the output terminal of the comparator 235 is used to output the pulse width modulation potential VM. For example, if the feedback potential VF is higher than or equal to the triangular wave potential VT, the pulse width modulation potential VM will be at a high logic level; otherwise, if the feedback potential VF is lower than the triangular wave potential VT, the pulse width modulation The variable voltage VM will be at a low logic level. In addition, the PWM IC 230 can further provide a supply potential VDD at a supply node NS. In some embodiments, the PWM IC 230 may further include a triangle wave generator and a power supply circuit (not shown).

The output stage circuit 240 includes a fifth diode D5 and a first capacitor C1. The fifth diode D5 has an anode and a cathode, wherein the anode of the fifth diode D5 is coupled to the second node N2, and the cathode of the fifth diode D5 is coupled to the output node NOUT. The first capacitor C1 has a first terminal and a second terminal, wherein the first terminal of the first capacitor C1 is coupled to the output node NOUT, and the second terminal of the first capacitor C1 is coupled to a common node NCM. The common node NCM can be regarded as another ground potential, which can be the same as or different from the aforementioned ground potential VSS.

The feedback compensation circuit 250 includes a first linear optocoupler 252, a second linear optocoupler 254, a voltage regulator 256, a first resistor R1, a second resistor R2, and a third resistor R3, a fourth resistor R4, a fifth resistor R5, a sixth resistor R6, and a second capacitor C2.

In some embodiments, the first linear optocoupler 252 is implemented by a PC817 electronics. The first linear optical coupler 252 includes a first light-emitting diode DL1 and a first bicarrier junction transistor Q1 (eg, NPN type). The first light emitting diode DL1 has an anode and a cathode, wherein the anode of the first light emitting diode DL1 is coupled to a third node N3, and the cathode of the first light emitting diode DL1 is coupled to a first node N3. Four nodes N4. The first bicarrier junction transistor Q1 has a collector and an emitter, wherein the collector of the first bicarrier junction transistor Q1 is coupled to a fifth node N5, and the first bicarrier junction transistor Q1 is coupled to a fifth node N5. The emitter of the surface transistor Q1 is coupled to a feedback node NF to output the feedback potential VF to the PWM IC 230 .

In some embodiments, the second linear optocoupler 254 is implemented by another PC817 electronics. The second linear optical coupler 254 includes a second light-emitting diode DL2 and a second bicarrier junction transistor Q2 (eg, NPN type). The second light emitting diode DL2 has an anode and a cathode, wherein the anode of the second light emitting diode DL2 is coupled to a sixth node N6, and the cathode of the second light emitting diode DL2 is coupled to the common node NCM. The second bicarrier junction transistor Q2 has a collector and an emitter, wherein the collector of the second bicarrier junction transistor Q2 is coupled to the fifth node N5, and the second bicarrier junction transistor Q2 The emitter of the transistor Q2 is coupled to the feedback node NF. For example, the first linear optocoupler 252 can be regarded as a main linear optocoupler, and the second linear optocoupler 254 can be regarded as an auxiliary linear optocoupler. However, the present invention is not limited thereto. In some other embodiments, the feedback compensation circuit 250 may further include more linear optocouplers, which may be respectively coupled to the fifth node N5 and the feedback node NF.

The first resistor R1 has a first end and a second end, wherein the first end of the first resistor R1 is coupled to the output node NOUT to receive the output potential VOUT, and the second end of the first resistor R1 is coupled to the third node N3. The second resistor R2 has a first end and a second end, wherein the first end of the second resistor R2 is coupled to the output node NOUT, and the second end of the second resistor R2 is coupled to a first end. Seven nodes N7. The third resistor R3 has a first end and a second end, wherein the first end of the third resistor R3 is coupled to the output node NOUT, and the second end of the third resistor R3 is coupled to a first end. Eight nodes N8. The fourth resistor R4 has a first end and a second end, wherein the first end of the fourth resistor R4 is coupled to the eighth node N8, and the second end of the fourth resistor R4 is coupled to the common Node NCM.

The fifth resistor R5 has a first end and a second end, wherein the first end of the fifth resistor R5 is coupled to the supply node NS to receive the supply potential VDD, and the second end of the fifth resistor R5 is coupled to the fifth node N5. In some embodiments, the supply potential VDD of the PWM IC 230 can be used to provide power to the first linear optocoupler 252 and the second linear optocoupler 254 . The sixth resistor R6 has a first end and a second end, wherein the first end of the sixth resistor R6 is coupled to the feedback node NF, and the second end of the sixth resistor R6 is coupled to the ground Potential VSS. In addition, a feedback current IF can flow through the sixth resistor R6. According to Ohm's law, the current value of the feedback current IF is proportional to the potential level of the aforementioned feedback potential VF. The second capacitor C2 has a first end and a second end, wherein the first end of the second capacitor C2 is coupled to the fourth node N4, and the second end of the second capacitor C2 is coupled to the eighth node N8 .

In some embodiments, voltage regulator 256 is implemented by a TL431 electronic component. The voltage regulator 256 has an anode, a cathode, and a reference terminal, wherein the anode of the voltage regulator 256 is coupled to the common node NCM, the cathode of the voltage regulator 256 is coupled to the fourth node N4, and the voltage regulator 256 is coupled to the fourth node N4. The reference terminal of 256 is coupled to the eighth node N8.

The detection and control circuit 260 includes a negative temperature coefficient (Negative Temperature Coefficient, NTC) resistor RN, a voltage dividing resistor RD, and a second transistor M2. In some embodiments, a negative temperature coefficient resistor RN is disposed adjacent to the first linear optocoupler 252 to monitor an operating temperature of the first linear optocoupler 252 . For example, the distance between the negative temperature coefficient resistor RN and the first linear optical coupler 252 may be less than or equal to 3 mm. In detail, the negative temperature coefficient resistor RN has a first terminal and a second terminal, wherein the first terminal of the negative temperature coefficient resistor RN is coupled to the output node NOUT to receive the output potential VOUT, and the negative temperature coefficient resistor RN The second end of the device RN is coupled to a control node NC to output a control potential VC. The voltage dividing resistor RD has a first end and a second end, wherein the first end of the voltage dividing resistor RD is coupled to the control node NC, and the second end of the voltage dividing resistor RD is coupled to the common node NCM. The second transistor M2 can be another N-type metal oxide semiconductor field effect transistor. The second transistor M2 has a control end (for example: a gate), a first end (for example: a source), and a second end (for example: a drain), wherein the control of the second transistor M2 The terminal is coupled to the control node NC to receive the control potential VC, the first terminal of the second transistor M2 is coupled to the sixth node N6, and the second terminal of the second transistor M2 is coupled to the seventh node N7 . In some embodiments, if it is assumed that the potential level of the common node NCM is 0V, the control potential VC can be calculated according to the following equation (1):

………………………………(1) 其中「VC」代表控制電位VC之電位位準，「VOUT」代表輸出電位VOUT之電位位準，「RN」代表負溫度係數電阻器RN之電阻值，而「RD」代表分壓電阻器RD之電阻值。

……………………………(1) “VC” represents the potential level of the control potential VC, “VOUT” represents the potential level of the output potential VOUT, and “RN” represents the negative temperature coefficient resistor RN The resistance value, and "RD" represents the resistance value of the voltage divider resistor RD.

FIG. 3 is a graph showing the operating characteristics of the negative temperature coefficient resistor RN according to an embodiment of the present invention, wherein the horizontal axis represents the operating temperature of the first linear optocoupler 252, and the vertical axis represents the negative temperature coefficient resistor. The resistance value of RN. According to the measurement results in FIG. 3, if the operating temperature of the first linear optocoupler 252 drops, the resistance value of the negative temperature coefficient resistor RN will increase; otherwise, if the first linear optocoupler 252 As the operating temperature rises, the resistance value of the negative temperature coefficient resistor RN will decrease. It must be understood that the operating characteristic diagram in Figure 3 is only an example, and the actual characteristics of the negative temperature coefficient resistor RN can still be adjusted according to different needs.

In some embodiments, the operation principle of the boost converter 200 can be as follows. Roughly speaking, after the boost converter 200 starts up, the first linear optocoupler 252 of the feedback compensation circuit 250 will always be enabled, but the second linear optocoupler 254 of the feedback compensation circuit 250 is based on The operating temperature of the first linear optocoupler 252 is selectively enabled or disabled. Initially, because the operating temperature of the first linear optocoupler 252 is relatively low and the resistance of the negative temperature coefficient resistor RN is relatively large, the control potential VC will not be sufficient to turn on the second transistor M2. The second transistor M2 is turned off, and the second linear optocoupler 254 is disabled. Then, the operating temperature of the first linear optocoupler 252 may gradually increase, which may cause the feedback current IF passing through the sixth resistor R6 to gradually decrease. When the operating temperature of the first linear optocoupler 252 reaches a critical temperature (for example: 140 degrees Celsius), according to the equation (1), the control potential VC can be increased due to the decrease of the resistance value of the negative temperature coefficient resistor RN, which It will be sufficient to turn on the second transistor M2. At this time, the second linear optocoupler 254 is enabled and the feedback current IF is increased, which can compensate the lower conversion efficiency of the first linear optocoupler 252 at high temperature.

FIG. 4 shows a potential waveform diagram of the boost converter 200 according to an embodiment of the present invention, wherein the horizontal axis represents time, and the vertical axis represents the potential levels of the triangular wave potential VT and the pulse width modulation potential VM . When the second linear optocoupler 254 is disabled, the corresponding feedback potential VF has a lower potential level LVF1, and the duty cycle of the pulse width modulation potential VM is relatively small (such as a first curve shown in CC1). On the contrary, when the second linear optocoupler 254 is enabled, the corresponding feedback potential VF has a higher potential level LVF2, and the duty cycle of the pulse width modulation potential VM is relatively larger (such as a first shown in the second curve CC2). According to the measurement results in FIG. 4, the addition of the second linear optocoupler 254 helps to increase the duty cycle of the pulse width modulation potential VM, thereby improving the overall output stability of the boost converter 200 (especially In case boost converter 200 operates at higher temperature).

The present invention proposes a novel boost converter that can dynamically adjust its feedback potential in response to different operating temperatures. According to the actual measurement results, the boost converter with the above design can effectively improve the overall output stability, so it is very suitable for various devices.

It should be noted that the potential, current, resistance value, inductance value, capacitance value, and other component parameters mentioned above are not limiting conditions of the present invention. Designers can adjust these settings according to different needs. The boost converter of the present invention is not limited to the states shown in FIGS. 1-4. The present invention may only include any one or multiple features of any one or multiple embodiments of Figures 1-4. In other words, not all the illustrated features must be implemented in the boost converter of the present invention at the same time. Although the embodiment of the present invention uses a metal oxide half field effect transistor as an example, the present invention is not limited thereto, and those skilled in the art can use other types of transistors, such as junction field effect transistors, or fin Type field effect transistors, etc., and will not affect the effect of the present invention.

The ordinal numbers in this specification and the scope of the patent application, such as "first", "second", "third", etc., have no sequential relationship with each other, and are only used to mark and distinguish between two The different elements of the name.

Although the present invention is disclosed above with preferred embodiments, it is not intended to limit the scope of the present invention. Anyone skilled in this art can make some changes and modifications without departing from the spirit and scope of the present invention. Therefore The scope of protection of the present invention should be defined by the scope of the appended patent application.

100,200: Boost Converter 110,210: bridge rectifier 120,220: Power Switcher 130,230: Pulse Width Modulation Integrated Circuit 140,240: output stage circuit 150,250: feedback compensation circuit 152,252: The first linear optocoupler 154,254: second linear optocoupler 160,260: detection and control circuit 235: Comparator 256:Voltage regulator C1: first capacitor C2: second capacitor CC1: First Curve CC2: Second Curve D1: the first diode D2: second diode D3: The third diode D4: The fourth diode D5: fifth diode DL1: the first light-emitting diode DL2: Second light-emitting diode IF: feedback current LU: boost inductor LVF1: The lower potential level of the feedback potential LVF2: The higher potential level of the feedback potential M1: the first transistor M2: second transistor N1: the first node N2: second node N3: the third node N4: the fourth node N5: fifth node N6: sixth node N7: seventh node N8: Eighth node NC: Control Node NCM: common node NF: Feedback Node NIN1: the first input node NIN2: Second input node NOUT: output node NS: supply node Q1: The first bicarrier junction transistor Q2: Second bicarrier junction transistor R1: first resistor R2: second resistor R3: Third resistor R4: Fourth resistor R5: fifth resistor R6: sixth resistor RD: Divider resistor RN: negative temperature coefficient resistor VC: control potential VDD: supply potential VF: feedback potential VIN1: the first input potential VIN2: the first input potential VM: pulse width modulation potential VOUT: output potential VR: rectification potential VSS: ground potential VT: triangle wave potential

FIG. 1 is a schematic diagram showing a boost converter according to an embodiment of the present invention. FIG. 2 shows a circuit diagram of a boost converter according to an embodiment of the present invention. FIG. 3 is a graph showing the operating characteristics of a negative temperature coefficient resistor according to an embodiment of the present invention. FIG. 4 is a potential waveform diagram of a boost converter according to an embodiment of the present invention.

100: Boost converter

110: Bridge rectifier

120: Power switcher

130: Pulse Width Modulation Integrated Circuit

140: Output stage circuit

150: Feedback compensation circuit

152: The first linear optocoupler

154: Second linear optocoupler

160: Detection and control circuit

LU: boost inductor

VIN1: the first input potential

VIN2: the first input potential

VF: feedback potential

VM: pulse width modulation potential

VOUT: output potential

VR: rectification potential

VSS: ground potential

Claims (10)

A boost converter, comprising: a bridge rectifier, which generates a rectified potential according to a first input potential and a second input potential; a boost inductor, which receives the rectified potential; a power switch, which generates a rectified potential according to a pulse wave a width modulation potential to selectively couple the boost inductor to a ground potential; a pulse width modulation integrated circuit to generate the pulse width modulation potential according to a feedback potential; an output a stage circuit, coupled to the boost inductor, and generating an output potential; a feedback compensation circuit, generating the feedback potential according to the output potential, wherein the feedback compensation circuit includes a first linear optocoupler and a second linear optocoupler; and a detection and control circuit for monitoring an operating temperature of the first linear optocoupler, wherein the detection and control circuit selectively enables or disabling the second linear optocoupler; wherein the detection and control circuit includes a negative temperature coefficient resistor, and the distance between the negative temperature coefficient resistor and the first linear optocoupler is less than or equal to 3mm . The boost converter of claim 1, wherein the bridge rectifier includes: a first diode having an anode and a cathode, wherein the anode of the first diode is coupled to a first input node to receive the first input potential, and the cathode of the first diode is coupled to a first node to output the rectified potential; a second diode has an anode and a cathode, wherein the second the anode of the diode is coupled to a second input node to receive the second input potential, and the cathode of the second diode is coupled to the first node; a third diode having an anode and a cathode, wherein the anode of the third diode is coupled to the ground potential and the cathode of the third diode is coupled to the first input node; and a fourth diode having an anode and a cathode, wherein the anode of the fourth diode is coupled to the ground potential and the cathode of the fourth diode is coupled to the second input node; Wherein the boost inductor has a first end and a second end, the first end of the boost inductor is coupled to the first node to receive the rectified potential, and the second end of the boost inductor The terminal is coupled to a second node. As the boost converter of claim 2, wherein the power switch includes: A first transistor has a control terminal, a first terminal, and a second terminal, wherein the control terminal of the first transistor is used to receive the pulse width modulation potential, and the first transistor The first terminal of the first transistor is coupled to the ground potential, and the second terminal of the first transistor is coupled to the second node. As the boost converter of claim 2, wherein the pulse width modulation integrated circuit includes: A comparator has a positive input terminal, a negative input terminal, and an output terminal, wherein the positive input terminal of the comparator is used to receive the feedback potential, and the negative input terminal of the comparator is used to receive a triangular wave potential, and the output terminal of the comparator is used to output the pulse width modulation potential; Wherein the PWM integrated circuit further provides a supply potential at a supply node. As the boost converter of claim 4, wherein the output stage circuit includes: a fifth diode having an anode and a cathode, wherein the anode of the fifth diode is coupled to the second node and the cathode of the fifth diode is coupled to an output node to output the output potential; and A first capacitor having a first terminal and a second terminal, wherein the first terminal of the first capacitor is coupled to the output node, and the second terminal of the first capacitor is coupled to a common node. The boost converter of claim 5, wherein the first linear optocoupler includes a first light emitting diode and a first bicarrier junction transistor, the first light emitting diode has an anode and A cathode, the anode of the first light emitting diode is coupled to a third node, the cathode of the first light emitting diode is coupled to a fourth node, the first bicarrier junction electrode The crystal has a collector and an emitter, the collector of the first BJT is coupled to a fifth node, and the emitter of the first BJT is coupled to Connect to a feedback node to output the feedback potential. The boost converter of claim 6, wherein the second linear optocoupler includes a second light emitting diode and a second bicarrier junction transistor, the second light emitting diode has an anode and an cathode, the anode of the second light emitting diode is coupled to a sixth node, the cathode of the second light emitting diode is coupled to the common node, the second bicarrier junction transistor has a collector and an emitter, the collector of the second BJT is coupled to the fifth node, and the emitter of the second BJT is coupled to The feedback node. Such as the boost converter of claim 7, wherein the feedback compensation circuit further includes: a first resistor having a first end and a second end, wherein the first end of the first resistor is coupled to the output node to receive the output potential, and the first end of the first resistor two terminals are coupled to the third node; a second resistor having a first end and a second end, wherein the first end of the second resistor is coupled to the output node, and the second end of the second resistor is coupled to to a seventh node; a third resistor having a first end and a second end, wherein the first end of the third resistor is coupled to the output node, and the second end of the third resistor is coupled to to an eighth node; and A fourth resistor has a first end and a second end, wherein the first end of the fourth resistor is coupled to the eighth node, and the second end of the fourth resistor is coupled to connected to the common node. Such as the boost converter of claim 8, wherein the feedback compensation circuit further includes: a fifth resistor having a first end and a second end, wherein the first end of the fifth resistor is coupled to the supply node to receive the supply potential, and the first end of the fifth resistor Two terminals are coupled to the fifth node; a sixth resistor has a first terminal and a second terminal, wherein the first terminal of the sixth resistor is coupled to the feedback node, and the The second end of the sixth resistor is coupled to the ground potential; a second capacitor has a first end and a second end, wherein the first end of the second capacitor is coupled to the fourth node, and the second terminal of the second capacitor is coupled to the eighth node; and a voltage regulator has an anode, a cathode, and a reference terminal, wherein the anode of the voltage regulator is coupled to To the common node, the cathode of the voltage regulator is coupled to the fourth node, and the reference terminal of the voltage regulator is coupled to the eighth node. The boost converter of claim 8, wherein the detection and control circuit includes: wherein the negative temperature coefficient resistor has a first end and a second end, and the first end of the negative temperature coefficient resistor is coupled to to the output node to receive the output potential, and the second end of the negative temperature coefficient resistor is coupled to a control node to output a control potential; a voltage dividing resistor has a first end and a second end, wherein the first end of the voltage dividing resistor is coupled to the control node, and the second end of the voltage dividing resistor is coupled to the common node; and a second transistor having a control Terminal, a first terminal, and a second terminal, wherein the control terminal of the second transistor is coupled to the control node to receive the control potential, the first terminal of the second transistor is coupled to The sixth node, and the second terminal of the second transistor is coupled to the seventh node.

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