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TWI721557B - High voltage gain dc/dc converter - Google Patents

High voltage gain dc/dc converter Download PDF

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Publication number
TWI721557B
TWI721557B TW108132623A TW108132623A TWI721557B TW I721557 B TWI721557 B TW I721557B TW 108132623 A TW108132623 A TW 108132623A TW 108132623 A TW108132623 A TW 108132623A TW I721557 B TWI721557 B TW I721557B
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Taiwan
Prior art keywords
diode
switch
voltage
converter
present
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TW108132623A
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Chinese (zh)
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TW202112044A (en
Inventor
楊松霈
陳信助
謝承道
林資祐
林加耀
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崑山科技大學
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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Dc-Dc Converters (AREA)

Abstract

The invention provides high voltage gain DC/DC converter, which overcomes usage constraint of conduction ratio and is able to output with high voltage. The invention is composed of high voltage conversion ratio for it does not operate within extreme wide responsibility of conduction ratio, the power switch comprises low voltage stress that is lower than output voltage so lower rated insulation voltage MOSFET with lesser conducting resistance can be used for reducing conduction loss and promote overall efficiency. Further, the invention solves the problem of reverse recovery of diodes and reduces interference directs to actuating circuit.

Description

高電壓增益直流轉換器High voltage gain DC converter

本發明係有關於一種高電壓增益直流轉換器，尤其是指一種不僅無導通比的使用限制，可得高電壓輸出，且由於不操作在極端寬大的導通責任比下，亦能具有高電壓轉換比，並因功率開關具有低於輸出電壓的低電壓應力，可使用導通電阻較小的低額定耐壓MOSFET，可降低導通損失，提升整體效率，同時能解決二極體的逆向恢復問題，從而降低雜訊對電路動作上的影響，而在其整體施行使用上更增實用功效特性者。The present invention relates to a high-voltage-gain DC converter, in particular to a high-voltage output that not only has no on-ratio usage restrictions, but also has high-voltage conversion due to not operating at an extremely wide on-duty ratio. Because the power switch has a low voltage stress lower than the output voltage, a low-rated withstand voltage MOSFET with a small on-resistance can be used, which can reduce the conduction loss and improve the overall efficiency. At the same time, it can solve the problem of reverse recovery of the diode. Reduce the influence of noise on the circuit operation, and increase the practical performance characteristics in its overall implementation.

按，對於直流升壓目的而言，理論上，操作在極高導通比的傳統升壓型〔boost〕轉換器能夠得到高電壓增益，但是實務上受到寄生元件的影響，電壓轉換比受限在約5倍以下，因此當電壓增益高達10倍左右的實務需求時，研發嶄新的高升壓轉換器拓樸是必要的。因此，於近幾年來，高升壓DC-DC轉換器是電力電子工程領域中常見的研究主題之一。For the purpose of DC boost, theoretically, a traditional boost converter operating at a very high conduction ratio can obtain high voltage gain, but in practice, it is affected by parasitic components and the voltage conversion ratio is limited. It is about 5 times or less, so when the voltage gain is as high as about 10 times of practical requirements, it is necessary to develop a new high-boost converter topology. Therefore, in recent years, high-boost DC-DC converters have been one of the common research topics in the field of power electronics engineering.

實務上操作在極大導通比的傳統升壓型轉換器其電壓增益是有所限制，而且轉換效率不佳。另一方面，操作在極大導通比的升壓型轉換器衍生了以下問題：容易產生很大的輸入電流漣波，使得太陽能電池模組輸出端的電解電容數量必須增加，減少燃料電池的使用壽命；另一方面，輸出二極體的反向恢復問題造成嚴重的反向恢復損失及EMI雜訊問題。In practice, the voltage gain of a traditional boost converter operating at a very large conduction ratio is limited, and the conversion efficiency is not good. On the other hand, a boost converter operating at a large conduction ratio has the following problems: it is prone to produce large input current ripples, so that the number of electrolytic capacitors at the output of the solar cell module must be increased, reducing the service life of the fuel cell; On the other hand, the reverse recovery problem of the output diode causes serious reverse recovery losses and EMI noise problems.

另，在轉換效率考量方面，由於環保意識高漲，節能減碳是各國的重要政策，轉換器的效率要求日益嚴苛，功率電子開關造成的功率損失必須善加考量。典型交錯式升壓型轉換器之功率開關與輸出二極體之電壓應力均為高壓的輸出電壓，由於高耐壓的MOSFET，一般都具有高導通電阻RDS(ON)的特性，導致較高的導通損失。In addition, in terms of conversion efficiency considerations, due to the high awareness of environmental protection, energy saving and carbon reduction are important policies of various countries. The efficiency requirements of converters are becoming increasingly stringent, and the power loss caused by power electronic switches must be carefully considered. The voltage stress of the power switch and the output diode of a typical interleaved boost converter are both high-voltage output voltages. Because high-voltage MOSFETs generally have the characteristics of high on-resistance RDS(ON), resulting in higher Conduction loss.

緣是，發明人有鑑於此，秉持多年該相關行業之豐富設計開發及實際製作經驗，針對現有之結構及缺失再予以研究改良，提供一種高電壓增益直流轉換器，以期達到更佳實用價值性之目的者。The reason is that, in view of this, the inventor upholds many years of rich experience in design, development and actual production in the related industry, and researches and improves the existing structure and deficiencies to provide a high-voltage-gain DC converter in order to achieve better practical value. The purpose of the person.

本發明之主要目的在於提供一種高電壓增益直流轉換器，主要係不僅無導通比的使用限制，可得高電壓輸出，且由於不操作在極端寬大的導通責任比下，亦能具有高電壓轉換比，並因功率開關具有低於輸出電壓的低電壓應力，可使用導通電阻較小的低額定耐壓MOSFET，可降低導通損失，提升整體效率，同時能解決二極體的逆向恢復問題，從而降低雜訊對電路動作上的影響，而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide a high voltage gain DC converter, which not only has no use restriction on the conduction ratio, but also obtains a high voltage output, and because it does not operate at an extremely wide conduction duty ratio, it can also have a high voltage conversion. Because the power switch has a low voltage stress lower than the output voltage, a low-rated withstand voltage MOSFET with a small on-resistance can be used, which can reduce the conduction loss and improve the overall efficiency. At the same time, it can solve the problem of reverse recovery of the diode. Reduce the influence of noise on the circuit operation, and increase the practical performance characteristics in its overall implementation.

為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：In order to make the technical content, the purpose of the invention and the effects achieved by the present invention more complete and clear, the following detailed descriptions are given, and please refer to the disclosed drawings and figure numbers together:

首先，請參閱第一圖本發明之電路圖所示，本發明之轉換器（１）主要係於輸入電壓

Figure 02_image025
之正極分別連接電感
Figure 02_image027
之第一端與電容
Figure 02_image029
之負極，而該輸入電壓
Figure 02_image025
之負極則分別連接有開關
Figure 02_image031
之第二端及電容
Figure 02_image033
之正極，該電感
Figure 02_image027
之第二端分別連接有二極體
Figure 02_image035
之正極及二極體
Figure 02_image037
之正極，該電容
Figure 02_image029
之正極分別連接有電容
Figure 02_image039
之負極、該二極體
Figure 02_image041
之負極及耦合電感一次側
Figure 02_image042
之第一端，該電容
Figure 02_image039
之正極分別連接有開關
Figure 02_image044
之第一端及電容
Figure 02_image046
之負極，該開關
Figure 02_image048
之第二端分別連接有該耦合電感一次側
Figure 02_image042
之第二端、該二極體
Figure 02_image037
之負極、該開關
Figure 02_image031
之第一端及耦合電感二次側
Figure 02_image049
之第一端，該電容
Figure 02_image046
之正極分別連接有二極體
Figure 02_image051
之負極及二極體
Figure 02_image053
之正極，該二極體
Figure 02_image054
之正極分別連接有該耦合電感二次側
Figure 02_image049
之第二端、二極體
Figure 02_image055
之負極、電容
Figure 02_image057
之負極及電容
Figure 02_image059
之正極，該二極體
Figure 02_image055
之正極分別連接有該電容
Figure 02_image033
之負極及二極體
Figure 02_image013
之負極，該二極體
Figure 02_image053
之負極分別連接有該電容
Figure 02_image057
之正極及輸出阻抗
Figure 02_image061
之正極，該二極體
Figure 02_image013
之正極分別連接有電容
Figure 02_image059
之負極及該輸出阻抗
Figure 02_image061
之負極。 First of all, please refer to the first diagram of the circuit diagram of the present invention. The converter (1) of the present invention is mainly based on the input voltage
Figure 02_image025
The positive pole is connected to the inductor
Figure 02_image027
The first terminal and the capacitor
Figure 02_image029
The negative pole, and the input voltage
Figure 02_image025
The negative pole is connected to the switch respectively
Figure 02_image031
The second terminal and capacitor
Figure 02_image033
The positive pole, the inductor
Figure 02_image027
Diodes are connected to the second ends
Figure 02_image035
The anode and diode
Figure 02_image037
The positive pole, the capacitor
Figure 02_image029
The positive poles are respectively connected with capacitors
Figure 02_image039
The negative pole, the diode
Figure 02_image041
The negative pole and the primary side of the coupled inductor
Figure 02_image042
The first terminal, the capacitor
Figure 02_image039
The positive pole is connected to the switch respectively
Figure 02_image044
The first terminal and capacitor
Figure 02_image046
The negative pole, the switch
Figure 02_image048
The second end is respectively connected to the primary side of the coupled inductor
Figure 02_image042
The second end, the diode
Figure 02_image037
The negative pole, the switch
Figure 02_image031
The first terminal and the secondary side of the coupled inductor
Figure 02_image049
The first terminal, the capacitor
Figure 02_image046
The positive poles are connected to the diodes
Figure 02_image051
The negative electrode and diode
Figure 02_image053
The positive pole, the diode
Figure 02_image054
The positive poles are respectively connected to the secondary side of the coupled inductor
Figure 02_image049
The second end, diode
Figure 02_image055
The negative electrode, capacitor
Figure 02_image057
The negative pole and capacitor
Figure 02_image059
The positive pole, the diode
Figure 02_image055
The positive pole is connected to the capacitor
Figure 02_image033
The negative electrode and diode
Figure 02_image013
The negative pole, the diode
Figure 02_image053
The negative pole is connected to the capacitor
Figure 02_image057
Positive and output impedance
Figure 02_image061
The positive pole, the diode
Figure 02_image013
The positive poles are respectively connected with capacitors
Figure 02_image059
The negative pole and the output impedance
Figure 02_image061
The negative electrode.

而根據各開關切換與各二極體導通與否，可以將該轉換器（１）在一個切換週期

Figure 02_image063
的動作，分成十個線性階段，其各線性階段等效線性電路以及主要元件波形如下，請再一併參閱第二圖本發明之主要元件時序及波形圖所示： According to the switching of each switch and the conduction of each diode, the converter (1) can be used in a switching cycle
Figure 02_image063
The action of is divided into ten linear stages. The equivalent linear circuit of each linear stage and the waveforms of the main components are as follows. Please refer to the second figure for the timing and waveform diagrams of the main components of the present invention:

預備階段［

Figure 02_image065
］：［開關
Figure 02_image031
：ON、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第三圖本發明之預備階段等效線性電路圖所示，本階段該開關
Figure 02_image031
已導通［ON］一段時間，該二極體
Figure 02_image013
、該二極體
Figure 02_image070
、該二極體
Figure 02_image071
皆因逆向偏壓而OFF。此時該電感
Figure 02_image027
因跨輸入電壓
Figure 02_image025
，則電感電流
Figure 02_image075
以斜率
Figure 02_image077
線性上升，而該耦合電感一次側
Figure 02_image042
之磁化電感
Figure 02_image079
因跨輸入電壓
Figure 02_image081
，則磁化電感電流
Figure 02_image083
以斜率
Figure 02_image085
線性上升。當該開關
Figure 02_image031
由ON切換至OFF時，則該轉換器（１）進入下一階段。 Preparatory stage
Figure 02_image065
]:[switch
Figure 02_image031
: ON, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
:ON]: Please refer to the third figure together as shown in the equivalent linear circuit diagram of the preparatory stage of the present invention. The switch at this stage
Figure 02_image031
Has been conducting [ON] for a period of time, the diode
Figure 02_image013
, The diode
Figure 02_image070
, The diode
Figure 02_image071
All are turned off due to reverse bias. At this time the inductance
Figure 02_image027
Because of the input voltage
Figure 02_image025
, The inductor current
Figure 02_image075
With slope
Figure 02_image077
Rises linearly, and the primary side of the coupled inductor
Figure 02_image042
Magnetizing inductance
Figure 02_image079
Because of the input voltage
Figure 02_image081
, Then the magnetizing inductance current
Figure 02_image083
With slope
Figure 02_image085
Linear increase. When the switch
Figure 02_image031
When switching from ON to OFF, the converter (1) enters the next stage.

第一階段［

Figure 02_image087
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第四圖本發明之第一階段等效線性電路圖所示，本階段該開關
Figure 02_image031
由ON切換至OFF，該耦合電感一次側
Figure 02_image042
之漏電感
Figure 02_image089
的漏電感電流
Figure 02_image091
對該開關
Figure 02_image031
的寄生電容
Figure 02_image093
充電，同時對該開關
Figure 02_image095
的寄生電容
Figure 02_image097
放電，當該開關
Figure 02_image031
的跨壓
Figure 02_image099
由零電壓開始上升至
Figure 02_image081
，則該二極體
Figure 02_image073
由ON切換至OFF，而該二極體
Figure 02_image073
由OFF切換至ON，該轉換器（１）進入下一階段。 The first stage[
Figure 02_image087
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
:ON]: Please refer to the fourth figure together as shown in the equivalent linear circuit diagram of the first stage of the present invention. The switch at this stage
Figure 02_image031
Switch from ON to OFF, the primary side of the coupled inductor
Figure 02_image042
Leakage inductance
Figure 02_image089
Leakage inductance current
Figure 02_image091
To the switch
Figure 02_image031
Parasitic capacitance
Figure 02_image093
Charge while the switch
Figure 02_image095
Parasitic capacitance
Figure 02_image097
Discharge when the switch
Figure 02_image031
Cross pressure
Figure 02_image099
Start from zero voltage and rise to
Figure 02_image081
, Then the diode
Figure 02_image073
Switch from ON to OFF, and the diode
Figure 02_image073
Switch from OFF to ON, the converter (1) enters the next stage.

第二階段［

Figure 02_image101
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：ON、二極體
Figure 02_image073
：OFF］：請再一併參閱第五圖本發明之第二階段等效線性電路圖所示，本階段該漏電感電流
Figure 02_image091
持續對該開關
Figure 02_image031
的寄生電容
Figure 02_image093
充電，同時對該開關
Figure 02_image095
的寄生電容
Figure 02_image097
放電，當該寄生電容
Figure 02_image097
的電壓
Figure 02_image103
下降至零，則該開關
Figure 02_image095
的本體二極體
Figure 02_image105
由OFF切換至ON，該開關
Figure 02_image095
可在此時切換至ON達成ZVS［Zero Voltage Switching］，該轉換器（１）進入下一階段。 second stage[
Figure 02_image101
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
: ON, diode
Figure 02_image073
：OFF]: Please refer to the fifth figure together as shown in the second stage equivalent linear circuit diagram of the present invention. The leakage inductance current at this stage
Figure 02_image091
Keep the switch
Figure 02_image031
Parasitic capacitance
Figure 02_image093
Charge while the switch
Figure 02_image095
Parasitic capacitance
Figure 02_image097
Discharge, when the parasitic capacitance
Figure 02_image097
Voltage
Figure 02_image103
Drop to zero, then the switch
Figure 02_image095
Body diode
Figure 02_image105
Switch from OFF to ON, the switch
Figure 02_image095
You can switch to ON at this time to achieve ZVS [Zero Voltage Switching], and the converter (1) enters the next stage.

第三階段［

Figure 02_image107
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：ON、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：ON、二極體
Figure 02_image073
：OFF］：請再一併參閱第六圖本發明之第三階段等效線性電路圖所示，本階段該開關
Figure 02_image031
保持為OFF，該開關
Figure 02_image109
由OFF切換至ON，該漏電感
Figure 02_image089
跨負電壓，則漏電感電流
Figure 02_image091
持續下降，當漏電感電流
Figure 02_image091
下降至該磁化電感電流
Figure 02_image083
，該二極體
Figure 02_image013
、該二極體
Figure 02_image070
由OFF切換至ON，而該二極體
Figure 02_image015
、該二極體
Figure 02_image069
由ON切換至OFF，該轉換器（１）進入下一階段。 The third phase[
Figure 02_image107
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
: ON, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
: ON, diode
Figure 02_image073
:OFF]: Please refer to the sixth figure together as shown in the equivalent linear circuit diagram of the third stage of the present invention. The switch at this stage
Figure 02_image031
Keep it OFF, the switch
Figure 02_image109
Switch from OFF to ON, the leakage inductance
Figure 02_image089
Across the negative voltage, the leakage inductance current
Figure 02_image091
Continue to decrease, when the leakage inductance current
Figure 02_image091
Down to the magnetizing inductance current
Figure 02_image083
, The diode
Figure 02_image013
, The diode
Figure 02_image070
Switch from OFF to ON, and the diode
Figure 02_image015
, The diode
Figure 02_image069
Switching from ON to OFF, the converter (1) enters the next stage.

第四階段［

Figure 02_image110
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：ON、二極體
Figure 02_image013
：ON、二極體
Figure 02_image015
：OFF、二極體
Figure 02_image069
：OFF、二極體
Figure 02_image070
：ON、二極體
Figure 02_image071
：ON、二極體
Figure 02_image073
：OFF］：請再一併參閱第七圖本發明之第四階段等效線性電路圖所示，本階段該開關
Figure 02_image031
保持為OFF，該開關
Figure 02_image109
保持為ON，因該磁化電感電流
Figure 02_image083
大於該漏電感電流
Figure 02_image091
，使該耦合電感二次側
Figure 02_image049
之電流
Figure 02_image112
流向相反，而該漏電感電流
Figure 02_image091
因跨負電壓而持續下降，當該漏電感電流
Figure 02_image091
由正值變成負值，即換向後，則該轉換器（１）進入下一階段。 The fourth stage [
Figure 02_image110
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
: ON, diode
Figure 02_image013
: ON, diode
Figure 02_image015
：OFF, diode
Figure 02_image069
：OFF, diode
Figure 02_image070
: ON, diode
Figure 02_image071
: ON, diode
Figure 02_image073
:OFF]: Please refer to the seventh figure together as shown in the equivalent linear circuit diagram of the fourth stage of the present invention. The switch at this stage
Figure 02_image031
Keep it OFF, the switch
Figure 02_image109
Remains ON, because the magnetizing inductance current
Figure 02_image083
Greater than the leakage inductance current
Figure 02_image091
, Make the secondary side of the coupled inductor
Figure 02_image049
The current
Figure 02_image112
Flow in the opposite direction, and the leakage inductance current
Figure 02_image091
Continues to drop due to the cross-negative voltage, when the leakage inductance current
Figure 02_image091
From a positive value to a negative value, that is, after commutation, the converter (1) enters the next stage.

第五階段［

Figure 02_image114
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：ON、二極體
Figure 02_image013
：ON、二極體
Figure 02_image015
：OFF、二極體
Figure 02_image069
：OFF、二極體
Figure 02_image070
：ON、二極體
Figure 02_image071
：ON、二極體
Figure 02_image073
：OFF］：請再一併參閱第八圖本發明之第五階段等效線性電路圖所示，本階段該漏電感電流
Figure 02_image091
因跨負電壓而持續下降，當該開關
Figure 02_image109
由ON切換至OFF時，則該轉換器（１）進入下一階段。 The fifth stage [
Figure 02_image114
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
: ON, diode
Figure 02_image013
: ON, diode
Figure 02_image015
：OFF, diode
Figure 02_image069
：OFF, diode
Figure 02_image070
: ON, diode
Figure 02_image071
: ON, diode
Figure 02_image073
:OFF]: Please refer to the eighth figure as shown in the fifth stage equivalent linear circuit diagram of the present invention. The leakage inductance current at this stage
Figure 02_image091
Continue to drop due to the negative voltage, when the switch
Figure 02_image109
When switching from ON to OFF, the converter (1) enters the next stage.

第六階段［

Figure 02_image116
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：ON、二極體
Figure 02_image015
：OFF、二極體
Figure 02_image069
：OFF、二極體
Figure 02_image070
：ON、二極體
Figure 02_image071
：ON、二極體
Figure 02_image073
：OFF］：請再一併參閱第九圖本發明之第六階段等效線性電路圖所示，本階段該開關
Figure 02_image109
由ON切換至OFF，該漏電感電流
Figure 02_image091
對該開關
Figure 02_image095
的寄生電容
Figure 02_image097
充電，同時對該開關
Figure 02_image031
的寄生電容
Figure 02_image093
放電，當該開關
Figure 02_image031
的跨壓
Figure 02_image099
由零電壓開始下降至
Figure 02_image081
時，則該二極體
Figure 02_image073
由OFF切換至ON，而該二極體
Figure 02_image071
由ON切換至OFF，該轉換器（１）進入下一階段。 Sixth stage [
Figure 02_image116
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
: ON, diode
Figure 02_image015
：OFF, diode
Figure 02_image069
：OFF, diode
Figure 02_image070
: ON, diode
Figure 02_image071
: ON, diode
Figure 02_image073
：OFF]: Please refer to the ninth figure as shown in the equivalent linear circuit diagram of the sixth stage of the present invention. The switch at this stage
Figure 02_image109
Switch from ON to OFF, the leakage inductance current
Figure 02_image091
To the switch
Figure 02_image095
Parasitic capacitance
Figure 02_image097
Charge while the switch
Figure 02_image031
Parasitic capacitance
Figure 02_image093
Discharge when the switch
Figure 02_image031
Cross pressure
Figure 02_image099
From zero voltage to
Figure 02_image081
When, then the diode
Figure 02_image073
Switch from OFF to ON, and the diode
Figure 02_image071
Switching from ON to OFF, the converter (1) enters the next stage.

第七階段［

Figure 02_image118
］：［開關
Figure 02_image031
：OFF、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：ON、二極體
Figure 02_image015
：OFF、二極體
Figure 02_image069
：OFF、二極體
Figure 02_image070
：ON、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第十圖本發明之第七階段等效線性電路圖所示，本階段該漏電感電流
Figure 02_image091
持續對該開關
Figure 02_image031
的寄生電容
Figure 02_image093
放電，同時對該開關
Figure 02_image095
的寄生電容
Figure 02_image097
充電，當該開關
Figure 02_image031
的跨壓
Figure 02_image099
下降至零，則該開關
Figure 02_image031
的本體二極體
Figure 02_image120
由OFF切換至ON，則該轉換器（１）進入下一階段。 Seventh stage [
Figure 02_image118
]:[switch
Figure 02_image031
: OFF, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
: ON, diode
Figure 02_image015
：OFF, diode
Figure 02_image069
：OFF, diode
Figure 02_image070
: ON, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
:ON]: Please also refer to the tenth figure as shown in the seventh stage equivalent linear circuit diagram of the present invention. The leakage inductance current at this stage
Figure 02_image091
Keep the switch
Figure 02_image031
Parasitic capacitance
Figure 02_image093
Discharge while the switch
Figure 02_image095
Parasitic capacitance
Figure 02_image097
Charge when the switch
Figure 02_image031
Cross pressure
Figure 02_image099
Drop to zero, then the switch
Figure 02_image031
Body diode
Figure 02_image120
Switch from OFF to ON, the converter (1) enters the next stage.

第八階段［

Figure 02_image122
］：［開關
Figure 02_image031
：ON、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：ON、二極體
Figure 02_image015
：OFF、二極體
Figure 02_image069
：OFF、二極體
Figure 02_image070
：ON、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第十一圖本發明之第八階段等效線性電路圖所示，本階段該開關
Figure 02_image095
保持為OFF，該開關
Figure 02_image031
由OFF切換至ON，該漏電感
Figure 02_image089
跨正電壓則該漏電感電流
Figure 02_image091
持續上升，當該漏電感電流
Figure 02_image091
上升至該磁化電感電流
Figure 02_image083
，該二極體
Figure 02_image013
、該二極體
Figure 02_image070
由ON切換至OFF，而該二極體
Figure 02_image015
、該二極體
Figure 02_image069
由OFF切換至ON，則該轉換器（１）進入下一階段。 Eighth stage [
Figure 02_image122
]:[switch
Figure 02_image031
: ON, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
: ON, diode
Figure 02_image015
：OFF, diode
Figure 02_image069
：OFF, diode
Figure 02_image070
: ON, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
：ON]: Please refer to the eleventh figure as shown in the eighth stage equivalent linear circuit diagram of the present invention. At this stage, the switch
Figure 02_image095
Keep it OFF, the switch
Figure 02_image031
Switch from OFF to ON, the leakage inductance
Figure 02_image089
Across the positive voltage, the leakage inductance current
Figure 02_image091
Continue to rise, when the leakage inductance current
Figure 02_image091
Up to the magnetizing inductance current
Figure 02_image083
, The diode
Figure 02_image013
, The diode
Figure 02_image070
Switch from ON to OFF, and the diode
Figure 02_image015
, The diode
Figure 02_image069
Switch from OFF to ON, the converter (1) enters the next stage.

第九階段［

Figure 02_image124
］：［開關
Figure 02_image031
：ON、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第十二圖本發明之第九階段等效線性電路圖所示，本階段該開關
Figure 02_image095
保持為OFF，該開關
Figure 02_image031
保持為ON，因該磁化電感電流
Figure 02_image083
持續小於該漏電感電流
Figure 02_image091
，使該耦合電感二次側
Figure 02_image049
之電流
Figure 02_image112
流向相反，而該漏電感電流
Figure 02_image091
因跨正電壓而持續上升，當該漏電感電流
Figure 02_image091
由負值變成正值，即換向後，則該轉換器進（１）入下一階段。 The ninth stage [
Figure 02_image124
]:[switch
Figure 02_image031
: ON, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
：ON]: Please refer to Figure 12 again as shown in the equivalent linear circuit diagram of the ninth stage of the present invention. At this stage, the switch
Figure 02_image095
Keep it OFF, the switch
Figure 02_image031
Remains ON, because the magnetizing inductance current
Figure 02_image083
Continuously less than the leakage inductance current
Figure 02_image091
, Make the secondary side of the coupled inductor
Figure 02_image049
The current
Figure 02_image112
Flow in the opposite direction, and the leakage inductance current
Figure 02_image091
Continues to rise due to the positive voltage, when the leakage inductance current
Figure 02_image091
From negative value to positive value, that is, after commutation, the converter enters (1) into the next stage.

第十階段［

Figure 02_image126
］：［開關
Figure 02_image031
：ON、開關
Figure 02_image067
：OFF、二極體
Figure 02_image013
：OFF、二極體
Figure 02_image015
：ON、二極體
Figure 02_image069
：ON、二極體
Figure 02_image070
：OFF、二極體
Figure 02_image071
：OFF、二極體
Figure 02_image073
：ON］：請再一併參閱第十三圖本發明之第十階段等效線性電路圖所示，本階段此即為預備階段，當該開關
Figure 02_image031
由ＯＮ切換至ＯＦＦ時，則該轉換器（１）進入下一週期的開始。 The tenth stage [
Figure 02_image126
]:[switch
Figure 02_image031
: ON, switch
Figure 02_image067
：OFF, diode
Figure 02_image013
：OFF, diode
Figure 02_image015
: ON, diode
Figure 02_image069
: ON, diode
Figure 02_image070
：OFF, diode
Figure 02_image071
：OFF, diode
Figure 02_image073
:ON]: Please refer to Figure 13 as shown in the equivalent linear circuit diagram of the tenth stage of the present invention. This stage is the preliminary stage. When the switch
Figure 02_image031
When switching from ON to OFF, the converter (1) enters the beginning of the next cycle.

據上述電路動作分析，使用IsSpice模擬軟體驗證其電路理論分析、電氣規格以及上述所及之優點，而該轉換器（１）之模擬電氣規格與元件參數設定如下表1所示： 表1電氣規格與元件參數 輸入電壓

Figure 02_image005
Figure 02_image128
 磁化電感
Figure 02_image130
Figure 02_image132
 輸出電壓
Figure 02_image007
Figure 02_image134
 輸入電感
Figure 02_image136
Figure 02_image137
 負載
Figure 02_image139
Figure 02_image140
 漏電感
Figure 02_image142
Figure 02_image144
 輸出功率
Figure 02_image146
Figure 02_image148
 升壓電容
Figure 02_image150
、
Figure 02_image152
Figure 02_image154
 切換頻率
Figure 02_image156
Figure 02_image158
 升壓電容
Figure 02_image160
Figure 02_image162
 耦合電感匝數比
Figure 02_image164
Figure 02_image166
 升壓電容
Figure 02_image168
Figure 02_image170
 According to the above-mentioned circuit operation analysis, the IsSpice simulation software is used to verify the circuit theoretical analysis, electrical specifications and the above-mentioned advantages. The analog electrical specifications and component parameter settings of the converter (1) are shown in Table 1 below: Table 1 Electrical specifications And component parameters Input voltage
Figure 02_image005
Figure 02_image128
 Magnetizing inductance
Figure 02_image130
Figure 02_image132
 The output voltage
Figure 02_image007
Figure 02_image134
 Input inductance
Figure 02_image136
Figure 02_image137
 load
Figure 02_image139
Figure 02_image140
 Leakage inductance
Figure 02_image142
Figure 02_image144
 Output Power
Figure 02_image146
Figure 02_image148
 Boost capacitor
Figure 02_image150
,
Figure 02_image152
Figure 02_image154
 Switching frequency
Figure 02_image156
Figure 02_image158
 Boost capacitor
Figure 02_image160
Figure 02_image162
 Coupling inductance turns ratio
Figure 02_image164
Figure 02_image166
 Boost capacitor
Figure 02_image168
Figure 02_image170

以下將介紹輸出功率

Figure 02_image172
之下相關模擬結果。請再一併參閱第十四圖本發明之模擬電路示意圖所示，模擬波形將驗正項目如下： The following will introduce the output power
Figure 02_image172
Related simulation results below. Please also refer to Figure 14 as shown in the schematic diagram of the analog circuit of the present invention. The analog waveform will be verified as follows:

A.電氣規格驗證：輸入電壓

Figure 02_image005
、輸出電壓
Figure 02_image007
、導通比
Figure 02_image174
A. Verification of electrical specifications: input voltage
Figure 02_image005
,The output voltage
Figure 02_image007
, Conduction ratio
Figure 02_image174

請再一併參閱第十五圖本發明之開關驅動信號

Figure 02_image001
、
Figure 02_image003
與輸入電壓
Figure 02_image005
及輸出電壓
Figure 02_image007
的模擬波形圖所示，由該第十五圖可知，輸入電壓
Figure 02_image176
、輸出電壓
Figure 02_image178
，滿足電氣之需求規格。 Please also refer to Figure 15 for the switch drive signal of the present invention
Figure 02_image001
,
Figure 02_image003
And input voltage
Figure 02_image005
And output voltage
Figure 02_image007
As shown in the analog waveform diagram, the fifteenth diagram shows that the input voltage
Figure 02_image176
,The output voltage
Figure 02_image178
, To meet the electrical requirements and specifications.

B.開關

Figure 02_image031
、開關
Figure 02_image067
的低電壓應力：
Figure 02_image180
及
Figure 02_image182
B. Switch
Figure 02_image031
,switch
Figure 02_image067
The low voltage stress:
Figure 02_image180
and
Figure 02_image182

經電路動作分析，該開關

Figure 02_image031
、該開關
Figure 02_image067
於OFF時，其跨壓
Figure 02_image009
及
Figure 02_image011
相等，在滿載
Figure 02_image184
時，請參閱第十六圖本發明之開關驅動信號
Figure 02_image001
、
Figure 02_image003
及其跨壓
Figure 02_image009
、
Figure 02_image011
的模擬波形圖所示，開關在OFF時的跨壓之模擬結果為
Figure 02_image186
，且驗證該開關
Figure 02_image031
及該開關
Figure 02_image067
確實具有遠小於輸出電壓
Figure 02_image178
之低電壓應力的性能。 After the circuit action analysis, the switch
Figure 02_image031
, The switch
Figure 02_image067
When OFF, its cross pressure
Figure 02_image009
and
Figure 02_image011
Equal, at full load
Figure 02_image184
, Please refer to Figure 16 for the switch drive signal of the present invention
Figure 02_image001
,
Figure 02_image003
And its cross pressure
Figure 02_image009
,
Figure 02_image011
As shown in the simulation waveform diagram, the simulation result of the cross voltage when the switch is OFF is
Figure 02_image186
And verify the switch
Figure 02_image031
And the switch
Figure 02_image067
Does have much less than the output voltage
Figure 02_image178
The performance of low voltage stress.

C.減緩二極體反向恢復問題：

Figure 02_image188
、
Figure 02_image190
C. Slow down the problem of reverse recovery of diodes:
Figure 02_image188
,
Figure 02_image190

請再一併參閱第十七圖本發明之二極體

Figure 02_image013
、二極體
Figure 02_image015
電壓與電流的模擬波形圖、第十八圖本發明之二極體
Figure 02_image017
、二極體
Figure 02_image019
電壓與電流的模擬波形圖所示，該二極體
Figure 02_image013
、該二極體
Figure 02_image015
、該二極體
Figure 02_image069
、該二極體
Figure 02_image070
之電流只有一段微小的逆向恢復電流，本發明確實能夠減緩反向恢復問題及EMI雜訊干擾。 Please also refer to Figure 17 of the diode of the present invention
Figure 02_image013
, Diode
Figure 02_image015
Analog waveform diagram of voltage and current, the eighteenth diagram of the diode of the present invention
Figure 02_image017
, Diode
Figure 02_image019
As shown in the analog waveform diagram of voltage and current, the diode
Figure 02_image013
, The diode
Figure 02_image015
, The diode
Figure 02_image069
, The diode
Figure 02_image070
The current is only a small reverse recovery current, and the present invention can indeed alleviate the reverse recovery problem and EMI noise interference.

而本發明之轉換器（１）與文獻中之高升壓比轉換器，在電壓轉換比與寬域輸入進行比較，請參閱下表2所示，本發明之轉換器（１）具有較高的電壓轉換比且導通比沒有限制： 表2參考文獻與本發明之比較表 高升壓轉換器 文獻［1］ 文獻［2］ 文獻［3］ 本發明 電壓轉換比

Figure 02_image192
Figure 02_image194
Figure 02_image194
Figure 02_image195
 導通比限制 D>0.5 D>0.5 D>0.5 無 The converter (1) of the present invention is compared with the high boost ratio converter in the literature in terms of voltage conversion ratio and wide-range input. Please refer to Table 2 below. The converter (1) of the present invention has a higher The voltage conversion ratio and the conduction ratio are not limited: Table 2 Comparison table of references and the present invention High boost converter Literature [1] Literature [2] Literature [3] this invention Voltage conversion ratio
Figure 02_image192
Figure 02_image194
Figure 02_image194
Figure 02_image195
 Conduction ratio limit D>0.5 D>0.5 D>0.5 no

請再一併參閱第十九圖本發明於匝數比

Figure 02_image021
時與文獻［1］之電壓轉換比比較曲線圖及第二十圖本發明於匝數比
Figure 02_image023
時與文獻［1］之電壓轉換比比較曲線圖所示，由於文獻［1］、文獻［2］、文獻［3］之電壓增益皆相同，取文獻［1］為代表與本發明之轉換器（１）進行比較可知，本發明之轉換器（１）具有最高之電壓增益，且當耦合電感匝數比
Figure 02_image197
越大時，則差距會更加明顯［請再一併參閱第二十一圖本發明於改變匝數比時之電壓轉換比曲線圖所示］。 Please also refer to the nineteenth figure of the present invention in the turns ratio
Figure 02_image021
The voltage conversion ratio comparison curve and the twentieth graph in the literature [1]
Figure 02_image023
When compared with the voltage conversion ratio curve of literature [1], since the voltage gains of literature [1], literature [2], and literature [3] are all the same, take literature [1] as a representative of the converter of the present invention (1) Comparison shows that the converter (1) of the present invention has the highest voltage gain, and when the coupled inductor turns ratio
Figure 02_image197
The larger the value, the more obvious the difference [please refer to the graph of the voltage conversion ratio of the present invention when changing the turns ratio as shown in Fig. 21].

參考文獻：references:

［1］L. He, and J. Lei, ”High Step-Up Converter with Passive Lossless Clamp Circuit and Switched-Capacitor: Analysis, Design, and Experimentation” IEEE Applied Power Electronics Conference and Exposition (APEC), March 2013［1］L. He, and J. Lei, ”High Step-Up Converter with Passive Lossless Clamp Circuit and Switched-Capacitor: Analysis, Design, and Experimentation” IEEE Applied Power Electronics Conference and Exposition (APEC), March 2013

［2］W. Li, Y. Zhao, J. Wu, and X. He, ” Interleaved High Step-Up Converter with Winding-Cross-Coupled Inductors and Voltage Multiplier Cells” IEEE Transactions on Power Electronics, Vol.27, No.1, January 2012 ［2］W. Li, Y. Zhao, J. Wu, and X. He, ”Interleaved High Step-Up Converter with Winding-Cross-Coupled Inductors and Voltage Multiplier Cells” IEEE Transactions on Power Electronics , Vol.27, No .1, January 2012

［3］K. C. Tseng, and C. C. Huang, ”High Step-Up High-Efficiency Interleaved Converter with Voltage Multiplier Module for Renewable Energy System” IEEE Transactions on Power Electronics, Vol. 61, No. 3, March 2014 ［3］KC Tseng, and CC Huang, ”High Step-Up High-Efficiency Interleaved Converter with Voltage Multiplier Module for Renewable Energy System” IEEE Transactions on Power Electronics , Vol. 61, No. 3, March 2014

藉由以上所述，本發明電路之組成與使用實施說明可知，本發明主要係具有下列特點：Based on the above description, the composition and use of the circuit of the present invention shows that the present invention mainly has the following characteristics:

1.寬輸入應用：由於本發明轉換器無導通比D>0.5的使用限制，因此輸入電壓由20V~40V，均可得輸出電壓達400V之高電壓。1. Wide input application: Since the converter of the present invention has no use limitation of conduction ratio D>0.5, the input voltage is from 20V to 40V, and the output voltage can reach 400V.

2.高升壓增益：本發明轉換器不操作在極端寬大的導通責任比下，亦能具有高電壓轉換比，於輸入電壓20V時輸出電壓可達400V。2. High boost gain: The converter of the present invention does not operate at an extremely wide on-duty ratio, but can also have a high voltage conversion ratio, and the output voltage can reach 400V when the input voltage is 20V.

3.低電壓應力：本發明轉換器之高電壓增益的達成，不必操作在極大的導通比，則功率開關具有低於輸出電壓的低電壓應力，故可使用導通電阻較小的低額定耐壓MOSFET，所以可降低導通損失，提升整體效率。3. Low voltage stress: The high voltage gain of the converter of the present invention does not need to be operated at a large conduction ratio, and the power switch has a low voltage stress lower than the output voltage, so a low rated withstand voltage with a small conduction resistance can be used MOSFET, so it can reduce the conduction loss and improve the overall efficiency.

4.無逆向恢復：本發明轉換器將耦合電感次級側的能量回饋至輸入端，解決二極體的逆向恢復問題，從而降低雜訊對電路動作上的影響。4. No reverse recovery: The converter of the present invention feeds back the energy of the secondary side of the coupled inductor to the input terminal, solving the problem of reverse recovery of the diode, thereby reducing the influence of noise on the circuit operation.

然而前述之實施例或圖式並非限定本發明之產品結構或使用方式，任何所屬技術領域中具有通常知識者之適當變化或修飾，皆應視為不脫離本發明之專利範疇。However, the foregoing embodiments or drawings do not limit the product structure or usage mode of the present invention, and any appropriate changes or modifications by persons with ordinary knowledge in the relevant technical field should be regarded as not departing from the patent scope of the present invention.

綜上所述，本發明實施例確能達到所預期之使用功效，又其所揭露之具體構造，不僅未曾見諸於同類產品中，亦未曾公開於申請前，誠已完全符合專利法之規定與要求，爰依法提出發明專利之申請，懇請惠予審查，並賜准專利，則實感德便。In summary, the embodiments of the present invention can indeed achieve the expected use effect, and the specific structure disclosed by it has not been seen in similar products, nor has it been disclosed before the application, since it has fully complied with the provisions of the patent law. In accordance with the requirements, Yan filed an application for a patent for invention in accordance with the law, and asked for favors for examination, and granted a patent for approval, which would be more virtuous.

（１）:轉換器(1): Converter

第一圖：本發明之電路圖Figure 1: Circuit diagram of the present invention

第二圖：本發明之主要元件時序及波形圖Figure 2: Timing and waveform diagram of the main components of the present invention

第三圖：本發明之預備階段等效線性電路圖Figure 3: Equivalent linear circuit diagram of the preparatory stage of the present invention

第四圖：本發明之第一階段等效線性電路圖Figure 4: The equivalent linear circuit diagram of the first stage of the present invention

第五圖：本發明之第二階段等效線性電路圖Figure 5: The second stage equivalent linear circuit diagram of the present invention

第六圖：本發明之第三階段等效線性電路圖圖Figure 6: The equivalent linear circuit diagram of the third stage of the present invention

第七圖：本發明之第四階段等效線性電路圖Figure 7: Equivalent linear circuit diagram of the fourth stage of the present invention

第八圖：本發明之第五階段等效線性電路圖Figure 8: Equivalent linear circuit diagram of the fifth stage of the present invention

第九圖：本發明之第六階段等效線性電路圖Figure 9: Equivalent linear circuit diagram of the sixth stage of the present invention

第十圖：本發明之第七階段等效線性電路圖Figure 10: Equivalent linear circuit diagram of the seventh stage of the present invention

第十一圖：本發明之第八階段等效線性電路圖Figure 11: Equivalent linear circuit diagram of the eighth stage of the present invention

第十二圖：本發明之第九階段等效線性電路圖Figure 12: Equivalent linear circuit diagram of the ninth stage of the present invention

第十三圖：本發明之第十階段等效線性電路圖Figure 13: Equivalent linear circuit diagram of the tenth stage of the present invention

第十四圖：本發明之模擬電路示意圖Figure 14: Schematic diagram of the analog circuit of the present invention

第十五圖：本發明之開關驅動信號

Figure 02_image001
、
Figure 02_image003
與輸入電壓
Figure 02_image005
及輸出電壓
Figure 02_image007
的模擬波形圖 Figure 15: The switch drive signal of the present invention
Figure 02_image001
,
Figure 02_image003
And input voltage
Figure 02_image005
And output voltage
Figure 02_image007
Analog waveform

第十六圖：本發明之開關驅動信號

Figure 02_image001
、
Figure 02_image003
及其跨壓
Figure 02_image009
、
Figure 02_image011
的模擬波形圖 Figure 16: The switch drive signal of the present invention
Figure 02_image001
,
Figure 02_image003
And its cross pressure
Figure 02_image009
,
Figure 02_image011
Analog waveform

第十七圖：本發明之二極體

Figure 02_image013
、二極體
Figure 02_image015
電壓與電流的模擬波形圖 Figure 17: Diode of the present invention
Figure 02_image013
, Diode
Figure 02_image015
Analog waveform diagram of voltage and current

第十八圖：本發明之二極體

Figure 02_image017
、二極體
Figure 02_image019
電壓與電流的模擬波形圖 Figure 18: Diode of the present invention
Figure 02_image017
, Diode
Figure 02_image019
Analog waveform diagram of voltage and current

第十九圖：本發明於匝數比

Figure 02_image021
時與文獻［1］之電壓轉換比比較曲線圖 Figure Nineteen: The present invention is in the turns ratio
Figure 02_image021
Comparison curve of voltage conversion ratio between time and literature [1]

第二十圖：本發明於匝數比

Figure 02_image023
時與文獻［1］之電壓轉換比比較曲線圖 Figure 20: The present invention is in the turns ratio
Figure 02_image023
Comparison curve of voltage conversion ratio between time and literature [1]

第二十一圖：本發明於改變匝數比時之電壓轉換比曲線圖Figure 21: The voltage conversion ratio curve diagram of the present invention when the turns ratio is changed

(1):轉換器 (1): Converter

Claims (1)

一種高電壓增益直流轉換器，其主要係令轉換器於輸入電壓
Figure 03_image025
之正極分別連接電感
Figure 03_image027
之第一端與電容
Figure 03_image029
之負極，而該輸入電壓
Figure 03_image025
之負極則分別連接有開關
Figure 03_image031
之第二端及電容
Figure 03_image033
之正極，該電感
Figure 03_image027
之第二端分別連接有二極體
Figure 03_image035
之正極及二極體
Figure 03_image037
之正極，該電容
Figure 03_image029
之正極分別連接有電容
Figure 03_image039
之負極、該二極體
Figure 03_image041
之負極及耦合電感一次側
Figure 03_image042
之第一端，該電容
Figure 03_image039
之正極分別連接有開關
Figure 03_image044
之第一端及電容
Figure 03_image046
之負極，該開關
Figure 03_image048
之第二端分別連接有該耦合電感一次側
Figure 03_image042
之第二端、該二極體
Figure 03_image037
之負極、該開關
Figure 03_image031
之第一端及耦合電感二次側
Figure 03_image049
之第一端，該電容
Figure 03_image046
之正極分別連接有二極體
Figure 03_image051
之負極及二極體
Figure 03_image053
之正極，該二極體
Figure 03_image054
之正極分別連接有該耦合電感二次側
Figure 03_image049
之第二端、二極體
Figure 03_image055
之負極、電容
Figure 03_image057
之負極及電容
Figure 03_image059
之正極，該二極體
Figure 03_image055
之正極分別連接有該電容
Figure 03_image033
之負極及二極體
Figure 03_image013
之負極，該二極體
Figure 03_image053
之負極分別連接有該電容
Figure 03_image057
之正極及輸出阻抗
Figure 03_image061
之正極，該二極體
Figure 03_image013
之正極分別連接有電容
Figure 03_image059
之負極及該輸出阻抗
Figure 03_image061
之負極。 A high-voltage-gain DC converter, which mainly makes the converter operate at the input voltage
Figure 03_image025
The positive poles are respectively connected to the inductor
Figure 03_image027
The first terminal and the capacitor
Figure 03_image029
The negative pole, and the input voltage
Figure 03_image025
The negative pole is connected to the switch respectively
Figure 03_image031
The second terminal and capacitor
Figure 03_image033
The positive pole, the inductor
Figure 03_image027
Diodes are connected to the second ends
Figure 03_image035
The anode and diode
Figure 03_image037
The positive pole, the capacitor
Figure 03_image029
The positive poles are respectively connected with capacitors
Figure 03_image039
The negative pole, the diode
Figure 03_image041
The negative pole and the primary side of the coupled inductor
Figure 03_image042
The first terminal, the capacitor
Figure 03_image039
The positive pole is connected to the switch
Figure 03_image044
The first terminal and capacitor
Figure 03_image046
The negative pole, the switch
Figure 03_image048
The second end is respectively connected to the primary side of the coupled inductor
Figure 03_image042
The second end, the diode
Figure 03_image037
The negative pole, the switch
Figure 03_image031
The first terminal and the secondary side of the coupled inductor
Figure 03_image049
The first terminal, the capacitor
Figure 03_image046
The positive poles are connected to the diodes
Figure 03_image051
The negative electrode and diode
Figure 03_image053
The positive pole, the diode
Figure 03_image054
The positive poles are respectively connected to the secondary side of the coupled inductor
Figure 03_image049
The second end, diode
Figure 03_image055
The negative electrode, capacitor
Figure 03_image057
The negative pole and capacitor
Figure 03_image059
The positive pole, the diode
Figure 03_image055
The positive pole is connected to the capacitor
Figure 03_image033
The negative electrode and diode
Figure 03_image013
The negative pole, the diode
Figure 03_image053
The negative pole is connected to the capacitor
Figure 03_image057
Positive and output impedance
Figure 03_image061
The positive pole, the diode
Figure 03_image013
Capacitors are connected to the positive pole
Figure 03_image059
The negative pole and the output impedance
Figure 03_image061
The negative electrode.
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
TWI792945B (en) * 2022-03-15 2023-02-11 崑山科技大學 High Voltage Gain DC Converter

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070216390A1 (en) * 2006-03-17 2007-09-20 Yuan Ze University High-efficiency high-voltage difference ratio bi-directional converter
CN201733220U (en) * 2010-07-16 2011-02-02 刘焕彩 Integrated Boost-Forward-Flyback High Voltage Gain Converter
TW201644165A (en) * 2015-06-01 2016-12-16 Univ Far East High step-up DC power converter
TWI664797B (en) * 2018-04-27 2019-07-01 崑山科技大學 Dc power converter with high voltage gain

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070216390A1 (en) * 2006-03-17 2007-09-20 Yuan Ze University High-efficiency high-voltage difference ratio bi-directional converter
CN201733220U (en) * 2010-07-16 2011-02-02 刘焕彩 Integrated Boost-Forward-Flyback High Voltage Gain Converter
TW201644165A (en) * 2015-06-01 2016-12-16 Univ Far East High step-up DC power converter
TWI664797B (en) * 2018-04-27 2019-07-01 崑山科技大學 Dc power converter with high voltage gain

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
TWI792945B (en) * 2022-03-15 2023-02-11 崑山科技大學 High Voltage Gain DC Converter

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