TW202228363A - Transfer pick-up circuit - Google Patents

Abstract

The invention relates to a transfer pick-up circuit for inductively picking up power from a cable carrying an alternating supply current, wherein the transfer pick-up circuit comprises: the main secondary winding of a transformer for providing an inductive coupling to the cable and a capacitive module connected in parallel to the main secondary winding; a switch mode converter connected in series to the main secondary winding and configured for converting a picked up alternating current to a direct current (DC); and a sensor configured for sensing at least one property of the alternating supply current carried by the cable and/or for sensing at least one property of the picked up alternating current, wherein the sensor is in electrical communication with the switch mode converter, wherein the switch mode converter further is configured for regulating a reactance on the input thereof to a predetermined setpoint on basis of the sensed at least one property of the alternating supply current.

Description

Transfer Pickup Circuit

A transfer pickup circuit for inductively picking up energy from a conductor carrying an AC supply current, wherein the transfer pickup circuit includes a first circuit including a primary secondary winding of a transformer for providing Inductive coupling of conductors and capacitor modules in parallel with the primary secondary winding.

Furthermore, the present invention relates to a node comprising a transfer pickup circuit.

A known transfer pickup circuit is known, for example, from JP2002-354711. FIG. 2 of JP2002-354711 shows a non-contact energy transmission device having a high frequency energy supply end 11 and a main energy supply line 12 connected to the high frequency energy supply end 11 . In addition, the contactless energy transmission device includes an energy supply transformer 13, the energy supply transformer 13 has a secondary winding 13s, a series-parallel resonance circuit 18 connected to the secondary and winding 13s, and a rectifying unit for rectifying transformation energy 15, and a fixed voltage control unit 16 for supplying voltage to the load.

In the known transfer pickup circuit, the high frequency energy supply terminal can provide the high frequency energy transmission signal. It should be noted that if the total length of the wires of the energy transfer system is greater than one tenth of the wavelength of the energy signal, the frequency of the energy signal is regarded as a high frequency. In this case, the energy transfer from the wire to the secondary winding of the energy supply is severely affected due to impedance changes caused by internal reflections in the wire. Therefore, the known energy transfer system has the disadvantage that the energy transfer system has a low system energy throughput and efficiency.

Furthermore, electrical components such as energy transfer systems have tolerances. For example, due to manufacturing tolerances, the value of the capacitor may vary by 10%, while the inductance value of the coil may vary by 5 to 10%. In addition, tolerances are due to operating temperature or component aging. In situations where the electrical components of the transfer pickup circuit determine the resonant frequency of the transfer pickup circuit, tolerances can cause significant deviations from the expected resonant frequency. Larger deviations from the expected resonant frequency will result in reduced system power throughput and efficiency.

It is an object of the present invention to ameliorate or eliminate one or more of the disadvantages of known energy transfer systems in order to provide an improved energy transfer system or at least an alternating current energy transfer system.

According to a first aspect, the present invention provides a transfer pickup circuit for inductively picking up energy from a wire carrying an AC supply current having a wire current frequency, wherein the transfer pickup circuit comprises: A main secondary winding of a transformer for providing an inductive coupling of the wire and a capacitor module in parallel with the main secondary winding; a switched mode converter in series with the primary secondary winding and configured to convert a pick-up alternating current to a direct current (DC); an inductor configured to sense at least one property of the AC supply current carried by the wire, and/or to sense at least one property of the pickup AC current, wherein the inductor is in electrical communication with the switch mode converter, Wherein, based on the at least one property of the sensed AC supply current, the switch mode converter is further configured to adjust a reactance of the input end of the switch mode converter to a predetermined set point.

。為了使導線與移轉拾取電路之間的能量移轉最佳化，負載的電抗部分需要最佳化。電抗部分取決於移轉拾取電路在導線上的位置、導線特性、負載的能量需求及導線電流。 As previously mentioned, the transfer of energy from the conductor to the primary secondary winding of the power supply transformer can be severely affected by impedance changes caused by internal reflections within the conductor operatively coupled to the base station as the energy source. The most pronounced impedance change occurs where a load (eg, a node) is placed on the wire. The impedance of the wire and the impedance of the load together determine the efficiency of energy transfer between them. Impedance includes a resistive part and a reactive part. The resistive part of the load is usually defined separately by the energy demand of the load and the amplitude of the AC supply current, as in the equation

. In order to optimize the energy transfer between the conductors and the transfer pickup circuit, the reactive portion of the load needs to be optimized. The reactance depends in part on the location of the transfer pickup circuit on the wire, the wire characteristics, the energy requirements of the load, and the wire current.

The inventors have surprisingly found that the wire current is most important for tuning the optimal imaginary part. The transfer pickup circuit of the present invention senses at least one property of the AC supply current, such as the current itself, by means of an inductor. The sensed current is supplied to the switched mode converter, which applies the sensed current to adjust the reactance (also referred to as the reactive portion) to a desired set point to produce the optimal reactive portion of the load. The optimal reactive portion of the load is accompanied by an optimal resistive portion of the load to produce optimal energy transfer from the base station to one or more transfer pickup circuits. Thus, the advantage of the present invention is the transfer of energy between the base station/conductor and the transfer pickup circuit, thereby making the load more efficient and ideally optimized.

Furthermore, by adjusting the reactive portion of the load due to the induced wire current, it may be possible to compensate for manufacturing tolerances of the components of the transfer pickup circuit.

In one embodiment, the sensor is configured to be selectively coupled to the wire. In one embodiment, the inductor is configured to sense the wire current of the AC supply current carried by the wire. As previously mentioned, the reactive portion of the impedance of the load depends on the following parameters: the location of the transfer pickup circuit on the wire, the wire characteristics, the energy requirements of the load, and the wire current. The inventors have surprisingly found that wire current is most important in determining the optimal reactive part of the load (ie the transfer pickup circuit). The advantage of this embodiment is that only the most important parameters can be used to determine the optimum reactance induced at the wire ends, keeping the transfer pick-up circuit relatively simple.

Additionally, the sensed wire current can be used to determine the reactance set point, maximizing energy transfer.

In one embodiment, during use, the inductor applies a current sensing method selected from the group consisting of resistance value sensing, magnetic field sensing, and inductance value sensing. In one embodiment, the inductor includes an inductive secondary winding of a transformer, inductively coupled to the wire.

In one embodiment, the inductor is configured to sense the wire voltage of the AC supply current carried by the wire and/or the voltage of the AC current being picked up. In one embodiment, the transfer pickup circuit is provided with additional sensors for sensing at least one property of the AC supply current carried by the wires and/or for sensing at least one property of the AC current being picked up. In one embodiment, the transfer pickup circuit may be provided with an inductor for sensing the wire current of the AC supply current, and with an additional inductor for sensing the voltage of the AC current being picked up. The benefit of having an inductor for sensing the wire current of the AC supply current and an additional inductor for sensing the voltage of the AC current being picked up is that it provides an optimum transfer of energy between the base station to the transfer pickup circuit ability to transform. In order to optimize energy transfer, the reactance on the side of the main winding of the transformer needs to be controlled. The reactance can be controlled by adjusting the reactive voltage of the transfer pickup circuit, especially its amplitude. In order to adjust the reactance, the induced wire current and the induced voltage of this picked-up AC current are necessary. By using the induced wire current, it is advantageous to reduce or ideally reduce the effects of transformer induction.

Note that the voltage on the secondary side is proportional to the voltage on the wire.

According to the present invention, the transfer pickup circuit includes a controller for controlling the switch mode converter to adjust the reactance of its input to a predetermined set point based on at least one sensed property of the AC supply current.

In one embodiment, the additional inductor includes a node voltage sensing circuit, connected in parallel with the primary secondary winding, and configured to sense the voltage of the energy being picked up by the wire, and/or an applied voltage sensing circuit, connected in parallel with the pick-up transfer output of the circuit and configured to sense the applied voltage. In one embodiment, additional sensors, node voltage sensing circuits and/or application voltage sensing circuits are in data communication with the controller. During use, the reactance of the input of the switch mode converter is adjusted to adjust the reactance to a predetermined set point based on at least one sensed property of the AC supply current. Adjusting the reactance at the input of the switched mode converter will affect the node voltage applied to the transfer pickup circuit or node in conjunction with the load (eg, a switchable light bulb). By inductively applying the transfer pickup circuit and transmitting the second node voltage to the controller, the controller receives feedback regarding the effect of the adjusted reactance. Thus, the controller has the ability to control the switched mode converter and is dependent on the sensed node voltage.

With regard to the application voltage sensing circuit, it should be noted that adjusting the reactance of the input of the switched mode converter also affects the application voltage applied to the load, such as a switchable light bulb. By sensing the applied voltage applied to the load and transmitting the sensed applied voltage to the controller, the controller receives feedback related to the adjusted reactance. Therefore, the controller has the ability to control the switched mode converter, and is dependent on the sensed application voltage.

According to an embodiment of the present invention, the controller has: an applied voltage controller configured to adjust the resistance value of the transfer pickup circuit on the wire to a predetermined applied voltage value, wherein preferably the applied voltage controller receives an applied voltage set point; and An imaginary power controller configured to adjust the reactance of the transfer pickup circuit to a predetermined reactance power value, wherein preferably the imaginary power controller receives an imaginary power setpoint. In other embodiments, the controller is configured to multiply the predetermined applied voltage by the wire current, which is preferably one cycle later than the wire current frequency, to generate the real part-shifted pickup circuit component. wherein the controller is further configured to multiply a preset imaginary power value by the inverse conducting current, which is preferably a quarter period later than the frequency of the conductor current, thereby generating an imaginary power voltage component, and Wherein, the controller is further configured to add up the real part transfer pickup circuit voltage component and the imaginary part voltage component to generate the preset output voltage.

In one embodiment, the predetermined output voltage is calculated by summing up the real-part shift pickup current-voltage component and the imaginary-part voltage component, wherein the real-part shift pickup current-voltage component and the imaginary-part voltage component are both: sine wave. The two components are generated by multiplying corresponding delays, which can be, for example, phase shifts. The conductor current has two controlled multiplicands, which are a preset applied voltage value and a preset electronically controlled energy value. The preset applied voltage circuit value represents the resistive part of the impedance, and the preset imaginary power value represents the imaginary part of the impedance. The binary value is controlled separately by applying a voltage controller and an imaginary power controller. The advantage is that a stable node/transfer pickup circuit impedance can be created instantaneously.

In one embodiment, the controller is further configured to divide the predetermined output voltage by the applied voltage determined by the applied voltage sensing circuit to generate a duty cycle (DTC) signal, and The controller includes a pulse width modulation (PWM) generator configured to generate one or more PWM switching signals based on the DTC signal, wherein the one or more PWM switching signals are used to inform the switching mode converter that the the resulting average voltage.

In this embodiment, the controller of the transfer pickup circuit has as output one or more PWM switching signals for switching the mode converter. Therefore, the controller advantageously provides control signals suitable for controlling the switch mode converter.

In one embodiment, the controller includes a power analyzer and a setpoint generator, wherein the power analyzer is configured to measure the actual voltage by integrating the sensed voltage product of the energy picked up from the wire and the sensed wire current. part power, and the imaginary part power is measured by integrating the voltage product of the energy picked up from the wire and the induced wire current offset by 90 degrees, where the measured real part power is transmitted from the power analyzer to a setpoint generator to generate a setpoint as a function of the measured real power, wherein the generated setpoint is provided to the imaginary power controller and the measured imaginary power is obtained from the power analyzer is passed to the imaginary power controller.

The amplitude and phase of the output voltage of the switched mode converter are not always equal to the amplitude and phase of the shift pickup circuit voltage or the node voltage. Manufacturing tolerances in the components of the transfer pickup circuit cause unwanted uncertainty in the reactance of the transfer pickup circuit or node. Feedback of imaginary power, imaginary voltage or reactance is necessary in order to compensate for component manufacturing tolerances. The power analyzer measures the real and imaginary powers as described above, and the feedback from the analyzer can be used to compensate for the error between the imaginary voltage component of the imaginary controller and the actual imaginary voltage. An advantage of this embodiment is therefore that manufacturing tolerances of the components of the transfer pickup circuit can be compensated.

In one embodiment, the switched mode converter is selected from the group consisting of a four-quadrant power converter, an H-bridge circuit topology, and a half-bridge circuit topology.

In one embodiment, the switching mode converter includes a switching coil, which together with the capacitor module forms a low-pass filter to pass frequencies substantially corresponding to the frequency of the AC supply current and block higher switching frequencies.

In one embodiment, the transfer pickup circuit includes a transformer inductive compensation element configured to compensate for transformer inductance. In one embodiment, the capacitance module has a value selected such that the capacitance module compensates for the typical inductance value of the primary secondary winding for the frequency of the AC supply current.

Alternatively, the inductance value measurement circuit is implemented to continuously measure the transformer inductance. The inductance value measuring circuit can measure the inductance value generated by inducting a small current passing through the transformer and having a frequency different from that of the wire current. By measuring only the current/voltage relationship at this frequency, the induction can be determined and compensated by adjusting the set point.

In one embodiment, the transfer pickup circuit includes an additional capacitor module connected in parallel with the switch mode converter.

During use, the additional capacitor module can be used as a buffer capacitor module to avoid or reduce filter surges of the DC power output by the switch mode converter. Accordingly, the output voltage of the switched mode converter is beneficial to avoid becoming a series or a rise and fall, and is closer to a straight line, like a real direct current, or the rise and fall can be reduced.

According to a second aspect, the present invention provides a node for the transfer pickup circuit of the first aspect.

The node of the second aspect of the present invention has at least the advantages associated with the transfer pickup circuit of the first aspect of the present invention described above.

The various viewpoints and features described and shown in the specification can be applied individually where possible. These individual parts, particularly the ideas and features described in the dependent claims, can be the subject of a divided patent application.

FIG. 1 shows a block diagram of a transfer pickup circuit 1 . The transfer pickup circuit 1 is configured to pick up energy inductively from a conductor 2 . Conductor 2 is connected to a base station, not shown, which is configured to provide an AC supply current, wherein the AC supply current is supplied to conductor 2 . The wires 2 carry the AC supply current to one or more regions, where the AC supply current can be inductively picked up from the wires by transferring the pickup circuit 1 .

The transfer pickup circuit 1 includes the main secondary winding 3 of a transformer. The primary secondary winding 3 is used to transfer the inductive coupling between the pickup circuit 1 to the conductor 2 . The first winding 4 of the transformer is schematically indicated on the wire 2 for clarity. The transfer pickup circuit 1 further includes a capacitor module 5 , and the capacitor module 5 is connected in parallel with the main secondary winding 3 . During use, the primary secondary winding 3 picks up energy from the wire 2 inductively.

Although not shown, in another embodiment, the transfer pick-up circuit has a ferrite element that can be placed near the wire 2 . The primary secondary winding 3 of the transformer may be placed at least partially around the ferrite element, so that the ferrite element forms the core of a transformer.

A switched mode converter, in particular a four quadrant power converter 6 , is connected in series with the main secondary winding 3 . The four-quadrant power converter 6 is configured to receive the picked-up energy (wherein the picked-up energy may be an alternating current (AC)) from the primary secondary winding 3 and convert the picked-up alternating current to a direct current Current (direct current, DC). DC current can be supplied from the four-quadrant power converter 6 terminals to a load (not shown), such as a light bulb that can be switched on or off according to demand.

As shown in FIG. 1 , an additional capacitor module 7 is connected in parallel with the four-quadrant power converter 6 . The extra capacitor module 7 is used as a buffer capacitor module 7 for reducing filter surges of the DC current output by the four-quadrant power converter 6 . Therefore, the rise and fall of the output voltage of the four-quadrant power converter 6 is reduced, so that the output voltage is closer to a straight line, like a real DC current.

The transfer pick-up circuit 1 further has a current clamp inductor 8 which is clamped to the wire 2 , as shown in FIG. 1 . The current clamp inductor 8 is in electrical communication with the four-quadrant power converter 6 so that the induced current of the AC supply current can be communicated to the four-quadrant power converter 6 .

， 其中R表示節點的電阻值，P表示節點的能量需求，且I表示交流供應電流的振幅。電抗部分的最佳值取決於下列參數： 節點的能量要求(power requirement)、節點在導線上的特定位置、導線特性及導線電流。導線電流是最重要的參數，且可用於決定節點的電抗部分的最佳值。電流鉗感應器8感應導線電流，並將感應到的導線電流傳輸至四象限功率轉換器6。四象限功率轉換器6將其輸入端的電抗調整至一預設的設定點，其中預設的設定點被決定以產生從基站至移轉拾取電路1(較佳為配置於多個節點上的多個移轉拾取電路1)的能量的最佳能量移轉。 In use, the transfer pick-up circuit 1 is used to inductively pick up energy from the wire 2 to power a load, which may be, for example, a switchable light bulb. In the following, the combination of the transfer pickup circuit 1 and the switchable bulb is referred to as a node. The efficiency of the energy transfer between the conductor 2 and the node depends in particular on the impedance of the node. The impedance of the node includes a resistive part and a reactive part. The resistive part is defined as the node's power demand and the amplitude of the AC supply current, which corresponds to the following equations:

, where R is the resistance value of the node, P is the energy demand of the node, and I is the amplitude of the AC supply current. The optimum value of the reactive part depends on the following parameters: the power requirement of the node, the specific location of the node on the wire, the wire characteristics, and the wire current. The wire current is the most important parameter and can be used to determine the optimum value for the reactive portion of the node. The current clamp inductor 8 senses the wire current and transmits the sensed wire current to the four-quadrant power converter 6 . The four-quadrant power converter 6 adjusts the reactance at its input to a preset set point, wherein the preset set point is determined to generate a transfer pick-up circuit 1 (preferably multiple units arranged on multiple nodes) from the base station The optimal energy transfer of the energy of the transfer pick-up circuit 1).

Since the reactive portion of the node is adjusted to a desired set point, the transfer pickup circuit 1 is able to adjust the reactive portion of the node to an optimum value for optimal energy transfer. Furthermore, the transfer pickup circuit 1 can compensate for manufacturing tolerances of its electrical components.

FIG. 2 shows a block diagram of the transfer pickup circuit 101 according to the first embodiment of the present invention. The transfer pickup circuit 101 also includes the primary secondary winding 103 of a transformer. The primary secondary winding 103 acts to transfer the inductive coupling of the pickup circuit 101 to the wire 102 . The first winding 104 of the transformer is schematically indicated in the conductor 102 for clarity. The transfer pickup circuit 101 further includes a capacitor module 105 , and the capacitor module 105 is connected in parallel with the main secondary winding 103 . During use, the primary secondary winding 103 picks up energy inductively from the wire 102 .

The value of the capacitance module 105 is chosen to compensate for the typical inductance value of the primary secondary winding 103 for the frequency (eg, 20 kHz) used for the AC supply current.

The transfer pickup circuit 101 also includes a four-quadrant power converter. In this embodiment, the four-quadrant power converter is formed by an H-bridge topology 106 and is connected in series with the main secondary winding 103 catch. The H-bridge circuit topology 106 is configured to receive picked-up energy (eg, an AC power source) from the primary secondary winding 103, and to convert the picked-up AC current to a DC current. DC current can be supplied from the H-bridge circuit topology 106 to a load 110, such as a switchable light bulb that can be turned on or off as needed. During use, the H-bridge circuit topology 106 operates according to a switching frequency that is at least 10 times higher than the frequency of the AC supply current. For example, when the frequency of the AC supply current is 20 kHz (Kilo Hertz, kHz), the switching frequency is 500 kHz.

As shown in FIG. 2, the H-bridge circuit topology 106 includes a switching coil 111. The switching coil 111 and the capacitor module 105 together form a low-pass filter, so that the frequency component ( frequency components) pass and block higher switching frequencies. The H-bridge circuit topology 106 further includes four switching elements Q1, Q2, Q3, and Q4, which are configured to switch to set the desired voltage. As shown in FIG. 2, the H-bridge circuit topology 106 has an H-bridge driver 112, schematically represented by two blocks, for driving according to a pulse width modulation (PWM) duty cycle signal. Four switching elements Q1, Q2, Q3 and Q4. The H-bridge circuit topology 106 also includes an overvoltage protection mechanism 113 for protecting the H-bridge driver 112 from overvoltage.

As shown in FIG. 2, the transfer pickup circuit 101 includes a controller 109, particularly a digital signal processor (DSP). The controller 109 is configured to generate a PWM duty cycle signal and to provide the generated PWM duty cycle signal to the H-bridge circuit topology 106, which will be described in detail below.

The transfer pickup circuit 101 also includes a current clamp inductor 108 for sensing the current of the AC supply current. Current clamp inductor 108 includes an inductive secondary winding 120 of an inductive transformer, wherein inductive secondary winding 121 is shown schematically in wire 102 . A sensing capacitor module 122 and a sensing resistor 123 are connected in parallel with the sensing secondary winding 120 . In addition, a node primary current sensing circuit 124 is connected in series with the sensing secondary winding 120 . The node main current sense circuit 124 includes a node current sense comparator 125 having a positive input terminal and a negative input terminal, as shown in FIG. 2 . The node current sense comparator 125 can be configured to amplify the difference between the positive input and the negative input, and provide the amplified difference as a wire current sense output signal 126 to the controller 109 .

As shown in FIG. 2 , the primary secondary winding 103 and the inductive secondary winding 120 can be provided in a single inductive clamp 127 so that the primary secondary winding 103 and the inductive secondary winding 120 can be clamped to the conductor 102 at once.

The transfer pickup circuit 101 further includes a node voltage sensing circuit 130 connected in parallel with the main secondary winding 103 . The node voltage sensing circuit 130 has a voltage sensing comparator 132, and the voltage sensing comparator 132 has a positive input terminal and a negative input terminal. The voltage sensing comparator 131 can be configured to amplify the difference between the positive input terminal and the negative input terminal, and provide the amplified difference as a node voltage sensing output signal 132 to the controller 109 .

In addition, the transfer pickup circuit 101 further includes an H-bridge current sensing circuit 135 which is connected in series with the main secondary winding 103 via another sensing resistor 138 . The H-bridge current sensing circuit 135 has an H-bridge current sensing comparator 136, and the H-bridge current sensing comparator 136 has a positive input terminal and a negative input terminal. The H-bridge current sense comparator 136 can be configured to amplify the difference between the positive input and the negative input, and provide the amplified difference as an H-bridge current sense output signal 137 to the controller 109 .

As shown in FIG. 2 , the controller 109 also receives an application voltage Vapp as the voltage on the load 110 , such as the signal 140 .

FIG. 3 shows a code block diagram of a digital signal processor (DSP). The controller 109 receives the wire current sensing output signal 126 , the voltage sensing output signal 132 and the signal 140 of the applied voltage Vapp as inputs. As shown in the block diagram, the H-bridge current sense output signal 137 is not received by the controller 109 .

As shown in FIG. 3 , the signal 140 of the applied voltage Vapp is received by a first AC-DC converter (AD-convertor, ADC) 150 to convert the signal 140 of the applied voltage Vapp. When the signal 140 of the applied voltage Vapp is converted, the signal 140 of the applied voltage Vapp is sampled at a first sampling frequency, wherein the first sampling frequency is lower than the switching frequency of the H-bridge circuit topology 106 . For example, the first sampling frequency is about 50 kHz. Next, the sampled signal 140 of the application voltage Vapp is sent to an application voltage controller 151 and a divider 152 to generate a duty cycle (DTC) for instructing the H-bridge circuit topology 106 to generate an average voltage The signal, represented by Vapp (VHB_in_V _app ), is the output between the source of the switching element Q1 and the source of the switching element Q2. In short, the application voltage controller 151 adjusts the resistance value of the node on the wire 102 to a value that achieves the desired application voltage.

The applied voltage controller 151, also known as a proportional integral (PI) controller, has a second input as the applied voltage setpoint 152, eg, 25V. The sampled signal of the applied voltage Vapp and the applied voltage set point 152 are input to a first subtractor 153, and the first subtractor 153 subtracts the applied voltage set point 152 from the sampled signal of the applied voltage Vapp to generate a Apply the voltage difference signal. The applied voltage difference signal is separated and input to a first amplifier 154 and a second amplifier 155 . The first amplifier 154 amplifies the applied voltage difference signal with a first gain parameter Kp _X , and the second amplifier 155 amplifies the applied voltage difference signal with a second gain parameter Ki _X. The first gain parameter Kp _X and the second gain parameter Ki _X are adjusted to provide a desired step response. The output of the first amplifier 154 is then sent to a first summer 158 .

The output of the second amplifier 155 is input to a second adder 156, which has a second adder output. The second adder output is passed to a first unit delay 157 for holding and delaying the second adder output, in this example for 1 iteration. The first unit delay output downstream of the first unit delay 157 is input to the first adder 158 and the second adder 156 as the other side of the first adder 158 and the second adder 156 . an input. The second adder 156 and the first unit delay 157 form an integrator. The output of the first adder 158 and the associated applied voltage controller 151 will indicate the resistance value formed by the transfer pickup circuit 1 or the resistance value of the node on the wire 2 . The indicated resistance value is input to a first multiplier 159 .

The node current sense output signal 126 is received by a second AC to DC converter 160 for converting the node current sense output signal 126 . When the node current sense output signal 126 is switched, the node current sense output signal 126 is sampled at a second sampling frequency, wherein the second sampling frequency is equal to or substantially equal to the switching frequency of the H-bridge circuit topology 106 . For example, the second sampling frequency is about 500 kHz. Next, the sampled wire current sense output signal is sent to a power analyzer 161 , a second unit delay 162 and a third unit delay 163 .

The second unit delay 162 inverts and delays the sampled wire current sense output signal at approximately one quarter of the wire current frequency and transmits the delayed sampled wire current sense output signal to a second multiplier 164. Correspondingly, the third unit delay 163 delays the sampled wire current sensing output signal by a period of the wire current frequency, and transmits the delayed sampled wire current sensing output signal to a first multiplier 159, wherein The delayed sampled wire current sense output signal is multiplied by the determined wire resistance value. The output of the first multiplier 159 is passed to a final adder 165 .

The voltage-sensing output signal 132 is received by a third AC-DC converter 166 for converting the voltage-sensing output signal 132 . When the voltage sensing output signal 132 is converted, the voltage sensing output signal 132 is sampled at the second sampling frequency. Next, the sampled voltage sensing output signal is sent to the power analyzer 161 . The power analyzer 161 is configured to measure the real power P by integrating the product of the sampled node voltage sensing output signal with the sampled wire current sensing output signal, and by integrating the sampled node voltage sensing output signal The product of , and a sampled wire current sense output signal offset by 90 degrees are integrated to measure the reactive power Q. The measured real power P is sent from the power analyzer 161 to a set point generator 167 , and the measured imaginary power Q is sent from the power analyzer 161 to an imaginary power controller 168 .

The set point generator 167 is configured to generate an imaginary power preset point, which is a function of the real power P measured. The resulting imaginary power preset point is sent to the imaginary power controller 168 .

The imaginary power controller 168 , also referred to as a PI controller, corresponds to the applied voltage controller 151 . Briefly, the imaginary power controller 168 controls the reactance of the node on the conductor 102 to a value that achieves the optimum node imaginary power. At the input, the imaginary power controller 168 receives the measured imaginary power Q and the resulting imaginary power setpoint as inputs, which are received by a second subtractor 169 which The generated imaginary power setpoint is subtracted from the measured imaginary power Q to form an imaginary power difference signal. The imaginary power difference signal is separated and input to a third amplifier 170 and a fourth amplifier 171 . The third amplifier 170 amplifies the imaginary power difference signal with the first gain parameter Kp _X , and the fourth amplifier 171 amplifies the imaginary power difference signal with the second gain parameter Ki _X. The first gain parameter Kp _X and the second gain parameter Ki _X are adjusted to provide the desired step response.

The fourth amplifier 171 is sent to a fourth adder 173, which has a fourth adder output. The fourth adder output is passed to a fourth unit delay 174 to hold and delay the fourth adder output for 1 iteration in this example. The fourth unit delay output of the fourth unit delay 174 is input downstream to the third adder 172 and the fourth adder 173 as the input of the third adder 172 and the fourth adder 173 . The fourth adder and the fourth unit delay 174 form an integrator. The output of the third adder 172 and the output of the imaginary power controller 168 is a compensation value for compensating for the manufacturing tolerance of the transfer pickup circuit 1 or the node. The determined compensation value is sent to the second multiplier 164, and the determined compensation value is multiplied by the sampled wire current sensing signal.

The output of the first multiplier 159 is a first sine wave _UR , also called the real node voltage component, which is in phase with the conductor current, and the output of the second multiplier 164 is a first sine wave _UR . The second sine wave U _{X ,} also known as the imaginary voltage component, leads the phase of the wire current by 90 degrees. The first sine wave _UR and the second sine wave _{UX are sent to the final adder 165, and the first sine wave UR and the second sine wave UX are added to generate a summation signal Uout , which is} Volts (VHB_in_V) represents the demanded average voltage produced by the H-bridge circuit topology 106 . The summed signal _Uout is sent to the divider 152, and the summed signal _Uout is divided by the applied voltage _Vapp to generate a DTC signal having a value between -1 and 1. The DTC signal is sent to a PWM generator 175, and the PWM generator 175 generates the PWM switching signal based on the received DTC signal. For example, when the value of the DTC signal is 1, it informs the PWM generator 175 that the H-bridge circuit topology 106 needs to generate an average voltage equal to the application voltage _Vapp , and when the value of the DTC signal is -1, it informs PWM generator 175 The H-bridge circuit topology 106 needs to generate an average voltage equal to the negative applied voltage -V _app . The PWM generator 175 generates a PWM schedule based on the DTC signal, and the PWM schedule is transmitted to the H-bridge driver 112 . The H-bridge driver 112 drives the H-bridge circuit topology based on the received PWM schedule, thereby controlling the voltages of the nodes, and thus the impedance, or at least the reactive portion thereof. By controlling the voltages of the nodes, the transfer of energy from the base station via the conductor 102 to the transfer pickup circuit 101 can be optimized.

It should be noted that the above descriptions are intended to illustrate the operation of the preferred embodiments, and do not mean that the protection scope of the present invention is limited to these descriptions. According to the foregoing content, those skilled in the art can appreciate many changes, and these changes will still be included in the protection scope of the present invention.

1: Transfer pickup circuit 2: Wire 3: Main secondary winding 4: The first winding 5: Capacitor module 6: Four-quadrant power converter 7: Additional capacitor module 8: Current clamp inductor 101: Transfer Pickup Circuit 102: Wire 103: Primary secondary winding 104: First winding 105: Capacitor module 106: H-bridge circuit topology 107: Additional Capacitor 108: Current clamp sensor 109: Controller 110: load 111: switch coil 112: H-bridge driver 113: Overvoltage protection mechanism 120: Inductive secondary winding 121: Induction Secondary Winding 122: Capacitor module 123: Induction resistance 124: Node main current sensing circuit 125: node current sense comparator 126: Wire current sensing output signal 127:Single induction clamp 130: Node Voltage Sensing Circuit 131: Voltage sensing comparator 132: Voltage sensing comparator 135: H bridge current sensing circuit 136: H-bridge current sense comparator 137: H bridge current sensing output signal 138: Another sense resistor 140:Signal Q1: Switching requirements Q2: Switching requirements Q3: Switching requirements Q4: Switching requirements 150: First AC-DC Converter 151: Application Voltage Controller 152: divider 153: First Subtractor 154: Amplifier 155: Second amplifier 156: Second adder 157: First Unit Delay 158: First adder 159: First Multiplier 160: Second AC-DC Converter 161: Power Analyzer 162: Second unit delay 163: Third Unit Delay 164: Second Multiplier 165: Final Adder 166: Third AC-DC Converter 167: Setpoint generator 168: Imaginary Power Controller 169: Second Subtractor 170: Third Amplifier 171: Fourth Amplifier 172: Third Adder 173: Fourth Adder 174: Fourth Unit Delay 175: PWM generator

The invention will be described on the basis of the examples shown in the drawings: 1 shows a block diagram of a transfer pickup circuit inductively coupled to a wire according to a first embodiment of the present invention; FIG. 2 shows a block diagram of a transfer pickup circuit inductively coupled to wires and having a controller according to another embodiment of the present invention; and FIG. 3 shows a block diagram of the DSP code of the controller of FIG. 2 .

1: Transfer pickup circuit

2: Wire

3: Main secondary winding

4: The first winding

5: Capacitor module

6: Four-quadrant power converter

7: Additional capacitor module

8: Current clamp inductor

Claims (19)

A transfer pickup circuit for inductively picking up energy from a wire carrying an AC supply current having a wire current frequency, wherein the transfer pickup circuit comprises: A main secondary winding of a transformer for providing an inductive coupling of the wire and a capacitor module in parallel with the main secondary winding; a switched mode converter in series with the primary secondary winding and configured to convert a pick-up alternating current to a direct current (DC); an inductor configured to sense at least one property of the AC supply current carried by the wire, and/or to sense at least one property of the pickup AC current, wherein the inductor is in electrical communication with the switch mode converter, wherein the switch mode converter is further configured to adjust a reactance of the input end of the switch mode converter to a preset set point based on the at least one property of the sensed AC supply current, Wherein the transfer pickup circuit further includes a controller, the controller is configured to control the switch mode converter, based on the sensed at least one property of the AC supply current, a reactance of the input end of the switch mode converter adjust to a preset set point, where the controller has: an applied voltage controller configured to adjust the resistance value of the transfer pickup circuit on the wire to a predetermined applied voltage value; and An imaginary power controller configured to adjust the reactance of the transfer pickup circuit to a predetermined reactance power value. The transfer pickup circuit of claim 1, wherein the inductor is configured to be selectively coupled to the wire. The transfer pickup circuit of claim 1 or 2, wherein the inductor is configured to sense the wire current of the AC supply current carried by the wire. The transfer pick-up circuit of claim 3, wherein the inductor uses a current sensing method during use, and the current sensing method is selected from a group including electrical group value sensing, magnetic field sensing, and inductance value induction. The transfer pickup circuit of any one of claims 1 to 4, wherein the inductor comprises an inductive secondary winding of a transformer inductively coupled to the wire. The transfer pickup circuit of claim 2, wherein the inductor is configured to sense the conductor voltage of the AC supply current carried by the conductor, and/or to sense a voltage of the pickup AC current. The transfer pickup circuit of any one of claims 1 to 6, wherein the transfer pickup circuit is further provided with an additional inductor for sensing at least one property of the AC supply current transmitted by the wire, and/ Or induction should pick up at least one property of the alternating current. The transfer pickup circuit of claim 7, wherein the additional inductor comprises a node voltage sensing circuit, connected in parallel with the primary secondary winding, and configured to sense the voltage of the energy picked up in the conductor, and /or the additional sensor includes an applied voltage sensing circuit, connected in parallel with an output of the transfer pickup circuit, and configured to sense the applied voltage. The transfer pickup circuit of claim 7 or 8, wherein the additional sensor, the node voltage sensing circuit, and/or the application voltage sensing circuit are in data communication with the controller. The transfer pickup circuit of any one of claims 1 to 9, wherein: - the application voltage controller receives an application voltage set point; - the imaginary power controller receives an imaginary power setpoint. The transfer pickup circuit of claim 10, wherein the controller is configured to multiply the predetermined applied voltage by a wire current, wherein the wire current is preferably one cycle later than the wire current frequency to generate a real-part shift pick-up circuit voltage component, The controller is further configured to multiply the preset imaginary power value by an inverting conductor current, wherein the inverting conductor current is preferably a quarter cycle later than the conductor current frequency, thereby generating an imaginary partial voltage components, and Wherein, the controller is configured to sum the real part shift pickup circuit voltage component and the imaginary part voltage component to generate a preset output voltage. The transfer pick-up circuit of claim 11, wherein the controller is further configured to divide the predetermined output voltage by the applied voltage, wherein the applied voltage is determined by the applied voltage sensing circuit to generate an operation the duty cycle (DTC) signal, and The controller includes a pulse width modulation (PWM) generator configured to generate one or more PWM switching signals based on the DTC signal, wherein the one or more PWM switching signals are used to generate The average voltage informs the four-quadrant power converter. The transfer pickup circuit of any one of claims 1 to 12, wherein the controller includes a power analyzer and a setpoint generator, wherein the power analyzer is configured to use the energy picked up from the wire The product of the induced voltage is integrated with the induced wire current to measure the real part power, and for integrating the product of the voltage by the energy picked up from the wire with an induced wire current offset by 90 degrees, to measure the imaginary part power, wherein the measured real part power is transmitted from the power analyzer to a set point generator configured to generate as the measured real part power A setpoint of a function of , wherein the generated setpoint is provided to the imaginary power controller, and the measured imaginary power is communicated from the power analyzer to the imaginary power controller. The transfer pickup circuit of any one of claims 1 to 13, wherein the switch mode converter is selected from a group comprising a quarter power converter, an H-bridge circuit topology, and a half Bridge extension. The transfer pickup circuit as claimed in any one of claims 1 to 14, wherein the switching mode converter comprises a switching coil, which forms a low-pass filter together with the capacitor module 105 so as to allow the AC supply current to have a Frequencies corresponding substantially to frequencies are passed and higher switching frequencies are blocked. The transfer pickup circuit of any one of claims 1 to 15, further comprising a transformer induction compensation component configured to compensate for the transformer induction. The transfer pickup circuit of claim 16, wherein the capacitance module has a value selected to compensate for the typical inductance value of the primary secondary winding for the frequency of the AC supply current. The transfer pickup circuit according to any one of claims 1 to 17, further comprising an additional capacitor module connected in parallel with the switching mode converter. A node for a transfer pickup circuit as claimed in any one of claims 1 to 18.

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