200941830 九、發明說明： 【發明所屬之技術領域】 本發明係有關於一種具全向性輕 線，尤其是指-種可同時抑制兩個頻帶之十天 線，其提供了超寬頻的操作頻帶，以及 操作，且完全不影響其全向性輕射，=頁▼的τ拒 訊應用，相當適合應用於橋接點天線及超^頻夕系^線通 【先前技術】 ' ^200941830 IX. Description of the Invention: [Technical Field] The present invention relates to an omnidirectional light wire, and more particularly to a ten-antenna capable of simultaneously suppressing two frequency bands, which provides an ultra-wideband operating frequency band. And operation, and does not affect its omnidirectional light shot, = page ▼ of the τ rejection application, quite suitable for use in bridge point antennas and ultra-frequency 夕 system ^ line pass [previous technology] ' ^
現今無線通訊在生活中已是不可或缺的如pDA 記型電腦、3G手機...為達到無線傳輸的需求，生: 可見的通訊頻段已達多頻甚至寬頻’而要增加通訊頻段就 必須增加天線的數目或以寬頻天線來涵蓋多頻操 段。隨著通訊頻^的増加’訊號干擾的問題亦如影隨形的 產生；例如：超寬頻系統之操作頻段為3.卜1〇 6GHz，然 而此頻段會與無線區域網路（wireless Local奸二 Networks, WLAN)的操作頻段5.2〜5. 8GHz相重疊，因 會產生訊號干擾等問題。於是在寬頻天線設計中，必須 會與無線區域網路之操作頻段重疊的頻帶加以抑制；j專統 抑制頻帶的方法大多是在寬頻天線加入濾波器，藉濾涔 之設置來抑制掉不需要的操作頻段，然而此舉無疑^掸二 成本。有鑑於此，近年來開始有人研究寬頻並兼具Y 帶的天線設計（以下簡稱帶拒天線）來達到多頻操作p 以節省資源與降低成本的目的。 ' ^ 現階段之帶拒天線的設計在不增加寬頻通 電路設計複雜度以及整體製作成本的前提下，可藉由、之 線輻射主體嵌入適當共振結構來產生可控制的^制頻= 200941830 操作，達成有效抑制超寬頻天線訊號干擾問題。常 拒天線可分為在平面單極天線上嵌人—個或二 槽孔或槽縫、在十字形單極天線上欲人對_ ^ ❿ 縫；前者雖可藉由被入槽孔或槽縫的數量來達到;= 帶或雙頻帶’然而在設計上需注意這兩個帶拒機制 互相干擾或耗合的問題產生，而導致無法有效的達 制頻帶的操作，並且受限於平面結構之特性，高頻p 因漣波效應易造成非全向性輻射。後者雖在高拉 良好的全向性輻射，但•其本身的天線架構 孔的部份等於單-金屬片單極天線的二分之—，心2 ^見的十字形單極帶拒天線之研究，多是敌人―個對= =槽孔或槽縫，來達成單頻帶拒之目的。在通訊科技^ 敷=進步之今日，可見的是天線僅有單頻帶拒機制將不 【發明内容】 7纟明人即是H於上述現有之寬頻天線在實際 由：失’於是乃-本孜孜不倦之精神，並藉 善，並據此研創出本發明。 人從 的，m全向性輻射之交叉單極天線的其1 作皆能保持良好的全向:輻射42 應m 全向性輕射特性之橋接點天線上。田適口 的，係在提供之―具種全4=之交又單極天線的其 、帶中的低頻抑制頻蓋::之天線，其中在雙抑制 貝贡已/函盍無線區域網路之頻段，可應 200941830 用在有訊號千擾問題的超寬頻系统中。 本發明之具全向性輕射之交又單極天線的其三目 的’係在提供-種超寬頻的操作頻帶與多抑制頻帶的帶拒 操作之天m全不影響其全向性輕射，可涵蓋更多的 無線通訊應用，相當適合應用於橋接點天線及超寬頻系統 等。 本發明之具全向性輻射之交叉單極天線的目的與功 效係由以下之技術所實現： ΟNowadays, wireless communication is indispensable in life, such as pDA recording computer, 3G mobile phone... In order to meet the demand of wireless transmission, the visible communication frequency band has reached multi-frequency or even broadband] and it is necessary to increase the communication frequency band. Increase the number of antennas or cover multiple frequency segments with wideband antennas. As the communication frequency increases, the problem of signal interference also occurs. For example, the operating frequency band of the ultra-wideband system is 3.Bu 1 〇 6 GHz, but this band will be associated with the wireless local area network (wireless local network, WLAN). The operating frequency band 5.2~5. 8GHz overlaps, causing problems such as signal interference. Therefore, in the design of the wideband antenna, it is necessary to suppress the frequency band overlapping with the operating frequency band of the wireless local area network; the method of suppressing the frequency band by the x special system is mostly to add a filter to the broadband antenna, and the setting of the filter is used to suppress the unnecessary Operating the frequency band, however, this move is undoubtedly the second cost. In view of this, in recent years, people have studied the broadband design and the Y-band antenna design (hereinafter referred to as the rejection antenna) to achieve multi-frequency operation p to save resources and reduce costs. ' ^ At present, the design of the rejection antenna can generate a controllable frequency by embedding the appropriate resonant structure with the radiation body without increasing the complexity of the design of the wide-band circuit and the overall production cost = 200941830 Operation To achieve effective suppression of ultra-wideband antenna signal interference problems. The repellent antenna can be divided into a single- or two-slot or slot on a planar monopole antenna, and a _ ^ sew on a cross-shaped monopole antenna; the former can be inserted into the slot or slot. The number of seams is reached; = band or dual band ' However, it is necessary to pay attention to the problem that the two rejection mechanisms interfere with each other or to be consumable, resulting in an inefficient operation of the frequency band and limited by the planar structure. The characteristic, high frequency p is easy to cause non-omnidirectional radiation due to the chopping effect. Although the latter has good omnidirectional radiation in the high-lying, but the part of its own antenna structure hole is equal to the dichotomy of the single-metal monopole antenna, the cross-shaped monopole-rejected antenna seen in the heart 2 ^ Most of the enemy - a pair = = slot or slot, to achieve the purpose of single-band rejection. In the communication technology ^ application = progress today, it can be seen that the antenna only has a single-band rejection mechanism will not [invention content] 7 纟明人 is H in the above-mentioned existing broadband antenna in the actual: loss of 'is is is - this is not tireless The spirit of the spirit, and the use of good, and based on this research and development of the invention. The one-way cross-monopole antenna of the omnidirectional radiation can maintain good omnidirectional: the radiation 42 should be on the omnidirectional light-radiation characteristics of the bridge antenna. Tian Shikou's, in the provision of a full 4 = intersection and monopole antenna, the band's low-frequency suppression frequency cover:: the antenna, which in the double suppression of the Begong has / function wireless local area network The frequency band can be used in the ultra-wideband system with signal interference problem in accordance with 200941830. The three-purpose of the omnidirectional light-emitting and monopole antenna of the present invention does not affect the omnidirectional light radiation in the operation band of the ultra-wideband operating band and the multi-suppression band. It can cover more wireless communication applications, and is quite suitable for use in bridge point antennas and ultra-wideband systems. The purpose and function of the cross-monopole antenna with omnidirectional radiation of the present invention is achieved by the following techniques:
該具全向性㈣之交又單極天線係在—接地金屬面 中央設穿孔’崎應穿設接额裝m，該天線主體 為兩矩形金屬片交叉重疊成立體十字形狀，且於交叉後所 形成之四個諸部的下方各裁切—角，使其下緣呈由外往 内向下斜設’並在各片體部上嵌人h形槽孔，使天線主體 具有帶拒功能，將；ί；需要的頻帶5 25GHz〜5 85GHz加以滤 ^另外還有-高絲拒舰可操作；據此，俾令該天線 ，有抑制雙頻之能力，並且可改善主體結構在高頻時所產 之漣波效應，進而達成全方向性的效果。 【實施方式】 為令本發明所運用之技術内容、發明目的及其成 功效有更完整料楚的揭露，肢下詳細㈣之、=之 併參閱所揭之圖式及圖號： 靖一 首先，第一圖所示者，係本發明之具全向性 又單極天線的立體結構示意圖；第二圖為本發明且之交 f生輻射之交叉單極天線的前視結構*意圖。 ’、全向 面 ⑴及該-具天全線 == 200941830 該接地金屬面（1)係採用厚度為0. lmm、長、寬 120mm><120mm為的金屬銅片，於該接地金屬面中央設 一穿孔（11) ’並使用一高頻50QSMA之接頭（12)自該穿孔 (11)下方饋入； 該天線主體（2)，係由二厚度同為〇.1 _、長、寬為 30mmx30匪的矩形金屬銅片（21)構成，該二金屬銅片（21) 係彼此交叉扣合組裝而形成立體十字形狀，並據此區分成 四片體部（21a)〜（21d)，各片體部（21a)〜（21d)的下方各裁 參 切一角’使其下緣（211a)~(211d)為由外往内向下斜設， 且在各片體部（21a)〜（21d)上設一 h形槽孔 (212a)〜（212d) ’同時相對應的片體部（21a)與片體部（21c) 之h形槽孔（212a)、（212c)，以及相對應的片體部（21b) 與片體部（21d)上之h形槽孔（212b)、（212d)亦呈相對應 設置；此外’該天線主體（2)係垂直接設於接地金屬面 之接頭（12)，並與接地金屬面（1)之間距為g=i_。 據此，在十字形天線主體（2)的各片體部（2ia)〜（2id) φ 上設置h形槽孔（212a)〜（212d)，可達到抑制雙頻帶之功 能。該h形槽孔（212a)〜（212d)共振長度約為〇.5λ，λ是 真空中的導波波長。而第一抑制頻帶（低頻）之共振長度為 2L2+W2、第二抑制頻帶（高頻）之共振長度則為L1 ;其中 L1為h形槽孔（212a)〜（212d)高度，L2為h形槽孔 (212a)〜（212d)下半段長度，S1為h形槽孔（212a)〜（212d) 對應十字形交叉線的距離，S2為h形槽孔（212a)〜（212d) 與片體部（21a)〜（21d)頂端之距離，W1為h形槽孔 (212a)〜（212d)寬度，W2為h形槽孔（212a)〜（212d)内寬 度。 8 200941830 第二圖為本發明之具全向性輻射之交又 返回損失頻率響應圖；其中，粗線為實驗量擔天線的 為Ansoft模擬軟體HFSS分析結果、雙細線=、細線 槽孔的十字形單極天線之量測數據。由圖可知=置h形 數據是吻合的，且抑制頻帶在4. 85GHz~6 =模擬 7. 13GHz〜7. 43GHz，其中第-抑制頻帶之返回 z與 傷 鲁 果約達4.3dB，並可完整涵蓋WUN之操作頻段貝抑制效 第四圖為本發明之具全向性輻射之交又 3.2GHz、6. 15GHz、10.4GHz時之遠場輕射場型量=線在 從圖可見其雖然設置h形槽孔，但仍擁有非常良姅、、、Q果。 性輻射特性。第五圖為本發明之具全向性輻射^々的=向 天線在X-Z及y-z平面之增益量測結果，由圖中單極 到，在抑制頻帶之處，增益會有明顯的下降，除扣σ凊楚看 其他頻段之增益變化量皆維持在3dBi以内。、15制頰段， 之 經由以上的實施說明，可知本發明之具全向 父叉單極天線至少具有如下所列之各項優點：°轉射 1. 本發明之具全向性輻射之交叉單極天線除具 阻抗頻寬之外（超過l3GHz)，因在天線主體/上於交寬的 以抑制掉不需要之頻段，因此不需再設置原本2孔， 所需之濾波器，而可降低成本。 頻天線 2. 本發明之具全向性輻射之交叉單極天線具有〜概 制，且能達到雙頻帶拒操作，相對而言，可带柜機 波器之成本。 $二個濾 3. ^發明之具全向性輻射之交叉單極天線與本發曰 月il申清之可抑制雙頻帶之立體十字型半梅圓月人先 利案相比較，本發明之天線擁有更全向性的輕^線專 射特性， 9 200941830 / 且製作方面亦較簡單。 4.本發明之具全向性輻射之交叉單極天線因具有更寬的 操作頻帶，多抑制頻帶的帶拒操作，且完全不影響其全 向性輻射，可涵蓋更多的無線通訊應用，適合應用於橋 接點天線及超寬頻系統。 綜上所述，本發明實施例確能達到所預期之使用功 效，又其所揭露之具體構造，不僅未曾見諸於同類產品 中，亦未曾公開於申請前，誠已完全符合專利法之規定與 φ 要求，爰依法提出發明專利之申請，懇請惠予審查，並賜 准專利，則實感德便。The omnidirectional (four) intersection and the monopole antenna are provided with a perforation in the center of the grounded metal surface, and the antenna body is formed by the two rectangular metal pieces overlapping and forming a body cross shape, and after the intersection The undercuts of the four formed portions are cut-angled so that the lower edge thereof is inclined downwardly from the outside to the inside and the h-shaped slot is embedded in each of the body portions, so that the antenna body has a function of rejecting. The filter band 5 25 GHz to 5 85 GHz is required to be filtered. In addition, the wire can be operated. According to this, the antenna has the capability of suppressing dual frequency and can improve the structure of the main body at high frequencies. The ripple effect of the production, and then achieve the omnidirectional effect. [Embodiment] In order to make the technical content, the purpose of the invention and its success effect of the present invention more fully disclosed, the details of the limbs (4), and the reference to the figure and the figure number: Jing Yi first The first figure shows a schematic view of the three-dimensional structure of the omnidirectional and monopole antenna of the present invention; the second figure is the front view structure of the cross-monopole antenna of the present invention. ', omnidirectional surface (1) and the - full line of the sky == 200941830 The grounded metal surface (1) is a metal copper sheet having a thickness of 0. lmm, length, width 120mm >< 120mm, in the center of the grounded metal surface A perforation (11)' is provided and fed from below the perforation (11) using a high frequency 50QSMA joint (12); the antenna body (2) is composed of two thicknesses of the same thickness 〇.1 _, length and width A 30mm x 30 inch rectangular metal copper piece (21) is formed by cross-locking and assembling to form a three-dimensional cross shape, and is thereby divided into four body parts (21a) to (21d), each of which is divided into four pieces (21a) to (21d). Each of the lower portions (211a) to (211d) of the lower portions (211a) to (211d) of the body portions (21a) to (21d) is inclined downward from the outside to the inside, and is in each of the body portions (21a) to (21d). An h-shaped slot (212a)~(212d)' is provided with the corresponding body portion (21a) and the h-shaped slot (212a), (212c) of the body portion (21c), and corresponding The body portion (21b) is also disposed corresponding to the h-shaped slots (212b) and (212d) on the body portion (21d); in addition, the antenna body (2) is a connector vertically connected to the grounded metal surface. (12), And the distance from the grounded metal surface (1) is g=i_. According to this, by providing the h-shaped slots (212a) to (212d) in the respective body portions (2ia) to (2id) φ of the cross-shaped antenna main body (2), the function of suppressing the dual band can be achieved. The h-shaped slots (212a) to (212d) have a resonance length of about 5.5λ, and λ is the wavelength of the guided wave in the vacuum. The resonance length of the first suppression band (low frequency) is 2L2+W2, and the resonance length of the second suppression band (high frequency) is L1; wherein L1 is the height of the h-shaped slot (212a)~(212d), and L2 is h The length of the lower half of the slotted holes (212a) to (212d), S1 is the distance of the h-shaped slot (212a)~(212d) corresponding to the cross-shaped cross line, and S2 is the h-shaped slot (212a)~(212d) and The distance between the top ends of the body portions (21a) to (21d), W1 is the width of the h-shaped slots (212a) to (212d), and W2 is the width of the h-shaped slots (212a) to (212d). 8 200941830 The second figure is the frequency response diagram of the omnidirectional radiation and the return loss of the invention; wherein the thick line is the experimental load antenna for the Ansoft simulation software HFSS analysis result, the double thin line =, the thin line slot ten Measurement data for a glyph monopole antenna. It can be seen from the figure that the h-shaped data is consistent, and the suppression band is 4.85 GHz~6 = analog 7.13 GHz~7. 43 GHz, wherein the return z of the first-suppression band is about 4.3 dB with the wounded fruit, and The fourth picture of the operating band of the WUN is fully covered. The fourth picture of the invention is the far field field type of the omnidirectional radiation at 3.2 GHz, 6.15 GHz, and 10.4 GHz = the line is visible from the figure. H-shaped slot, but still has very good,, and Q fruit. Sexual radiation characteristics. The fifth figure is the result of the gain measurement of the omnidirectional radiation of the invention in the XZ and yz planes of the invention. From the unipolar to the figure, the gain will be significantly reduced in the suppression band. The gain variation of other frequency bands is maintained within 3dBi. According to the above description, it can be seen that the omnidirectional parent fork monopole antenna of the present invention has at least the following advantages: °Transfer 1. The omnidirectional radiation cross of the present invention In addition to the impedance bandwidth (more than l3GHz), the monopole antenna is used in the antenna body/upper to widen the unwanted frequency band, so there is no need to set the original 2 holes, the required filter, but cut costs. Frequency Antenna 2. The cross-monopole antenna with omnidirectional radiation of the present invention has a profile and can achieve double-band rejection operation, and relatively, the cost of the cabinet. $Two filters 3. The invention of the cross-monopole antenna with omnidirectional radiation is compared with the three-dimensional cross-shaped half-meter round moonman case of the present invention. The antenna has a more omnidirectional light-wire feature, 9 200941830 / and the production is relatively simple. 4. The cross-monopole antenna with omnidirectional radiation of the present invention can cover more wireless communication applications because it has a wider operating frequency band, multiple rejection band rejection operations, and does not affect its omnidirectional radiation at all. Suitable for bridge point antennas and ultra-wideband systems. In summary, the embodiments of the present invention can achieve the expected use efficiency, and the specific structure disclosed therein has not been seen in similar products, nor has it been disclosed before the application, and has completely complied with the provisions of the Patent Law. With the requirement of φ, if you apply for an invention patent according to law, you are welcome to review it and grant a patent.
10 200941830 【圖式簡單說明】 第一圖：本發明之具全向性輻射之交叉單極天線的立 體結構示意圖 第二圖：本發明之具全向性輻射之交叉單極天線的前 視結構示意圖 第三圖：本發明之具全向性輻射之交叉單極天線之返 回損失量測與模擬結果 第四圖：本發明之具全向性輻射之交叉單極天線之遠 場幸畐射場型量測結果 第五圖：本發明之具全向性輻射之交叉單極天線在 (a)x-z及（b)y-z平面之增益量測結果 【主要元件符號說明】 (1) 接地金屬面（11) 穿孔 (12) 接頭 （2) 天線主體 (21) 金屬銅片 （21a)〜（21d) 片體部 (211a)〜（211d)下緣 （212a)〜（212d)槽孔 1110 200941830 [Simple description of the diagram] First diagram: Schematic diagram of the three-dimensional structure of the crossed monopole antenna with omnidirectional radiation of the present invention. Second diagram: the front view structure of the crossed monopole antenna with omnidirectional radiation of the present invention FIG. 3 is a diagram showing the return loss measurement and simulation result of the cross-monopole antenna with omnidirectional radiation according to the present invention. FIG. 4 is a far-field lucky field type of the cross-monopole antenna with omnidirectional radiation of the present invention. Measurement results Fifth figure: Gain measurement results of (a) xz and (b) yz planes of the cross-monopole antenna with omnidirectional radiation of the present invention [Description of main components] (1) Grounded metal surface (11) ) Perforation (12) Connector (2) Antenna body (21) Metal copper sheet (21a) ~ (21d) Sheet body portion (211a) ~ (211d) Lower edge (212a) ~ (212d) slot 11