200525924 九、發明說明： 【叙明所屬之技術領域】 本發明係關於一種決定經由第一及第二路徑而傳播的一 展頻#遽之相對時間延遲之方法，以及關於一種決定一展 ^員^口號之口口貝^日示之方法。本發明亦係關於一種用以決定 i由第一及第二路徑而傳播的一展頻信號之相對時間延遲 之裝置，以及關於包含此類裝置之產品。 【先前技術】 有許多使用展頻信號之無線電應用，其中需要決定經由 二或更多路徑而傳播的展頻信號之相對時間延遲。 此類應用之一範例係測距，其中從一收發器發射一展頻 無線電信號，於該收發n回收對所發射信號之反射，而在 延遲測里7G件中決定所發射信號與所接收信號之間延遲 的以便計算該反射表面之距離。在此範例中，一路徑包含 該發射器、該反射表面及該接收器，而另_路徑在該收發 裔内部並包含從該發射器至該延遲測量元件之信號耗合。 其中經由多個天 此類應用之另一範例係一分集接收器 線來接收一展頻益線雷古缺，# > …深^彳°唬，並使來自每一天線的信號在 經歷組合及解調變之前名主 艾別在4間上對齊。為執行該時間對 齊，首先必須衫來自每-天線的信號之相對時間延遲。 在此範例中’該信號遵循從該發射源至每_接收天線之一 不同路控。 此類應用t進一步乾例係一發射器測量機制，其中藉 由產生一展頻信號、讓該展頻信號穿過該發射器，並且於 96518.doc 200525924 一畸變測量元件φ μμ “办、 於，以俤W士 父穿過該發射器之前與之後的該信 :二便蝴發射器所引入的崎變，從而評估該發射器 r ϋ口貝。在此㈣中，—路徑包含該發射器，而另-路# 係用以將所產生的# % ^ 口號傳遞給該畸變測量元件之麵合。此 ㈣]量機财用於，例如，驗證該發射器是否符人 2關類型的㈣規格，或係嘗試使該發射器之功率效㈣ 么化的一可調適控制系統之部分。 用於評估發射器畸變之一度量值係誤差向量大小 (M) S £魏測量_，將發射器輸出處的信號之振幅 及相位軌道與穿過該發射器前之基頻信號之振幅及相位執 道相比’後者係充當-參考信號。此舉包括取該發射器輸 出處之-信號樣本，將其向下混合至基頻，然後讓其穿過 、—類比至數位轉換H(ADC)。然後，將該數位化信號視為一 複數向里，假定該複數向量之值序列遵循在複數平面中的 規疋點群集内之允許的特定轉變。經與該參考信號相比 較，該等複數向量值之差係所謂的誤差向量，而且正是該 等誤差向量的RMS值與參考信號的RMS值之比構成evm 值。200525924 IX. Description of the invention: [Description of the technical field to which this invention belongs] The present invention relates to a method for determining the relative time delay of a spread frequency # 遽 transmitted through the first and second paths, and a method for determining a display member ^ The slogan of mouth mussel ^ The method of showing the day. The invention also relates to a device for determining the relative time delay of a spread spectrum signal propagating through the first and second paths, and to a product comprising such a device. [Prior art] There are many radio applications that use spread spectrum signals, in which the relative time delay of the spread spectrum signal that is propagated through two or more paths needs to be determined. An example of this type of application is ranging, where a spread-spectrum radio signal is transmitted from a transceiver, the reflection of the transmitted signal is recovered at the transceiver n, and the transmitted signal and the received signal are determined in the 7G delay measurement Delayed in order to calculate the distance of the reflective surface. In this example, one path includes the transmitter, the reflective surface, and the receiver, and the other path is inside the transceiver and includes the signal depletion from the transmitter to the delay measurement element. Another example of this kind of application through multiple days is a diversity receiver line to receive a spread-spectrum line Lei Guque, # >… deep ^ 彳 °, and make the signals from each antenna undergo combination And before the demodulation, the master Abe was aligned on the 4 rooms. To perform this time alignment, the relative time delay of the signal from each antenna must first be worn. In this example, the signal follows a different routing from the transmitting source to one of each receiving antenna. A further example of this type of application is a transmitter measurement mechanism, in which a distortion measurement element φ μμ is generated by generating a spread-spectrum signal and passing the spread-spectrum signal through the transmitter. In order to evaluate the launcher r ϋ shellfish, Mr. Master W passed the letter before and after the launcher: the rugged changes introduced by the launcher of Erbian Butterfly. In this case, the path contains the launcher. And the other way is used to pass the generated #% ^ slogan to the face of the distortion measurement element. This is used to measure, for example, to verify whether the transmitter conforms to the human level 2 type. Specifications, or part of an adaptive control system that attempts to reduce the power efficiency of the transmitter. One of the measurements used to evaluate the distortion of the transmitter is the error vector size (M) S The amplitude and phase orbit of the signal at the output is compared with the amplitude and phase of the fundamental frequency signal before passing through the transmitter. The latter serves as a reference signal. This includes taking a signal sample at the output of the transmitter, Mix it down to the fundamental frequency and let Through,-analog to digital conversion H (ADC). The digitized signal is then treated as a complex direction, assuming that the sequence of values of the complex vector follows a specific allowed transition within a cluster of rule points in the complex plane Compared with the reference signal, the difference between the complex vector values is a so-called error vector, and the ratio of the RMS value of the error vector to the RMS value of the reference signal constitutes the evm value.
在決定該EVM之前，需要使所比較的信號在時間上對 齊，否則該EVM將係錯誤的。所需的時序精確度實質上小 於所包括的取樣間隔（即，1/取樣速率）。實驗顯示，對於用 在通用行動電訊系統（UMTS)中的發射器，若欲獲得對EVM 之了罪測ΐ ’則精碟度需要為該取樣間隔之S 1 %，等於該 晶片週期之幺0.1 %。 96518.doc 200525924 在上述應用範例的每一範例 夕心一庙 關中，皆必須決定經由二或更 夕路徑而傳播的一展頻信號 邳對日守間延遲。決定二展頻 k唬之間的時間延遲之一 ？知 已知方法係’執行相關，在時間 上杈％另一信號而掃描一作 〜 H问時尋找一最大相關。在 该k號之頻寬係與其他传梦丘古 r# ^ ，、他仏唬共予以致信號對干擾比低劣之 氪用中’相關為有效。但是，相關 τ々 疋祁關係一重複而緩慢的程序。 【發明内容】 本發明之一目的係提供一錄、土〜 ^ 于、種决疋經由第一及第二路徑而 傳播的-展頻信號之相對時間延遲之替代性方法。 依據本發明之一第一方而，担糾 方面緹供一種決定經由一及第二 =而傳播的—展頻信號之相對日㈣延遲之方法，其包 決定該信號在經由該等第一及第二路徑傳播後之相位 _特徵；依據該相位對頻率特徵來為該信號頻寬之至 --部分決定與頻率成函數關係的相位差；將一直線函數 適配於與頻率成函數關係之相位差；以及，依據該直線函 數斜率來決定該相對時間延遲。 一=本發明之-第：方面，提供_種決定—展頻信號的 貝私不之方法’其包含：在一發射器中產生處於基頻 之一展頻信號；經由包含該發射器中的向上轉換與-向下 轉換級之一第—路徑並經由處於基頻之一第二路徑而將該 信號選路給-延遲測量裝置；在該延遲測量裝置中，依據 本發明弟一方面之方法來決定經由該等第一及第二路徑而 傳，的信號之相對時間延遲；藉由施加與該相對時間延遲 相寺之-差動延遲’使經由該等第一及第二路徑而傳播的 96518.doc 200525924 信號之延遲等化；在等化該延遲後 而傳播的信號相對於經由該第一路、疋、、工由§亥弟一路徑 之一指示。 由°亥弟—路徑而傳播的信號之品質 依據本發明之一皆一 《二方面，提供-種用以決定經由第一 弟一路徑而傳播的_展 之相位對頻率特徵™構件， 部八卜相位對頻率特徵來為該信號頻寬之至少- 以二：TL率成函數關係的相位差；適配構件，其係用 將直線函數適配於與頻率成函數關係之相位差；以及 =::::其仙™線一^ 依據本發明之_ ^ TO He JE1 收發器…A . 彳面’ k供-種用於測距之無線電 八匕3 .產生構件，其係用以產生處於基頻之一 ，員信號；發射器構件，其係用以發射 發明第三方面之裝置，：所發射信號;依據本 _ ^ /、係耦合至該接收器構件並耦合至 二生構件，用以決定經由第一及第二路徑而傳播的信號 时目對時間延遲’其中該第_路徑包含該發射器構件：接 收益構件及該反射表面’而該第二路徑包含至該產生構件 之轉以及距離決定構件’其係調適成依據該相對時門 :決定該反射表峨等發射器構件及接收器構件； 依據本發明之一第五方面，提供一種用以接收一展頻信 96518.doc 200525924 器二其包含：第一接收器構件，其係用以接收經 匕各一第一天線之一第一路徑而傳播之展頻信號；第二 接，器構件，其係用以接收經由包含一第二天線之^第: 路位而傳播之展頻信號；依據本發明第三方面之务士置，盆 軸合至該等第—及第二接收器構件，用以決^經由該等 弟一及弟二路徑而傳播的信號之相對時間延遲；延遲等化 ^牛，其_合至依據本發明第三方面之裝置並搞合至該 寺第:及:二接收器構件，用以藉由施加與該相對時間延 遲相等之-差動延遲來使經由該等第一及第二路徑而接收 之延遲等化；組合構件，其係輕合至該延遲等化構 件，用以在延遲等化後組合經由該等第一及第二路徑而接 收的信號；以及解調變構件，其係耗合至該組合構件，用 以解調變由該組合產生之信號。 依據本發明之-第六方面，提供—種用以發射—展頻作 號之發射器，其包含：產生構件，其係用以產生處於基頻 之一展頻信號；向上轉換構件，其係用以向上轉換供發射 之基頻展頻信號；向下轉換構件，其係用以將經向上轉換 的基頻展頻信號向下轉換至基頻；依據本發明第三方面之 裝置，其係麵合至該向下轉換構件並輕合至該產生構件， 用以決定經由第-及第二路徑而傳播的信號之相對時間延 遲，其中該第一路徑包含該向上轉換構件與該向下轉換構 件’而該第二路徑包含至該產生構件之叙合；延遲等化構 件，其係轉合至依據本發明第三方面之裝置並麵合至該 第一及第二路徑’用以藉由施加與該相對時間延遲相等之 96518.doc 200525924 一差動延遲來使經由該等第一及第二路徑而傳播的信號之 延遲等化，以及處理構件，其係調適成在該延遲等化後決 定經由該第一路徑而傳播的信號相對於經由該第二路徑而 傳播的信號之品質之一指示。 在本發明之一項具體實施例中，可在適配該直線函數之 前，對在該等第一及第二路徑的至少一路徑中由一或多個 元件（例如 ，慮波益）引入的任何相位偏移進行補償。 在本發明之一項具體實施例中，該品質指示係誤差向量 大小（EVM)之一指示。 在本發明之—項具體實施例中，可藉由採取—初始粗略 測量及調整，接下來採取一精細測量及調整，而以多個步 ，來使經由該等第一與第二路徑而傳播的信號之間的延遲 藉由提供一替代方崇决#Before deciding on the EVM, the compared signals need to be aligned in time, otherwise the EVM will be wrong. The required timing accuracy is substantially smaller than the included sampling interval (ie, 1 / sampling rate). Experiments have shown that for transmitters used in the Universal Mobile Telecommunications System (UMTS), if the EVM is to be measured, then the precision level must be S 1% of the sampling interval, which is equal to 幺 0.1 of the chip period. %. 96518.doc 200525924 In each of the above application examples, the Xixinyimiao Pass must determine a spread-spectrum signal that propagates through the two or more paths. Determine one of the time delays between the two spreading frequencies k? Known method is to perform the correlation, scan another operation at the same time as the other signal, and look for a maximum correlation when asked. In this k-band, it is effective to correlate it with other Chuanmengougu r # ^, and he bluffs the signal to the interference ratio, which is inferior. However, the related τ々 疋 qi relationship is an iterative and slow process. SUMMARY OF THE INVENTION An object of the present invention is to provide an alternative method for recording the relative time delay of a spread-spectrum signal propagated through the first and second paths. According to a first party of the present invention, the correction method provides a method for determining the relative sundial delay of a spread-spectrum signal that is propagated through one and the second =, which includes determining whether the signal passes the first Phase_characteristics of the second path after propagation; according to the phase-to-frequency characteristics, to determine the signal bandwidth to the extent that the phase difference that is a function of frequency is partially determined; the linear function is adapted to the phase that is a function of frequency Poor; and, the relative time delay is determined based on the slope of the linear function. 1 = The first aspect of the present invention, providing _ a kind of decision-making method of spread spectrum signal, which includes: generating a spread spectrum signal at a fundamental frequency in a transmitter; and including the spread spectrum signal in the transmitter. Up-convert and down-convert one of the first paths and route the signal to a delay measurement device via a second path at a fundamental frequency; in the delay measurement device, the method according to one aspect of the present invention To determine the relative time delay of the signals transmitted through the first and second paths; 96518.doc 200525924 The delay of the signal is equalized; the signal propagated after equalizing the delay is indicated by one of the paths of §Hidi, relative to the signal passing through the first path. The quality of the signal propagated through the helium path is in accordance with one of the two aspects of the present invention, which provides a kind of phase-to-frequency characteristic ™ component for determining the _ exhibition propagated through the first path. The phase-to-frequency characteristics are at least the bandwidth of the signal-two: the phase difference as a function of the TL rate; an adapting component that adapts a linear function to the phase difference as a function of frequency; and = :::: 其 仙 ™ 线 一 ^ _ ^ TO He JE1 Transceiver according to the present invention ... A. 彳 面 'k-a radio dagger for distance measurement 3. Generate a component, which is used to generate One of the fundamental frequencies, the signal; the transmitter component, which is used to transmit the device of the third aspect of the invention: the transmitted signal; according to this _ ^ /, is coupled to the receiver component and coupled to the second component, using To determine the time-to-time delay of the signal propagating through the first and second paths 'where the _th path includes the transmitter component: the receiving component and the reflective surface' and the second path includes the transition to the generating component And the distance determines the component According to the relative time gate: the transmitter and receiver components of the reflection meter are determined; according to a fifth aspect of the present invention, a receiver for receiving a spread spectrum signal 96518.doc 200525924 is provided, which includes: a first receiver A component for receiving a spread-spectrum signal propagating through a first path of each of the first antennas; a second component for receiving a spreading signal via a second antenna : Spread-spectrum signal transmitted by the road; according to the third aspect of the present invention, the pedestal device is connected to the first and second receiver components for determining the path through the first and second paths. The relative time delay of the transmitted signal; the delay is equalized to the device according to the third aspect of the present invention and to the temple: and: two receiver components for applying the relative time by applying Equal delays-differential delays to equalize the delays received via the first and second paths; composite components, which are lightly coupled to the delay equalization components, and are used to combine the Signals received on the first and second paths; and demodulation A component that is consumed by the combination component to demodulate signals generated by the combination. According to a sixth aspect of the present invention, there is provided a transmitter for transmitting-spread spectrum numbering, comprising: a generating component for generating a spread-spectrum signal at a fundamental frequency; and an up-converting component for Used for up-converting the baseband spread spectrum signal for transmission; a down-converting component for down-converting the up-converted base-band spread-spectrum signal to the base frequency; Face-to-down conversion component and light-to-generation component are used to determine the relative time delay of the signal propagating through the first and second paths, wherein the first path includes the up-conversion component and the down-conversion Component 'and the second path contains the description to the generating component; the delayed equalization component is transferred to the device according to the third aspect of the present invention and faced to the first and second paths' by A differential delay of 96518.doc 200525924 equal to the relative time delay is applied to equalize the delay of the signals propagating through the first and second paths, and the processing component is adapted to equalize the delay Decide Phase signal propagating through the first path to the one indicating the quality of signals propagating through the second path. In a specific embodiment of the present invention, before the linear function is adapted, the introduction of one or more elements (for example, considering wave benefits) in at least one of the first and second paths may be performed. Any phase offset is compensated. In a specific embodiment of the present invention, the quality indication is an indication of an error vector size (EVM). In a specific embodiment of the present invention, it is possible to propagate through the first and second paths by taking an initial coarse measurement and adjustment, and then taking a fine measurement and adjustment, in multiple steps. Delay between signals by providing an alternative
… 代万Μ使用不需要-重複程序之相I 本兔明提供一種決定經由第一 _… Generation of MW uses no need to repeat the phase of the procedure I this rabbit provides a decision via the first _
田弟及第一路徑而傳播的一JTian J and the first path
4藏之相對時間延遲 片；…， 法。在該等信號路徑不今 明最為有效。 在-内建傳播環境中’4 本發明即使在一豐富的多 由於該展頻信號之較大頻寬 徑環境下亦可能有效。 【貫施方式】 參考圖1之流程圖，在步驟10中 傳播的一展個 、疋错由一第一與 展頻k旒之相位對頻率特 中，決定蕤ώ结 只早特敛Λ(〇，而在步 疋错由一苐二路徑而傳播 備的展頻信號之相位斐 96518.doc -10- 200525924 知铽〆2(f)。f係以兆赫計的頻率。在步驟14中，與頻率成函 數關係之相位差屋〆(f)係決定為屋〆(f)=〈（f)_/2⑺。在步驟16 中，表示一直線的一數學函數關係式y=mx + c適配於該函數 屋^f)，而在步驟18中，依據該直線之斜率爪而將該等第一 與第二路徑所發射的信號之間的相對時間延遲。決定為 td=m/20。 一下面解說以上方法之數學依據。沿—單—路徑而行進的 一單一頻率信號之相位偏移， ⑴與該頻率及該路徑所引入 的延遲成比例，即勘，其中m該信號之頻率，而t :該延遲。因,匕，對於包含一系列間隔緊密的頻譜成分之 率來決定該時間延遲，即t=丄. 2π df 二展?25=;該相位差對頻率特徵之斜率與該延遲成比 df xt。因此，可依據該相位差對頻率特徵之斜 以一系列頻率而非一 二^率為依據來進行時間延遲測量之-優點係，使測量 誤差得以平均而使得精確度提高°可藉由從該延遲信號之 相位對頻率特徵減去該信號之初始相位對頻率特徵，來決 定該相位差對頻率特徵。因此，對於經由二路徑而傳播之 :信號^於該初始相位特徵對於二路㈣為相同，因此， td=丄頻率特=差來決定該相對時間延遲，即 2π df 與使^號相關以求出其相對時間延遲之 已知的重複方法相比，以上方法並非重 快速解決方法。 攸而貫現一 下面將針對-實際情況說明該基本方法之進—步精要細 96518.doc 200525924 節。圖2顯示一展頻信號的基頻頻譜之-範例。該調變頻寬 約為4 MHz，該晶片速率為3·84 MHz，並使用—過度取樣 比8來產生該信號。因此，取樣速率為Μ.”趣而取樣間 隔為32.6 ns。圖3中顯示此信號之相位對頻率特徵，並能看 出其具有類似於雜訊之特徵。若沿一路徑傳播此信號，則 每-頻率皆經歷如上所述之—不同的相位偏移，但由該傳 播路徑引人的相位差隨頻率而線性變動，如上所述以及圖4 之說明。在-實際的實施方案中，可能將雜訊及畸變引入 該展頻信號。例如，數位至類比轉換器可能引入量化雜訊， 遽波器可能引入相位偏移’而放大器可能引入雜訊及互調 變畸變。圖5說明一雜訊展頻信號的基頻頻譜之一範例；4 MHz中心頻寬以外的雜訊位準升高了約4()犯。該雜訊所引 起之結果係使得該相位特徵改變。圖6說明該展頻之最初相 位特徵（標記為「參考信號」），卩及在經由引入雜訊的一路 控傳播後該展頻之相位特徵（標記為「延遲信號」圖7說 ^亥些相位特徵之間的差。儘管該等相位特徵具有看似隨 思之性^ ’但其之間的差在中心頻率4 MHz區域中仍呈現一 線性關係；該雜訊主要干擾了旁帶。此情況之結果係，時 間延遲之決定將僅依據該相位對頻率特徵之中心部分。可 依據對調變頻寬以及沿該等信號路徑引入的雜訊及崎變之 頒5L及範圍之瞭解來選擇所使用部分之頻寬。 即使出現分散’只要該分散引入對該信號的直線相位特 徵之一大致週期性的擾亂，便亦能容許分散；於是，該直 線函數便可適配於整個擾亂。 96518.doc -12- 200525924 用在發射或接收裝置中的元件（例如，濾波器）可引入一 =偏移而使得產生並非—直線的—相位差對頻率特徵。 疋可藉由决疋此類元件之相位特徵並從該相位對頻率 寺u或。亥相位差對頻率特徵移除此類元件之相位特徵而留 下一直線函數可適配之一直線特徵，來補償此類元件對該 信號之影響。 x 一：考圖8，所示係用以;夬定經由第一及第二路徑而傳播的 -信號之相對時間延遲之一裝置! 〇 〇之一方塊示意圖。該裝 f 100包3第一及第二輸入110、120，該等二輸入係用以將 弟一及第二信號分別提供給第一及第二相位決定構件 130、140來決定該等第一及第二信號之相位對頻率特徵。 =一輸出來自於第-及第二相位決定構件13〇、14〇中的每 一構件’該輸出係用以將該相位對頻率特徵提供給一相位 差決定構件150來決定該等第一及第二信號的相位對頻率 =之間=差。該相位差決定構件15〇有—輸出係用以將該 寻弟-與第二信號的相位對頻率特徵之間的差提供給一適 配構件160以將-直線函數y=mx+c適配於該i。該適配構 件160有-輸出係用以將適配的直線函數之梯度爪提供給一 延遲決定構件17〇’以將該等第—及第二信號之相對延私 決定為td=m/M。有—輸出18G係用以傳遞所蚊的延遲td。 所述位於該裝置100内的方塊13〇至17〇可實施於一或多個 處理器中。 依據樣本數目及可用的計算資源，可藉由使用一離散富 利葉轉換（DFT)或一快速富利葉轉換（FFt)來使提供給該等 96518.doc -13- 200525924 第:及第二輸出11〇、12〇之信號數位化並決定該些信號之 頻譜，士來操作該等第-及第二相位決定構件130、140。 β衣置1GG所處理的信號之持續時間係經折衷考慮而得 亥等 諕之持續時間越長，則該時間延遲計算將越可 靠，但計算負載將越高。同樣，該持續時間必須足夠大， 以使預期的時間延遲於耐或附中所造成的從一頻率位 7G至下一頻率位元之相位偏移不超過數度。 —該相位差決定構件15()可藉由對由該第_及第二相位決 定構件130 ' 140提供的複數頻譜進行分頻且然後將結果轉 換成極座標來操作。在執行—FFT或附之前轉換成極座標 且然後減去該相位對頻率特徵之替代性方法將易於發生誤 差，特別是在時間延遲較大之情況下。 在將該直線函數適配於該適配構件16〇 該相位差特徵而使得不以4模數來表示超過“之= 值。 上文中提到的補償，即對該發送或接收裝置中的元件效 果進行補償，（例如）可藉由該等第一及第二相位決定構件 1 3〇、140、該相位差決定構件15〇來執行或執行於一分離的 補償構件中。 如上文中參考圖丨及圖8而說明的用以依據本發明來決定 相對時間延遲之方法及裝置之一應用係用以決定範圍。參 考圖9，其顯示一測距裝置2〇〇之一方塊示意圖。有一產生 器210用以產生一展頻信號。有一發射器22〇係耦合成經由 天線240發射所產生的展頻信號。該發射器22〇係藉由— 96518.doc -14- 200525924 耦合構件230而耦合至該天線24〇，該耦合構件23〇可為（例 如）一循％為。傳播所發射的信號，從與該測距裝置距離d 之一反射器290反射所發射的信號，並於該天線240回收所 發射的信號。經由該耦合構件230而將一接收器250耦合至 該天線240來接收所反射之信號。用以決定沿第一及第二路 技而傳播的一信號之相對時間延遲之裝置丨〇〇(如上文參考 圖8所发明）係耦合成在其第一輸入丨1〇上從該接收器接 收該反射信號’而在其第二輸人12G上直接從該產生器210 接收所產±的信號。該第一路徑包含該發射器22〇、通向及 發自該反射II29G之路線、該接收器25()，而該第二路徑包 含從該產生器210至該裝置1〇〇之直接耦合。延遲之計算可 將發生於設備中的任何延遲考慮進去，可藉由校準該設備 來決定該等延遲本身。該裝置1〇〇之輸出係耦合至一範圍決 定構件260,以將該反射器29〇與該測距裝置2〇〇之距離計算 為tdc/2其中“為相對時間延遲，而c為光速。舉例而言， 使用信號頻寬為4 MHz之一 μ相产咕 ， 卜 ^ 展頻^旎，一 1 m範圍等於約 4」8。之-相位偏移。此程度之解析度在該延遲計算方法及當 ，前的處理設備範圍内係不錯的，並實則爪以⑼爪等級的 範圍内約土 1 m之精確度。 上文中參考圖i及圖8所說明）之另—應用係用以接收㈣ 多個天線而接收之一展頻信號。參考圖1〇,其說明用以指 收一展頻信號之-接收器3⑼。該接收器有第—及第二天缚 3^ 320用以接收經由第—及第二路徑而傳播的信號。用 96518.doc 200525924 以放大、過濾並將所接收的信號向下轉換至基頻之第一及 第二接收器前端330、340分別耦合至該等第一及第二天線 310、320。如上所述，來自該等第一及第二接收器前端33〇、4 Tibetan relative time delay films; ..., method. It is most effective when such signal paths are not known. In the -built-in propagation environment, the invention may be effective even in a rich environment with a large bandwidth due to the spread spectrum signal. [Implementation method] With reference to the flowchart of FIG. 1, in the step 10, the number of spreads and errors in step 10 is determined by the phase and frequency of the first and spread frequency k 旒. The phase of the spread spectrum signal propagated by the one or two paths at the wrong step is shown in Fig. 96518.doc -10- 200525924. 2 (f). F is the frequency in megahertz. In step 14, The phase difference house 〆 (f) which is a function of frequency is determined as house 〆 (f) = <(f) _ / 2⑺. In step 16, a mathematical function relation y = mx + c that represents a line is adapted In the function house ^ f), in step 18, the relative time between the signals transmitted from the first and second paths is delayed according to the slope claw of the straight line. Decided to be td = m / 20. The following explains the mathematical basis of the above methods. The phase offset of a single frequency signal traveling along a -single-path, 比例 is proportional to the frequency and the delay introduced by the path, that is, where m is the frequency of the signal, and t is the delay. Therefore, for a rate containing a series of closely spaced spectral components, the time delay is determined, that is, t = 丄. 2π df two extensions? 25 =; the slope of the phase difference to the frequency characteristic is proportional to the delay df xt. Therefore, the time delay measurement can be performed based on the phase difference to the slope of the frequency characteristics based on a series of frequencies instead of one or two ^-the advantage is that the measurement error can be averaged and the accuracy can be improved. The phase-to-frequency characteristic of the delayed signal is subtracted from the initial phase-to-frequency characteristic of the signal to determine the phase-to-frequency characteristic. Therefore, for the propagation through the two paths: the signal ^ is the same as the initial phase characteristics for the two paths ㈣, so td = 丄 frequency characteristics = difference to determine the relative time delay, that is, 2π df is related to the ^ sign to obtain The above method is not a fast solution compared to the known iterative methods that show their relative time delay. The following will be explained in accordance with the actual situation-detailed steps 96518.doc 200525924. Figure 2 shows an example of the fundamental frequency spectrum of a spread spectrum signal. The modulation bandwidth is approximately 4 MHz, the chip rate is 3.84 MHz, and the signal is generated using an oversampling ratio of 8. Therefore, the sampling rate is M. "and the sampling interval is 32.6 ns. The phase-to-frequency characteristics of this signal are shown in Figure 3, and it can be seen that it has noise-like characteristics. If this signal propagates along a path, then Each frequency undergoes different phase shifts as described above, but the phase difference introduced by the propagation path varies linearly with frequency, as described above and illustrated in Figure 4. In the actual implementation, it is possible Noise and distortion are introduced into the spread spectrum signal. For example, digital-to-analog converters may introduce quantization noise, chirpers may introduce phase shifts, and amplifiers may introduce noise and intermodulation distortion. Figure 5 illustrates a noise An example of the fundamental frequency spectrum of a spread spectrum signal; the level of noise outside the 4 MHz center bandwidth is increased by about 4 (). The result of this noise is to cause the phase characteristics to change. Figure 6 illustrates this The initial phase characteristics of the spread spectrum (labeled as "reference signals"), and the phase characteristics of the spread spectrum (labeled as "delayed signals") after propagating through a route that introduces noise. Poor. Despite Isophase characteristics are seemingly random ^ 'but the difference between them still shows a linear relationship in the center frequency 4 MHz region; the noise mainly interferes with the sidebands. The result of this case is the decision of the time delay Only the central part of the phase-to-frequency characteristics will be selected. The bandwidth of the used part can be selected based on the knowledge of the modulation bandwidth and the noise and variability of the 5L and range introduced along these signal paths. As long as the dispersion introduces a roughly periodic disturbance of one of the linear phase characteristics of the signal, the dispersion can also be tolerated; therefore, the linear function can be adapted to the entire disturbance. 96518.doc -12- 200525924 Used for transmission or reception Components (for example, filters) in the device can introduce an offset to produce a non-linear-phase difference versus frequency characteristic. 疋 You can determine the phase characteristics of such components and determine the frequency from this phase or The phase difference on the frequency characteristics removes the phase characteristics of such components and leaves a straight line function that can be adapted to a linear characteristic to compensate for the effect of such components on the signal. : Consider Figure 8. The system shown is used to determine the relative time delay of a signal that is propagated through the first and second paths. A block diagram of 〇〇. This equipment f 100 packs 3 first and first The two inputs 110 and 120 are used to provide the first and second signals to the first and second phase determining members 130 and 140, respectively, to determine the phase-to-frequency characteristics of the first and second signals. = An output is from each of the first and second phase determining members 13 and 14 ′. The output is used to provide the phase versus frequency characteristics to a phase difference determining member 150 to determine the first and The phase-to-frequency of the second signal = between = difference. The phase-difference determining means 15 has an output for providing the difference between the phase-finding characteristic of the second-seeking signal and the second signal to an adapting means. 160 to fit the -line function y = mx + c to the i. The adapting member 160 has an output to provide a gradient claw of the adapted linear function to a delay determining member 17 ′ to determine the relative extension of the first and second signals as td = m / M. . Yes-The output 18G is used to transmit the delayed td of the mosquito. The blocks 130 to 170 located in the device 100 may be implemented in one or more processors. Depending on the number of samples and available computing resources, these can be provided to the 96518.doc -13- 200525924 by using a discrete Fourier transform (DFT) or a fast Fourier transform (FFt). The signals of output 110 and 120 are digitized and the spectrum of these signals is determined, and the first- and second-phase determining members 130 and 140 are operated by Shilai. The duration of the signal processed by β-clothing 1GG is calculated by compromise. The longer the duration of 亥 and so on, the more reliable the time delay calculation, but the higher the calculation load. Similarly, the duration must be large enough so that the expected time delay is no more than a few degrees from the phase shift from 7G to the next frequency bit caused by resistance or attachment. -The phase difference determining means 15 () can be operated by frequency-dividing the complex spectrum provided by the first and second phase determining means 130'140 and then converting the result into polar coordinates. Alternative methods of converting to polar coordinates before performing the FFT or appending and then subtracting the phase versus frequency characteristics will be prone to errors, especially if the time delay is large. The linear function is adapted to the phase difference characteristic of the adapting member 16 so that it is not expressed by 4 modulus exceeding "of = value. The compensation mentioned above is the component in the transmitting or receiving device Effect compensation, for example, the first and second phase determination members 130, 140, and the phase difference determination member 150 may be executed or executed in a separate compensation member. An application of the method and device for determining the relative time delay according to the present invention described with reference to FIG. 8 is to determine the range. Referring to FIG. 9, a block diagram of a ranging device 2000 is shown. There is a generator 210 is used to generate a spread-spectrum signal. A transmitter 22 is coupled to transmit the generated spread-spectrum signal via an antenna 240. The transmitter 22 is coupled to-96518.doc -14- 200525924 coupling member 230 The antenna 24, and the coupling member 23 may be, for example, a cycle-by-cycle. The transmitted signal is propagated, the emitted signal is reflected from a reflector 290 at a distance d from the distance measuring device, and the antenna 240 Recycle issued A signal transmitted by the receiver. A receiver 250 is coupled to the antenna 240 via the coupling member 230 to receive the reflected signal. A device for determining the relative time delay of a signal propagating along the first and second road techniques 丨〇〇 (as invented above with reference to FIG. 8) is coupled to receive the reflected signal from the receiver on its first input, 10, and directly receive the produced signal from the generator 210 on its second input, 12G. ± signal. The first path includes the transmitter 22o, the route to and from the reflection II29G, the receiver 25 (), and the second path includes the generator 210 to the device 100. Direct coupling. The calculation of the delay can take into account any delays that occur in the device, and the delay itself can be determined by calibrating the device. The output of the device 100 is coupled to a range determination component 260 to The distance between the reflector 29 and the distance measuring device 200 is calculated as tdc / 2, where “is a relative time delay, and c is the speed of light. For example, using a μ-phase signal with a signal bandwidth of 4 MHz and a spreading frequency of ^ 旎, a 1 m range is equal to about 4 ″ 8. Of-phase offset. The resolution of this degree is good within the range of the delay calculation method and current processing equipment, and in fact, the accuracy of the soil is about 1 m within the range of the claw level. (Explained above with reference to FIG. I and FIG. 8) Another application is to receive a plurality of antennas and receive a spread spectrum signal. Reference is made to Fig. 10, which illustrates a receiver 3 "for receiving a spread spectrum signal. The receiver has first- and second-day radio signals 3 ^ 320 for receiving signals propagated through the first- and second paths. 96518.doc 200525924 is used to amplify, filter, and down-convert the received signals to the first and second receiver front ends 330, 340 of the fundamental frequency, which are coupled to the first and second antennas 310, 320, respectively. As mentioned above, from the first and second receiver front ends 33o,
340中每一前端之一輸出係分別耦合至裝置1〇〇之第一及第 二輸入110、120，以決定接收於每一天線31〇、32〇的信號 之相對時間延遲。該裝置100之輸出18〇係耦合成將該相對 延遲。之一指示提供給一延遲等化級35〇之一輸入。來自該 寺第一及第二接收器前端33〇、34〇中每一前端之輸出亦係 分別耦合至該延遲等化級35〇之進一步輸入。該延遲等化級 350使用所提供的該相對延遲之值。來操作，使接收於每一 天線310、320處的信號所經歷的延遲等化。該延遲等化級 350之第一及第二輸出將該等延遲等化信號耦合至一組合 級360以組合該等信號。該組合級36〇之一輸出係耦合至一 解調變器370以解調變該等組合的信號。在_輸出上提 供經解調變的信號。One output of each front end in 340 is coupled to the first and second inputs 110, 120 of the device 100, respectively, to determine the relative time delay of the signals received at each antenna 31, 32. The output 180 of the device 100 is coupled to the relative delay. One of the indications is provided to one of the inputs of a delay equalization stage 350. The outputs from each of the temples' first and second receiver front-ends 33 and 34 are also coupled to further inputs of the delay equalization stage 35 respectively. The delay equalization stage 350 uses the value of the relative delay provided. To equalize the delay experienced by the signal received at each antenna 310, 320. The first and second outputs of the delay equalization stage 350 couple the delay equalization signals to a combination stage 360 to combine the signals. One of the outputs of the combining stage 36 is coupled to a demodulator 370 to demodulate the combined signals. A demodulated signal is provided on the _ output.
用以依據本發明來決定相對時間延遲之方法及裝置（ 上文中參考圖1及圖8所說明）之另一應用係一種（例如）用 在.平估一發射器品質以及在調整該發射器以提高信號品 時決定一展頻信號品質的一指示之方法。 。儿口口 芩考圖11，其說明一種決定一展頻信號品質之方法。 方法開始方；產生一展頻信號之步驟4〇。在步驟41中，在 1射夯中向上轉換並放大該展頻信號。在步驟42中，對 ^射杰之輸出取樣，並向下轉換所取樣的信號。在步驟 中决定所產生的展頻信號與向下轉換的信號之間的相 96518.doc -16- 200525924 :間延遲。在步驟44中，使該些二信號之時間延遲等化。 步驟45中，藉由將此信號與所產生的信號相比來決定經 向下轉換亚延遲的信號之E VM。 、 忒EVMk供该發射器品質 才日示。視需要’在步驟4 6 φ可分义 中可调適该發射器以改善該 V Μ 〇 視需要可藉由-粗略的時間延遲估計及調整來進行步驟 44中相對時間延遲之等化’例如’使該相對時間延遲等於 最近的數位時間樣本。若該等二信號之時間偏離很… 能很大，貝此類二級方法不失為明智之舉。一很大的時間 延遲將會對應於時間延遲決定中—很大的相位斜率，而若 該延遲太大’則此情況可能易於出現誤差，例如，大於冗 之相位步幅可能變得模糊。可藉由使用若干個完整的取樣 間隔而橫跨另—信號掃描—信號，並尋找EVM的最小值， 來執行粗略調整。聽料夠長的信號，則此舉不可能產 生錯誤答案。 參考圖12，其係配備成決定_所發射的展頻信號品質之 -發射器400之方塊示意圖。有用以產生—展頻信號之一產 生器410。該產生器410之一輸出係耦合至一前端級以對 所產生的信號作向上轉換及放大。該前端級42〇之一輸出係 耦合至一天線430。該前端級420之輸出亦係耦合至一向下 轉換級440以向下轉換由該前端級42〇所提供的信號。如上 所述，4產生益410之輸出及該向下轉換級44〇之輸出係分 別耦〇至一裹置1 〇〇之第一及第二輸入，以決定提供給該等 輸入110、120的信號之相對時間延遲。該裝置1〇〇之輸出18〇 96518.doc 200525924 係麵合成將該相對延遲α—指示提供給—延遲等化級 350(如上所述）之—輸人。該產生器㈣之輪心及該向下轉 換級440之輸出亦係分別輕合至該延遲等化級⑽之進一步 輸入。該延遲等化級35〇使用所提供的該相對延遲之值W 使該產生器4H)的輸出處之信號及該向下轉換級4⑽輸出 處之信號所經歷的延遲等化。該延遲等化級可能額外地操 作以藉由該等信號之複數縮放來移除該等二信號之間的振 幅或相位偏離。該延遲等化級35〇之第一及第二輸出係柄合 至一品質評估級4 6 G ’該品質評估級進行操作以比較該等延 遲等化信號並產生-輸出4 5 G上的向下轉換信號品質之一 指示。視需要可將該品質評估級偏之—輸出4馳合至一 控制構件470 ’該控制構件係耦合至該產生器41〇並耦合至 該前端級42卜該控制構件47〇進行操作以調整該產生器41〇 及該前端級420之一或多個參數，以便提高該前端級42〇輸 出處的信號品質。此類調整可包含，例如，預先畸變由該 產生器410產生的信號，或調整用於在該前端級42〇中作向 上轉換的正交混合器中之不平衡。 該發射器400可為一收發器之發射器部分。在此情況下， 該向下轉換級440可能係該收發器的接收器部分之一部 为’而可使用該接收器中提供用於選擇頻道及減小取樣速 率（例如’抽取）之濾波器（例如，數位根升餘弦濾波器）來實 施該延遲等化級350。 在一項替代性具體實施例甲，如上所述與決定一展頻信 號品質之方法相關，可併入時間延遲估計及調整之二級， 96518.doc -18- 200525924 在該裝置H)0之前可能具有或該裝置1〇〇可包括一粗略的延 遲估計及調整級以減小該差動延遲（例如，將時間延遲調整 為最近的時間樣本），此粗略的延遲估計及調整級在由該裝 置1 〇 〇所作的精細時間延遲估計及由該延遲等化級3 5 〇所作 的精細調整之前。 本說明書及"專利範圍中，_元件前面所用的詞 「一」或「一個」並不排除存在複數個此類元件。進一步 σ ^ 包含」並不排除除所列舉元件以外還存在其 他元件或步驟。 、 热白此項技術者在讀過本揭示内容後將會明白其他修 此類修改可包括無線技術及展頻通訊中已知並可在本 文已說明的特徵之外，作為替代或額外地加以使用之並他 特徵。 【圖式簡單說明】 上文參考隨附的圖式並僅以實例來說明本發明，在該 圖式中： 圖1係用以決定經由筮—β给—a斤 、 第 及第一路徑而傳播的一展頻作 號之相對時間延遲之一方法之一流程圖； σ 圖2係一參考展頻信號之頻率頻譜； 圖3係一參考展頻信號之相位特徵； 圖4係彼此相對延遲的二展頻信號之間的相位差。 圖5係展頻信號在穿過一發射器後的頻率頻譜； 一圖6係彼此相對延遲且該延遲信號添加有雜訊的二展頻 "ί吕號之相位特徵； 96518.doc -19- 200525924 圖7係彼此相對延遲且該延遲信號添加有雜訊之二展頻 k號之間的相位差； 圖8係依據本發明用以決定延遲之一裝置之一方塊示意圖； 圖9係用以測距之一裝置之一方塊示意圖； 圖1〇係用以接收一展頻信號之一接收器之一方塊示意圖； 圖11係決定一展頻信號品質的一指示之一方法之一流程 圖；以及 圖12係用以發射一展頻信號之一接收器之-方塊示意圖。 在該等圖式中，已使用相同的參考數字來標示不同圖式 中相對應的特徵。 【主要元件符號說明】 100 決定延遲之裝置 110 第一輸入 120 第二輸入 130 第一相位決定構件 140 第二相位決定構件 150 相位差決定構件/韦 160 適配構件 170 延遲決定構件 180 輸出 200 測距裝置 210 產生器 220 發射器 230 孝禺合構件 96518.doc -20- 200525924 240 250 260 290 290 300 300 310 320 330 340 350 360 370 380 400 400 410 420 430 440 450 460 470 天線 接收器 距離決定構件 反射器 反射器 分集接收器 接收器 第一天線 第二天線 第一接收器前端/第一接收器構件 第二接收器前端/第二接收器構件 延遲等化級/延遲調整構件 組合級/組合構件 解調變器/解調變構件 輸出 發射器 發射器 產生器/產生構件 前端級/向上轉換構件 天線 向下轉換級/向下轉換構件 輸出 品質評估級/處理構件 控制構件/調適構件 96518.doc -21 -Another application of the method and device for determining the relative time delay according to the present invention (explained above with reference to FIGS. 1 and 8) is another application, for example, for estimating the quality of a transmitter and adjusting the transmitter. In order to improve the signal quality, an indication method for determining the quality of a spread spectrum signal. . Erkoukou Consider Figure 11 which illustrates a method for determining the quality of a spread spectrum signal. Method start; step 40 of generating a spread spectrum signal. In step 41, the spread spectrum signal is up-converted and amplified in 1 shot. In step 42, the output of the radio signal is sampled, and the sampled signal is down-converted. The phase between the generated spread-spectrum signal and the down-converted signal is determined in the step 96518.doc -16- 200525924: inter-delay. In step 44, the time delays of the two signals are equalized. In step 45, the EVM of the down-converted sub-delayed signal is determined by comparing this signal with the generated signal. , 忒 EVMk will be displayed for the quality of this transmitter. If necessary, 'the transmitter can be adjusted to improve the V Μ in step 4 6 φ separable. If necessary, the relative time delay in step 44 can be equalized by-rough time delay estimation and adjustment', for example 'Make this relative time delay equal to the most recent digital time sample. If the time deviations of these two signals are ... can be large, it may be wise to use such secondary methods. A large time delay will correspond to the time delay decision-a large phase slope, and if the delay is too large 'this situation may be prone to errors, for example, phase steps larger than redundant may become blurred. A coarse adjustment can be performed by using several complete sampling intervals across the other-signal sweep-signal and finding the minimum value of EVM. Listening to a long enough signal, this is unlikely to produce the wrong answer. Referring to FIG. 12, it is a block diagram of a transmitter 400 configured to determine the quality of the transmitted spread spectrum signal. A generator 410 is used to generate one of the spread spectrum signals. An output of the generator 410 is coupled to a front-end stage to up-convert and amplify the generated signal. One of the outputs of the front-end stage 42 is coupled to an antenna 430. The output of the front-end stage 420 is also coupled to a down-conversion stage 440 to down-convert the signal provided by the front-end stage 420. As mentioned above, the output of 4 generating benefits 410 and the output of the down conversion stage 44 are respectively coupled to a first and a second input of 100, to determine the output provided to these inputs 110, 120. Relative time delay of the signal. The output of the device 100 is 18060518.doc 200525924. The synthesizer provides the relative delay α-indication to the delay equalization stage 350 (as described above) and enters it. The wheel core of the generator ㈣ and the output of the down conversion stage 440 are also closed to further inputs of the delay equalization stage 分别 respectively. The delay equalization stage 350 uses the provided value of the relative delay W to equalize the delay experienced by the signal at the output of the generator 4H) and the signal at the output of the down conversion stage 4 级. The delay equalization stage may additionally operate to remove the amplitude or phase deviation between the two signals by complex scaling of the signals. The first and second outputs of the delay equalization stage 35 are coupled to a quality evaluation stage 4 6 G 'The quality evaluation stage operates to compare the delayed equalization signals and generate-output a direction on 4 5 G An indication of the quality of the down-converted signal. If necessary, the quality evaluation level can be biased-the output 4 is connected to a control component 470 'The control component is coupled to the generator 41o and coupled to the front-end stage 42 and the control component 47o is operated to adjust the One or more parameters of the generator 41 and the front-end stage 420, so as to improve the signal quality at the output of the front-end stage 420. Such adjustments may include, for example, predistorting the signal generated by the generator 410, or adjusting imbalances in the quadrature mixer used for up conversion in the front-end stage 42. The transmitter 400 may be a transmitter part of a transceiver. In this case, the down-conversion stage 440 may be part of the receiver portion of the transceiver, and filters provided in the receiver for selecting channels and reducing the sampling rate (eg, decimation) may be used. (Eg, a digital root raised cosine filter) to implement the delay equalization stage 350. In an alternative embodiment A, as described above, it is related to the method for determining the quality of a spread spectrum signal, and can be incorporated into the second level of time delay estimation and adjustment, 96518.doc -18- 200525924 before the device. It may have or the device 100 may include a coarse delay estimation and adjustment stage to reduce the differential delay (for example, adjust the time delay to the nearest time sample). The coarse delay estimation and adjustment stage is determined by the Prior to the fine time delay estimation made by the device 100 and the fine adjustment made by the delay equalization stage 3500. The use of the word "a" or "an" in front of an element in this specification and the "Patent" does not exclude the presence of a plurality of such elements. Further σ ^ includes does not exclude the presence of other elements or steps in addition to the listed elements. After reading this disclosure, those skilled in the art will understand that other modifications such as these may include features known in wireless technology and spread spectrum communications and may be used in place of or in addition to the features already described herein. And other characteristics. [Brief description of the drawings] The invention is described above with reference to the accompanying drawings and by way of example only. In the drawing: FIG. 1 is used to determine the first, second, and first paths via A flowchart of one method of the relative time delay of a spread-spectrum signal; σ Figure 2 is a frequency spectrum of a reference spread-spectrum signal; Figure 3 is a phase characteristic of a reference spread-spectrum signal; Figure 4 is a relative delay to each other The phase difference between the two spread spectrum signals. Figure 5 shows the frequency spectrum of a spread-spectrum signal after passing through a transmitter; Figure 6 shows the phase characteristics of the second spread-spectrum " ίLu number, which are delayed relative to each other and noise is added to the delayed signal; 96518.doc -19 -200525924 Figure 7 is the phase difference between the two delayed relative signals and the delayed signal is added to the delayed signal k; Figure 8 is a block diagram of a device for determining the delay according to the present invention; Figure 9 is used A block diagram of a device for distance measurement; Figure 10 is a block diagram of a receiver for receiving a spread spectrum signal; Figure 11 is a flowchart of a method for determining the quality of a spread spectrum signal And FIG. 12 is a block diagram of a receiver for transmitting a spread spectrum signal. In these drawings, the same reference numerals have been used to indicate corresponding features in different drawings. [Description of the main component symbols] 100 The device for determining the delay 110 The first input 120 The second input 130 The first phase determination member 140 The second phase determination member 150 The phase difference determination member / Wei 160 The adaptation member 170 The delay determination member 180 The output 200 measurement Distance device 210 Generator 220 Transmitter 230 Coupling member 96518.doc -20- 200525924 240 250 260 290 290 300 300 310 320 330 340 350 360 360 370 380 400 400 410 420 430 440 450 460 470 Antenna receiver distance determining member Reflector reflector diversity receiver receiver first antenna second antenna first receiver front end / first receiver component second receiver front end / second receiver component delay equalization level / delay adjustment component combination level / Combination component demodulator / demodulation component output transmitter transmitter generator / generation component front-end stage / up-conversion unit antenna down-conversion stage / down-conversion unit output quality evaluation level / processing unit control unit / adaptation unit 96518 .doc -21-