SU1689877A1 - Method of measuring proper reflection factor of radiating member of phased array - Google Patents

Abstract

The invention relates to radio metering and antenna technology and can be used in research and quality assessment of the manufacture of complex antenna systems. The purpose of the invention is to reduce the measurement time. The method of measuring the intrinsic reflectance of a radiating element of a phased antenna array is based on applying a manipulated microwave signal to the measured radiating element, summing the signal reflected from it with the incident signal, detecting and measuring the total signal. The goal is achieved by the fact that the manipulated microwave signal is obtained by phase manipulation with a phase deviation of 90 ° C, additionally changing the phase supplied to the measured radiating element of the manipulated microwave signal by 180 ° C, summing the signal reflected from it the incident signal is detected and the total signal is measured and the measured values of the total signals are summed. 1 il. W Ё

Description

The invention relates to radio metering and antenna technology and can be used in research and quality assessment of the manufacture of complex antenna systems.

The intrinsic reflection coefficient (MSD) of the radiating element (IE) of a phased array antenna (PAR) is the reflection coefficient of the radiating element located in the aperture surrounded by other IE loaded on matched loads.

Sometimes, instead of MSE, IEs measure their own input resistances of IE, which are associated with MSE dependency.

7 1 + SKO

 1 - SKO

The purpose of the invention is to reduce the measurement time.

The drawing shows a structural electrical circuit of the device by which the proposed method is realized.

A device that implements a method for measuring the intrinsic reflection coefficient of the EITAR HEADLAMP contains a microwave signal generator 1, sensor 2 with four probes. divider 3, phase shifter 4 with electric control, IE 5, PAR 6, selective amplifier 7 FM modulation frequency signals, synchronous detector 8, subtraction unit 9, switch 10, memory unit 11, adder 12, calculation unit 13, control unit 14 generators of geneO 00 u 00

VI

VI

ratora 15 modulating signal and block 16 Total signal in the cross section of the first

measurement control sensor 2 sensor is equal to the sum

The method is implemented as follows: O + Ol + Ootr

zom. To simplify subsequent calculations

The continuous microwave signal from the output of ge-5 will be considered the module of the coefficient of the regenerator 1 passes through sensor 2 at the sensor 2 sensor output equal to one, i.e. communication

Liter 3, the output signal of each output probes with a small fcw line f. Actually through the phase shifter 4 arrivals) Ksv | of course, but the loss due to communication

on IE 5 PAR 6. 6. can be easily taken into account:

To the control input of a 90 ° section of fa-10. . i ()

zovraschatel 4c generator output 15 through ,, 61h |

block 14 enters a rectangular for example — i (wf) ..., 2 (ch1.h} ,,, Och

type meander frequency FM. In this case, e p; Je (-)

the output signal of the phase shifter 4 is preter- «e e / s; J / s; tJ

sings phase manipulation with deviation 15 j {(bg,, V) j | ri

phase 90 °. e J.

Microwave signals at the inputs of each of the Th-For subsequent calculations will present

The three probes of sensor 2 are (2) in simplified form:

the sum of the incident and reflected signals.us, - / um / к е ((1 / g

Falling and reflected signals in ce-20 j | v ™ Jf g

the first detector of sensor 2 can e ° 6I / „// g„, / “| a m P

present as. . / M ,.))

31Jv h 5 / j,

II .III / c e Wb iГДб - +

 PQA cb, 3.25 V (2) to simplify the idea that the phases

(.. The Oped signal and kCB are zero.

h0tr (sve ygo & cse + At the output of the first detector of sensor 2

r2 t M + signal will be equal

Rmgl v 2

./h. /, .. (1) 3 ° V W (e 4Mf 1 l t / eiit

where Decay is a continuous microwave signal, pro-x / Gpe1 / 5; 1a // ce / 2 / P, BC / co5 ((rOBts +

coming from the generator 1 to the input of the splitter L / L2 / / / l 3 s

) Goe (C-module and phase of the total coefficient + 4

reflection coefficient from the input de 35 td / G 06C | / ef // rn7 / cos (2Cf4-Cfr cpoew) - letter 3 (this includes reflections in the line

/ W / 5, J / Sic Jcos (cffCfЈ-Cf)

connection of the transmitter 2, the divisor 3, in the phase-gap + g || ots | / Hz, 1 // 5 | c & | coS (tf 4-Cf2-Cf 06) 4th base x 4 and all IE 5 that are in this / // ./ ,,,., .-,

the moment does not change); I SJ12 le -4Q F; “// Pi // sv || G e / C05 (avg Crg (/ yP

module and phase of transmission coefficient de-Output voltages from the outputs of the polishing 3 from the input of divider 3 to the input of measuring-next detectors of sensor 2 will be the current IE 5 that is being depleted, but without taking into account expression (3) taking into account the phases of the phase shifter 4 W e is the phase (phase shifted by their location in the line, high shift) of the phase shifter 4; 45 V, the currently measured IE 5 1 GPA module and the phase of the self-signal are subjected to phase shift keying from the reflection coefficient measured by phase emulation) l ie with the frequency Fm, the phase of the IE 5 (here includes connecting lines, b to take the value of transitional and matching devices, B50 including microwave connectors) 0 And f - yI SJCB I - module and the phase factor-signal Ugi will be for the first and second

an attribute that characterizes the j-ro bond, the measurement of the half-periods of manipulation equal to

currently available IE 5 with V / U / W / 5 // rn /

surrounding IE 5, i.e.55 M / SiJ /co./

S, S, J12,, S (, // Wco, (4,, l7U2Nt ,,, (4)

jЈi J12 / s, J- (cf, t, a / r064 |, 5;, /,

where Ksv is the coefficient of communication with the line v / g / s K-obI 2 / gsi, / | 5 ("/.

Sensor 2. / $; ,, / costcb-qW /Or.,,/,

d / H 06C | / ef // rn7 / cos (2Cf4-Cfr cpoew)

/ W / 5, J / Sic Jcos (cffCfЈ-Cf)

+ g || ots | / bc, 1 // 5 | c & | coS (tf 4-Cf2-Cf 06)

 / // ./ ,,,., .-,

516898776

 iv r 4 fh / s; j / 5 ,,

um ° ivnthl Ксв1 L oeu / Viui / wf The signals Upi and UP2 contain the second weak% + / s1 (J2 / 5, te /% a / r064fcos ((4fi)), which are inaccuracies.

-a / e // gp, / sob (h, 2}) + g / b1v // 5; „/ 5 Through switch 10, control

 Ј // c1 // g / which is performed from block 16, the signals

 1 - / - / | obi // b. “// pe / Up1 and Up2 are fed to blocks 11, where they are stored Cos r oeJ / W / .J / SuB / minimized.

 Cos (| i 4 z-tPoem) 4-1 / 5Hillrn J) lSignal input measurement, | slw || 5, tg | cos (|, (5) we currently have IE 5, optional

shifted in phase by 180 °, i.e. in the process

At the output of the selective amplifier 7 and manipulation, the angle p will receive the sign- synchronous detector 8 receive a signal, „,. . ",,, L equal p-l: and JT + 215 Substituting the values of p in the expressions c1 (u, l-uJ, / unaA // Kce / l" (3), receive at the output of voltage block 9

Vc, 4 5 "UcoeMr) -, ,,

- s-KJ J-Up (/ UnoA; / koefKc cg -8 / 5- (J | rn9 /

6Yy 1 // and% 06ts4) "(6) 20 xsin () + / 5itJ / 5, c6 | 5mq 2 3 (

./51s./g | | / Gi | / 5, -and | /51./. „,. .-2. -.

.6in {lf, -4t | bUp2 / UnOAl / l C6 / KS | C 8/5114 // GPE / 1

xco5 (c),) - 4/5; 4 | / 5; s. / So ff. where Key and Ced-factor transfer selek- 25v 4 I v / on // ICBI ZJ

The active amplifier 7 and the synchronous detector 8. The signals (10) and (11) also pass through the output of the selective amplifier 7 and the switches 10 are memorized by blocks of the synchronous detector 8 connected to 11.

to the third detector of sensor 2, the output is 30 Signals from blocks 11 are supplied to the correlating equilibrium adders 12, where feasible / H. / i / v Ch / A2 j / r / is the summation of the signals.

 Uc "a / lW / kce / KcJ4 / 5; J / rn3 / XU pl + UV HU p2 + and | Gr2.

/ with-. g- / c / Output voltages of the adder 12

(c | 1-T) t a / 5iia // 5icB / emC 2+ 35 will be equal

| / GobM // 5 11 // Gpe | ow () h-Us - / UnQA | 2 / KCB | 2K K - 6/5 / x

 / g05ts1 / 5; cV | (h) Lbi 4Kx / rn, / 5m (Q, ffh (12)

/ S J / r j / B flSice / smlCf, - 4 U / UnaA | 2 | k ,, e /

 (JWrn9 / c0e (4), M3)

The voltages (6) and (7) from the synchronous de-signals (12) and (13) are fed to block 13,

tectors 8 arrive at block 9, output 45 where operations are performed

the voltage of which is equal to П7г ..г,. , g, g

umHus u / unQA / / kc6 / x

ir1 Shpad12 iKCBi2 x Ckse b / 5t // Gpe / 3 (I}

xKsu Ked -8 U94 MGpe1H81p () - -aPctQfc-M-cp, -. (15)

 S.1 I

 S112 II S, CB I slntfJz. (8) Um signals with known | ipad1.1KSB1,

Key, Ked allows to evaluate the reflected signal module from the second block 9, which is a p-55 signal, and if ISnzl is taken into account, the signal from the second and fourth detectors can be measured, to evaluate the module of its own coefficients of sensor 2 „E1.

2 ,, D, Expression (13) has the form

  p + Ј 2 + fpe + t and allows

g / jPaA // & / cH1 (cd 8/5; 1a // Gp9 /

to estimate (at the known phase of the RM) the phase of the standard deviation.

Thus, it is shown how to measure the MSE of the 1st IE 5. In the same way, the MSE of other radiating elements is measured by the commands from block 16.

Compared with the known method, the measurement time is significantly reduced by eliminating the need to connect matched loads to the non-measurable at the moment IE

Claims (1)

Invention Formula A method for measuring the intrinsic reflectance of a radiating element of a phased antenna array (PAR), based on applying a manipulated microwave signal to the measured radiating element, extracting the reflected signal and the formation of the resulting signal of the interaction of the incident and reflected signals, characterized in that, in order to reduce the measurement time, The microwave signal is divided and fed simultaneously to all the radiating elements of the HEADLAMP, the manipulation of the microwave signal at the output of the measured radiating element is obtained by phase manipulation and 90 ° phase deviation The microwave signal directly at the input of the measured radiating element, promoted by the frequency F, the microwave signal is separated from the total reflected signal and its amplitude is recorded; the input of the measured radiating element is additionally shifted by 180 ° and the amplitude of the secondary extracted microwave frequency F-induced signal is summed with the previously stored amplitude.