JPH02206364A - Control method for pulse-width control system power converter apparatus - Google Patents
Control method for pulse-width control system power converter apparatusInfo
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- JPH02206364A JPH02206364A JP2215889A JP2215889A JPH02206364A JP H02206364 A JPH02206364 A JP H02206364A JP 2215889 A JP2215889 A JP 2215889A JP 2215889 A JP2215889 A JP 2215889A JP H02206364 A JPH02206364 A JP H02206364A
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- 238000003079 width control Methods 0.000 title claims description 9
- 238000006243 chemical reaction Methods 0.000 claims description 12
- 238000001514 detection method Methods 0.000 claims 1
- 239000004065 semiconductor Substances 0.000 claims 1
- 230000006698 induction Effects 0.000 abstract description 11
- 230000002457 bidirectional effect Effects 0.000 abstract description 2
- 238000010586 diagram Methods 0.000 description 6
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- MXBCYQUALCBQIJ-RYVPXURESA-N (8s,9s,10r,13s,14s,17r)-13-ethyl-17-ethynyl-11-methylidene-1,2,3,6,7,8,9,10,12,14,15,16-dodecahydrocyclopenta[a]phenanthren-17-ol;(8r,9s,13s,14s,17r)-17-ethynyl-13-methyl-7,8,9,11,12,14,15,16-octahydro-6h-cyclopenta[a]phenanthrene-3,17-diol Chemical compound OC1=CC=C2[C@H]3CC[C@](C)([C@](CC4)(O)C#C)[C@@H]4[C@@H]3CCC2=C1.C1CC[C@@H]2[C@H]3C(=C)C[C@](CC)([C@](CC4)(O)C#C)[C@@H]4[C@@H]3CCC2=C1 MXBCYQUALCBQIJ-RYVPXURESA-N 0.000 description 1
- 108091034117 Oligonucleotide Proteins 0.000 description 1
- 238000001467 acupuncture Methods 0.000 description 1
- 239000003990 capacitor Substances 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 238000004146 energy storage Methods 0.000 description 1
- 238000010438 heat treatment Methods 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 230000007935 neutral effect Effects 0.000 description 1
- 230000010363 phase shift Effects 0.000 description 1
- 230000001172 regenerating effect Effects 0.000 description 1
- 238000003756 stirring Methods 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明はパルス幅制御方式電力変換装置の制御方法に係
り、交流電源から直接具なった周波数の出力が得られ、
４象限運転も容易なことから、誘導電動機等のＡＣドラ
イブに適用して効果大であり、他に大容量の誘導加熱、
誘導攪拌への応用にも適しているパルス幅制御方式電力
変換装置を実現し易る制御方法に関するものである。[Detailed Description of the Invention] [Industrial Application Field] The present invention relates to a control method for a pulse width control type power conversion device, which enables output of a specific frequency to be obtained directly from an AC power supply,
Since four-quadrant operation is easy, it is highly effective when applied to AC drives such as induction motors, and is also useful for large-capacity induction heating,
The present invention relates to a control method that facilitates the realization of a pulse width control type power conversion device that is also suitable for application to induction stirring.
第４図は本発明の理解を容易にするため示したサイクロ
コンバータの主回路図であり、’Ｕ ＊ ｅＶ ＋ｅｗ
は三相交流電源、Ｌｌ、Ｏｌ、Ｌ２．０２はフィルタ、
ＳＡＵ”””ＳＣＷはスイッチング素子、ＩＭは負荷と
なる誘導電動機である。Figure 4 is a main circuit diagram of a cycloconverter shown to facilitate understanding of the present invention, and 'U * eV +ew
is a three-phase AC power supply, Ll, Ol, L2.02 is a filter,
SAU"""SCW is a switching element, and IM is an induction motor serving as a load.
ここに、サイクロコンバータは交流電源から直接異なっ
た周波数の交流を得るものであり、入出力とも三相の例
で示しであるが、単相、その他の多相であってもよい。Here, the cycloconverter directly obtains alternating currents of different frequencies from an alternating current power supply, and although both input and output are shown as three-phase examples, they may be single-phase or other multi-phase.
従来、第４回生回路例においては、スイッチング素子Ｓ
ＡＵ ＊ ８ＡＶ ＋ ＳＡＷ ＋ ＳＢＵ ＊ ＳＢ
Ｙ −ＳＢＷ ｒ ＳＣＵ ＋ｓｃｖ ｌ ｓｃｗに双
方向性スイッチング素子が、具体的には逆並列接続され
たサイリスタなどが用いられ、入出力周波数に比べて高
周波のチョッピングを行い、出力電圧・力率などを調整
することが行われている。Conventionally, in the fourth regenerative circuit example, the switching element S
AU * 8AV + SAW + SBU * SB
Y -SBW r SCU +scv l A bidirectional switching element, specifically a thyristor connected in anti-parallel, is used for scw, and it chops a high frequency compared to the input/output frequency and adjusts the output voltage, power factor, etc. Adjustments are being made.
しかし、その出力電圧は入力電圧の（１／２）までが限
度であり、高い出力が得られなかった。However, the output voltage was limited to (1/2) of the input voltage, and high output could not be obtained.
このことは、文献ＩＥＦ３Ｅ、ＴＲＡＮ８ＡＣＴＩＯＮ
ＯＮ ＰＯＷｇＲｇＬＥＯＴＲ，０ＮＩ０８．ＡＰＲＩ
Ｌ、１９８８゜ｒＩ−ｔｇｓＥＮＴ ＰＩ（，０ＧＥＳ
８ ＩＮ Ｔｌ（ＢＤＥＶＥＬＯＰＭＥＮＴ ＯＦ
５ＯＬＤ ５ＴＡＴＥ ＡＣＭＯＴＯＲＤＲＩ
ＶＩＪ等にも見られる。This is explained in the document IEF3E, TRAN8ACTION
ON POWgRgLEOTR,0NI08. APRI
L, 1988°rI-tgsENT PI(,0GES
8 IN Tl(BDEVELOPMENT OF
5OLD 5TATE ACMOTORDRI
It can also be seen in VIJ etc.
本発明は上述したような点に鑑みなされたもので、特に
ほぼ入力電圧に等しい出力電圧が得られ、かつ入力力率
なども制御可能な電力変換装置を実現し得る格別な制御
方法を提供するものである。The present invention has been made in view of the above-mentioned points, and particularly provides an exceptional control method capable of realizing a power conversion device that can obtain an output voltage substantially equal to the input voltage and also control the input power factor. It is something.
以下、本発明を図面に基づいて詳細説明する。Hereinafter, the present invention will be explained in detail based on the drawings.
まず、本発明に係る成力変換装置を第４図により説明す
る。First, the force conversion device according to the present invention will be explained with reference to FIG.
（５０、６０Ｈｚ等）の三相１源から異なった周波数（
例えばＯ〜１２０市）の成力を誘導１ば動機ＩＭに供給
することができ、かつスイッチング素子ＳＡＵ””ＳＣ
Ｗを高周波（例えば１〜２０に托Ｑのパルス幅制御する
ことにより、出力電圧をｉｇ整し入出力環流波形を正弦
波に近いものとしたことができるため、電動機損失の少
ない可変電圧・可変周波数（ＶＶＶＦ’）駆動を実現す
ることができる。(50, 60Hz, etc.) from one three-phase source to different frequencies (
For example, the power of 0 to 120) can be supplied to the induction 1 motor IM, and the switching element SAU""SC
By controlling the pulse width of W to a high frequency (for example, 1 to 20), the output voltage can be adjusted and the input/output circulation waveform can be made close to a sine wave. Frequency (VVVF') driving can be realized.
また、出力電流を電源のどの相から得るかを、スイッチ
ング素子ＳＡＵ””’ＳＣＷにより選択することにより
電源側力率を調整することができる・例えば、遅れ力率
の誘導電動機ＩＭを負荷とした場合でも電源側力率を１
としたことができ、かつ電流波形は正弦波に近いために
高調波も少なく、電源側に与える撹乱の少ない成力変換
装置としたことができる。In addition, the power factor on the power supply side can be adjusted by selecting from which phase of the power supply the output current is obtained using the switching element SAU""'SCW. For example, when an induction motor IM with a lagging power factor is used as the load. Even if the power factor on the power supply side is 1
In addition, since the current waveform is close to a sine wave, there are few harmonics, and it is possible to create a force conversion device that causes less disturbance to the power source side.
この種の成力変換装置は、負荷の各相の底流を電源の任
意の相から得ることができかつスイッチング素子がパル
ス幅制御されるため、ＰＷＭサイクロコンバータと呼ば
れる。This type of power conversion device is called a PWM cycloconverter because the undercurrent of each phase of the load can be obtained from any phase of the power supply and the switching elements are pulse width controlled.
ＰＷＭサイクロコンバータはつぎのような特長を有する
。The PWM cycloconverter has the following features.
（１）通常使用されている（コンバータ）−（インバー
タ）方式の成力変換装置のような直流リンク回路の平滑
リアクトル、平滑コンデンサなどのエネルギー蓄積要素
を必要としないため、小形で大容量の装置を製作し易い
。(1) It is a small and large-capacity device because it does not require energy storage elements such as smoothing reactors and smoothing capacitors in DC link circuits like the normally used (converter)-(inverter) type power conversion devices. Easy to produce.
（２１（コンバータ）−（インバータ）方式ニ比べて直
列に入るスイッチング素子数が少ないため、素子損失が
少なく効率を上げることができる。(21) Compared to the (converter)-(inverter) system, the number of switching elements connected in series is smaller, so element loss is reduced and efficiency can be increased.
（３）主回路構成より明らかな如く４象限運転がスイッ
チング素子の点弧操作のみで容易に実現できる。(3) As is clear from the main circuit configuration, four-quadrant operation can be easily achieved by simply igniting the switching elements.
係る第４図の主回路構成装置の制御方法につき、つぎに
そのスイッチング素子の点弧方法について説明する。す
なわち、前述の如く本点弧方式によれば、出力電圧とし
てほぼ入力電圧に等しいものを得ることができる。Regarding the method of controlling the main circuit configuration device shown in FIG. 4, a method of igniting the switching element will be described next. That is, as described above, according to this ignition method, it is possible to obtain an output voltage approximately equal to the input voltage.
第１図は本発明を説明するため示したスイッチング素子
の動作状態を表す説明図であり、誘導電動機１量ノＡ
、 Ｂ 、 Ｃ各相（ＤＦＫ圧指令１ＪＡ 、’ｓ 。FIG. 1 is an explanatory diagram showing the operating state of the switching element shown for explaining the present invention, and is an illustration showing the operating state of the switching element shown for explaining the present invention.
, B, C phases (DFK pressure command 1JA,'s.
υＣ＊と各相のスイッチング素子ｓＡＩ ＳＢ ＋ ｓ
ｃのスイッチング方法の関係を示したものである。ここ
に、スイッチング素子８人は第４図に示したスイッチン
グ素子ＳＡＵ ＋ ｓＡｖ＋ ＳＡＷの総称であり、他
のスイ、チング素子ＳＢ、Ｓｃも同様である。υC* and each phase switching element sAI SB + s
This figure shows the relationship between the switching methods of c. Here, the eight switching elements are a general term for the switching elements SAU+sAv+SAW shown in FIG. 4, and the same applies to the other switching elements SB and Sc.
まず、電圧指令υＡ ＊ ＵＢ ＋ひＣのうち一番低い
相はスイッチング素子により、電源は圧の一番低い相に
接続される〇
区間工を例にとると、電圧指令υＡ ’Ｈに比べて電
圧指令υＣが最低ゆえ、スイッチング素子Ｓｃは誘導電
動機ＩＭのＣ相を電源の最低１位ｅＭＩＮをもつ相に接
続する。ここで、
ａｓｏＮ＝ＭＩＮ［ｅｕ、ｅｖ＋ｅｗｌである。仮１（
、（ｅｖ≦ｅｗ）でかつ（ｅｖ≦εＵ）であれば、（ｅ
ＭｒＮ＝’ｖ ）ゆえ、誘導電動機ＩＭのＣ相は電源の
Ｕ相に接続される。First, taking as an example a section construction where the lowest phase of the voltage command υA * UB + HIC is connected to the switching element and the power supply is connected to the phase with the lowest voltage, compared to the voltage command υA 'H. Since the voltage command υC is the lowest, the switching element Sc connects the C phase of the induction motor IM to the phase of the power supply having the lowest position eMIN. Here, asoN=MIN[eu, ev+ewl. Temporary 1 (
, (ev≦ew) and (ev≦εU), then (e
MrN='v) Therefore, the C phase of the induction motor IM is connected to the U phase of the power supply.
すなわち、スイッチング素子８ＣＶが閉路され、スイッ
チング素子５ＣＵｓＳＣＷは開路される。That is, switching element 8CV is closed, and switching element 5CUsSCW is opened.
一方、電圧指令が最低でない他の相は電源の最大電圧ε
ＭＡＸと最低上位ａＭＩＮ間でパルス幅制御（ＰＷＭ制
御）される。ここで、
ｅ、ＡＸ＝ＭＡｘｃ ｅｕｒ已Ｖ ＋ ’Ｗ ］である
。On the other hand, for other phases whose voltage command is not the lowest, the maximum voltage ε of the power supply
Pulse width control (PWM control) is performed between MAX and the lowest aMIN. Here, e, AX=MAXc eur 已V + 'W].
さらに前述の例に従い区間工について述べると、スイッ
チング素子ＳＡは出力線間電圧指令１７ＡＣ＊により、
スイッチング素子ＳＢは出力線間電圧指令υＢｃ＊によ
り、それぞれ鍼源のεＭＡＸ＋ ’ＭＥＮ間でＰＷＭ制
御される。Furthermore, referring to the section construction according to the above-mentioned example, the switching element SA is activated by the output line voltage command 17AC*.
The switching element SB is PWM-controlled between εMAX+'MEN of each acupuncture source by the output line voltage command υBc*.
他の区間１１．ＯＩについても各相が入れ換わるのみで
同様の動作を行う。Other sections 11. The same operation is performed for OI, only the phases are replaced.
つぎに、ＰＷＭ制御の方法を第２図により説明示したも
のと考えてよい。Next, the method of PWM control may be considered to be explained and illustrated with reference to FIG.
ここに、第２図（イ）は三相交流１１ ｒＡ”ｕ ＊ε
Ｖ＊”Ｗの４［圧を、第２図（０）ハ（ｅＭＡＸ−ｅＭ
ＩＮ ） ｔｃヨり振ｓ変調されたキャリア三角波と出
力線間電圧指令す
υ８．ヲ示し、スイッチング素子ＳＡ ＊ ＳＢは三角
波とυＢＣの交点に従ってＰＷＭ制御されるものとなる
。Here, Fig. 2 (a) shows three-phase AC 11 rA”u *ε
4 [pressure of V*”W, Fig. 2 (0) C (eMAX-eM
IN) tc yaw s modulated carrier triangular wave and output line voltage command υ8. The switching elements SA*SB are PWM-controlled according to the intersection of the triangular wave and υBC.
また、第２図（ハ）は閉路されるスイッチング素子を示
したものであり、スイッチング素子Ｓｃについて言えば
、時刻Ｔ２まではＶ相素子すなわちスイッチング素子Ｓ
ＣＶが、時刻Ｔ２以降はＷ相素子のスイッチング素子Ｓ
ＣＷが閉路されることを示している。Moreover, FIG. 2(C) shows a switching element that is closed, and regarding the switching element Sc, until time T2, the switching element Sc is a V-phase element, that is, the switching element Sc.
CV is the switching element S of the W-phase element after time T2.
This indicates that CW is closed.
スイッチング素子ＳＢについて見ると、時刻ＴＩと時刻
Ｔ２１ｕｌ ’Ｔ’ ｇｉ、（％Ａｘ＝８ｕ ） ｔ
（’ａ（ＩＮ＝ｅＶ ） テｉｊ。Looking at the switching element SB, time TI and time T21ul 'T' gi, (%Ax=8u) t
('a(IN=eV) Teij.
るから、スイッチング素子ｓＢυ＋ＳＢＹにより、第２
図（０）の三角波と１ｒＢＣとの交点に従ってＰＷＭ制
御される。当然ながら、スイッチング素子８ＢＷはこの
間開路を保つ。Therefore, the second
PWM control is performed according to the intersection of the triangular wave and 1rBC in figure (0). Naturally, the switching element 8BW remains open during this time.
第２図に）は（源の中性点に対するＢ、Ｃ相の出力１圧
υＢ、υＣを示したものである。ここに、時刻Ｔ１〜時
刻Ｔ２間に着目すると、出力電圧ｖＣはスイッチング素
子Ｓｃｖが閉路されているため、υｃ＝８ｖ （＝ｅＭ
ＩＮ ）
であり、出力４圧υＢはスイッチング素子ＳＢＵが閉路
されている二
υＢ＝εσ（〒８ＭＡＸ ）
スイッチング素子ＳＢＶが閉路されている間υｓ ＝ｅ
ｖ （＝ＱＭＩＮ ）
となり、図示の如（ＰＷＭ制御された矩形波となるＯ
第２図（ホ）は出力線間電圧υ８Ｃ（＝１）Ｂ−ひＣ）
波形を示したものである。(Figure 2) shows the output voltages υB and υC of the B and C phases with respect to the neutral point of the source.If we pay attention to the period from time T1 to time T2, the output voltage vC is the voltage of the switching element. Since Scv is closed, υc=8v (=eM
IN ), and the output 4 voltage υB is 2 υB = εσ (〒8MAX) while the switching element SBU is closed, υs = e
v (=QMIN), as shown in the figure (it becomes a PWM-controlled rectangular wave).
This shows the waveform.
かくの如き点弧方式より明らかなように、出力線間電圧
υＩＩｃは出力線間電圧指令υＢＣに従って已ＭＡＸ
＊ ’ＭＩＮ間でＰＷＭ制御されるため、出力線間電圧
指令ｙＢＣにより出力電圧および屯田波形の制御が可能
である。As is clear from such an ignition method, the output line voltage υIIc is MAX according to the output line voltage command υBC.
* 'Since PWM control is performed between MIN, the output voltage and the Tonta waveform can be controlled by the output line voltage command yBC.
出力電圧値としても、出力線間電圧υＢＣのピーク値が
（’ＭＡＸ−ｅＭｒＮ）までとれるとしたさ、入力屯田
と等しいところまで上げることが可能である。As for the output voltage value, assuming that the peak value of the output line voltage υBC can be taken up to ('MAX-eMrN), it is possible to raise it to a point equal to the input voltage.
なお、（ＬＩ Ｏｆ）、（Ｌ２ Ｃ２）は入出カル流中
のキャリア周波数成分を除去し、より正弦波に近づける
ため設けられる。Note that (LI Of) and (L2 C2) are provided in order to remove the carrier frequency component in the input/output Cull flow and make it closer to a sine wave.
つぎにまた、第２図は出力電圧をυＢＣ＊により電圧制
御したものであるが、さらに出力電流制御に適用した例
を第３図に示す。Next, while FIG. 2 shows the output voltage controlled by υBC*, FIG. 3 shows an example in which it is further applied to output current control.
第３図（イ）は第２図（イ）と同様のｅＵ ＋ ’Ｖ
＋ ｅＷを示したものであり、第３図（ロ）はＢ相の出
力直流指令Ｌｎ＊と市流実測値ｔＢを示したものである
。Figure 3 (a) is the same eU + 'V as in Figure 2 (a).
+eW, and FIG. 3(b) shows the B-phase output DC command Ln* and the actual measured value tB of the commercial current.
第３図（ハ）はＢ相の出力電圧ｖＢを示したものであり
、ここで’ＭＡＸ ＋ ”Ｍ Ｉ Ｎの選び方は前述の
通りである。FIG. 3(C) shows the output voltage vB of the B phase, and the method of selecting 'MAX + MIN' is as described above.
すなわち、出力直流指令ＬＢ が４流実測値ＬＢより
大きい区間では（νＢ ＝ ｅＭＡＸ ）に、小さい区
間では（υＢ＝εＭＩＮ ）となるようスイッチングを
行う。ここに、図は一定時間毎に上述の判別を行い、電
流かようにして、第２図において出力線間電圧υｎｃ
カｅＭＡｘ ＋ ”ＭＩＮ間でＰＷＭ制御されており、
１源の最高電位の相が主として負荷に電流を供給する。That is, switching is performed so that the output DC command LB is larger than the measured value LB of the 4th current (νB=eMAX), and the output DC command LB is smaller than the measured value LB (υB=εMIN). Here, the figure performs the above-mentioned determination at regular intervals, and in this way, the output line voltage υnc is determined in Figure 2.
PWM control is performed between the eMAX + MIN and
The highest potential phase of one source primarily supplies current to the load.
従って、電源側力率は負荷力率によって一義的に定まっ
てしまい、誘導成動機ＩＭのような遅れ力率の負荷では
嶋源側も遅れ力率となる。Therefore, the power factor on the power source side is uniquely determined by the load power factor, and in a load with a lagging power factor such as the induction motor IM, the Shimamoto side also has a lagging power factor.
しかし、電源相を’ＭＡＸ ＊ ｅＭＩＮ以外の相とし
たことにより、出力最高電圧の低下は招くものの、電源
側力率を任意に、制御、することができる。However, by setting the power supply phase to a phase other than 'MAX*eMIN, it is possible to arbitrarily control the power factor on the power supply side, although this causes a decrease in the maximum output voltage.
例えば、第２図の（′ｒ２〜Ｔ３）間ではスイッチング
素子ＳＢカ（ｅ−ｕ ＝ｅＭＡＸ ）と（８Ｗ＝８Ｍｘ
Ｎ）間でＰＷＭ制御され、Ｂ相に遅れ電流を供給してい
るところを、εＶと８ｗ間の制御により以前と同位相の
電流を供給するようにすることにより、電源電圧位相が
遅れて同位相としたことが可能である。For example, between ('r2 and T3) in FIG. 2, switching element SB power (eu = eMAX) and (8W = 8Mx
By controlling between εV and 8W to supply current in the same phase as before, the power supply voltage phase is delayed and the same current is supplied to the B phase. It is possible to set it as a phase.
そして、ａＵとｅｖの割り合いをＰＷＭｆｆｉｌＪ鐸す
ることにより、電源屯田の移相量をＡｌ４ｍすることが
できるのは勿論である。Of course, by controlling the ratio between aU and ev, the amount of phase shift of the power source can be reduced to Al4m.
以上詳述した如く本発明によれば、ＰＷＭサイクロコン
バータの以前の特色を失うことなく出力最高電圧を上昇
させ、出力電流の制御も容易に行うことが可能な電力変
換装置を実現し得る格別な制御方法を提供することがで
き、産業上の効果は極めて犬である。As detailed above, according to the present invention, it is possible to realize an exceptional power conversion device that can increase the maximum output voltage and easily control the output current without losing the previous features of the PWM cycloconverter. It can provide a control method and the industrial effect is extremely dog.
第１図〜第３図は本発明を説明するため示した、スイッ
チング素子の動作状態を表した説明図、第２図は第１図
を展開した各部波形図および第３図は底流制御の適用例
の波形図である。第４図は本発明の理解を容易にするた
め示したサイクロコンバータの主回路図である。
ｖＡ＊ｒυ−１υｃ＊−−４，圧指令、ｓＡｌ ｓ、
ｌ ｓｃ １ｓＡｔｒ−ｓｃｗ・・・・・・スイッチン
グ素子、υＡＢ ＋・νＡｃ＊＊
＊
ｖａｃ ・・・・・・出力線間電圧指令、ＶＢ ＊
Ｚ’Ｃ・・・・・・出力ぼ・ ＊
圧、υＢＣ・・・・・・出力線間電圧、しＢ ・・・・
・・出力電流指令、し８・・・・・・電流実測値。Figures 1 to 3 are explanatory diagrams showing the operating states of switching elements, shown to explain the present invention, Figure 2 is a waveform diagram of each part expanded from Figure 1, and Figure 3 is an application of undercurrent control. FIG. 3 is an example waveform diagram. FIG. 4 is a main circuit diagram of a cycloconverter shown to facilitate understanding of the present invention. vA*rυ-1υc*--4, pressure command, sAl s,
l sc 1sAtr-scw...Switching element, υAB +・νAc** * vac...Output line voltage command, VB *
Z'C...Output voltage, υBC...Output line voltage, B...
...Output current command, 8...Actual current measurement value.
Claims (4)
己消弧形半導体スイッチを用い、交流電源より任意の周
波数の多相交流出力を得るパルス幅制御方式電力変換装
置の制御方法において、出力電圧指令が最も低い電圧の
相に関係するスイッチ群を電源電圧の最も低電位の相に
接続するとともに、出力の他の相のスイッチ群は電源の
最高位電位相および最低位電位相のいずれかに接続する
ようにし、この両者への選択接続するオンオフ比を変え
ることにより出力電圧を調整することを特徴としたパル
ス幅制御方式電力変換装置の制御方法。(1) In a control method for a pulse width control type power conversion device that obtains multiphase AC output of any frequency from an AC power supply using a self-extinguishing semiconductor switch that can conduct or cut off the main circuit current in response to an energizing signal. , the switch group related to the phase with the lowest output voltage command is connected to the phase with the lowest potential of the power supply voltage, and the switch groups of the other output phases are connected to the highest potential phase and lowest potential phase of the power supply. 1. A method for controlling a pulse width control type power conversion device, characterized in that the output voltage is adjusted by connecting one of the two and changing the on/off ratio of the selective connection to both.
チ群を電源の最高電位相に接続し、指令値より大なる場
合は最低電位相に接続することにより出力電流を調整す
ること特徴とした請求項第（１）項記載のパルス幅制御
方式電力変換装置の制御方法。(2) When the output current is smaller than the command value, the switch group of that phase is connected to the highest voltage phase of the power supply, and when it is larger than the command value, the output current is adjusted by connecting it to the lowest voltage phase. A method for controlling a pulse width control type power conversion device according to claim (1).
択接続することにより、電源側あるいは出力側の力率調
整を行うことを特徴とした請求項第（１）項および第（
２）項記載のパルス幅制御方式電力変換装置の制御方法
。(3) The power factor of the power supply side or the output side is adjusted by selectively connecting to a power supply phase other than the highest or lowest phase of the power supply.
2) A method for controlling a pulse width control type power converter according to item 2).
電流を制御することを特徴とした請求項第（２）項記載
のパルス幅制御方式電力変換装置の制御方法。(4) A method for controlling a pulse width control type power conversion device according to claim (2), further comprising providing a power supply side input current detection means and controlling the power supply current.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1022158A JPH0744834B2 (en) | 1989-01-31 | 1989-01-31 | Pulse width control power converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1022158A JPH0744834B2 (en) | 1989-01-31 | 1989-01-31 | Pulse width control power converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH02206364A true JPH02206364A (en) | 1990-08-16 |
| JPH0744834B2 JPH0744834B2 (en) | 1995-05-15 |
Family
ID=12075029
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP1022158A Expired - Lifetime JPH0744834B2 (en) | 1989-01-31 | 1989-01-31 | Pulse width control power converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0744834B2 (en) |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0852425A1 (en) * | 1995-09-08 | 1998-07-08 | Kabushiki Kaisha Yaskawa Denki | Power converter and power converting method |
| JPH1118489A (en) * | 1997-06-19 | 1999-01-22 | Toyo Electric Mfg Co Ltd | Drive controller for synchronous motor |
| JP2004222337A (en) * | 2003-01-09 | 2004-08-05 | Fuji Electric Holdings Co Ltd | Ac-ac power converter |
| JP2006020389A (en) * | 2004-06-30 | 2006-01-19 | Yaskawa Electric Corp | Noise filter and motor drive mounted with it |
| WO2006112275A1 (en) * | 2005-04-15 | 2006-10-26 | Kabushiki Kaisha Yaskawa Denki | Matrix converter apparatus |
| JP2006325327A (en) * | 2005-05-19 | 2006-11-30 | Toyo Electric Mfg Co Ltd | Protecting unit of matrix converter |
| JP2009535013A (en) * | 2006-04-24 | 2009-09-24 | パワー コンサベイション リミテッド | Harmonic current suppression and power saving in nonlinear load systems |
-
1989
- 1989-01-31 JP JP1022158A patent/JPH0744834B2/en not_active Expired - Lifetime
Cited By (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0852425A4 (en) * | 1995-09-08 | 1999-12-29 | Yaskawa Denki Seisakusho Kk | Power converter and power converting method |
| EP0852425A1 (en) * | 1995-09-08 | 1998-07-08 | Kabushiki Kaisha Yaskawa Denki | Power converter and power converting method |
| JPH1118489A (en) * | 1997-06-19 | 1999-01-22 | Toyo Electric Mfg Co Ltd | Drive controller for synchronous motor |
| JP2004222337A (en) * | 2003-01-09 | 2004-08-05 | Fuji Electric Holdings Co Ltd | Ac-ac power converter |
| JP2006020389A (en) * | 2004-06-30 | 2006-01-19 | Yaskawa Electric Corp | Noise filter and motor drive mounted with it |
| US7782643B2 (en) | 2005-04-15 | 2010-08-24 | Kabushiki Kaisha Yaskawa Denki | Matrix converter apparatus |
| WO2006112275A1 (en) * | 2005-04-15 | 2006-10-26 | Kabushiki Kaisha Yaskawa Denki | Matrix converter apparatus |
| GB2439035A (en) * | 2005-04-15 | 2007-12-12 | Yaskawa Denki Seisakusho Kk | Matrix converter apparatus |
| GB2439035B (en) * | 2005-04-15 | 2008-10-22 | Yaskawa Denki Seisakusho Kk | Matrix converter apparatus |
| JP4803177B2 (en) * | 2005-04-15 | 2011-10-26 | 株式会社安川電機 | Matrix converter device |
| KR100963725B1 (en) * | 2005-04-15 | 2010-06-14 | 가부시키가이샤 야스카와덴키 | Matrix converter device |
| JP2006325327A (en) * | 2005-05-19 | 2006-11-30 | Toyo Electric Mfg Co Ltd | Protecting unit of matrix converter |
| JP4640794B2 (en) * | 2005-05-19 | 2011-03-02 | 東洋電機製造株式会社 | Matrix converter protection device |
| JP2009535013A (en) * | 2006-04-24 | 2009-09-24 | パワー コンサベイション リミテッド | Harmonic current suppression and power saving in nonlinear load systems |
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0744834B2 (en) | 1995-05-15 |
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