JP5650276B2 - Rotor and rotating electric machine equipped with the same - Google Patents

Description

  The present invention relates to a rotating electrical machine and an electric vehicle including the rotating electrical machine.

  Since a drive motor used in an electric vehicle or a hybrid vehicle is required to have a large output, a permanent magnet motor using a rare earth sintered magnet that retains powerful energy is generally used. As the drive motor, an embedded magnet motor that can satisfy the requirements of a low speed and a large torque and a wide range of rotation speed is used among permanent magnet motors.

  By the way, the torque pulsation of the motor causes noise and vibration, and particularly in an electric vehicle, there is a problem that the torque pulsation on the low speed side deteriorates the riding comfort. Conventional motors generally employ a countermeasure for skewing to reduce torque pulsation. For example, a motor is known in which a groove is provided in an electromagnetic steel plate on the outer periphery side of a magnet that is embedded, and the groove is shifted in the axial direction (see, for example, Patent Document 1).

JP 2005-176424 A

  In the motor provided with a groove on the outer peripheral side of the magnet described above, for example, the groove is provided in a place where the magnetic flux flows both in the non-energized state and in the energized state. If a groove is provided at a position where the cogging torque increases and the cogging torque decreases, torque pulsation during energization increases.

  An object of the present invention is to improve motor performance (for example, efficiency, reliability, cost performance, or productivity).

In order to solve the above problems, for example, the configuration described in the claims is adopted. The present application includes a plurality of means for solving the above-described problems. To give an example, the present application has a rotor core in which a hole into which a magnet is inserted is formed, a permanent magnet is inserted into the hole, and the permanent A rotor in which a magnetic auxiliary salient pole portion is formed between poles of a magnet, wherein a magnetic air gap is provided on a side surface of the permanent magnet, and is symmetrical with respect to the d axis and asymmetric with respect to the q axis. A second magnetic air gap is formed in the magnetic auxiliary salient pole portion of the rotor core, and the second magnetic air gap is such that torque pulsation during energization is canceled in a cross section perpendicular to the axial direction. provided deviated to the right or left with respect to the axis, the second magnetic air gap is provided independently of the magnetic gap, the pole pitch τp of the permanent magnet, the permanent magnet and a side surface When the angle combined with the magnetic gap provided in is τg, Ishianakyokukodo .tau.g / .tau.p is characterized in that 0.9 to 0.5.

  According to the present invention, motor performance (for example, efficiency, reliability, cost performance, or productivity) can be improved.

1 shows a schematic configuration of a hybrid electric vehicle equipped with a rotating electric machine according to an embodiment of the present invention. The circuit diagram of the power converter device 600 of FIG. 1 is shown. Sectional drawing of the rotary electric machine 200 or the rotary electric machine 202 of FIG. 1 is shown. The perspective view of the rotor core 252 of FIG. 3 is shown. The disassembled perspective view of the rotor core 252 of FIG. 3 is shown. AA sectional drawing of the stator 230 and the rotor 250 of FIG. 3 is shown. FIG. 4 shows a BB cross-sectional view of the stator 230 and the rotor 250 of FIG. 3. The AA sectional view which expanded the neighborhood of permanent magnet 254b of Drawing 3 is shown. The BB sectional drawing which expanded the vicinity of the permanent magnet 254b of FIG. 3 is shown. An explanatory view of reluctance torque is shown. The magnetic flux distribution of the AA cross section at the time of non-energization is shown. The magnetic flux distribution of the rotary electric machine only of the area | region 401 is shown. The magnetic flux distribution of the rotary electric machine only of the area | region 402 is shown. The waveform of the conging torque at the time of non-energization is shown. The waveform of the line induced voltage at the time of non-energization is shown. The magnetic flux distribution of the AA cross section at the time of electricity supply is shown. The magnetic flux distribution of the rotary electric machine only of the area | region 401 is shown. The magnetic flux distribution of the rotary electric machine only of the area | region 402 is shown. The waveform of torque pulsation during energization is shown. The waveform of the line voltage at the time of energization is shown. FIG. 5 is a diagram for explaining conging torque reduction, and is a cross-sectional view showing a part of a stator core 232 and a rotor 250. It is a figure which shows the relationship between ratio of magnet pole arc degree (tau) m / (tau) p, and conging torque. It is a figure which shows the maximum torque at the time of changing magnet pole arc degree τm / τp and magnet hole pole arc degree τg / τp. The cross section of the stator 230 and the rotor 250 of the surface magnet type rotary electric machine which makes other embodiment of this invention is shown. The cross section of the stator 230 and the rotor 250 of the rotary electric machine of the type which has arrange | positioned the several magnet which makes other embodiment of this invention in the V hour shape is shown. The cross section of the stator 230 and the rotor 250 which make other embodiment of this invention is shown. The cross section of the stator 230 and the rotor 250 which make other embodiment of this invention is shown. The cross section of the stator 230 and the rotor 250 which make other embodiment of this invention is shown. The cross section of the stator 230 and the rotor 250 which make other embodiment of this invention is shown. It is a figure which shows the cross section of the stator 230 which makes other embodiment of this invention, and the rotor 250, and shows the rotary electric machine of concentrated winding. The perspective view of the rotor core 252 which makes other embodiment of this invention is shown. The disassembled perspective view of the rotor core 252 which makes other embodiment of this invention is shown. The AA cross section which passes through the part of the core 301 of the stator 230 and the rotor 250 is shown. FIG. 5 shows a B-B cross section through a portion of core 302 of stator 230 and rotor 250. FIG. The figure which expanded and showed the vicinity of the permanent magnet 254b of an AA cross section. The figure which expanded and showed the vicinity of the permanent magnet 254b of a BB cross section. The surface magnet type rotary electric machine which makes the other Example of this invention is shown. The rotary electric machine of the type which has arrange | positioned the several magnet which makes the other Example of this invention in the V hour shape is shown. It is a figure which shows the cross section of the stator 230 and the rotor 250, and shows the rotary electric machine which provided the two magnetic space | gap 258 for every auxiliary salient pole part 259. FIG. Sectional drawing of the stator 230 and the rotor 250 which comprise the other Example of this invention is shown. Sectional drawing of the stator 230 and the rotor 250 which comprise the other Example of this invention is shown. Sectional drawing of the stator 230 and the rotor 250 which comprise the other Example of this invention is shown. It is a figure which shows the cross section of the stator 230 and the rotor 250, and shows the rotary electric machine of concentrated winding.

  Hereinafter, embodiments of the present invention will be described with reference to the drawings.

  As will be described below, the rotating electrical machine according to the present embodiment can suppress the conging torque when not energized and the torque pulsation when energized, and can realize a small size, low cost, and low torque pulsation. Therefore, for example, it is suitable as a driving motor for an electric vehicle, and it is possible to provide an electric vehicle that has low vibration, low noise, and is comfortable to ride. The rotating electrical machine according to the present embodiment can be applied to a pure electric vehicle that runs only by the rotating electrical machine or a hybrid type electric vehicle that is driven by both the engine and the rotating electrical machine. Explained.

  FIG. 1 is a diagram showing a schematic configuration of a hybrid electric vehicle equipped with a rotating electrical machine according to an embodiment of the present invention. The vehicle 100 is mounted with an engine 120, a first rotating electrical machine 200, a second rotating electrical machine 202, and a battery 180. The battery 180 supplies DC power to the rotating electrical machines 200 and 202 when the driving force by the rotating electrical machines 200 and 202 is required, and receives DC power from the rotating electrical machines 200 and 202 during regenerative travel. Transfer of direct-current power between the battery 810 and the rotating electrical machines 200 and 202 is performed via the power conversion device 600. Although not shown, the vehicle is equipped with a battery that supplies low-voltage power (for example, 14 volt system power) and supplies DC power to a control circuit described below.

  Rotational torque generated by engine 120 and rotating electrical machines 200 and 202 is transmitted to front wheel 110 via transmission 130 and differential gear 132. The transmission 130 is controlled by a transmission control device 134, and the engine 120 is controlled by an engine control device 124. The battery 180 is controlled by the battery control device 184. The transmission control device 134, the engine control device 124, the battery control device 184, the power conversion device 600 and the integrated control device 170 are connected by a communication line 174.

  The integrated control device 170 transmits information representing the respective states from the transmission control device 134, the engine control device 124, the power conversion device 600, and the battery control device 184, which are lower-level control devices than the integrated control device 170, to the communication line. Receive via 174. The integrated control device 170 calculates a control command for each control device based on these pieces of information. The calculated control command is transmitted to each control device via the communication line 174.

  The high voltage battery 180 is formed of a secondary battery such as a lithium ion battery or a nickel metal hydride battery, and outputs a high voltage DC power of 250 volts to 600 volts or more. The battery control device 184 outputs the discharge status of the battery 180 and the status of each unit cell battery constituting the battery 180 to the integrated control device 170 via the communication line 174.

  When integrated control device 170 determines that charging of battery 180 is necessary based on information from battery control device 184, integrated control device 170 issues an instruction for power generation operation to power conversion device 600. The integrated control device 170 mainly manages the output torque of the engine 120 and the rotating electrical machines 200 and 202, and calculates the total torque and torque distribution ratio between the output torque of the engine 120 and the output torque of the rotating electrical machines 200 and 202. Then, a control command is transmitted to the transmission control device 134, the engine control device 124, and the power conversion device 600 based on the calculation processing result. Based on the torque command from the integrated control device 170, the power conversion device 600 controls the rotating electrical machines 200 and 202 so that torque output or generated power is generated as commanded.

  The power conversion device 600 is provided with a power semiconductor that constitutes an inverter for operating the rotating electrical machines 200 and 202. The power conversion device 600 controls the switching operation of the power semiconductor based on a command from the integrated control device 170. By such a power semiconductor switching operation, the rotating electrical machines 200 and 202 are operated as an electric motor or a generator.

  When the rotary electric machines 200 and 202 are operated as an electric motor, DC power from the high-voltage battery 180 is supplied to the DC terminal of the inverter of the power conversion device 600. The power converter 600 converts the supplied DC power into three-phase AC power by controlling the switching operation of the power semiconductor, and supplies it to the rotating electrical machines 200 and 202. On the other hand, when the rotating electrical machines 200 and 202 are operated as a generator, the rotors of the rotating electrical machines 200 and 202 are rotationally driven with a rotational torque applied from the outside, and the stator windings of the rotating electrical machines 200 and 202 are three-phased. AC power is generated. The generated three-phase AC power is converted into DC power by the power converter 600, and charging is performed by supplying the DC power to the high-voltage battery 180.

  FIG. 2 shows a circuit diagram of the power converter 600 of FIG. The power conversion device 600 is provided with a first inverter device for the rotating electrical machine 200 and a second inverter device for the rotating electrical machine 202. The first inverter device includes a power module 610, a first drive circuit 652 that controls the switching operation of each power semiconductor 21 of the power module 610, and a current sensor 660 that detects the current of the rotating electrical machine 200. . The drive circuit 652 is provided on the drive circuit board 650. On the other hand, the second inverter device includes a power module 620, a second drive circuit 656 that controls the switching operation of each power semiconductor 21 in the power module 620, and a current sensor 662 that detects the current of the rotating electrical machine 202. ing. The drive circuit 656 is provided on the drive circuit board 654. The control circuit 648 provided on the control circuit board 646, the capacitor module 630, and the transmission / reception circuit 644 mounted on the connector board 642 are commonly used by the first inverter device and the second inverter device.

  The power modules 610 and 620 operate according to drive signals output from the corresponding drive circuits 652 and 656, respectively. Each of the power modules 610 and 620 converts DC power supplied from the battery 180 into three-phase AC power and supplies the power to stator windings that are armature windings of the corresponding rotating electric machines 200 and 202. Further, the power modules 610 and 620 convert AC power induced in the stator windings of the rotating electric machines 200 and 202 into DC and supply it to the high voltage battery 180.

  The power modules 610 and 620 include a three-phase bridge circuit as shown in FIG. 2, and series circuits corresponding to the three phases are electrically connected in parallel between the positive electrode side and the negative electrode side of the battery 180, respectively. ing. Each series circuit includes a power semiconductor 21 constituting an upper arm and a power semiconductor 21 constituting a lower arm, and these power semiconductors 21 are connected in series. The power module 610 and the power module 620 have substantially the same circuit configuration as shown in FIG. 2, and the power module 610 will be described as a representative here.

  In the present embodiment, an IGBT (insulated gate bipolar transistor) 21 is used as a switching power semiconductor element. The IGBT 21 includes three electrodes, a collector electrode, an emitter electrode, and a gate electrode. A diode 38 is electrically connected between the collector electrode and the emitter electrode of the IGBT 21. The diode 38 includes two electrodes, a cathode electrode and an anode electrode. The cathode electrode is the collector electrode of the IGBT 21 and the anode electrode is the IGBT 21 so that the direction from the emitter electrode to the collector electrode of the IGBT 21 is the forward direction. Each is electrically connected to the emitter electrode.

  A MOSFET (metal oxide semiconductor field effect transistor) may be used as the switching power semiconductor element. The MOSFET includes three electrodes, a drain electrode, a source electrode, and a gate electrode. In the case of a MOSFET, a parasitic diode whose forward direction is from the drain electrode to the source electrode is provided between the source electrode and the drain electrode, so there is no need to provide the diode 38 of FIG.

  The arm of each phase is configured by electrically connecting the source electrode of the IGBT 21 and the drain electrode of the IGBT 21 in series. In the present embodiment, only one IGBT for each upper and lower arm of each phase is shown, but since the current capacity to be controlled is large, a plurality of IGBTs are actually electrically connected in parallel. ing. Below, in order to simplify description, it demonstrates as one power semiconductor.

  In the example shown in FIG. 2, each upper and lower arm of each phase is composed of three IGBTs. The drain electrode of the IGBT 21 of each upper arm of each phase is electrically connected to the positive electrode side of the battery 180, and the source electrode of the IGBT 21 of each lower arm of each phase is electrically connected to the negative electrode side of the battery 180. The middle point of each arm of each phase (the connection portion between the source electrode of the upper arm side IGBT and the drain electrode of the lower arm side IGBT) is the armature winding (fixed) of the corresponding phase of the corresponding rotating electric machine 200, 202. Is electrically connected to the secondary winding.

  The drive circuits 652 and 656 constitute a drive unit for controlling the corresponding inverter devices 610 and 620, and generate a drive signal for driving the IGBT 21 based on the control signal output from the control circuit 648. To do. The drive signals generated by the drive circuits 652 and 656 are output to the gates of the power semiconductor elements of the corresponding power modules 610 and 620, respectively. Each of the drive circuits 652 and 656 is provided with six integrated circuits that generate drive signals to be supplied to the gates of the upper and lower arms of each phase, and the six integrated circuits are configured as one block.

  The control circuit 648 constitutes a control unit of each of the inverter devices 610 and 620, and is constituted by a microcomputer that calculates a control signal (control value) for operating (turning on / off) a plurality of switching power semiconductor elements. ing. The control circuit 648 receives a torque command signal (torque command value) from the host controller, sensor outputs of the current sensors 660 and 662, and sensor outputs of the rotation sensors mounted on the rotating electrical machines 200 and 202. The control circuit 648 calculates a control value based on these input signals and outputs a control signal for controlling the switching timing to the drive circuits 652 and 656.

  The transmission / reception circuit 644 mounted on the connector board 642 is for electrically connecting the power conversion apparatus 600 and an external control apparatus, and communicates information with other apparatuses via the communication line 174 in FIG. Send and receive. Capacitor module 630 constitutes a smoothing circuit for suppressing fluctuations in the DC voltage caused by the switching operation of IGBT 21, and is electrically connected to the DC side terminal of first power module 610 or second power module 620. Connected in parallel.

  3 shows a cross-sectional view of the rotating electrical machine 200 or the rotating electrical machine 202 of FIG. The rotating electrical machine 200 and the rotating electrical machine 202 have substantially the same structure, and the structure of the rotating electrical machine 200 will be described below as a representative example. In addition, the structure shown below does not need to be employ | adopted for both the rotary electric machines 200 and 202, and may be employ | adopted for at least one.

  A stator 230 is held inside the housing 212, and the stator 230 includes a stator core 232 and a stator winding 238. Inside the stator core 232, a rotor 250 is rotatably held through a gap 222. The rotor 250 includes a rotor core 252, a permanent magnet 254, and a non-magnetic cover plate 226, and the rotor core 252 is fixed to the shaft 218. The housing 212 has a pair of end brackets 214 provided with bearings 216, and the shaft 218 is rotatably held by these bearings 216.

  As shown in FIG. 3, the shaft 218 is provided with a resolver 224 that detects the position and rotation speed of the pole of the rotor 250. The output from the resolver 224 is taken into the control circuit 648 shown in FIG. The control circuit 648 outputs a control signal to the drive circuit 653 based on the fetched output. The drive circuit 653 outputs a drive signal based on the control signal to the power module 610. The power module 610 performs a switching operation based on the control signal, and converts DC power supplied from the battery 180 into three-phase AC power. This three-phase AC power is supplied to the stator winding 238 shown in FIG. 3 and a rotating magnetic field is generated in the stator 230. The frequency of the three-phase alternating current is controlled based on the detected value of the resolver 224, and the phase of the three-phase alternating current with respect to the rotor 250 is also controlled based on the detected value of the resolver 224.

  FIG. 4A is a perspective view showing the rotor core 252 of the rotor 250. The rotor core 252 includes two cores 301 and 302 as shown in FIG. The axial length H2 of the core 302 is set to be substantially the same as the axial length H1 of the core 301. 5 (a) and 5 (b) are views showing cross sections of the stator 230 and the rotor 250, and FIG. 5 (a) is a cross-sectional view taken along the line AA through the core 301 (see FIG. 3). FIG. 5B is a cross-sectional view taken along the line BB through the core 302 (see FIG. 3). 5A and 5B, the housing 212, the shaft 218, and the stator winding 238 are not shown.

  On the inner peripheral side of the stator core 232, a large number of slots 24 and teeth 236 are arranged uniformly over the entire circumference. In FIGS. 5 (a) and 5 (b), not all of the slots and teeth are denoted by reference numerals, but only a part of the teeth and slots are represented by representative numerals. Slot insulation (not shown) is provided in the slot 24, and a plurality of phase windings of u phase to w phase constituting the stator winding 238 are mounted. In this embodiment, distributed winding is adopted as a method of winding the stator winding 238.

  The distributed winding is a winding method in which the phase winding is wound around the stator core 232 so that the phase winding is accommodated in two slots that are spaced apart from each other across the plurality of slots 24. In this embodiment, distributed winding is adopted as the winding method, so that the formed magnetic flux distribution is close to a sine wave shape, and it is easy to obtain reluctance torque. Therefore, it is possible to control not only a low rotational speed but also a wide rotational speed range up to a high rotational speed by utilizing field weakening control and reluctance torque, which is suitable for obtaining motor characteristics of an electric vehicle or the like.

  Each core 301, 302 of the rotor core 252 has a hole 310 into which a rectangular magnet is inserted. A permanent magnet 254 is embedded in the hole 310 and fixed with an adhesive or the like. The circumferential width of the hole 310 is set to be larger than the circumferential width of the permanent magnet 254, and magnetic gaps 257 are formed on both sides of the permanent magnet 254. The magnetic gap 257 may be embedded with an adhesive, or may be solidified integrally with the permanent magnet 254 with a shaping resin. Permanent magnet 254 acts as a field pole for rotor 250.

  The magnetization direction of the permanent magnet 254 faces the radial direction, and the direction of the magnetization direction is reversed for each field pole. That is, if the stator side surface of the permanent magnet 254a is N-pole and the surface on the shaft side is S-pole, the stator side surface of the adjacent permanent magnet 254b is S-pole and the surface on the shaft side is N-pole. . These permanent magnets 254a and 254b are alternately arranged in the circumferential direction. In the present embodiment, twelve permanent magnets 254 are arranged at equal intervals, and the rotor 250 has 12 poles.

  The permanent magnet 254 may be magnetized and then embedded in the rotor core 252 or may be magnetized by applying a strong magnetic field after being inserted into the rotor core 252 before being magnetized. The magnetized permanent magnet 254 is a strong magnet. If the magnet is magnetized before the permanent magnet 254 is fixed to the rotor 250, a strong attractive force is generated between the permanent magnet 254 and the rotor core 252 when the permanent magnet 254 is fixed. And this centripetal force hinders work. Moreover, there is a possibility that dust such as iron powder adheres to the permanent magnet 254 due to the strong attractive force. Therefore, the productivity of the rotating electrical machine is improved when the permanent magnet 254 is magnetized after being inserted into the rotor core 252.

  As the permanent magnet 254, a neodymium-based or samarium-based sintered magnet, a ferrite magnet, a neodymium-based bonded magnet, or the like can be used. The residual magnetic flux density of the permanent magnet 254 is about 0.4 to 1.3 T.

  FIG. 6A is an enlarged view of a part of the cross-sectional view shown in FIG. In addition to the magnetic gap 257 formed on both sides of the permanent magnet 254, the core 301 of the rotor core 252 is provided with a groove constituting the magnetic gap 258 on the surface of the rotor 250. The magnetic air gap 257 is provided to reduce cogging torque, and the magnetic air gap 258 is provided to reduce torque pulsation during energization. When viewed from the inner peripheral side of the rotor 250, if the central axis between the left magnets of the permanent magnet 254a is q-axis a and the central axis between the left magnets of the permanent magnet 254b is q-axis b, the magnetic gap 258a is q The magnetic air gap 258b is arranged on the right side with respect to the axis a and is shifted to the left side with respect to the q axis b. Further, the magnetic air gap 258a and the magnetic air gap 258b are arranged symmetrically with respect to the d axis which is the central axis of the magnetic pole.

  On the other hand, FIG. 6B is an enlarged view of a part of the cross-sectional view shown in FIG. In the case of the core 302 of the rotor core 252, magnetic gaps 258c and 258d are formed instead of the magnetic gaps 258a and 258b. When viewed from the inner peripheral side of the rotor 250, the magnetic air gap 258c is shifted to the left with respect to the q axis a, and the magnetic air gap 258d is shifted to the right with respect to the q axis b. As can be seen from FIGS. 5 and 6, the cross-sectional shapes of the core 301 and the core 302 are the same except for the positions of the magnetic air gaps 258a, 258b and 258c, 258d.

  Here, the magnetic gaps 258a and 258d, 258b and 258c are arranged at positions shifted by 180 degrees in electrical angle. That is, the core 302 can be formed by rotating the core 301 by one magnetic pole. Thereby, the core 301 and the core 302 can be manufactured by the same type | mold, and manufacturing cost can be reduced. Further, the circumferential positions of the holes 310 of the cores 301 and 302 coincide with each other without deviation. As a result, the permanent magnets 254 mounted in the holes 310 penetrate the cores 301 and 302 integrally without being divided in the axial direction. Of course, a plurality of permanent magnets 254 may be provided so as to be laminated in the axial direction of the hole 310.

  When a rotating magnetic field is generated in the stator 230 by the three-phase alternating current, the rotating magnetic field acts on the permanent magnets 254a and 254b of the rotor 250 to generate magnet torque. Further, reluctance torque acts on the rotor 250 in addition to the magnet torque.

  FIG. 7 is a diagram for explaining the reluctance torque. In general, the axis through which the magnetic flux passes through the center of the magnet is called the d axis, and the axis through which the magnetic flux flows from one pole to another between the poles is called the q axis. At this time, the iron core portion at the center between the magnets is called an auxiliary salient pole portion 259. Since the magnetic permeability of the permanent magnet 254 provided on the rotor 250 is substantially the same as that of air, the d-axis portion is magnetically concave and the q-axis portion is magnetically convex when viewed from the stator side. It has become. Therefore, the core part of the q-axis part is called a salient pole. The reluctance torque is generated by the difference in the ease of passing the magnetic flux between the d-axis and the q-axis, that is, the salient pole ratio.

  Thus, the rotating electrical machine to which this embodiment is applied is a rotating electrical machine that uses both the magnet torque and the auxiliary salient pole reluctance torque. And torque pulsation generate | occur | produces from each of a magnet torque and a reluctance torque. Torque pulsation has a pulsation component that occurs when current is not applied and a pulsation component that is generated when current is applied, and the pulsation component that occurs when current is not applied is generally called cogging torque. When used, torque pulsation is generated by combining cogging torque and pulsation components during energization.

  Most of the methods described as a method for reducing the torque pulsation of the rotating electric machine refer only to the reduction of the cogging torque, and there are many cases where the torque pulsation generated by energization is not described. However, the noise of a rotating electrical machine often occurs at the time of loading, not at no loading. In other words, it is important to reduce the torque pulsation at the time of load reduction in the rotating electric machine, and measures using only the cogging torque are insufficient.

  Next, a method for reducing torque pulsation in the present embodiment will be described.

  First, the influence of the magnetic air gap 258 at the time of non-energization will be described. FIG. 8A shows a simulation result of a magnetic flux distribution when no current is passed through the stator winding 238, that is, a magnetic flux distribution by the permanent magnet 254. The region 401 configured by the permanent magnet 254a is shown in FIG. The two poles of the area | region 402 comprised with the permanent magnet 254b are represented. That is, it is a result of simulating a rotating electrical machine in which the region 401 and the region 402 are alternately arranged in the circumferential direction, and shows an AA cross section. Since the rotating electrical machine of this embodiment has 12 poles, 6 poles are alternately arranged in the circumferential direction. Paying attention to the pole unit, the magnetic gaps 258 a and 258 b are arranged in the auxiliary salient pole part 259 in the region 401, and the auxiliary salient pole part 259 in the region 402 does not have the magnetic gap 258.

  When not energized, the magnetic flux of the permanent magnet 254 short-circuits the magnet end. Therefore, no magnetic flux passes through the q axis. It can also be seen that the magnetic flux hardly passes through the magnetic gaps 258a and 258b provided at positions slightly deviated from the magnetic gap 257 at the end of the magnet. The magnetic flux passing through the stator core 232 reaches the teeth 236 through the stator core side of the permanent magnet 254. For this reason, the magnetic air gaps 258a and 258b hardly affect the magnetic flux at the time of non-energization related to the conging torque, so that the magnetic air gaps 258a and 258b do not affect the cogging torque.

  8B is a simulation result of only the region 401, and FIG. 8C is a simulation result of only the region 402. FIG. 8B shows only the region 401, and FIG. 8C shows the magnetization of the permanent magnet 254 in the circumferential direction only. 12 shows a rotating electrical machine in which 12 poles are arranged so that the direction is reversed for each pole. 8B and 8C also have the same magnetic flux distribution as FIG. 8A, and no magnetic flux passes through the q axis.

  FIG. 9A shows the waveform of the cogging torque, and FIG. 9B shows the waveform of the induced voltage between the lines generated on the stator side when the rotor 250 rotates. . The horizontal axis represents the rotation angle of the rotor and is indicated by the electrical angle. Line L11 shows the case of the rotor of FIG. 8A in which the region 401 having the magnetic air gap 258 and the region 402 having no magnetic air gap 258 are alternately arranged, and the line L12 is the region 401 having the magnetic air gap 258. 8B shows the case of the rotating electrical machine of FIG. 8B, and the line L13 shows the case of the rotating electrical machine of FIG. 8C where only the region 402 without the magnetic gap 258 is placed. From the result of FIG. 9A, it can be seen that the presence or absence of the magnetic air gap 258 has little influence on the cogging torque.

  The induced voltage is a voltage generated when the magnet magnetic flux of the rotating rotor 250 is linked to the stator winding 238. As shown in FIG. 9B, the induced voltage waveform is also the magnetic gap 258. It can be seen that it does not affect the presence or absence. The induced voltage is a reflection of the magnetic flux of the magnet in the simulation results shown in FIGS. 8A, 8B, and 8C. The fact that the induced voltage has not changed indicates that the magnetic air gap 258 is almost the same as the magnetic flux. It will not have an effect.

  Next, the influence of the magnetic air gap 258 during energization will be described. FIG. 10 shows a simulation result of the magnetic flux distribution when the stator winding 238 is energized. FIG. 10 (a) shows the AA cross section of this embodiment of FIG. 8 (a). FIG. 10 (b) shows the motor shown in FIG. 8 (b), and FIG. 10 (c) shows the motor shown in FIG. 8 (c). The rotating electrical machine of the present embodiment is a motor having 6 slots per pole, and the coil 233 of the stator winding 238 provided in the slot 24 of the stator core 232 has two layers in the slot depth direction. I know. The coil 233 arranged on the bottom side of the slot is a short-pitch winding that is inserted into the rotor side of the slot 24 that is 6 slots apart from 1 slot to 5 slots when the adjacent slot is counted as one slot. The short-pitch winding is characterized in that the harmonics of the magnetomotive force of the stator can be reduced, the coil end is short, and the copper loss is reduced. In addition, this way of reducing harmonics can reduce the 6th-order torque pulsation unique to the three-phase motor, and only the 12th-order component remains.

  Referring to FIG. 10, magnetic flux flows on the q axis in any simulation result. This is because the current of the stator 230 creates a magnetic flux on the q axis. 10 (a) and 10 (b), the magnetic air gap 258 changes the flow of the magnetic flux of the auxiliary salient pole portion 259, as compared with the result of FIG. 10 (c) without the magnetic air gap 258. Recognize. Therefore, it can be said that the magnetic air gap 258 in the auxiliary salient pole portion 259 has a magnetic influence only when energized.

  FIG. 11A shows the torque waveform during energization, and FIG. 11B shows the waveform of the line voltage during energization. The horizontal axis represents the rotation angle of the rotor and is indicated by the electrical angle. Line L21 shows the case of the rotor of FIG. 10A in which the region 401 having the magnetic air gap 258 and the region 402 having no magnetic air gap 258 are alternately arranged, and the line L22 is the region 401 having the magnetic air gap 258. 10B shows the case of the rotating electrical machine in FIG. 10B, and the line L23 shows the case of the rotating electrical machine in FIG. 10C in which only the region 402 without the magnetic gap 258 is arranged.

From FIG. 11 (a), it can be seen that the rotating electrical machine of the present embodiment has a 12th-order torque pulsation component, that is, a component with an electrical angle of 30 deg.
Further, it can be seen that the torque pulsation waveform is changed in both L21 and L22 with respect to the torque pulsation L23 in the case where the magnetic air gap 258 is not formed, that is, only in the region 402. This indicates that the magnetic flux during energization is affected by the magnetic gap 258. Further, the torque pulsation L22 of the rotating electrical machine only in the region 401 and the torque pulsation L23 of the rotating electrical machine only in the region 402 are almost opposite in phase. As shown in FIG. 10A, the rotating electrical machine according to the present embodiment has a configuration in which the regions 401 and the regions 402 are alternately arranged. Is the average value of torque pulsation L22 and torque pulsation L23.

  Thus, in this embodiment, the torque pulsation during energization can be reduced by providing the magnetic gaps 258a and 258b as described above. In order to obtain such an effect, the width angle (circumferential angle) of the grooves constituting the magnetic air gap 258 is set to a range of ¼ to ½ of the pitch angle of the teeth 236. preferable. Two or more kinds of magnetic gaps 258 formed in the auxiliary salient pole portion 259 may be used. Thereby, the freedom degree of torque pulsation reduction increases, and pulsation reduction can be performed in more detail.

  Further, it has a feature that the torque does not decrease compared to the case where no magnetic gap is provided. Conventionally, in the case of a structure called skew for reducing torque pulsation, there has been a drawback that the torque is lowered by the skew and hinders downsizing. However, this embodiment has an advantage that not only the torque pulsation during energization can be reduced independently of the cogging torque, but also the torque itself does not decrease. This is because the torque pulsation in the case of the original grooveless rotor is dominated by the twelfth component, which is also effective because the stator winding has a short-pitch winding.

Further, it is understood that the voltage at the time of energization affects the presence or absence of the magnetic gap 258 as shown in FIG. In this case, a potential difference is generated between each phase winding of the stator winding 238 facing the rotor 250 in the region 401 and each phase winding of the stator winding 238 facing the rotor 250 in the region 402. When the windings are connected in parallel to each phase, the circulating current flows and the loss increases. As shown in FIG. 6, the rotating electrical machine of the present embodiment has a core 302 formed by rotating the core 301 by one pitch of the magnetic pole, and the core 301 and the core are formed as shown in FIG. Since the axial lengths of 302 are set to be substantially equal, the voltages generated in the phase windings of the stator winding 238 facing each pole can be made substantially equal, and almost no circulating current flows.
However, when the phase windings of the stator windings 238 facing the rotor 250 in the regions 401 and 402 are connected in series, the circulating current hardly flows. Therefore, even in the configuration of only the core 301 or only the core 302 no problem.

  As described above, the formation of the magnetic air gaps 258a and 258b does not affect the cogging torque during non-energization. Therefore, by applying a conventional cogging torque reduction method, it is possible to reduce the cogging torque separately from the reduction of energization torque pulsation. In this embodiment, the cogging torque is reduced by adopting the following configuration.

  12 and 13 are diagrams for explaining a method for reducing the cogging torque. FIG. 12 is a cross-sectional view showing a part of the rotor 250 and the stator core 232. In FIG. 12, τp is the pole pitch of the permanent magnet 254, and τm is the width angle of the permanent magnet 254. Further, τg is an angle obtained by combining the permanent magnet 254 and the magnetic air gap 257 provided on both sides thereof, that is, the width angle of the hole 310 shown in FIG. The cogging torque can be reduced by adjusting the ratios τm / τp and τg / τp of these angles. In this embodiment, τm / τp is called a magnet pole arc degree, and τg / τp is called a magnet hole pole arc degree.

  FIG. 13 is a diagram showing the relationship between the ratio of the magnet pole arc degree τm / τp and the conging torque. The results shown in FIG. 13 are obtained when τm = τg, and when the permanent magnet 254 and the magnetic air gap 257 are concentric with the outer periphery of the rotor 250. When this is a rectangular magnet as in this embodiment, the optimum value changes slightly, but it goes without saying that the idea is the same. In FIG. 13, the vertical axis represents the amplitude of the conging torque, and the horizontal axis represents the rotation angle represented by the electrical angle of the rotor 250. The magnitude of the pulsation amplitude changes depending on the ratio τm / τp. When τm = τg, the congging torque can be reduced by selecting τm / τp to be about 0.75. Further, the tendency that the cogging torque is not changed by the magnetic air gap 258 shown in FIG. 9A can be applied in the same manner where the ratio τm / τp of the magnet width and the pole pitch shown in FIG. Therefore, by making the shape of the rotor 250 as shown in FIG. 5 under the above conditions, both the cogging torque and the torque pulsation during energization can be reduced.

  In the example shown in FIG. 13, the description has been made on the assumption that τm = τg. However, in order to efficiently use the reluctance torque which is the effect of the auxiliary salient pole portion 259, the magnet hole pole arc degree τg / τp is set to 0.5 to 0.9. It is good to set the degree, more preferably about 0.7 to 0.8.

  FIG. 14 is a calculation example of the maximum torque when the magnet pole arc degree τm / τp and the magnet hole pole arc degree τg / τp are changed. As in FIG. 13, the permanent magnet 254 and the magnetic gap 257 are fan-shaped concentric with the outer periphery of the rotor 250. The abscissa indicates the magnet hole pole arc degree τg / τp, and a value of 0.7 indicates that the ratio of the auxiliary salient pole part 259 to the pitch between the poles is 0.3. Here, since the magnet width τm cannot be larger than the opening angle τg of the magnet hole, τg ≧ τm. As τm increases, the width of the permanent magnet 254 increases, so the torque increases. On the other hand, when τm is constant, τg has an optimum value, and the maximum torque becomes the largest when τg / τp is about 0.7 to 0.8. This is because there is an appropriate value for the size of the auxiliary salient pole portion 259, and the reluctance torque becomes small if τg is made too large or too small. When τm is larger than 0.75, τm = τg is desirable so that the auxiliary salient pole portion 259 is as large as possible.

  Thus, when τg / τp is about 0.7 to 0.8, the reluctance torque can be used most efficiently, and the permanent magnet 254 can be made small. When a rare earth sintered magnet is used for the permanent magnet 254, the magnet is extremely expensive as compared with other materials, so that it is required to use the magnet amount most effectively. Moreover, since the permanent magnet 254 becomes small, the induced voltage due to the magnetic flux of the permanent magnet 254 can be reduced, and the rotating electrical machine can be rotated at a higher speed. Therefore, a rotating electrical machine using reluctance torque as in the present embodiment is generally used for an electric vehicle.

  FIG. 15A and FIG. 15B show a rotor according to another embodiment of the present invention. Except for the items described below, the second embodiment is the same as the first embodiment.

  FIG. 15A shows a surface magnet type rotor, and FIG. 15B shows a rotor in which a plurality of magnets are arranged in a V hour shape. In any rotor, an auxiliary salient pole portion 259 is provided between the permanent magnets 254, and a magnetic gap 258 is disposed in the auxiliary salient pole portion 259. The magnetic air gaps 258 are respectively defined as q axis a for the central axis between the left magnets of the permanent magnet 254a when viewed from the inner periphery side of the rotor 250, and q axis b for the central axis between the left magnets of the permanent magnet 254b. The magnetic gap 258a is shifted to the right side with respect to the q axis a, and the magnetic gap 258b is shifted to the left side with respect to the q axis b. Further, the magnetic air gap 258a and the magnetic air gap 258b are arranged symmetrically with respect to the d axis which is the central axis of the magnetic pole. FIG. 15 shows the AA cross section of the rotor, and the BB cross section is formed by rotating the shape of the AA cross section by one pitch of the magnetic pole, as in the above-described embodiment. It becomes a shape. As described with reference to FIG. 8, the reduction of torque pulsation in this embodiment is not affected by the magnetic flux of the magnet, and thus does not depend on the shape of the magnet.

  FIG. 16 shows a reduction in torque pulsation by providing two magnetic air gaps 258 according to this embodiment for each auxiliary salient pole portion 259.

  When the central axis between the left magnets of the permanent magnet 254a as viewed from the inner peripheral side of the rotor 250 is q-axis a, and the central axis between the left magnets of the permanent magnet 254b is q-axis b, this shape is q-axis. The right magnetic air gap 258a is large with respect to a, the left magnetic air gap 258e is small with respect to the q axis a, the right magnetic air gap 258b is large with respect to the q axis b, and the left side with respect to the q axis b. The magnetic air gap 258f is small. Further, the magnetic air gaps 258a and 258b and the magnetic air gaps 258e and 258f are arranged symmetrically with respect to the d axis which is the central axis of the magnetic pole. FIG. 16 shows the AA cross section of the rotor, and the BB cross section is formed by rotating the shape of the AA cross section by one pitch of the magnetic pole, as in the above-described embodiment. It becomes a shape. Other matters are the same as those described in the first embodiment.

  In the example shown in FIGS. 5, 15, and 16, the magnetic air gap 258 is a groove provided on the outer periphery of the rotor 250, but it may be a hole in the auxiliary salient pole 259 as shown in FIG. Alternatively, as shown in FIG. 17B, the magnetic gap 257 and the magnetic gap 258 may be integrated. Further, as shown in FIG. 17 (c), the auxiliary salient pole portion 259 can be realized by providing portions having different magnetic permeability. In FIG. 17C, the magnetic permeability of the auxiliary salient pole part 259a is set lower than the magnetic permeability of the auxiliary salient pole part 259b. Other matters are the same as those described in the first embodiment.

  FIG. 18 shows a case where the stator winding 238 shown in FIG. 5 is concentrated. Since the torque pulsation in this embodiment depends on the shape of the rotor 250, the torque pulsation can be reduced in the same manner as described above even in the case of concentrated winding with different winding methods on the stator side. Other matters are the same as those described in the first embodiment.

  FIG. 19A is a perspective view showing a rotor core 252 of a rotor 250 according to another embodiment of the present invention. Except for the items described below, the second embodiment is the same as the first embodiment.

  The rotor core 252 includes two cores 301 and 302 as shown in FIG. The axial length H2 of the core 302 is set to be substantially the same as the axial length H1 of the core 301. 20 is a view showing a cross section of the stator 230 and the rotor 250, FIG. 20 (a) is a cross-sectional view taken along the line AA (see FIG. 3) through the core 301, and FIG. It is BB sectional drawing (refer FIG. 3) which passes through the part of 302. FIG. In FIG. 20, the housing 212, the shaft 218, and the stator winding 238 are not shown.

  On the inner peripheral side of the stator core 232, a large number of slots 24 and teeth 236 are arranged uniformly over the entire circumference. In FIG. 20, not all of the slots and teeth are denoted by reference numerals, and only some of the teeth and slots are representatively denoted. Slot insulation (not shown) is provided in the slot 24, and a plurality of phase windings of u phase to w phase constituting the stator winding 238 are mounted. In this embodiment, distributed winding is adopted as a method of winding the stator winding 238.

  Each core 301, 302 of the rotor core 252 has a hole 310 into which a rectangular magnet is inserted. A permanent magnet 254 is embedded in the hole 310 and fixed with an adhesive or the like. The circumferential width of the hole 310 is set to be larger than the circumferential width of the permanent magnet 254, and magnetic gaps 257 are formed on both sides of the permanent magnet 254. The magnetic gap 257 may be embedded with an adhesive, or may be solidified integrally with the permanent magnet 254 with a shaping resin. Permanent magnet 254 acts as a field pole for rotor 250.

  The magnetization direction of the permanent magnet 254 faces the radial direction, and the direction of the magnetization direction is reversed for each field pole. That is, if the stator side surface of the permanent magnet 254a is N-pole and the surface on the shaft side is S-pole, the stator side surface of the adjacent permanent magnet 254b is S-pole and the surface on the shaft side is N-pole. . These permanent magnets 254a and 254b are alternately arranged in the circumferential direction. In the present embodiment, twelve permanent magnets 254 are arranged at equal intervals, and the rotor 250 has 12 poles.

  FIG. 21A is an enlarged view of a part of the cross-sectional view shown in FIG. In addition to the magnetic gap 257 formed on both sides of the permanent magnet 254, the core 301 of the rotor core 252 is provided with a groove constituting the magnetic gap 258 on the surface of the rotor 250. The magnetic air gap 257 is provided to reduce cogging torque, and the magnetic air gap 258 is provided to reduce torque pulsation during energization. When viewed from the inner peripheral side of the rotor 250, if the central axis between the left magnets of the permanent magnet 254a is q-axis a and the central axis between the left magnets of the permanent magnet 254b is q-axis b, the magnetic gap 258a is q The magnetic air gap 258b is arranged on the right side with respect to the axis a and shifted to the left side with respect to the q axis a, and there is no magnetic air gap on the left and right of the q axis b. Further, the magnetic air gap 258a and the magnetic air gap 258b are arranged symmetrically with respect to the q axis, which is the central axis between the magnets.

  On the other hand, FIG. 21B is an enlarged view of a part of the cross-sectional view shown in FIG. In the case of the core 302 of the rotor core 252, magnetic gaps 258c and 258d are formed instead of the magnetic gaps 258a and 258b. When viewed from the inner peripheral side of the rotor 250, the magnetic air gap 258c is arranged on the right side with respect to the q axis b, and the magnetic air gap 258d is arranged on the left side with respect to the q axis b. There is no static void. As can be seen from FIGS. 20 and 21, the cross-sectional shapes of the core 301 and the core 302 are the same except for the positions of the magnetic air gaps 258a, 258b and 258c, 258d.

  Here, the magnetic gaps 258a and 258c, 258b and 258d are arranged at positions shifted by 180 degrees in electrical angle. That is, the core 302 can be formed by rotating the core 301 by one magnetic pole. Thereby, the core 301 and the core 302 can be manufactured by the same type | mold, and manufacturing cost can be reduced. Further, the circumferential positions of the holes 310 of the cores 301 and 302 coincide with each other without deviation. As a result, the permanent magnets 254 mounted in the holes 310 penetrate the cores 301 and 302 integrally without being divided in the axial direction. Of course, a plurality of permanent magnets 254 may be provided so as to be laminated in the axial direction of the hole 310.

  The rotating electrical machine illustrated in FIG. 21A has a configuration in which regions 403 and regions 404 are alternately arranged. Here, the region 403 in FIG. 21A is equivalent to the region 401 in FIG. 8A, and the region 404 in FIG. 21A is equivalent to the region 402 in FIG. 8A, and is shown in FIG. The rotating electrical machine of the embodiment can be said to be electrically and magnetically equivalent to the rotating electrical machine of the embodiment shown in FIG. 6 although the position where the magnetic air gap 258 is disposed is different. That is, also in this embodiment, different torque pulsations are generated in the region 403 and the region 404, and the torque pulsations can be reduced by acting so that they cancel each other. Similarly to the first embodiment, since the magnetic air gap 258 is formed in the auxiliary salient pole portion 259, the cogging torque is hardly affected. That is, by providing the magnetic air gap 258, the influence of the cogging torque on the pulsation can be suppressed, and the energization torque pulsation can be reduced almost independently.

  Further, as shown in FIG. 21, the rotating electrical machine of this embodiment has a core 302 formed by rotating the core 301 by one pitch of the magnetic pole, and as shown in FIG. Since the axial lengths of the core 302 and the core 302 are set to be substantially equal, the voltages generated in the respective phase windings of the stator winding 238 facing each pole can be made substantially equal, and almost no circulating current flows. However, when the phase windings of the stator windings 238 facing the rotor 250 in the regions 403 and 404 are connected in series, the circulating current hardly flows. Therefore, even in the configuration of only the core 301 or only the core 302 no problem.

  FIG. 22 shows a rotor according to another embodiment of the present invention. The items other than those described below are the same as in the above embodiment.

  22A shows a surface magnet type rotor, and FIG. 22B shows a rotor in which a plurality of magnets are arranged in a V-hour shape. In any rotor, an auxiliary salient pole portion 259 is provided between the permanent magnets 254, and a magnetic gap 258 is disposed in the auxiliary salient pole portion 259. The magnetic air gaps 258 are respectively defined as q axis a for the central axis between the left magnets of the permanent magnet 254a when viewed from the inner periphery side of the rotor 250, and q axis b for the central axis between the left magnets of the permanent magnet 254b. The magnetic air gap 258a is arranged on the right side with respect to the q axis a, and the magnetic air gap 258b is arranged on the left side with respect to the q axis a, and there is no magnetic air gap on the left and right sides of the q axis b. Further, the magnetic air gap 258a and the magnetic air gap 258b are arranged symmetrically with respect to the q axis, which is the central axis between the magnets. FIG. 22 shows the AA cross section of the rotor, and the BB cross section is formed by rotating the shape of the AA cross section by one pitch of the magnetic pole, as in the above-described embodiment. It becomes a shape. As described with reference to FIG. 8, the reduction of torque pulsation in this embodiment is not affected by the magnetic flux of the magnet, and thus does not depend on the shape of the magnet.

  FIG. 23 shows that the torque pulsation is reduced by providing two magnetic gaps 258 of this embodiment for each auxiliary salient pole portion 259, and the shape thereof is viewed from the inner peripheral side of the rotor 250. If the central axis between the left magnets of the permanent magnet 254a is q-axis a and the central axis between the left magnets of the permanent magnet 254b is q-axis b, the left and right magnetic gaps 258a and 258b of the q-axis a are large, q The magnetic gaps 258e and 258f on the left and right of the axis b are arranged small. Further, the magnetic air gaps 258a and 258b and the magnetic air gaps 258e and 258f are arranged symmetrically with respect to the q axis which is the central axis between the magnets. FIG. 23 shows the AA cross section of the rotor, and the BB cross section is formed by rotating the shape of the AA cross section by one pitch of the magnetic pole, as in the above-described embodiment. It becomes a shape.

  In the examples shown in FIGS. 20, 22, and 23, the magnetic gap 258 is a groove provided on the outer periphery of the rotor 250, but it is in the auxiliary salient pole portion 259 as shown in FIG. It may be a hole, or the magnetic air gap 257 and the magnetic air gap 258 may be integrated as shown in FIG. Further, as shown in FIG. 24C, the auxiliary salient pole portion 259 can be realized by providing portions having different magnetic permeability. In FIG. 24C, the permeability of the auxiliary salient pole part 259a is set lower than the permeability of the auxiliary salient pole part 259b.

  FIG. 25 shows a case where the stator winding 238 shown in FIG. 20 is concentrated. Since the torque pulsation in this embodiment depends on the shape of the rotor 250, the torque pulsation can be reduced in the same manner as described above even in the case of concentrated winding with different winding methods on the stator side.

The various embodiments described above have the following operational effects.
(1) Magnetic air gaps 258a and 258b are provided in the auxiliary salient pole portion 259, and the magnetic air gap 258a and the magnetic air gap 258b are supported so that torque pulsations generated by the magnetic air gaps 258a and 258b cancel each other. Each salient pole portion 259 is shifted and arranged. As a result, it is possible to reduce the torque pulsation of the rotating electrical machine during energization. In particular, when the rotating electrical machine of the present embodiment that can reduce torque pulsation during energization is applied as a vehicle driving motor such as an electric vehicle, vibration and noise during low-speed acceleration can be reduced, and riding comfort is good. An electric vehicle with high silence can be provided.
(2) At the time of non-energization, the magnetic air gap 258 has little influence on the magnetic flux. Therefore, a countermeasure for reducing the conging torque caused by the magnetic flux of the permanent magnet 254 and a countermeasure for reducing the torque pulsation during energization can be independently performed. As a result, it is possible to achieve both the optimization of the magnet torque so that the congging torque is small and the torque during energization is large and the reduction of torque pulsation during energization. Conventionally, since the magnet is configured so that the torque is maximized and then skew is applied so that the conging torque is reduced, there has been a disadvantage that the torque (magnet torque) is reduced. In the embodiment, it is possible to avoid a decrease in torque due to a reduction in torque pulsation.
(3) As described above, since it is possible to prevent a decrease in magnet torque associated with torque pulsation reduction, the magnet can be made as small as possible, and the rotating electrical machine can be reduced in size and cost. (4) Since the torque pulsation during energization is reduced by shifting the positions of the magnetic air gaps 258a and 258b provided in the auxiliary salient pole portion 259, the permanent magnet 254 as in the conventional skew structure. There is no need to divide the wire into a plurality of portions in the axial direction or skew the magnetization. As the permanent magnet 254, for example, a rare earth magnet typified by neodymium is used. However, since the magnet shaping is performed by polishing in the rare earth magnet, increasing the accuracy of the manufacturing error directly leads to an increase in cost. Therefore, according to the present embodiment that does not require the magnet to be divided in the axial direction, the cost of the rotating electrical machine can be reduced. In addition, there is no concern that the dispersion of performance increases due to the accumulation of magnet tolerances or that the yield deteriorates. Thus, according to the present embodiment, it is possible to reduce the productivity and the production cost of the rotating electrical machine.

  According to the above embodiment, it is possible to reduce cogging torque and torque pulsation during energization. The amount of deviation in the circumferential direction from the q-axis of the part where the magnetic resistance is changed is made different for each magnetic auxiliary salient pole so that the torque pulsation at the time of energization caused by the part where the magnetic resistance is changed is canceled out. Thus, it is possible to reduce torque pulsation.

  In the above embodiment, the motor for driving the vehicle has been described as an example. However, the present invention can be applied to various motors as well as for driving the vehicle. Furthermore, the present invention can be applied not only to motors but also to various rotating electrical machines such as generators such as alternators. In addition, the present invention is not limited to the above embodiment as long as the characteristics of the present invention are not impaired.

DESCRIPTION OF SYMBOLS 100 Vehicle 180 Battery 200, 202 Rotating electrical machine 212, 214 Housing 230 Stator 232 Stator core 236 Teeth 238 Stator winding 250 Rotor 252 Rotor core 254 Permanent magnet 257, 258 Magnetic gap 259 Auxiliary salient pole 301, 302 Core 310 hole

Claims (4)

Having a rotor core with a hole into which a magnet is inserted;
A permanent magnet is inserted into the hole,
A rotor in which a magnetic auxiliary salient pole portion is formed between poles of the permanent magnet,
A magnetic gap is provided on a side surface of the permanent magnet;
a second magnetic air gap is formed in the magnetic auxiliary salient pole of the rotor core symmetrically with respect to the d axis and asymmetric with respect to the q axis;
The second magnetic gap is provided on the right side or the left side with respect to the q axis so that torque pulsation during energization is canceled in a cross section perpendicular to the axial direction.
The second magnetic gap is provided independently of the magnetic gap;
When the pole pitch of the permanent magnet is τp, and the angle of the permanent magnet and the magnetic gap provided on the side surface is τg,
A rotor having a magnet hole pole arc degree τg / τp of 0.5 to 0.9. The rotor according to claim 1,
A rotor having a magnet hole pole arc degree τg / τp of 0.7 to 0.8. The rotor according to claim 1 or 2,
The rotor, wherein the second magnetic gap is a groove provided on an outer periphery of the rotor core.   The rotary electric machine provided with the rotor in any one of Claims 1 thru | or 3.

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