JP5040287B2 - Three-phase AC-AC converter - Google Patents

Description

The present invention relates to a device for converting an alternating current input into another alternating current having a different voltage or frequency, or a configuration and control method for an uninterruptible power supply that compensates for alternating voltage fluctuation, frequency fluctuation or power failure and supplies a stable voltage to a load. About.

8 and 9 show the circuit configuration of a three-phase AC-AC converter according to the prior art. The circuit of FIG. 8 has the same principle as that shown in FIG. 1 of Patent Document 1 and the circuit of FIG. 9 has the same principle as that shown in FIG. In FIG. 8, 1 is an AC power source, 2 to 15 are semiconductor switches, 16A and 16B are DC capacitors, 17 to 23 are reactors, and 24 to 29 are filter capacitors.
Semiconductor switches 2-7, DC capacitors 16A, 16B, reactors 17-19, filter capacitors 24-26 constitute a forward converter, and the power of AC power supply 1 is converted to DC by high-frequency switching of semiconductor switches 2-7. The operation of converting and accumulating in the DC capacitors 16A and 16B is performed. This is, for example, the average voltage between R1-S1 and S1-T1 (here, the average voltage refers to the pulse waveform excluding high-frequency components higher than the high-frequency switching frequency component; the same applies hereinafter) between RS and ST voltage. This can be realized by switching based on pulse width modulation so that the amplitude and phase are slightly different, and controlling the current flowing through the reactors 17 to 19 by controlling the voltage difference.

On the other hand, the DC capacitors 16A and 16B, the semiconductor switches 8 to 13, the reactors 20 to 22 and the filter capacitors 27 to 29 constitute an inverse converter (inverter), and the DC capacitors 16A and 16B are used as a DC power source, and the semiconductor switch 8 By performing high frequency switching of ˜13, an AC voltage with small waveform distortion is generated in the filter capacitors 27 to 29, and an operation of supplying AC power to a load (not shown) is performed. This performs switching based on pulse width modulation so that the average voltage between U1 and V1 and between V1 and W1 is approximately equal to the desired voltage between UV and VW, and the high frequency switching frequency component included in the waveform is converted into reactors 20 to 22. It is realized by removing with an LC filter comprising filter capacitors 27-29.
Further, in the neutral point arm composed of the semiconductor switches 14 and 15, the potential at the N point and the potential at the DC neutral point (point M in FIG. 8), that is, the EP point, are turned on and off at a 50% duty ratio. Each of the AC output terminals U, V, and W and the neutral point terminal N are set so that the average voltage between the EN points and the intermediate potential is 0, and the potential for the DC part at the N point is actively determined. It is possible to cope with a load having a so-called three-phase four-wire configuration in which loads are individually connected between the two.

In the circuit of FIG. 9, the potential of the DC point at the N point is determined by connecting the connection point M of the DC capacitors 16A and 16B directly to the N point. Here, the semiconductor switches 14 and 15 and the reactor 23 act as a voltage balance circuit for the DC capacitors 16A and 16B.
These circuits are so-called uninterruptible power supplies that continue to supply power to the load even when an input power failure occurs as a device that converts alternating current input into alternating current with a different voltage or frequency, or by connecting a storage battery (not shown) to the direct current section. Used as a device.
Japanese Unexamined Patent Publication No. 2000-224862 (FIGS. 1 and 3)

In FIG. 8, along with the high-frequency switching operation of the semiconductor switches 2 to 7, the potentials at the AC input terminals R, S, and T at the connection point M between the DC capacitors 16A and 16B vary at high frequencies. Further, along with the high frequency switching operation of the semiconductor switches 8 to 13, the potential of each of the AC output terminals U, V, and W with respect to the point M varies at high frequencies. In general, in an AC power supply, one phase or a neutral point is directly grounded, or each phase is often grounded via a capacitor. For this reason, the high-frequency potential fluctuation with respect to the AC input leads to the high-frequency potential fluctuation with respect to the ground potential. When this circuit is used as an uninterruptible power supply, electronic equipment is generally present in the load, so high-frequency potential fluctuations may cause problems such as malfunction of electronic equipment and burning of filter circuits to remove high-frequency noise. Become.
In the circuit of FIG. 9, since the potentials of the DC circuit and the AC circuit are fixed, the problem of high-frequency potential fluctuation does not occur, but the reactor becomes large. This is due to the following reason.

In FIG. 8, for example, when the semiconductor switch 8 is switched, the path of the ripple current flowing through the reactor 20 is the path of the semiconductor switch 8 → reactor 20 → filter capacitor 27 → reactor 23 → semiconductor switch 15, semiconductor switch 8 → reactor 20 → filter capacitor. There are a plurality of paths such as 27 → filter capacitor 28 → reactor 21 → semiconductor switch 11, but there are two reactors and two switching elements in each path. For this reason, since the change in the reactor applied voltage is divided by two, the average is E / 2, and the frequency at which the voltage pulse is applied is the switching frequency of the semiconductor switches 8 to 13 and the switching frequency of the semiconductor switches 14 and 15. Is equivalent to twice that.
On the other hand, in FIG. 9, the path of the ripple current is, for example, semiconductor switch 8 → reactor 20 → filter capacitor 27 → DC capacitor 16B, and there is one reactor and one switching element on the path. For this reason, the voltage value applied to the reactor of the circuit of FIG. 9 due to switching is equivalent to twice the voltage value and the application time compared to the case of FIG. Since the ripple current of the reactor is proportional to the applied voltage time product, the inductance value needs to be quadrupled to make the ripple current the same as in FIG. Moreover, the loss which a reactor generate | occur | produces also becomes large by this, and there exists a subject that efficiency falls.

Furthermore, in both the circuit of FIG. 8 and the circuit of FIG. 9, the reverse converter has a line voltage (voltage between UV, VW, WU) and phase voltage (voltage between UN, VN, WN) for a three-phase four-wire load. Therefore, there is a problem that the following trapezoidal wave modulation cannot be applied.
The trapezoidal wave modulation will be described below. FIG. 10 shows an example of the waveform control method of the forward converter or the inverse converter. (A) controls the average voltage at points U1, V1, W1 or R1, S1, T1 with respect to point M in FIG. 8 or FIG. In this method, the voltage at each point can have a peak value of ± E / 2 at the maximum, but the average voltage between the points corresponding to the line voltage has an upper limit of √3E / 2 due to the nature of the three-phase waveform . Hereinafter, this method is referred to as sinusoidal modulation.
As another control method, there is a method in which a zero-phase voltage having a frequency three times and an amplitude of about 10% to 15% shown in (b) is added to the waveform of (a). The waveform after the addition is a trapezoidal waveform shown in (c). Since the fundamental wave can be increased as much as the peak value is suppressed compared to (a), the average voltage between the points can be increased to E. Since the zero-phase voltage of the same value is added to each point, the influence of the zero-phase voltage does not appear in the voltage waveform between the phases, and it becomes a sine wave. Hereinafter, this method is referred to as trapezoidal wave modulation.

  When trapezoidal wave modulation is used, the voltage between each phase, that is, the line voltage, can be increased with respect to the same DC voltage as compared with the sine wave modulation. The voltage can be lowered. As a result, it is possible to use a component with a low withstand voltage as a component to be used, and to reduce circuit loss. For this reason, trapezoidal wave modulation is often used in a three-phase three-wire circuit. However, if trapezoidal wave modulation is used, the phase voltage becomes trapezoidal, so sine wave modulation must be applied to the three-phase four-wire load, and the necessary DC voltage becomes high, so the components need high withstand voltage. Therefore, there is a problem that the loss becomes large.

In the first invention, a forward converter connected to a three-phase AC power source, comprising a semiconductor switch, a reactor, and a filter capacitor, and performing AC-DC conversion by high-frequency switching operation of the semiconductor switch, and a semiconductor switch, reactor, filter capacitor And a reverse converter that performs DC-AC conversion by high-frequency switching operation of a semiconductor switch and outputs a three-phase AC voltage, and a star connection method for connecting the forward converter and the filter capacitor of the reverse converter A neutral point arm composed of a series circuit of an even number of semiconductor switches between the forward converter and the inverse converter, or both DC positive terminals and DC negative terminals. Connecting the intermediate point and the neutral point of the filter capacitor via a reactor, The DC positive terminal of the forward converter and the DC positive terminal of the reverse converter are connected via the primary winding of the transformer, and the DC negative terminal of the forward converter and the DC negative terminal of the reverse converter are connected. In the three-phase AC-AC converter connected via the secondary winding of the transformer, the pulse width is changed according to the instantaneous value of the signal wave for controlling the inverter and the neutral point arm. The so-called pulse width modulation control is used, and a distorted wave obtained by adding a harmonic component to a sine wave is used as the signal wave of the inverse converter according to the AC output voltage, while the signal wave of the neutral point arm control is used. Uses a waveform corresponding to the harmonic component of the signal wave controlled by the inverse converter, thereby making the output phase voltage of the inverse converter a sine wave.

  In the second invention, a forward converter connected to a three-phase AC power source, comprising a semiconductor switch, a reactor, and a filter capacitor, and performing AC-DC conversion by high-frequency switching operation of the semiconductor switch, a semiconductor switch, a reactor, and a filter capacitor And a reverse converter that performs DC-AC conversion by high-frequency switching operation of a semiconductor switch and outputs a three-phase AC voltage, and a star connection method for connecting the forward converter and the filter capacitor of the reverse converter A neutral point arm composed of a series circuit of an even number of semiconductor switches between the forward converter and the inverse converter, or both DC positive terminals and DC negative terminals. Connect the intermediate point of the filter capacitor and the neutral point of the filter capacitor via a reactor. In the three-phase AC-AC converter, the forward converter includes means for superimposing a third harmonic component in accordance with an AC power supply voltage, and means for adjusting a DC voltage command. The neutral point arm includes means for superimposing the third harmonic component according to the AC output voltage. When the AC power supply voltage and the AC output voltage are asynchronous, each converter converts power by sinusoidal modulation. In operation, the neutral point arm performs zero voltage control, and when the AC power supply voltage and the AC output voltage are in a synchronized state, the forward converter transmits a signal wave in which the third harmonic component is superimposed according to the AC power supply voltage. The trapezoidal wave modulation using the signal, the inverse converter using the signal wave with the third harmonic component superimposed according to the AC output voltage, the neutral point arm using the trapezoidal wave modulation of the inverse converter 3rd harmonic component used for the signal wave The voltage control is performed respectively.

In a third invention, in the second invention, the three-phase AC-AC converter is a means for detecting a phase difference between the AC power supply voltage and the AC output voltage, and the difference between the AC power supply voltage frequency and the AC output voltage frequency. Or a means for detecting a zero-phase current (common mode current) flowing between the forward converter and the reverse converter, and when any of the detection means deviates from a predetermined range, Stop superimposing the 3rd harmonic.
In a fourth invention, in the second invention, the three-phase AC-AC converter is a means for detecting a phase difference between the AC power supply voltage and the AC output voltage, and the difference between the AC power supply voltage frequency and the AC output voltage frequency. , Or means for detecting a zero-phase current (common mode current) flowing between the forward converter and the reverse converter, and depending on the detection amount of the detection means, the superposition amount of the third harmonic Is adjusted to suppress the zero-phase current within a predetermined range.

In the first embodiment, it is possible to prevent high-frequency potential fluctuations in the output without increasing the size of the reactor, and further, trapezoidal wave modulation can be applied, and a lower DC voltage can be used compared to the conventional method. An equivalent fundamental wave voltage can be taken out, the breakdown voltage of the parts can be lowered, and the loss of the apparatus can be reduced. Even when trapezoidal wave modulation is performed, the output phase voltage can be converted into a sine wave, so that it is possible to cope with three-phase four-wire.
Further, in the second to fourth embodiments, trapezoidal wave modulation can be applied in a state where the AC power supply voltage and the AC output voltage are synchronized (normal operation state), and the loss in the normal operation state is reduced. be able to. In addition, even when the AC power supply voltage and the AC output voltage are in an asynchronous state, it is possible to suppress the zero-phase current flowing between the forward converter and the inverse converter within a predetermined range.

  The gist of the present invention is that the connection method of the forward converter and the filter capacitor of the reverse converter is a star connection, the neutral points are connected to each other, and the DC positive terminal and the DC of the forward converter and / or the reverse converter are connected. A three-phase AC-AC connection consisting of a neutral point arm consisting of a series circuit of an even number of semiconductor switches connected to the negative terminal, and an intermediate point connected to the neutral point of the filter capacitor via a reactor. In the converter, so-called pulse width modulation control that changes the pulse width according to the instantaneous value of the signal wave is used for the control of the inverse converter and the neutral point arm. While using a distorted wave to which a wave component is added, a signal corresponding to the harmonic component of the signal wave of the inverse converter control is used for the neutral point arm control signal wave, so that the output phase voltage of the inverse converter is sine. In terms of waves That.

FIG. 1 shows a first embodiment of the present invention. The same parts as those in FIG. The AC input and AC output are commonly connected at point N, and potential fluctuations between the input and output are prevented.
The principle difference from FIG. 9 is that the direct current portion and the N point are not connected directly or with a capacitor, and the high frequency potential fluctuation of the direct current portion is allowed.
When trapezoidal wave modulation is used in the inverse converter, the voltage of each phase with respect to the Mb point becomes a trapezoidal wave as shown in FIG. At the same time, as shown in FIG. 2B, the neutral point arm is modulated with the same waveform as the zero-phase voltage included in the trapezoidal wave so that the N-point voltage has a zero-phase component with respect to the Mb point. As a result, the AC output terminals U, V, W, and N have the same zero-phase voltage component with respect to the Mb point, so the zero-phase voltage component is not only between the lines but also between the UN, VN, and WN. It cancels out, leaving only a sine wave.

At this time, if the potential at the point N is fixed to the ground potential, for example, the point Mb has a ground voltage corresponding to the zero-phase voltage. Similar control can be performed for the forward converter. Here, the neutral line current required by the load is supplied from the neutral point arm of the reverse converter, and the forward converter does not need to take the neutral line current. Although the arm is omitted, a neutral point arm can be similarly provided for the purpose of determining the potential of the forward converter, for example, when devices are connected in parallel. Like the Mb point, the Ma point has a ground voltage equivalent to the zero-phase voltage.
Considering the voltage between the Ma point and Mb point, when the zero-phase voltage of the same phase and the same amplitude is added by the forward converter and the inverse converter, these are canceled out and the potential difference of the zero-phase component in the output is Although it does not appear, for example, as shown in FIG. 2 (d), if the zero-phase voltage of the forward converter is VP1 and the zero-phase voltage of the reverse converter is VP2, A phase difference of 180 ° occurs between the zero-phase voltages. For example, at the timing t, the potential at the N point is lower by VP1 than the potential at the Ma point, and the potential at the N point is higher by VP2 than the point Mb. Under this condition, a potential difference is generated between the Ma point and the Mb point with an amplitude VP1 + VP2 and a frequency three times the input / output frequency. For this reason, if the forward converter and the inverse converter are directly connected, the circuit cannot operate normally.
The transformer 100 is for handling this potential difference, and the turns ratio of both windings is 1: 1. When a voltage is applied to one of the windings between EPa and EPb, for example, the same voltage is generated at the winding between the other windings ENa and ENb. For this reason, DC voltage can be transmitted between capacitors having different potentials. In one circuit of EPa → EPb → ENb → ENa, the electromotive force of the transformer 100 becomes 0 V in total, and the transformer 100 does not transmit power between the windings.

FIG. 3 shows a circuit configuration of the second embodiment of the present invention, FIG. 4 shows a control block diagram of a forward converter, and FIG. 5 shows a control block diagram of an inverse converter.
In the circuit configuration shown in FIG. 3, the transformer 100 and the capacitors 101A, 101B, 102A, and 102B are excluded from the circuit configuration shown in FIG. This is a circuit configuration in which a common DC electrode is connected by an inverse converter.
In a state where the voltage Vin of the AC power supply 1 and the AC output voltage Vout are synchronized, the signal wave for the inverse converter formed by superimposing the third harmonic component on the IBGTs 14 and 15 of the neutral point arm on the sine wave. The AC output voltage Vout becomes a sine wave for both the line voltage and the phase voltage.
On the other hand, in order to suppress the zero-phase current Icom when the frequency of the voltage Vin of the AC power supply 1 is different from the frequency of the AC output voltage Vout, or when a phase difference occurs due to load fluctuation or power fluctuation, in the first embodiment, A method for adding a transformer 100 and capacitors 101A, 101B, 102A, 102B to a DC circuit is proposed. This proposed method is an effective means that low-voltage components can be used when the withstand voltage of semiconductor devices differs greatly due to the difference between trapezoidal wave modulation and sinusoidal wave modulation. The transformer 100 and the capacitors 101A, 101B, 102A, and 102B increase the size and loss of the device.

In the second embodiment, when the frequencies of the AC power supply voltage Vin and the AC output voltage Vout are different or when a phase difference occurs, the forward converter and the inverse converter are switched from trapezoidal wave modulation to sine wave modulation, and at the same time. This is a control method for suppressing the zero-phase current Icom between the forward converter and the reverse converter by switching the neutral point arm to zero voltage control. 4 and 5 are control block diagrams for realizing the above, and portions 30, 40 surrounded by a broken line are conventional control block diagrams.
The forward converter control block diagram of FIG. 4 inputs the deviation between the DC voltage command value Vdc ^ж and the DC voltage detection value Vdc to the voltage regulator (AVR) 32, and outputs the average value command Icnvave ^ж of the input current as its output. obtain. The phase-synchronized oscillator (PLL) 37 outputs a reference sine wave Vinref synchronized with the AC power supply voltage and a reference waveform 3ωcnvref of the third harmonic component. The input current waveform command Icnv ^ж is generated by multiplying the input current average value command Icnvave ^ж by the reference sine wave Vinref. The deviation between the input current waveform command Icnv ^ж and the input current detection Icnv is input to the current regulator (ACR) 35, and the output control signal λcnv for the forward converter is obtained as the output. At the time of trapezoidal wave modulation, trapezoidal wave modulation is realized by adding a third harmonic component synchronized with the AC power supply voltage Vin to the output control signal λcnv by the adder 36. Here, as the third harmonic component, the AC power supply voltage Vin, the AC output voltage Vout, and the zero-phase current Icom are detected, and the signals are processed by the input / output synchronization determination circuit 39 to thereby generate the third harmonic component. Is calculated by multiplying the reference waveform 3ωcnvref of the third harmonic component by the multiplier 38.

FIG. 5 shows the control block of the inverse converter and the control block of the neutral point arm. By inputting the deviation between the AC output voltage command value Vout ^ж and the output voltage detection value Vout to the voltage regulator (AVR) 42, the inverse converter output control signal λinv is obtained. At the time of trapezoidal wave modulation, trapezoidal wave modulation is realized by adding a third harmonic component synchronized with the output voltage command to the output control signal λinv by the adder 43. Further, the output signal λcom of the neutral point arm becomes the third harmonic component waveform. Generally, the superimposed third harmonic effective value is set to about 15% of the desired fundamental effective value. Here, as the third harmonic component, the AC power supply voltage Vin, the AC output voltage Vout, and the zero-phase current Icom are detected, and the signals are processed by the input / output synchronization determination circuit 45 to thereby generate the third harmonic component. Is calculated by multiplying the reference waveform 3ωinvref of the third harmonic component by the multiplier 44. The reference waveform 3ωinvref of the third harmonic component is generated by a circuit similar to the circuit that generates the reference waveform 3ωcnvref of the third harmonic component shown in FIG. 4, and has the same waveform during normal operation.

  FIG. 6 shows a third embodiment of the present invention. It is an example of a control block of the input / output synchronization determination circuit 45 in the second embodiment. A ΔF detector 51 that detects the absolute value | ΔF | of the frequency deviation between the AC power supply voltage Vin and the AC output voltage Vout; a determination circuit 52 that compares the output with the set value n1 [Hz] of the setter 53; Δφ detector 56 that detects the absolute value | Δφ | of the phase difference between voltage Vin and AC output voltage Vout; a determination circuit 57 that compares the output with set value n2 [° el] of setter 58; and zero-phase current When a determination circuit 59 that detects Icom and compares it with the set value n3 [A] of the setting device 60, a logical OR circuit 54, and a switching circuit 55 is provided, and one of the comparison results deviates from the setting range Operates to switch from trapezoidal wave modulation to sine wave modulation by switching the superposition gain G3ω to zero.

  FIG. 7 shows a fourth embodiment of the present invention. It is an example of a control block of the input / output synchronization determination circuit 39 or 45 in the second embodiment. A ΔF detector 60 for detecting the absolute value | ΔF | of the frequency deviation ΔF between the AC power supply voltage Vin and the AC output voltage Vout, and a gain for adjusting the amount of superposition of the third harmonic to an appropriate value according to the deviation amount , A Δφ detector 61 for detecting the absolute value | Δφ | of the phase difference Δφ between the AC power supply voltage Vin and the AC output voltage Vout, and an appropriate amount of superposition of the third harmonic according to the deviation amount A circuit 63 for multiplying a gain to be adjusted to an appropriate value, and a circuit 64 for multiplying a gain for detecting the zero-phase current Icom and adjusting the superposition amount of the third harmonic to an appropriate value according to the deviation amount, Are added by an adder 65 and subtracted from a value that is normally superposed (generally about 15% and set by a setter 67) to adjust the superposition gain G3ω. Here, the superposition gain G3ω is limited by the limiter 68, and the third harmonic component is limited to a range of 0% to 15%.

  By the method described above, trapezoidal wave modulation can be applied in a state where the AC power supply voltage Vin and the AC output voltage Vout are synchronized (normal operation state), and loss in the normal operation state can be reduced. Further, even when the AC power supply voltage Vin and the AC output voltage Vout are in an asynchronous state, the zero-phase current Icom flowing between the forward converter and the reverse converter can be suppressed within a predetermined range. Further, according to this proposed method, a reactor (or a transformer) and a capacitor for suppressing the zero-phase current Icom are not necessary, and the apparatus can be reduced in size and cost.

  The present invention can be applied to a multi-phase AC power source such as a 400 Hz power source for aircraft as well as an inverter for driving a motor and an uninterruptible power supply.

1 is a circuit configuration diagram showing a first embodiment of the present invention. Waveform of each part in Figure 1 Circuit configuration diagram showing a second embodiment of the present invention Block diagram of the forward converter control circuit of FIG. Inverter control circuit block diagram of FIG. Control circuit block diagram showing a third embodiment of the present invention Control circuit block diagram showing a fourth embodiment of the present invention Circuit configuration example 1 of a conventional three-phase AC-AC converter Circuit configuration example 2 of a conventional three-phase AC-AC converter Comparison of sinusoidal and trapezoidal modulation

Explanation of symbols

1 ... AC power supply 2-15 ... Semiconductor switch (IGBT)
16, 16A, 16B, 101A, 101B, 102A, 102B ... DC capacitor 17-23 ... Reactor 24-29 ... Filter capacitor 100 ... Transformer 31, 34, 36, 41, 43, 65 , 66 ... Adder 32, 42 ... Voltage regulator 35 ... Current regulator
37 ... Phase-synchronized transmitter 33, 38, 44 ... Multiplier 39, 45 ... I / O synchronization determination circuit 51, 60 ... Frequency deviation detector 56, 61 ... Phase difference detector 52, 57, 59 ... judgment circuit 53, 58, 60, 67 ... setter 54 ... logic OR circuit 62-64 ... gain 55 ... switch 68 ... limiter

Claims (4)

Connected to a three-phase AC power supply, consisting of a semiconductor switch, a reactor, and a filter capacitor, consisting of a forward converter that performs AC-DC conversion by high-frequency switching operation of the semiconductor switch, a semiconductor switch, a reactor, and a filter capacitor. DC-AC conversion is performed by switching operation, and is composed of an inverse converter that outputs a three-phase AC voltage, the forward converter and the filter capacitor connection method of the inverse converter is a star connection, A neutral point arm composed of a series circuit of an even number of semiconductor switches between the DC positive terminal and the DC negative terminal of the forward converter or the reverse converter or both of them, and an intermediate point thereof And the neutral point of the filter capacitor are connected via a reactor,
A DC positive terminal of the forward converter and a DC positive terminal of the reverse converter are connected via a primary winding of a transformer, and a DC negative terminal of the forward converter and a DC negative terminal of the reverse converter are connected. In the three-phase AC-AC converter connected via the secondary winding of the transformer, the pulse width is changed according to the instantaneous value of the signal wave to control the inverse converter and the neutral point arm. The so-called pulse width modulation control is used, and a distorted wave obtained by adding a harmonic component to a sine wave is used for the signal wave of the inverse converter according to the AC output voltage, while the signal wave for the neutral point arm control is used. A three-phase AC-AC converter characterized in that the output phase voltage of the inverse converter is a sine wave by using a waveform corresponding to the harmonic component of the signal wave of the inverse converter control. Connected to a three-phase AC power supply, consisting of a semiconductor switch, a reactor, and a filter capacitor, consisting of a forward converter that performs AC-DC conversion by high-frequency switching operation of the semiconductor switch, a semiconductor switch, a reactor, and a filter capacitor. DC-AC conversion is performed by switching operation, and is composed of an inverse converter that outputs a three-phase AC voltage, the forward converter and the filter capacitor connection method of the inverse converter is a star connection, A neutral point arm composed of a series circuit of an even number of semiconductor switches between the DC positive terminal and the DC negative terminal of the forward converter or the reverse converter or both of them, and an intermediate point thereof And a neutral point of the filter capacitor are connected via a reactor. In the location,
The forward converter includes means for superimposing a third harmonic component in accordance with an AC power supply voltage and means for adjusting a DC voltage command, and the inverse converter and the neutral point arm have an AC output voltage. And a means for superimposing the third harmonic component according to the above. When the AC power supply voltage and the AC output voltage are asynchronous, each converter performs power conversion operation by sinusoidal modulation, and the neutral point arm has zero voltage. When the AC power supply voltage and the AC output voltage are synchronized, the forward converter performs the trapezoidal wave modulation using the signal wave on which the third harmonic component is superimposed according to the AC power supply voltage. The converter uses trapezoidal wave modulation using a signal wave with the third harmonic component superimposed according to the AC output voltage, and the neutral point arm uses the third harmonic component used for trapezoidal wave modulation of the inverse converter. The voltage control used for the signal wave is performed individually. The three-phase AC - AC converter.   The three-phase AC-AC converter includes a means for detecting a phase difference between an AC power supply voltage and an AC output voltage, a means for detecting a difference between an AC power supply voltage frequency and an AC output voltage frequency, or a forward converter and an inverse converter. Means for detecting a zero-phase current (common mode current) flowing between the devices, and when any of the detecting means deviates from a predetermined range, the superposition of the third harmonic is stopped. The three-phase AC-AC converter according to claim 2.   The three-phase AC-AC converter includes a means for detecting a phase difference between an AC power supply voltage and an AC output voltage, a means for detecting a difference between an AC power supply voltage frequency and an AC output voltage frequency, or a forward converter and an inverse converter. Means for detecting a zero-phase current (common mode current) flowing between the detectors, and adjusting the amount of superimposition of the third harmonic according to the detection amount of the detection means, so that the zero-phase current is predetermined. The three-phase alternating current-alternating current converter according to claim 2, wherein the three-phase alternating current to alternating current conversion device is controlled within the range.

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