JP4127689B2 - Wireless communication device - Google Patents

Description

  The present invention relates to a wireless communication apparatus having a plurality of transmission / reception units.

In general, a wireless communication apparatus has a single transmission unit and reception unit. On the other hand, recently, in order to increase the transmission speed, to provide directivity, or to support a plurality of communication methods, a plurality of reception units or a plurality of transmissions are described as described in Patent Document 1 or the like. Research and development of wireless communication devices with units is underway. Each of the reception units includes, for example, a low noise amplifier, a down converter, a variable gain amplifier, a quadrature demodulator, a low pass filter, and an A / D converter. Each of the transmission units includes, for example, an A / D converter, a low-pass filter, a quadrature modulator, a variable gain amplifier, an up converter, and a power amplifier.
Japanese Patent Laid-Open No. 11-103325

  When mounting a wireless communication apparatus including a plurality of receiving units or a plurality of transmitting units (hereinafter, the receiving unit and the transmitting unit are collectively referred to as a transmitting / receiving unit), the required number of ICs each including the transmitting / receiving units integrated are required. Generally, it is mounted on a substrate, but there is a problem in that the cost increases and the mounting area increases.

  Such a problem can be solved by integrating a plurality of transmission / reception units in one integrated circuit (IC), but local signal components (basic of local signals) to the power supply line and ground line which are power supply circuits of the IC Wave component and harmonic component), that is, local leak increases, and distortion characteristics of the transmission / reception unit deteriorate. For example, assuming that the local leak amount in one transmission / reception unit is 1, the local leak amount when N transmission / reception units are integrated in one IC is N.

  Local leakage is induced due to parasitic inductors in power supply lines and ground lines, manufacturing variations of transistors included in local buffers that amplify local signals, parasitic capacitors, and the like. That is, when a local signal is amplified by the local buffer, a current change of the fundamental wave component of the local signal occurs in the power supply line and the ground line by the parasitic inductor, and the fundamental wave component is induced as a leak. In addition, a non-linear component of the amplifier serving as the local buffer causes a current change in the harmonic component of the local signal, and the harmonic component is induced as a leak.

  An object of the present invention is to reduce local leakage to a power supply line and a ground line in a wireless communication apparatus having a plurality of transmission / reception units.

  In order to solve the above problems, a wireless communication device according to a first aspect of the present invention has a plurality of fixed phase differences set so that local signal components leaking to a power supply line and a ground line are canceled out, respectively. A local signal generator for generating individual local signals, and a plurality of multipliers for multiplying each of the individual local signals by a plurality of input signals.

  According to a second aspect, a local signal generator that generates a plurality of individual local signals having a fixed phase difference set so that local signal components leaking to the power supply line and the ground line are canceled out, and Provided is a radio communication apparatus comprising a plurality of receiving units integrated in one integrated circuit, each including at least one multiplier for multiplying each of local signals and each of a plurality of input signals related to reception To do.

  According to a third aspect, a local signal generator that generates a plurality of individual local signals having a fixed phase difference set so that local signal components leaking to the power supply line and the ground line are canceled out, and Provided is a wireless communication apparatus comprising a plurality of transmission units integrated in one integrated circuit, each including at least one multiplier for multiplying each of a local signal and each of a plurality of input signals related to transmission To do.

  According to a fourth aspect of the present invention, a local signal generator that generates a plurality of individual local signals and at least one multiplier that performs multiplication of each of the individual local signals and each of a plurality of input signals related to reception. And a plurality of receiving units integrated in one integrated circuit, and a power supply line and a ground line for individually supplying power to the receiving unit.

  According to a fifth aspect of the present invention, at least one multiplication for multiplying a local signal generator for generating a plurality of individual local signals and each of the individual local signals and each of a plurality of input signals related to transmission. There is provided a wireless communication apparatus including a plurality of transmission units integrated in one integrated circuit, each including a transmitter, and a power line and a ground line for individually supplying power to the transmission unit.

  According to the present invention, even when a plurality of transmission / reception units are integrated in one IC, local leakage to the power supply line and the ground line can be reduced. As a result, integration can be easily performed, the manufacturing cost is reduced, and the mounting cost is also reduced.

Embodiments of the present invention will be described below with reference to the drawings.
In the local signal supply circuit shown in FIG. 1, the local signal source 11 is realized by an oscillator and generates a reference local signal. The reference local signal is input to a phase shifter (fixed phase shifter) 12 and subjected to a phase shift by a plurality of phase shift amounts, whereby a plurality (N) individual local signals f _LO ¹ to f having a fixed phase difference Δθ. f _LO ^N is generated. The individual local signals f _LO ^{1 to} f _LO ^N are amplified by the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N, respectively, and then N multipliers (mixers). 15-1 to 15-N are supplied to local (LO) signal terminals.

  The multipliers 15-1 to 15-N are elements of N receiving units or transmitting units, and have a high frequency (RF) signal terminal and an intermediate frequency (IF) signal terminal in addition to the LO signal terminal. N receiving units or N transmitting units are integrated in one IC.

When the multipliers 15-1 to 15 -N are frequency converters as elements of the receiving unit, for example, RF signals having frequencies f _RF ^{1 to} f _RF ^N are input to the RF signal terminals. In the multipliers 15-1 to ¹⁵ -N, down-conversion is performed by multiplying the RF signals of the frequencies f _RF ^{1 to} f _RF ^N by the individual local signals of the frequencies f _LO ^{1 to} f _LO ^N , and the frequency f _IF signals of _IF ^{1 to} f _IF ^N are generated.

When the multipliers 15-1 to 15 -N are frequency converters as elements of the transmission unit, for example, IF signals with frequencies f _IF ^{1 to} f _IF ^N are input to the IF signal terminals. Multipliers 15-1 to ¹⁵ -N perform up-conversion by multiplying the IF signals of frequencies f _IF ^{1 to} f _IF ^N and the individual local signals of frequencies f _LO ^{1 to} f _LO ^N to obtain the frequency f _RF signals of _RF ^{1 to} f _RF ^N are generated.

  Thus, the multipliers 15-1 to 15-N function as, for example, a down converter as an element of the reception unit, and function as, for example, an up converter as an element of the transmission unit. As will be described later, the multipliers 15-1 to 15-N can be used as elements of a quadrature demodulator or a quadrature modulator.

  An output from the DC power supply 16 that supplies power to the reception unit or the transmission unit is supplied to the reception unit or the transmission unit via a power supply pad 17 provided on the IC. Here, only power supply paths to the first local buffers 13-1 to 13-N, the second local buffers 14-1 to 14-N, and the multipliers 15-1 to 15-N are shown. The inductance indicated by the symbol L in the power supply path is a parasitic inductance of the power supply line and the ground line. However, the parasitic inductor of the ground line is omitted in FIG.

  The first local buffers 13-1 to 13-N are arranged in the vicinity of the local signal source 11 and the phase shifter 12, and the second local buffers 14-1 to 14-N are multipliers 15-1 to 15-N of each system. It is arranged in the vicinity of The distance between the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N is generally 1 mm or more. As the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N, single-phase amplifiers or differential amplifiers are used.

  Here, when the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N are single-phase amplifiers, the phase shifter 12 has individual local signals having a phase difference Δθ of 360 ° / N, That is, individual local signals each having a phase of 360 ° × (i−1) / N (i = 1,..., N) are generated. When the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N are differential amplifiers, the phase shifter 12 has individual local signals with a phase difference Δθ of 180 ° / N, that is, Generates an individual local signal having a phase of 180 ° × (i−1) / N (i = 1,..., N).

The phase shifter 12 is realized by combining several phase shifter elements. 2, 3 and 4 show examples of phase shifter elements used for the phase shifter 12. When the input signal V _IN , the output signal is V _OUT , the resistance value is R, the capacitor value is C, and R = 1 / (ω _LO C), the circuit in FIG. 2 is a −45 ° phase shifter, The circuit of 3 acts as a 45 ° phase shifter, and the circuit of FIG. 4 acts as a 0 ° phase shifter (same as a simple distributor). By appropriately combining these various phase shifter elements, a phase shifter having a phase difference Δθ that is a multiple of 45 ° can be realized.

  Here, when a single-phase amplifier is used as the local buffer, N = 2, 4, and 8 can be applied, and when a differential amplifier is used, N = 2 and 4 are applicable. Further, since an arbitrary phase difference can be set by changing the value of the resistor or capacitor constituting the phase shifter element of FIGS. 2 and 3, a phase difference such as N = 3 can also be realized. However, in this case, the element accuracy is deteriorated as compared with the 45 ° phase shifter, but there is no particular problem in application to the phase shifter 12 in the present embodiment.

In FIG. 5, the common local signal f _LORF is supplied to the multipliers from the local signal source via the common first local buffer BURFFC and the individual second local buffers BURFFC ^{11 to} BURFFC ^N1 without using the phase shifter 12. Show the state. FIG. 6 shows a local signal f common to the multipliers from the local signal source through the common first local buffer BURFFC, individual second local buffers BURFFC ^{11 to} BURFFC ^N1, and a 90 ° phase shifter (π / 2). _Shows how _LORF is supplied. As will be described later, this simulates the configuration in the case where the Lo signal is input to the quadrature modulator / demodulator. As shown in FIGS. 5 and 6, when the phase shifter 12 is not provided, f _LORF and 2f _LORF are largely leaked to the power supply line and the ground line. This is particularly noticeable when the local buffer is a single phase, but the same is true for the differential buffer. This will be described below.

  When a single-end amplifier is used for the local buffer, the local signal component induced in the power supply line and the ground line is very large for both the fundamental wave component and the harmonic component. This is because the signal amplified by the single-phase amplifier is converted into a current, and the current flows through the parasitic elements of the power supply line and the ground line. On the other hand, as shown in FIG. 7, if a differential amplifier using differential pair transistors Q1 and Q2, load resistors R1 and R2 and current source transistor Q3 is used as a local buffer, local buffers induced on a power supply line or a ground line are used. The fundamental wave component and harmonic component of the signal are reduced. This is because a constant current always flows through the differential amplifier, and even when a signal is input, a constant current flows through the power supply line and ground line, so no voltage is induced even if there is a parasitic inductor in the power supply line or ground line. is there.

However, the fundamental component (f _LO component) and the harmonic component (figure of the local signal) are affected by the operation of the differential amplifier, the voltage offset (V _ofs ) due to manufacturing variations, and the influence of the capacitor C1 parasitic on the collector of the current source transistor Q3. 7, the second harmonic 2f _LO component) flows to the power supply line. Since the potential of the common emitter terminal of the differential pair transistors Q1 and Q2 follows the higher one of the potentials of the base terminals of Q1 and Q2, the 2f _LO component of the signal input to the base terminal is applied to the common emitter terminal. Is generated and transmitted to the power line.

Next, the local leak will be described with reference to FIG. In FIG. 8, the voltage offset (V _ofs ) between the differential pair transistors Q1 and Q2 due to transistor manufacturing variations is considered. In this case, not only the 2f _LO component but also the f _LO component is generated at the common emitter terminal of the transistors Q1 and Q2 due to the offset. This is because the symmetry of the differential circuit is lost due to the offset.

  As described above, at least local leakage to the power supply line is caused by the inductor parasitic on the power supply line and the ground line, the manufacturing variation of the transistor, and the parasitic capacitor of the transistor. When a plurality of transmission / reception units are integrated in one IC, local leakage to the power supply line and the ground line increases, and the distortion characteristics of the transmission / reception units deteriorate.

According to an embodiment of the present invention, the individual local signals f _LO ^{1 to} f _LO ^N having a fixed phase difference Δθ are generated from the reference local signal generated by the local signal source 11 by the phase shifter 12, and these are generated as the ^first local signals. By supplying the signals to the LO signal terminals of the multipliers 15-1 to 15-N via the buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N, such a problem is solved. The Hereinafter, this reason will be described.

FIG. 9 shows the phase relationship between the f _LO component and the 2f _LO component when a single-phase amplifier is used for the local buffer. The phase reference is the phase number 1. When the number of multipliers (number of individual local signals) N is N = 2, the f _LO components of the two individual local signals are out of phase with each other, so components leaking to the power supply line and ground line cancel each other. Significantly smaller. On the other hand, since the 2f _LO components of the two individual local signals are in phase and are not canceled out, this is the same as the case without the phase shifter 12. In the case of N = 3 and N = 4, the f _LO component and 2f _LO component of the 3 and 4 individual local signals cancel each other, so that any component that leaks to the power supply line or the ground line is large. To decrease.

  Thus, when a single-phase amplifier is used for the local buffer, the phase difference Δθ of N individual local signals is 360 ° / N, in other words, the phase of each individual local signal is 360 ° × (i−1) / By setting N (i = 1,..., N), it is possible to effectively reduce local leakage to the power supply line and ground line, that is, leakage of local frequency components and harmonic components thereof.

FIG. 10 shows the phase relationship between the f _LO component and the 2f _LO component when a differential amplifier is used for the local buffer. In the case of the differential amplifier, the paired signals (differential signal pair) are out of phase with each other, so + and − are used to distinguish the two differential signals. That is, 1+, 1- is a differential signal pair with i = 1, 2+, 2- is a differential signal pair with i = 2, 3+, 3- is a differential signal pair with i = 3, 4+, 4- is i. = 4 represents local leakage due to differential signal pairs. However, i = 1,..., N.

When the local buffer is a single phase amplifier, the phase difference of the individual local signal is 360 ° / N, whereas when the local buffer is a differential amplifier, the phase difference of the individual local signal is 180 ° / N, that is, The phase of each individual local signal may be 180 ° × (i−1) / N (i = 1,..., N). The phase reference is the phase number 1+. As can be seen from FIG. 10, in both cases of N = 2, N = 3, and N = 4, the f _LO component and the 2f _LO component leaking to the power supply line and the ground line are in a mutually canceling relationship. Is also significantly reduced. In other words, even if the local buffer is a differential amplifier, the local leakage is reduced by providing the phase shifter 12 in consideration of the local leakage due to the variation.

The local buffer is a differential amplifier, in the case of using the phase shifter 12 when not used (Fig. 1) and local f _LO component and 2f _LO components leaking to the power supply line and a ground line for (FIG. 5) Compare leaks. FIG. 11 shows a comparison of local leak amounts when N = 2. As a comparison assumption, as described with reference to FIG. 8, it is assumed that the f _LO component generated at the common emitter terminal of the transistors Q1 and Q2 leaks to the power supply line and the ground line due to the difference in symmetry of the differential circuit. Two individual local signals are identical.

In the case where the phase shifter 12 is not provided, the f _LO component is included in the differential signal 1+, 1-pair and the differential signal pair 2+, 2- in the example of N = 2, so that the leak amount is generated by one differential signal pair. This is twice the amount of leakage. That is, for example, if the leak amount generated by the differential signal pair 1+, 1− is Δ1, the leak amount of the f _LO component is 2 × Δ1. For the 2f _LO component, leaks generated by 1+, 1-, 2+, 2- are respectively added in phase. Assuming that these leak amounts are all the same, for example, if the leak amount due to 1+ is L (1+), the leak amount of the 2f _LO component is 4 × L (1+).

On the other hand, when the phase shifter 12 is provided, the differential signal pair 1+, 1- and the differential signal pair 2+, 2- have a phase difference of 90 ° from Δθ = 180 ° / N. When the leak amount generated by the pair 1+, 1− is Δ1, the leak amount of the f _LO component is a combination of two Δ1 having a phase difference of 90 °, and is 2 ^1/2 × Δ1. 2f The _LO component, 1 + differential signal pair, 2 + 1- 2f _LO component and the differential signal pair, since 2f _LO component of 2- cancel each other become opposite phase, the leakage amount is no phase shifter 12 Compared to 4 × L (1+) in the case, it is greatly reduced.

  The above is the case where N = 2 and the local buffer is a differential amplifier. However, by using the phase shifter 12, the same principle is applied to the case where N = 3 or more and when a single-phase amplifier is used for the local buffer. Leakage can be reduced.

In the above description, in order to minimize the local leakage of the f _LO component and the 2f _LO component to the power supply line and the ground line, the phase difference Δθ of the individual local signal is set to 360 ° / N (the local buffer is simply used). In the case of a phase amplifier) or 180 ° / N (when the local buffer is a differential amplifier), the phase difference Δθ does not necessarily have to be set strictly.

That is, only varying the phase of the individual local signal, f _LO component and 2f _LO component leaks to the power supply line and the ground line than in the case of the same phase be less is clear. This is because the local leak becomes the largest when the f _LO component and the 2f _LO component of the individual local signal have the same phase. Therefore, the local leak of the f _LO component and the 2f _LO component can be reduced only by giving an arbitrary phase difference to the individual local signal.

Next, a specific example in which the above-described local signal supply circuit is actually applied to a reception system or a transmission system of a wireless communication device will be described.
FIG. 12 shows a specific example of a reception system for a wireless communication apparatus according to an embodiment of the present invention. The plurality (N) of receiving units RX ^{1 to} RX ^N are mounted on a single IC. On the other hand, in addition to the receiving units RX ^{1 to} RX ^N , the RF local signal source 11A, the IF local signal source 11B, the RF phase shifter 12A, the IF phase shifter 12B, the RF first local buffer 13A, and the IF first A local buffer 13B is provided.

The RF reference local signal of frequency f _LORF output from the RF local signal source 11A is made into N individual local signals for _{RF with} a phase difference Δθ _RF by the RF phase shifter 12A, and then the first local RF signal. The signals are distributed to the receiving units RX ^{1 to} RX ^N via the buffer 13A.

Similarly, the IF reference local signal _having the frequency f _LOIF output from the IF local signal source 11B is converted into N IF individual local signals having the IF phase shifter 12B phase difference Δθ _IF and then the IF reference local signal. 1 is distributed to the receiving units RX ^{1 to} RX ^N via the local buffer 13B.

Received RF signals of frequencies f _RF ^{1 to} f _RF ^N are output from the antennas 21-1 to 21 ^-N and input to the receiving units RX ^{1 to} RX ^N. In FIG. 12, only one receiving unit RX ¹ is shown in detail, but the same applies to the other receiving units.

In the reception unit RX ¹ , the input received RF signal is amplified by a low noise amplifier (LNA) and then input to an up-converter 15 A composed of a multiplier. The down-converter 15A is configured such that the RF individual local signal distributed to the receiving unit from the RF local signal source 11A via the RF phase shifter 12A and the RF local buffer 13A is an RF second local buffer 14A inside the receiving unit. , The received reception RF signal is down-converted and converted to an IF signal of frequency f _IF ¹ .

  The IF signal output from the down converter 15A is freed from unnecessary components by a band pass filter (BPF) and further amplified by a variable gain amplifier (VGA). Then, two multipliers 15B constituting the quadrature demodulator 18 and It is input to 15C. The IF individual local signal distributed to the receiving unit from the IF local signal source 11B via the IF phase shifter 12B and the IF local buffer 13B is taken in via the IF second local buffer 14B inside the receiving unit. Then, two local signals orthogonal to each other are input to the multipliers 15B and 15C via the 90 ° phase shifter (π / 2).

The signal demodulated by the quadrature demodulator 18 is subjected to removal of unnecessary components by a low-pass filter (LPF) and then converted to a digital signal by an A / D converter, whereby digital quadrature baseband signals I _CH ¹ and Q _The transmission data is reproduced by being set to _CH ¹ and further input to a baseband processing unit (not shown). The same processing is performed in the other receiving units 12-2,... 12-N, and a digital quadrature baseband signal is generated.

Here, the phase difference Δθ IF between the _RF individual local signals and the phase difference Δθ _IF between the _RF individual local signals are equal to 360 ° / N when the local buffers 13A, 13B and 14A, 14B are single-phase amplifiers, as described above. When the local buffers 13A, 13B and 14A, 14B are differential amplifiers, the angle is set to 180 ° / N. As a result, it is possible to suppress leakage of local signal components (fundamental wave components and harmonic components) to the power supply line and the ground line.

FIG. 13 shows another specific example of a receiving system for a wireless communication apparatus according to an embodiment of the present invention. In this example, an adaptive array technology is used for the IF section. The IF unit down-converts the IF signal of the frequency f _IF ^{1 to} f _IF ^{N to} the second IF signal of the frequency f _IF2 ^{1 to} f _IF2 ^N by the multiplier 15B, and then adds the second IF signal of f _IF2 ^{1 to} f _IF2 ^N Then, by extracting as a single second IF signal f _IF2 , it is possible to give directivity to reception.

  In such an adaptive array technology, the directivity is adjusted by controlling the phase of a local signal having a relatively low frequency that is supplied to the IF section. Therefore, in the specific example of FIG. 13, the phase shifter 12B that generates the IF individual local signal by phase-shifting the IF reference local signal output from the IF local signal source 11B is a variable phase shifter with a variable phase shift amount. Is used. Therefore, the phase difference of the IF individual local signal is also variable. The IF individual local signal output from the phase shifter 12B is supplied to the down converter 15D via the local buffers 13B and 14B.

On the other hand, the RF individual local signal uses a phase shifter with a fixed amount of phase shift in the phase shifter 12A, so that the phase difference Δθ _RF can be obtained as in the specific example of FIG. 12 when the local buffers 13A and 14A are single-phase amplifiers. 360 ° / N, and 180 ° / N when the local buffers 13A and 14A are differential amplifiers. Since the leakage of the local signal component to the power supply line and the ground line increases as the frequency increases, the leakage can be reduced by providing a fixed phase difference Δθ _RF only for the RF local signal in this way, This is advantageous for integration.

FIG. 14 shows a specific example of a transmission system for a wireless communication apparatus according to an embodiment of the present invention. A plurality (N) of transmission units TX ^{1 to} TX ^N are mounted on a single IC. On the other hand, in addition to the transmission units TX ^{1 to} TX ^N , the RF local signal source 11A, IF local signal source 11B, RF phase shifter 12A, IF phase shifter 12B, RF first local buffer 13A, and IF first A local buffer 13B is provided.

The RF reference local signal of frequency f _LORF output from the RF local signal source 11A is made into N individual local signals for _{RF with} a phase difference Δθ _RF by the RF phase shifter 12A, and then the first local RF signal. The signals are distributed to the transmission units TX ^{1 to} TX ^N via the buffer 13A.

Similarly, the IF reference local signal _having the frequency f _LOIF output from the IF local signal source 11B is converted into N individual local signals for _{IF having} a phase difference Δθ _IF by the IF phase shifter 12B, and then the IF reference local signal. The signals are distributed to the transmission units TX ^{1 to} RTX ^N via the first local buffer 13B.

Digital orthogonal baseband signals I _CH ⁱ and Q _CH ⁱ (i = 1,..., N) generated from transmission data by a baseband processing unit (not shown) are input to the transmission units TX ^{1 to} RTX ^N. FIG. 14 shows only the transmission unit TX ^{1 in} detail, but the same applies to the other transmission units.

In the transmission unit TX1, the input orthogonal baseband signals I _CH ¹ and Q _CH ¹ are converted into analog signals by a D / A converter, and then passed through a low-pass filter (LPF) for removing unnecessary components, The signals are input to two multipliers 15E and 15F constituting the quadrature modulator 19, respectively. The IF individual local signal distributed to the transmission unit from the IF local signal source 11B via the IF phase shifter 12B and the IF local buffer 13B is taken in via the IF second local buffer 14B inside the reception unit. Then, two local signals orthogonal to each other are input to the multipliers 15E and 15F via the 90 ° phase shifter (π / 2).

An IF signal obtained by synthesizing the outputs of the multipliers 15E and 15F is output from the quadrature modulator 19, and is input to an upconverter 15C including a multiplier via a variable gain amplifier (VGA) and a bandpass filter (BPF). The up-converter 15C is configured such that the RF individual local signal distributed to the transmission unit from the RF local signal source 11A via the RF phase shifter 12A and the RF local buffer 13A is an RF second local buffer 14A inside the transmission unit. The input IF signal is up-converted and converted into an RF signal having a frequency f _IF ¹ . The RF signal is amplified by a power amplifier (PA) and then supplied to the antenna 22-1 for transmission. Similar processing is performed in the other transmission units TX2,..., TXN, and transmission is performed by the antennas 22-2,.

Next, still another embodiment of the present invention will be described with reference to FIG.
In FIG. 15, the local signal output from the local signal source 11 is divided into N branches, amplified by the first local buffers 13-1 to 13-N and the second local buffers 14-1 to 14-N, and then N signals. Are respectively supplied to local (LO) signal terminals of the multipliers 15-1 to 15-N.

  The multipliers 15-1 to 15-N are elements of N receiving units or transmitting units, and have a high frequency (RF) signal terminal and an intermediate frequency (IF) signal terminal in addition to the LO signal terminal. N receiving units or N transmitting units are integrated in one IC.

When the multipliers 15-1 to 15 -N are frequency converters as elements of the receiving unit, for example, RF signals having frequencies f _RF ^{1 to} f _RF ^N are input to the RF signal terminals. In the multipliers 15-1 to ¹⁵ -N, down-conversion is performed by multiplying the RF signals of the frequencies f _RF ^{1 to} f _RF ^{N and} the _LO signals of the frequencies f _LO ^{1 to} f _LO ^N , and the frequency f _IF IF signals of ^{1 to} f _IF ^N are generated.

When the multipliers 15-1 to 15 -N are frequency converters as elements of the transmission unit, for example, IF signals with frequencies f _IF ^{1 to} f _IF ^N are input to the IF signal terminals. In the multipliers 15-1 to ¹⁵ -N, up-conversion is performed by multiplying the IF signals of the frequencies f _IF ^{1 to} f _IF ^{N and} the _LO signals of the frequencies f _LO ^{1 to} f _LO ^N , and the frequency f _RF RF signal ¹ ~f _RF ^N is generated.

  That is, the multipliers 15-1 to 15-N function as, for example, a down converter as an element of the reception unit, and function as, for example, an up converter as an element of the transmission unit. As described above, the multipliers 15-1 to 15-N can be used as elements of a quadrature demodulator or a quadrature modulator.

  In the example of FIG. 15, a power supply circuit is provided independently for N receiving units or N transmitting units. That is, the outputs from the DC power supplies 16-1 to 16-N are respectively sent to N reception units or N transmission units via power supply pads 17-1 to 17-N provided on the IC. Supplied. Here, only power supply paths to the first local buffers 13-1 to 13-N, the second local buffers 14-1 to 14-N, and the multipliers 15-1 to 15-N are shown. The inductance indicated by the symbol L in the power supply path is a parasitic inductance of the power supply line and the ground line. However, in FIG. 15, the parasitic inductor of the ground line is omitted.

  As described above, in this embodiment, a power supply circuit (power supply line and ground line) is individually provided for each of a plurality of transmission units or a plurality of reception units, so that power supply is not shared in the IC. Therefore, leakage of local signal components in each transmission unit or reception unit does not affect other transmission units or reception units, and reduces local signal interference between transmission units or reception units. be able to.

  Note that the present invention is not limited to the above-described embodiment as it is, and can be embodied by modifying the constituent elements without departing from the scope of the invention in the implementation stage. In addition, various inventions can be formed by appropriately combining a plurality of constituent elements disclosed in the embodiment. For example, some components may be deleted from all the components shown in the embodiment. Furthermore, constituent elements over different embodiments may be appropriately combined.

The figure which shows the local signal supply circuit in the radio | wireless communication apparatus which concerns on one Embodiment of this invention. Equivalent circuit diagram of -45 ° phase shifter used for the phase shifter in FIG. Equivalent circuit diagram of 45 ° phase shifter used for phase shifter in FIG. Equivalent circuit diagram of 0 ° phase shifter (voltage divider) used for the phase shifter in FIG. Diagram for explaining the leakage of f _LO component and 2f _LO component to the power supply line and the ground line of the RF local signal in the absence of a phase shifter Diagram for explaining the leakage of f _LO component and 2f _LO component to the power supply line and the ground line of the IF local signal in the absence of a phase shifter Figure for leakage f _LO component and 2f _LO component is described to the power supply line and the ground line when using a differential amplifier to the local buffer Figure for leakage f _LO component and 2f _LO component is described to the power supply line and the ground line when using a differential amplifier to the local buffer The figure showing the phase of f _LO component and 2f _LO component when a single phase amplifier is used for the local buffer The figure showing the phase of f _LO component and 2f _LO component when a differential amplifier is used for the local buffer FIG local buffer will be described leakage of f _LO component and 2f _LO component to the power supply line and the ground line when not used with the case of using the phase shifter when the differential amplifier The block diagram which shows an example of the receiving system of the radio | wireless communication apparatus which concerns on one Embodiment of this invention. The block diagram which shows another example of the receiving system of the radio | wireless communication apparatus which concerns on one Embodiment of this invention. The block diagram which shows an example of the transmission system of the radio | wireless communication apparatus which concerns on one Embodiment of this invention. The circuit diagram of the radio | wireless communication apparatus which concerns on another embodiment of this invention.

Explanation of symbols

11, 11A, 11B ... local signal source;
12, 12A, 12B ... phase shifter;
13-1 to 13-N, 13A, 13B... First local buffer;
14-1 to 14-N, 14A, 14B ... second local buffer;
15-1 to 15-N, 15A, 15B, 15C ... multipliers;
16, 16-1 to 16-N ... DC power supply;
17, 17-1 to 17-N: power supply pads;
18: Quadrature demodulator;
19: Quadrature modulator;
21-1 to 21-N: receiving antenna;
22-1 to 22-N: Receive antennas.

Claims (10)

A local signal source for generating a reference local signal;
A phase shifter for phase shifting the reference local signal to generate a plurality (N) of individual local signals having a phase difference of 360 ° / N;
A plurality of single-phase amplifiers each amplifying the individual local signals;
A plurality of integrated circuits integrated in one integrated circuit, each including at least one multiplier for multiplying each of the individual local signals amplified by the plurality of single-phase amplifiers and each of the plurality of input signals related to reception. A wireless communication apparatus comprising a receiving unit. A local signal source for generating a reference local signal;
A phase shifter that phase-shifts the reference local signal to generate a plurality (N) of individual local signals having a phase difference of 180 ° / N;
A plurality of differential amplifiers each amplifying the individual local signals;
A plurality of integrated circuits in one integrated circuit each including at least one multiplier for multiplying each of the individual local signals amplified by the plurality of differential amplifiers and each of a plurality of input signals related to reception; A wireless communication apparatus comprising a receiving unit. Wherein the input signal is the received RF signal, the multiplier radio communication apparatus according to claim 1 or 2 according to any one of generating an intermediate frequency signal. 3. The wireless communication apparatus according to claim 1, wherein the input signal is an intermediate frequency signal, and the multiplier includes first and second multipliers that perform orthogonal demodulation on the intermediate frequency signal. 4. . A local signal source for generating a reference local signal;
A phase shifter for phase shifting the reference local signal to generate a plurality (N) of individual local signals having a phase difference of 360 ° / N;
A plurality of single-phase amplifiers each amplifying the individual local signals;
A plurality of integrated circuits in one integrated circuit, each including at least one multiplier for multiplying each of the individual local signals amplified by the plurality of single-phase amplifiers and each of a plurality of input signals related to transmission; A wireless communication apparatus comprising a transmission unit. A local signal source for generating a reference local signal;
A phase shifter that phase-shifts the reference local signal to generate a plurality (N) of individual local signals having a phase difference of 180 ° / N;
A plurality of differential amplifiers each amplifying the individual local signals;
A plurality of integrated circuits in one integrated circuit each including at least one multiplier for multiplying each of the individual local signals amplified by the plurality of differential amplifiers and each of a plurality of input signals related to transmission; A wireless communication apparatus comprising a transmission unit. The radio communication apparatus according to claim 5, wherein the input signal is an intermediate frequency signal, and the multiplier generates a transmission RF signal. Wherein the input signal is the two data signals that are orthogonal to each other, the multiplier of any of claims 5 or 6 including first and second multipliers for performing orthogonal modulation on the data signal Wireless communication device. The wireless communication apparatus according to claim 1 , further comprising a power line and a ground line that individually supply power to the plurality of receiving units. The wireless communication apparatus according to claim 5 , further comprising a power line and a ground line that individually supply power to the plurality of transmission units.

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