JP3404105B2 - rectifier - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a rectifier that realizes a high power factor for AC-DC power conversion.

[0002]

2. Description of the Related Art Conventionally, single-phase capacitor input type rectifiers, which have been widely used mainly for home electric appliances, have a low power factor,
Since the AC side current contains a lot of harmonics, it has been a cause of a reduction in the utilization rate of power transmission equipment and distortion of the power supply voltage waveform.

Therefore, in recent years, attention has been paid to a rectifier which is intended to improve the power factor and reduce the AC side harmonic current.

The principle of improving the power factor and the waveform by the rectifier is to control the AC side current to have a similar waveform and the same phase as the power supply voltage.

Most of the conventional rectifiers that realize a high power factor have adopted a method called a step-up chopper. As a method of operating this boost chopper circuit, FIG.
There are a current reset type and a current continuous type as shown in (3), and the current continuous type further includes a fixed hysteresis method, a current proportional hysteresis method, a constant frequency method, and the like.

First, the current reset type is a discontinuous current control system in which the inductance current is dry-out every cycle, as shown in FIG. On the contrary, the continuous current type is a control method in which an inductance current as shown in FIGS.

Generally, the hysteresis control uses a comparator having hysteresis to have a positive and negative binary voltage, and to reduce the current when the actual current flowing through a certain load exceeds a set reference current. A negative voltage is applied, and when the voltage is lower than the negative voltage, a positive voltage is instantaneously switched and applied by a switch element. As a result, the current control is such that the actual current flows while fluctuating up and down around the set reference current, and the current of the input reactor is controlled within a certain hysteresis width range from the target current. In this case, the error between the actual current and the reference current depends on the width of the hysteresis of the comparator provided in the controller. Such hysteresis control is applied to a rectifier, and in order to control the AC side current to have a similar waveform and the same phase as the power supply voltage, the reference current is obtained from the similar form of the reference voltage, and it is compared with the actual current. The switching element is switched instantaneously by the current control as shown in FIG.

On the other hand, in the constant frequency control, for the purpose of keeping the switching frequency constant, first, the detected value of the DC output voltage is compared and amplified with the set value by the configuration shown in FIG. Get the signal. Next, the reference sine wave in phase with the AC input voltage is multiplied by this error signal to obtain the target value of the AC input current. Further, the detected value of the AC input current is compared with this target value and amplified to obtain an error signal of the AC input current. Finally, the error signal of the AC input current is modulated with the reference carrier wave to obtain the PWM signal for driving the switch element. In this way, as shown in FIG. 15D, the AC input current can be controlled to have a sine wave in phase with the AC input voltage while maintaining the DC output voltage at a constant voltage. Proportional / integral control (PI control) has been mainly used in this control system.

[0009]

In such a conventional rectifier, in principle, the current reset method has a large peak voltage in principle, resulting in a large switching loss and a large element, which requires a large capacity. It was not suitable for conversion.

According to the conventional hysteresis control method, if the setting of the hysteresis width is narrowed in order to reduce the error between the actual current and the reference current, the switching frequency increases, and conversely the setting of the hysteresis width is widened. If this is attempted, the switching frequency will decrease, but the error will increase and current followability will deteriorate. Also, for a certain width of hysteresis, when the reference current changes, the switching frequency changes accordingly, so when the current becomes large, the switching frequency also becomes large, and the switching frequency is not fixed. It is known that there is a possibility that an unknown frequency, which is not preferable in terms of noise countermeasures, may be included in the above. To improve this, FIG.
As shown in (c), change the input reactor current to
A method called a window comparator for controlling between two sine waves has also been devised. According to this method, the oscillation frequency fluctuation, control delay, etc. are slightly improved, but the fundamental problem has not been solved.

It has been pointed out that in the constant frequency control, the responsiveness and stability of current control due to the PI control system are poor.

In addition, as a method based on the instantaneous value predictive control of the current which has been conventionally used to solve these responsiveness, a method mainly applying digital control has been proposed. According to this method, since a device such as a digital signal processor or an analog-digital converter is required, it is very expensive as compared with analog control, and it is not suitable for a small system such as a single-phase rectifier. Also,
There is also a limit to high-speed operation, and when trying to increase the switching frequency, more expensive digital signal processors and analog-digital converters were required. In addition, it is not possible to deal with power supply distortion and frequency fluctuations. Furthermore, since the frequency is fixed, there is a drawback that the audible noise is large due to the single and high sound pressure level compared to the frequency fluctuation method. It was also pointed out.

As described above, the conventional techniques do not always satisfy all of the points of noise generation, device complexity and cost, rapid response, stability against power supply fluctuation, and the above problems. It is a first object of the present invention to provide a new control technique to overcome, and to provide a device that can operate at high speed at a low cost with a simple configuration.

A second object is to realize an input power factor of 100% by making an alternating current follow an alternating current voltage with a device which can operate at high speed at a low cost with a simple structure.

A third object is to realize a simple structure and high speed operation which does not require a conventional analog divider and does not depend on load fluctuation.

A fourth object is to reduce annoying electromagnetic noise generated from the reactor.

[0017]

A first means for achieving the first object of the present invention is to provide a reactor on the input side and a capacitance on the direct current side of a rectifying circuit composed of a switch device. In the rectifier consisting of the connection, the input AC voltage detecting means for detecting the instantaneous value of the input AC voltage, the input AC current detecting means for detecting the instantaneous value of the AC current, and the DC output voltage for detecting the instantaneous value of the DC output voltage. Detection means,
Instantaneous value detection means including at least one of the input AC voltage detection means, the input AC current detection means, and the DC output voltage detection means, and an input AC voltage estimated value for detecting an estimated value of the input AC voltage Detecting means, input AC current estimated value detecting means for detecting the estimated value of the input AC current, DC output voltage estimated value detecting means for detecting the estimated value of the DC output voltage, the input AC voltage estimated value detecting means, and the input An estimated value detection unit including at least one of the AC current estimated value detection unit and the DC output voltage estimated value detection unit, and at least one of the instantaneous value detection unit and the estimated value detection unit The detection means, the signal generation means for generating a reference signal of an appropriate frequency, and the output of the detection means are input, and the conduction period of the device is queried.
Uses an analog adder / subtractor / multiplier / divider calculator
And an analog calculation means, a setting means for setting a certain fixed time, a measuring means for measuring an elapsed time from an appropriate timing point of the reference signal output from the signal generating means, and a measuring means for measuring by the measuring means. The determination means for determining that the elapsed time has reached the constant time set by the setting means, and the conduction period calculated by the calculation means, and the device after the fixed time determined by the determination means The gate control means for controlling conduction is configured.

A second means for achieving the second object is that the arithmetic means outputs the input AC voltage detection means output or the input AC voltage estimated value detection means output to the first operational amplification means and the variable gain means. And the input AC current detection means output or the input AC current estimated value detection means output is input to the second operational amplification means, and the first operational amplification means, the variable gain means, and the second operational amplification means At least one of the outputs is used as an input for addition / subtraction means for performing an analog operation, and an output signal of the signal generation means and an output signal of the addition / subtraction means are input and a pulse signal generation means for outputting a gate pulse signal to the gate control means. Configured, analog
The simple structure does not require a calculator .

The third means for achieving the third object is an amplitude for amplitude-modulating the reference signal of the signal generating means according to the output of the DC output voltage detecting means or the DC output voltage estimated value detecting means. The modulation means is arranged.

The fourth means for achieving the fourth object is to set an appropriate value within the range of the output level or phase detected by the input AC voltage detecting means or the input AC voltage estimated value detecting means. Setting means, the input AC voltage detecting means or the input AC voltage estimated value detecting means, a comparing means for comparing the output level or the phase of the setting means, and a signal generation according to the comparison result in the comparing means. The frequency modulation means for frequency-modulating the reference signal of the means is arranged.

[0021]

According to the present invention, with the configuration of the above-mentioned first means, at least one of the instantaneous value and the estimated value of the AC voltage, the AC current, and the DC voltage detected by the detecting means is converted into the conduction of the switch device by using an analog operation. The period can be realized at high speed and easily with an analog circuit.

With the configuration of the second means, the AC voltage and the AC current can be controlled to be similar to each other by controlling the current waveform to follow the constant voltage waveform of the AC voltage waveform by the variable gain amplifier or the like. It is possible.

Further, according to the structure of the third means, the structure in which the reference carrier signal is amplitude-modulated with the DC output voltage signal as a reference eliminates the need for the conventional analog divider and suppresses the fluctuation of the load constant. Therefore, the operation method that does not depend on the load fluctuation can be realized easily and at high speed.

Further, with the configuration of the fourth means, the reference carrier can have a plurality of frequencies within one cycle of the power supply by simply frequency-modulating the analog circuit according to the AC voltage. Since the sound pressure level of one frequency is reduced and dispersed, it is possible to reduce the jarring noise that cannot be avoided by the control with a single carrier frequency.

[0025]

EXAMPLE An example of a rectifier according to the present invention is a rectifier circuit 2 composed of four sets of switch devices 1a to 1d as shown in FIG. 2, a reactor 4 on an input side 3 and a capacitance on a DC side 5. 6 is provided, and its input terminal 7
A and 7b are basically connected to an AC power supply voltage 8 and output terminals 5a and 5b are connected to a load 9. Figure 3
This is an example of the switch devices 1a to 1d, and the IGBTs 11a to 11d are shown here, but the same applies to the case where transistors, MOSFETs, and the like are used. The diodes 11'a to 11'd shown in the figure are the IGBT 11a.
Although the parasitic diodes that exist in the configuration of 11d are shown, it goes without saying that an external diode also functions in the same manner. Hereinafter, those having the same function will be denoted by the same symbols, and description thereof will be omitted.

An embodiment of the first configuration of the rectifier of the present invention will be described with reference to FIG. In the figure, 10 is a rectifier composed of a connection in which a reactor 4 is provided on an input side 3 of a rectifying circuit 2 composed of switch devices 1a to 1d and a capacitance 6 is provided on a DC side 5, and 13 is an instantaneous value of an input AC voltage. Input AC voltage detecting means for detecting, 14 is input AC current detecting means for detecting an instantaneous value of AC current, 15 is a DC output voltage detecting means for detecting an instantaneous value of DC output voltage, and 16 is the input AC voltage detecting means. 13 and the input AC current detection means 1
4 and at least one of the DC output voltage detecting means 15
An instantaneous value detecting means composed of one or more parts; 17 an input AC voltage estimated value detecting means for detecting an estimated value of the input AC voltage;
Reference numeral 18 is an input AC current estimated value detecting means for detecting an estimated value of the input AC current, 19 is a DC output voltage estimated value detecting means for detecting an estimated value of the DC output voltage, and 20 is the input AC voltage estimated value detecting means 17 Estimated value detecting means composed of at least one of the input AC current estimated value detecting means 18 and the DC output voltage estimated value detecting means 19, and 21 of the instantaneous value detecting means 16 and the estimated value detecting means 20. Detecting means composed of at least one of them, 22 is a signal generating means for generating a reference signal of an appropriate frequency, 23 is an arithmetic means for receiving the output of the detecting means 21 as an input, and performing an analog operation of the conduction period of the switch device, 24 Is a setting means for setting a certain fixed time, 25 is the signal generating means 2
Measuring means for measuring the elapsed time from the appropriate timing of the two-output reference signal, 26 indicates that the elapsed time measured by the measuring means 25 has reached the certain time set by the setting means 24. Judgment means for judging, 27 is a conduction period calculated by the calculation means 23,
The gate control means is configured to control the conduction of the switch device after a fixed time determined by the determination means 26.

Next, an arithmetic expression used in the arithmetic means 23 of the rectifier of the present invention will be described. In FIG. 1, if the input AC voltage is v _s , the input AC current is i _s , and the voltage between the bridge input terminals 3a and 3b is v _B , the relationship of (Equation 1) is obtained.

[0028]

[Equation 1]

Here, L is the inductance of the reactor. Further, if the DC output voltage is v ₀ , the bridge input terminal voltage v _B can be divided into cases as in (Equation 2) (Equation 3) (Equation 4) by controlling the switch devices 1a to 1d.

[0030]

[Equation 2]

[0031]

[Equation 3]

[0032]

[Equation 4]

1 is to connect the switch devices 1a and 1b or 1c and 1d, (Formula 3) is to connect the switch devices 1a and 1c, and (Formula 4) is to connect the switch devices 1b and 1d. Can be expressed as Here, when the cycle for controlling the switch device is T _s, and both sides of (Equation 1) are subjected to definite integration from a certain time t to t + T _s ,
(Equation 5) is obtained.

[0034]

[Equation 5]

Here, i _s (t) and i _s (t + T _s ) are instantaneous alternating current values at time t and time t + T _s , respectively. Further, the definite integral on the left side of (Equation 5) is approximated to obtain (Equation 6).

[0036]

[Equation 6]

(Equation 6) gives a constant integral value of the bridge input terminal voltage v _B by giving a target current value at the time point t + T _s to i _s (t + T _s ) at the time point t. By controlling the switch device so as to satisfy the above condition, the AC side current can be set to the target value at the time t + T _s .

In this embodiment, as an example of satisfying the definite integral on the right side of (Equation 6), the switch device control period T _s
(Formula 3) or (Formula 4) is generated once for a certain period of time, and the rest is set to (Formula 2). In this one-cycle configuration, the definite integral on the right side of (Equation 6) can be approximately represented by (Equation 7) (Equation 8) from (Equation 2) (Equation 3) (Equation 4).

[0039]

[Equation 7]

[0040]

[Equation 8]

Here, (Equation 7) represents a case where (Equation 3) is generated within one cycle of the switch device control, and Expression (Equation 8) represents a case where (Equation 4) is generated. There is.
λ'is the time for generating (Equation 3) or (Equation 4). Further, if the variable λ having a positive or negative value is further associated with (Equation 7) and (Equation 8), (Equation 9) is obtained.

[0042]

[Equation 9]

Substituting (Equation 9) into (Equation 6) and solving for λ yields (Equation 10).

[0044]

[Equation 10]

In (Equation 10), when the sign of λ is positive,
Occurrence of (Equation 3) within the switch device control cycle,
When it is negative, the occurrence of (Equation 4) is represented, and the absolute value of λ represents the connection time. Here, in order to make the input power factor 100%, that is, the AC side current waveform has a similar shape and the same phase as the AC side voltage waveform, the AC side current target value in (Equation 10) is proportional to the AC voltage. If you give something, (Equation 1
0) can be rewritten as in (Equation 11).

[0046]

[Equation 11]

Here, α is a coefficient for adjusting the amplitude of the alternating current. Further, in (Equation 10), the AC current target value must be originally expressed by using the AC side voltage v _s at the time t + T _s , but since this value is unknown at the time t, the AC at the time t The side voltage v _s is used for approximation.

As described above, the computing means 23 sets the control pulse width λ applied to the switch device to ( _equation 11), where the AC voltage is v _s , the AC current is i _s , and the DC voltage is v _0.
Determined by Here, T _s is a cycle for controlling the switch device, and is given by the reference signal generated by the signal generating means 22.

The operation of one embodiment of the first configuration will be described based on the configuration and the calculating means described above.

In the configuration shown in FIG. 1, as shown in FIG. 4, the switch devices 1a to 1d are switched to S1 to _S at a cycle T _s .
When was the switching operation at the fourth timing, the alternating current detected by the input alternating current detecting means 14 becomes a stepped waveform as shown in FIG i _s. The operation within the period T _s of the power supply voltage v _s at any time t _k is shown in FIG. At that time t _k , when the detection means 21 is composed of the instantaneous value detection means 16 composed of the input AC voltage detection means 13, the input AC current detection means 14 and the DC output voltage detection means 15, the detected AC voltage v _s , AC current i _s , DC voltage v
Three instantaneous values of ₀ are detected. Then, the calculation means 2
Assuming that the input is 3, the calculation means 23 calculates
The control pulse width λ applied to the switch device is determined by the four arithmetic operations of addition, subtraction, multiplication and division shown in 1). That (number 1
The four arithmetic operations of addition, subtraction, multiplication and division shown in 1) have a simple configuration by using an analog adder, subtraction, multiplication and division calculator using a widely used quad operational amplifier. Then, for each generation cycle T _s of the reference signal of the signal generating means 22,
It was previously set in the setting means 24 (T _s
At time t _p of after determining 1-?) / 2 hours at determining means 26, conduction time λ that is calculated by the calculating means 23
The switch device is controlled by the gate control means 27. In this way, a rectifier with a simple structure and a high-speed operation can be realized with only the four arithmetic operations of addition, subtraction, multiplication and division by the analog calculator.

In this embodiment, only the instantaneous value detecting means is used as the input means for calculating means. However, in order to give each parameter of the calculating formula, the input AC voltage, input AC current,
Even if the DC output voltage is detected by the estimated value detecting means 20 constituted by the estimated value detecting means having a lead phase, this value is input to the calculating means 23 to calculate the conduction time λ and the above operation is carried out. Performance was obtained. Furthermore, the detecting means 2
As a combination of one configuration, for example, two of the input AC voltage detection means 13 and the DC output voltage detection means 15 are used as the instantaneous value detection means 16, and the input AC current estimated value detection means 18 is
Each of them is used as the estimated value detecting means 20, and this instantaneous value detecting means 1 is used.
6 and the estimated value detecting means 20 constitute three result detecting means 21,
Alternatively, two of the input AC voltage detection means 13 and the input AC current detection means 14 are used as the instantaneous value detection means 16, and the estimated value detection means 20 is not provided, and the instantaneous value detection means 16 and the estimated value detection means 20 detect two results. The configuration of the means 21 and the like are also conceivable, but the same result is naturally obtained as long as the above-mentioned arithmetic expression parameters are given. Needless to say, the same can be said for the following embodiments.

Next, an embodiment having the second structure will be described with reference to FIG. The calculation means 23 uses the output of the input AC voltage detection means 13 or the output of the input AC voltage estimated value detection means 17 as the input of the first calculation amplification means 28 and the variable gain means 29, and outputs the input AC current detection means 14 or the input AC current. The output of the estimated value detection means 18 is input to the second operational amplification means 30, and at least one of the outputs of the first operational amplification means 28, the variable gain means 29, and the second operational amplification means 30.
An adder / subtractor 31 for performing analog calculation with one or more outputs as inputs, and a pulse signal generator 32 for outputting a gate pulse signal to the gate controller 27 with the output signal of the signal generator 22 and the output signal of the adder / subtractor 31 as inputs. It is composed of.

Although it is basically the same as the first configuration, in the present embodiment, the first term T _s × v _s is calculated for each term of the analog four arithmetic expressions shown in (Equation 11). The second term α × v _s is implemented by the variable gain means 29, and the third term L × i _s (t) is implemented by the second operational amplifier means 30. The input that determines the gain of the variable gain means 29 is the input signal α here, and the magnitude of the alternating current can be specified by this, and a simple analog circuit configuration by such a combination of operational amplification means. Then, make the alternating current follow the alternating voltage at high speed,
An input power factor of 100% was achieved. The input AC voltage and the input AC current waveforms are shown in FIG. 12 as the experimental results by the rectifier of the second embodiment of the present invention. As shown in the figure, a power factor of almost 100% is achieved.

An embodiment having the third structure will be described with reference to FIG. In accordance with the output of the DC output voltage detecting means 15 or the DC output voltage estimated value detecting means 19, the signal generating means 22
The amplitude modulation means 33 for performing amplitude modulation on the reference signal is arranged. The operation will be described below.

A load fluctuation as shown in FIG.
DC output voltage v with ripple component ₀DC output voltage detection
When detected by the output means 15, output from the signal generation means 22
The reference signal generated by the amplitude modulation means 33 is shown in FIG.
The waveform is amplitude-modulated as shown. Carry this signal waveform
Used as a wave, the output of the calculation means 23 is an analog comparator
By performing analog comparison and generating a pulse signal
The simple structure that does not require the conventional analog divider
Rectifier with high power factor that does not depend on load fluctuation
The operation could be realized. Of the third embodiment of the present invention.
As a result of the experiment with the rectifier, the DC output voltage and the amplitude change
The adjusted reference signal waveform is shown in FIG.

An embodiment of the fourth structure will be described with reference to FIG. Setting means 34 for setting an appropriate value within the range of the output level or phase detected by the input AC voltage detecting means 13 or the input AC voltage estimated value detecting means 17.
According to the comparison result in the comparison means 35, the input AC voltage detection means 13 or the input AC voltage estimated value detection means 17, the comparison means 35 for comparing the output level or the phase of the setting means 34, Signal generating means 2
The frequency modulation means 36 for performing frequency modulation on the second reference signal is arranged. The operation will be described below.

When the comparing means 35 determines that the output value detected by the input AC voltage detecting means 13 exceeds the preset value set by the setting means 34, the frequency modulating means 36 causes the signal generating means 22 to operate. Of the reference signal is frequency-modulated so that it becomes the oscillation frequency 1, and conversely, when it falls below the set value, it is modulated to the oscillation frequency 2. The current waveform at this time is in a state in which a plurality of frequency components are included in one cycle of the power supply as shown in FIG. Further, the sound pressure level at this time is as shown in FIG. 11 (b), and the sound pressure level at the time when this control is not performed is lower than that of FIG. As a result, the jarring noise was significantly reduced. In the present embodiment, the frequency switching is performed only at one point of the output voltage level, but it goes without saying that the same effect can be expected by a method of providing a plurality of switching points or a method of detecting a phase and performing switching. There is no Further, in the present embodiment, since the main point is to simplify the configuration and increase the speed, the analog circuit is used, but the voltage level or the phase is detected by a digital method using a microcomputer to save the memory. Of course, the same operation can be performed by switching.

FIG. 14 shows an input AC current waveform at the time of control with a plurality of frequency reference signals as an experimental result by the rectifier of the second embodiment of the present invention. As shown in the figure, a power factor of almost 100% is achieved.

Of course, the present invention is not limited to the above-mentioned embodiments, but can be applied to various types of single-phase and multi-phase rectifiers, for example, pure bridges, mixed bridges and the like.

[0060]

As is apparent from the above description of the embodiments, each invention has the following effects.

The arithmetic means has a simple structure of only four arithmetic operations of addition, subtraction, multiplication and division, and the speed can be increased by the analog circuit. In addition, the input power factor is approximately 100 by a simple configuration with an analog circuit that is a combination of operational amplifiers and by allowing the alternating current to follow the alternating voltage at high speed.
% Was realized. Furthermore, the conventional analog divider is not required, and operation that does not depend on load fluctuations has been simplified and achieved at high speed. It also reduces the sound pressure level of a single frequency,
Since the components are dispersed, the annoying electromagnetic noise generated from the reactor can be significantly reduced.

[Brief description of drawings]

FIG. 1 is a block diagram of a rectifier according to a first embodiment of the present invention.

FIG. 2 is a circuit diagram of the rectifier of the first embodiment.

FIG. 3 is a circuit diagram of a switch device of the rectifier of the first embodiment.

FIG. 4 is a timing chart for explaining the first embodiment.

FIG. 5 is an operation diagram at time t _k for explaining the first embodiment.

FIG. 6 is a block diagram of a rectifier according to the second embodiment.

FIG. 7 is a block diagram of a rectifier according to the third embodiment.

FIG. 8 is an amplitude-modulated reference signal waveform diagram for explaining the third embodiment.

FIG. 9 is a block diagram of a rectifier according to the fourth embodiment.

FIG. 10 is an input AC current waveform diagram at the time of control with a plurality of frequency reference signals for explaining the fourth embodiment.

FIG. 11 is a sound pressure level waveform characteristic diagram based on the fourth embodiment.

FIG. 12 is a waveform diagram of an input AC voltage and an input AC current by the rectifier of the second embodiment.

FIG. 13 is a waveform diagram of a DC output voltage and an amplitude-modulated reference signal in the third embodiment.

FIG. 14 is an AC current waveform diagram when a plurality of frequency reference signals are used in the fourth embodiment.

15A is a principle diagram illustrating a conventional boost chopper system. FIG. 15B is a principle diagram illustrating a conventional boost chopper system. FIG. 15C is a principle diagram illustrating a conventional boost chopper system. Principle diagram explaining the method

FIG. 16 is a block diagram of a conventional constant frequency control method.

[Explanation of symbols]

1 switch device 2 rectifier circuit 3 Input side 4 reactor 5 DC side 6 capacitance 13 Input AC voltage detection means 14 Input AC current detection means 15 DC output voltage detection means 16 Instantaneous value detection means 17 Input AC voltage estimated value detection means 18 Input AC Current Estimated Value Detection Means 19 DC output voltage estimated value detection means 20 Estimated value detection means 21 Detection means 22 Signal generation means 23 Computing means 24 Setting means 25 Measuring means 26 Judgment means 27 Gate control means 28 First operational amplification means 29 Variable gain means 30 Second operational amplification means 31 Addition / subtraction means 32 pulse signal generating means 33 Amplitude modulation means 34 Setting means 35 Comparison means 36 Frequency Modulation Means

Front page continuation (72) Inventor Toshiya Onuki 2-5-15, Uemachi, Chichibu-shi, Saitama (72) Inventor Etsunao Otsuji 3-4-5, Sumiyoshi-cho, Shibata, Niigata (72) Inventor Norihito Mochida Osaka Matsushita Seiko Co., Ltd. 6-2 61, Imafuku Nishi, Joto-ku, Osaka City, Japan (72) Inventor Yasuyuki Chihara 6-2 61 Imafuku Nishi, Joto-ku, Osaka City, Osaka Prefecture (56) Reference (56) References Special Kaihei 4-236168 (JP, A) JP-A-3-3665 (JP, A) Actual Kaihei 4-25480 (JP, U) Actual Kaihei 5-91197 (JP, U) (58) Fields investigated ( Int.Cl. ⁷ , DB name) H02M 7/217 H02M 1/15

Claims (4)

(57) [Claims] 1. A rectifier comprising a connection in which a reactor is provided on the input side and a capacitance is provided on the direct current side of a rectifying circuit composed of a switch device, and input AC voltage detecting means for detecting an instantaneous value of the input AC voltage. An input AC voltage detecting unit configured to detect at least one of an input AC current detecting unit detecting an instantaneous value of an AC current and a DC output voltage detecting unit detecting an instantaneous value of a DC output voltage; An input AC voltage estimated value detecting means for detecting an estimated value of the input AC current estimated value detecting means for detecting an estimated value of the input AC current; and a DC output voltage estimated value detecting means for detecting an estimated value of the DC output voltage. Among the estimated value detecting means including at least one of the above, a detecting means including at least one or more, and a signal generating means for generating a reference signal of an appropriate frequency Stage and the output of the detection means as input, and the conduction period of the device is controlled by a quad operational amplifier.
And an arithmetic unit for performing an analog arithmetic operation using an arithmetic unit for analog addition, subtraction, multiplication and division, a setting unit for setting a certain fixed time, and an elapsed time from an appropriate timing point of the reference signal output from the signal generating unit. Measuring means, judging means for judging that the elapsed time measured by the measuring means has reached the certain time set by the setting means, and the judging means based on the conduction period calculated by the calculating means. A rectifier having a gate control means for controlling conduction of the device after a fixed time determined by. 2. The calculation means uses the input AC voltage detection means output or the input AC voltage estimated value detection means output as the input to the first operational amplification means and the variable gain means, and the input AC current detection means output or the input AC current estimation. The output of the value detection means is input to the second operational amplification means, and at least one output of the first operational amplification means, the variable gain means and the output of the second operational amplification means is used as an input to perform analog operation It is composed of a unit, the gate controller output signal of the output signal of the subtraction means of the signal generating means as an input a pulse signal generating means for outputting a gate pulse signal, an analog
The rectifier according to claim 1, which has a simple structure and does not particularly require a divider. 3. The rectifier according to claim 1, further comprising an amplitude modulation means for performing amplitude modulation on the reference signal of the signal generation means in accordance with the output of the DC output voltage detection means or the DC output voltage estimated value detection means. 4. Setting means for setting an appropriate value within the range of the output level or phase detected by the input AC voltage detecting means or the input AC voltage estimated value detecting means, and the input AC voltage detecting means or the input AC. Arranged are voltage estimated value detection means, comparison means for comparing the output level or phase of the setting means, and frequency modulation means for performing frequency modulation on the reference signal of the signal generation means according to the comparison result in the comparison means. The rectifier according to claim 1, wherein