JP3046794B2 - Detector using transmitter - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a detecting device such as a gas meter load measuring device which uses a transmitter provided in connection with a gas meter and transmits a measured value of the amount of gas used such as city gas by an electric signal.

[0002]

2. Description of the Related Art Conventionally used gas meters are:
For example, there are a membrane gas meter, a roots gas meter, a turbine gas meter, and the like. A plurality of these various gas meters are scattered and installed in a wide area such as a factory and an apartment house. The gas meter load measuring device measures the gas usage measured by each of these gas meters, and calculates, for example, the total integrated value of the gas meters. Such a gas meter load measuring device is, for example, Japanese Utility Model Laid-Open Publication No. 7-20526.

[0003]

Conventionally, there are two types of configurations of a transmitter whose switching state is changed by the magnetism of a rotating magnet piece, one of which is formed by a single reed switch and whose two contacts are conductive. The other has two reed switches, one end of each reed switch is connected in common, and these reed switches are alternately turned on / off by the rotating magnetic field of the rotating magnet piece. It has a configuration that repeatedly shuts off. It is desired that the outputs obtained from these two types of transmitters be counted with a common configuration to calculate the gas usage and the like.

An object of the present invention is to provide a detection device which is used in common for a plurality of types of transmitters having different configurations and uses a transmitter which counts and calculates the output from each of the transmitters. .

[0005]

According to the present invention, there is provided a first oscillator RSW1 in which two contacts repeat conduction and interruption, and a first oscillator which responds to the output of the first oscillator and which is predetermined from conduction or interruption of the contact. A first monostable circuit F1 that derives an output that lasts for the time limit W03, and an output of the first monostable circuit is 1 /
A frequency divider circuit F4 that divides the frequency by 2 and two output lines in response to respective outputs of the first monostable circuit and the frequency divider circuit;
First logic means G1 and G12 for outputting to each output line first and second detection pulses which alternately change the logic value each time the transmitter is turned on or off; one first contact and two second contacts; A second transmitter RSW2 that alternately and repeatedly conducts and cuts off each of the second contacts;
In response to the output between the first contact of the transmitter and one of the second contacts, the first contact of the second transmitter during normal operation is less than a first time W1 during which the first contact is conducted to the one second contact. And a second monostable circuit F5 for deriving an output that lasts for a predetermined second time limit W01 exceeding a second time W2 when noise from the second transmitter occurs, and a first contact of the second transmitter. In response to the output between the second contact and the one second contact and the output of the second monostable circuit F5, and the conduction or cutoff state between the first contact of the second transmitter and the one second contact. Is longer than the second time limit W01, the second logic means for deriving the third detection pulse, and the second signal is output in response to the output between the first contact and the other second contact of the second transmitter. Time W in which the first contact is conducted to the other second contact when the vessel is normal
3 and a predetermined third time limit W0 exceeding a fourth time W4 during which noise from the second transmitter occurs.
Third monostable circuit F15 that derives an output that lasts 2
Responsive to the output between the first contact of the second transmitter and the other second contact and the output of the third monostable circuit F15, the first contact of the second transmitter and the other A third logic means for deriving a fourth detection pulse and a first logic gate G3 for deriving the first and third detection pulses when the conduction or cutoff state between the two contacts exceeds the third time limit W02; ,
Second logic gate G for deriving second and fourth detection pulses
13 and two inputs, each having a first and a second
A bistable circuit G2 which receives outputs from logic gates G3 and G13 and switches between two stable states for output.
7, G37, and G37.

According to the present invention, the output from the first oscillator RSW1 in which two contacts repeatedly conduct and cut off is provided to the first monostable circuit F1, and the output of the first monostable circuit is divided by the frequency dividing circuit. The frequency is divided by 1/2 by F4. This allows the first logic means G2, G12 to connect to each of the two output lines each time the two contacts of the first transmitter are turned on / off.
The logic values of logic "1" and logic "0" are alternately changed and derived to obtain first and second detection pulses. Further, when the first contact is electrically connected to one second contact by an output from the second transmitter RSW2 having one contact and two second contacts, for example, having the above-mentioned two reed switches, One contact is disconnected from the other second contact, and the first contact is electrically connected to the other second contact when the first contact is disconnected from the one second contact. This transmitter may be configured so that a state in which the first contact is interrupted by any of the two second contacts is generated. The first of the transmitter
The output between the contact and one of the second contacts is supplied to the second monostable circuit F5, and the second logic means prevents the noise corresponding to the first and one of the second contacts from being mixed. Similarly, the output between the first contact of the transmitter and the other second contact is provided to a third monostable circuit, and the third logic means corresponds to the first contact and the other second contact. Noise contamination is avoided.

The third and fourth detection pulses from the second and third logic means are supplied to first and second logic gates G3 and G3, respectively.
The signal is supplied to two inputs of a bistable circuit, for example, an RS flip-flop via 13. Thus, the two stable states of the bistable circuit correspond to the first contact of the second
Switching is performed alternately according to the state of conduction to the contact. In this way, for example, by counting the output of the bistable circuit, it is possible to integrate the gas usage.

For example, W01 = W02 = W03 = 150
msec. W1 = W3 and W2 = W4 may be satisfied.

According to the present invention, the outputs of the first and second oscillators RSW1 and RSW2 are applied to the first and second logic gates G3 and G13. The two stable states of the bistable circuits G27 and G37 are switched by the respective outputs of the first and second logic gates G3 and G13. Outputs of the bistable circuits G27 and G37 can be counted by, for example, a counter to measure gas usage and the like.

Further, according to the present invention, when the first oscillator RSW1 is not detected, it remains in a predetermined conducting or blocking state, whereby the output of the first monostable circuit F1 has a predetermined logical value, Therefore, the first logic means keeps deriving a predetermined logic value on the first and second output lines, whereby the first and second logic gates derive outputs corresponding to the third and fourth detection pulses. It is characterized by doing.

According to the present invention, the first transmitter RSW1 comprises:
At the time of non-detection, that is, for example, when the first oscillator is realized by a reed switch, in the absence of the magnetism of the rotating magnet piece, the two contacts of the first oscillator RSW1 remain conductive. , Or remains in the interrupted state. Therefore, a logical value corresponding to the conductive or cut-off state when the first oscillator RSW1 is not detected, for example, a value having an H level as in an embodiment described later, is output from the first logical means G2 and G12 to each of the two outputs. It remains derived on the line. Therefore, the first and second
From the logic gates G3 and G13, third and fourth detection pulses corresponding to conduction / interruption of the first and second contacts of the second oscillator RSW2 are respectively derived, and the bistable circuit G2
7, G37. Therefore, even when the first transmitter RSW1 is not detected, the second transmitter RSW1 is not detected.
2 can be used to operate the detection device of the present invention.

Further, the present invention is characterized in that the second oscillator RSW2 can be connected to and disconnected from each input of the second and third monostable circuits F5 and F15.

According to the present invention, the second oscillator RSW2 is
Removed from the second and third monostable circuits F5 and F15,
By using only the first monostable circuit F1, for example, the gas usage can be detected as described above.

Further, according to the present invention, the frequency dividing circuit is realized by a D-type flip-flop F4, which has a clock input terminal CK to which an output of the first monostable circuit F1 is applied. Clock input terminal CK
When the output of the first monostable circuit F1 is applied to the input terminal, the logic value applied to the data input terminal D is derived to one output terminal Q, and the output of the one output terminal Q is inverted. A logic value is derived to the other output terminal Q /, and the output of the other output terminal Q / is provided to a data input terminal D. The first logic means includes two logic gates G2 and G12. The output of the first monostable circuit F1 is commonly applied to one input of each of the logic gates G2 and G12, and the other input of the D-type flip-flop F4 is applied to the other input of each of the logic gates G2 and G12. Each output terminal Q, Q / is provided respectively.

According to the present invention, the frequency divider associated with the first oscillator RSW1 is realized by a D-type flip-flop F4, and the first logic means is constituted by two logic gates G2 and G2.
12, for example, realized by a NAND gate, so that the first and second detection pulses can be generated with a relatively simple configuration.

[0016]

FIG. 1 is a block diagram showing the overall configuration of an embodiment of the present invention. Gas meter load measuring device 1 that measures and calculates gas usage such as city gas
, A transmitter RSW consisting of a single reed switch
1 and another transmitter RSW2 consisting of two reed switches 2,3. These transmitters RSW
1 and RSW2 change their switching modes for each predetermined gas usage detected by gas meters 76 and 83 described later. The transmitter RSW1 is built in the gas meter load measuring device 1 of the present invention. The transmitter RSW2 is
It is detachably connected to the connection terminals A1, B1, and C1 of the input connector 4. The output of the transmitter RSW2 is connected to lines 5 and 6
Are supplied to the detection pulse generation circuits 7 and 8 via. The detection pulse from one detection pulse generation circuit 7 passes through a line 9 and the detection pulse from another detection pulse generation circuit 8 passes through a line 10, and AND gates G3 and G13, which are first and second logic gates. , Respectively.

The detection pulse generation circuit 11 of the transmitter RSW1
Derives detection pulses to two output lines 12 and 13, respectively. The detection pulses from the output lines 12 and 13 are applied to the other inputs of the AND gates G3 and G13, respectively. The transmitter RSW1 has a configuration in which two contacts 24 and 25 repeat conduction and interruption as shown in FIG. 13 described later. Each of the contacts 24 and 25 of the transmitter RSW1 has a characteristic that it conducts in a magnetic field when any one of the N and S poles of the rotating magnet piece approaches, and shuts off when these magnetic poles move away.

The bistable circuit F2 is an RS flip-flop and includes two NAND gates G27 and G37. The outputs of the AND gates G3 and G13 are connected to the two NAND gates G27 and G3 forming the bistable circuit F2.
7 is provided to one input. NAND gate G27,
Each output of G37 is applied via lines 14 and 15 to the other inputs of their NAND gates G27 and G37, respectively. Thus, the AND gates G3 and G13 are
The detection pulse from the transmitter RSW1 via the lines 12, 13 is derived, and the detection pulse from the other transmitter RSW2 is derived from the lines 9, 10. Thus, the configuration including the bistable circuit F2 for calculating each detection pulse corresponding to the two types of transmitters RSW1 and RSW2 and the subsequent processing circuits 21 such as a microcomputer can be shared. . Thereby, the configuration can be simplified. Outputs from the lines 14 and 15 of the bistable circuit F2 are supplied to detection pulse generation circuits 7 and 8 via lines 16 and 17.

The gas meter load measuring device 1 is further provided with an input connector 18 for connecting terminals A2, B2, C2.
A transmitter RSW3 having a configuration similar to that of the transmitter RSW2 described above can be detachably connected. The input connector 18 is connected to detection pulse generation circuits 19 and 20, and further includes NAND gates G12 and G13 forming a bistable circuit F3. These detection pulse generation circuits 19 and 20 are composed of the detection pulse generation circuits 7 and 8 described above.
And the bistable circuit F3 has the same configuration as the above-described bistable circuit F2.

The stable output of one of the NAND gates G27 and G12 of the bistable circuits F2 and F3 is supplied to the processing circuit 21 via the lines 22 and 23. The integrated value can be calculated and obtained, and other calculations can be performed, and the calculation result is displayed on the liquid crystal display panel.

FIG. 2 is a diagram showing the configuration of the transmitter RSW2. The first contacts 27 and 28 commonly connected to the line 26 of the two reed switches 2 and 3 are two second contacts 2
Conduction and interruption to 9,30. When the rotating magnet piece 31 composed of a permanent magnet rotates with its angular displacement around the rotation axis 32 for each predetermined amount of gas used and rotates, one reed switch 2 uses the magnetic field generated by the proximity of its N pole to generate a magnetic field. The first and second contacts 27 and 29 conduct. In another reed switch 3, the first magnetic field is obtained by the magnetic field obtained when the S pole of the rotating magnet piece 31 approaches.
And the second contacts 28 and 30 conduct. The reed switches 2 and 3 are arranged very close. The switching mode of the transmitter RSW2 changes by alternately approaching the N pole or the S pole of the rotating magnet piece 31.

FIG. 3 is a diagram showing a conductive state and a disconnected state obtained from the transmitter RSW2 to the connection terminals A1 to C1 of the connector 4. When the N pole and the S pole of the rotating magnet piece 31 alternately approach the transmitter RSW2 due to the rotation of the rotating magnet piece 31, the first and second contacts 27 and 29 of one reed switch 2 conduct, and At this time, the first and second contacts 28 and 30 of the other reed switch 3 are closed. Thereafter, the two reed switches 2 and 3 are both turned off. Next, the first and second contacts 28 and 30 of the reed switch 3 conduct, and at this time, the first and second contacts 27 and 29 of the reed switch 2 remain disconnected. Such an operation is repeated by the rotation of the rotating magnet piece 31.

Referring again to FIG. 1, in input connector 4, connection terminal C1 is connected to one connection terminal of DC power supply 33 realized by, for example, a battery or the like via resistor R19, and is set to the ground potential. You. Connection terminals A1, B
1 has resistors R11 and R20 interposed between lines 5 and 6. The voltage at the other output terminal of DC power supply 33 is indicated by a reference sign + Vcc, and may be, for example, 3.0 V. In addition, varistors Z7, Z9, Z8 are connected in connection with these connection terminals A1, B1, C1, and on lines 5, 6 a zener diode ZD having a breakdown voltage exceeding the power supply voltage + Vcc, for example 5.6V.
5 and ZD6 are respectively connected. Thus, large-amplitude noise is prevented from being applied to the detection pulse generation circuits 7 and 8. Voltage + Vcc is, for example, 3V.

FIG. 4 is an electric circuit diagram showing a specific configuration of the detection pulse generation circuit 7. The differential capacitor C4 is connected to the connection point 35 of the line 5, and the line 36 is connected to the terminal of the DC power supply 33 via the resistor R13 to receive the voltage + Vcc. The connection point 35 is connected to the line 17 via the resistor R12. When the line 17 is at the H level which is a logic “1”, for example, 3V
At this time, the connection point 35 is connected to the first and second contacts 27 and 29 of the reed switch 2 by the resistor R12.
Are clamped high to the H level in a state where is shut off. The output of line 36 is the input terminal C of monostable circuit F5.
K, and in response to the negative pulse, the time limit W
The timing operation of 01 is started.

The detection pulse generating circuit 7 basically further comprises:
Pulse leading edge forming means 38 for forming the leading edge of the detection pulse led out to the line 9, pulse trailing edge forming means 39 for forming the trailing edge of the detection pulse, and the first and second contact points 27 of the transmitter RSW2. , 29 are provided. Power supply means 4
The power supply means 41 includes a reed switch 2
When the first and second contacts 27 and 29 are turned on, a current flows to maintain the contact state of these contacts 27 and 29 well.

The time limit W01 of the monostable circuit F5 is set by the capacitor C5 and the resistor R14 (W01 =
C5 · R14), for example, 0.1 msec. This time limit time W01 is the first time at the maximum flow rate at which the gas consumption can be measured while the transmitter RSW2 is in a normal state.
And a value that is shorter than the conducting time W1 of the second contacts 27 and 29 and exceeds the duration W2 of noise generated by the noise mixed from the transmitter RSW2 through the line 5 (W2 <W01 < W1).

FIG. 5 is a diagram showing the configuration of the input terminal CK of the monostable circuit F5. Line 36 is connected to the base of transistor 42, which is an input terminal, and has a high input impedance. The monostable circuit F5 receives a negative-going falling waveform, so that one output terminal Q derives an H-level signal that lasts for a time limit W01 from the time of the input, and the other output Q / (Hereinafter, “Q /” indicates an inverted output of Q) has an inverted waveform of the output Q.
The output Q and Q / signals of the monostable circuit F5 are
44 respectively.

The switching detecting means 40 functions to detect the conduction / interruption of the first and second contacts 27 and 29 of the reed switch 2. This switching detection means 40
Is a resistor R16 having one terminal connected to the connection point 35.
A PNP transistor TR6, which is a switching element for level discrimination, in which the other terminal of the resistor R16 is connected to the base, and is connected between the collector of the transistor TR6 and the ground potential of the one output terminal of the DC power supply 33. And the output of which is derived from line 45.

First and second contacts 2 of reed switch 2
When the nodes 7 and 29 are turned on, the connection point 35 becomes L level, and the transistor TR6 is turned on. This brings line 45 to the voltage at the emitter of transistor TR6. A voltage is applied from the power supply 41 to the emitter of the transistor TR6.

The power supply means 41 includes a resistor R15 having one terminal connected to the connection point 35, and a switching element PN having the other terminal of the resistor R15 connected to the collector.
P transistor TR5. This transistor TR
The emitter of No. 5 is connected to the other output terminal of the DC power supply 33, and is supplied with the voltage + Vcc. The collector of the transistor TR5 is also connected at the connection point 46 to the emitter of the transistor TR6 of the switching detection means 40. A resistor R17 is connected to the base of the transistor TR5, and a control signal is applied to the resistor R17 via a line 47.

The first logic circuit 61 includes a pulse leading edge forming means 38, a pulse trailing edge forming means 39, and a switching detecting means 40. By the switching detection means 40,
In order to be able to detect the switching state of the first and second contacts 27, 29 of the reed switch 2, a resistor R1119 between the connection point 35 when the reed switch 2 is conducting and the ground potential is provided. (= R11 +
R19), and the resistance value of each resistor is indicated by the same reference numeral, Equation 1 holds.

R1119 <R15 <R12 (1) For example, R1119 = 150Ω, R15 = 2.2 kΩ,
R12 may be 100 kΩ. Further, a resistor R13
= 50 kΩ and R16 = 50 kΩ. In this way, the resistance value of the resistor R12, the resistance value of the resistor R13, and the sum R1119 of the resistors R11 and R19 are selected as in the above equation 1 so as to decrease in this order.

As shown in FIG. 6, the discrimination level V0 of the connection point 35 by the transistor TR6 of the switching detection means 40 is the same as that shown in FIG. The voltage V when the first and second contacts 27 and 29 are conducting.
2, which is not less than V3 and less than the voltage V1 when the reed switch 2 is turned off. Voltage V2 is the voltage at node 35 when reed switch 2 is conducting and transistor TR5 is conducting. The voltage V3 is equal to the connection point 35 when the reed switch 2 is conducting and the transistor TR5 is off.
Voltage. When the reed switch 2 is off, the voltage V1 at the connection point 35 is equal to the voltage + Vc regardless of whether the transistor TR5 is on or off.
This is a value approximately similar to the H-level voltage c.

V1>V0>V2> V3 (2) Therefore, as described above, the transistor TR6 is on when the reed switch 2 is on, and off when the reed switch 2 is off.

The leading edge of the detection pulse derived from the line 9 of the first logic circuit 7 is generated from the NAND gate G7 constituting the pulse leading edge forming means 38. The output Q / of the monostable circuit F5 is connected to the NAND gate G7 via line 48.
And switching detection means 4
The output of 0 is input via line 45. Thus N
The AND gate G7 performs a logical operation on the output of the monostable circuit F5 and the output of the switching detection means 40 to start measuring the time limit W01 of the monostable circuit F5, that is, the first and second contacts of the reed switch 2. 27 and 29 become conductive, a pulse of negative polarity is input to the input terminal CK of the monostable circuit F5 via the line 36, and when the conduction of the reed switch 2 is detected by the switching detecting means 40, the following diagram will be used. As shown in FIG. 10 (11), the logic level is set to the H level corresponding to the logical value "1", and is maintained at the H level in the embodiment shown in FIG.

The pulse trailing edge forming means 39 for forming the trailing edge of the detection pulse led to the line 9 includes D-type flip-flops F6 and F8 and an AND gate G8. The D-type flip-flop F6 has a clock input terminal CK to which the output Q of the monostable circuit F5 is provided via a line 43. When the rising waveform output of the line 43 is given to the clock input terminal CK of the D-type flip-flop F6,
The logic value provided to the data input terminal D is output to one output terminal Q, and the inverted logic value of the output of the output terminal Q is derived to the other output terminal Q /. D
The preset input terminal PR of the flip-flop F6
When a waveform falling from the H level to the L level is applied, the output Q is set to the H level. When a falling waveform that changes from H level to L level is input to the clear terminal CLR, the output terminal Q is set to L level.

The preset input terminal PR of the D-type flip-flop F6 is kept at the voltage + Vcc. The clear input terminal CLR of the D-type flip-flop F6 is supplied with the output of the AND gate G8 via a line 50. Data input terminal D is connected to line 17. Output terminal Q
Is connected via a line 51 to a preset input terminal PR of another D-type flip-flop F8. Another output terminal Q / of the D-type flip-flop F6 is connected via a line 47 to the resistor R17 of the power supply means 41, and provides its output to the base of the transistor TR5.

The D-type flip-flop F8 has a configuration similar to that of the above-described D-type flip-flop F6, and a voltage + Vcc is applied to its clear input terminal CLR. The output Q / of the monostable circuit F5 is applied to the clock input terminal CK of the D-type flip-flop F8 via a line 48. The output of the switching detecting means 40 is supplied to the data input terminal D via a line 45.

The two inputs of the AND gate G8 are provided with the detection pulse on line 9 and the output Q of the D-type flip-flop F8 via line 52. In this way, the pulse trailing edge forming means 39 performs a logical operation on the output of the monostable circuit F5 and the output of the switching detection means 40 via the line 45, and the time limit W0 of the monostable circuit F5 has elapsed, When the first and second contacts 27 and 29 are conducting, the detection pulse on line 9
As shown in (11), the other logical value is set, for example, H
Change from level to L level. The detection pulse of the line 9 is input from the AND gate G3 to the bistable circuit F2 via the line 53. Similarly, the detection pulse derived from the other detection pulse generation circuit 8 to the line 10 is:
The signal is input from the line 54 to the bistable circuit F2 via the AND gate G13.

FIG. 7 shows the NAN constituting the bistable circuit F2.
FIG. 13 is an electric circuit diagram showing a configuration of a part of an output stage connected to a line 14 of a D gate G27. In this output stage, an NPN transistor 55 and a PNP transistor 56 having different conduction types are connected to two output terminals of the DC power supply 33,
That is, it is connected between the ground potential and the voltage + Vcc.
The bases of these transistors 55 and 56 are commonly connected to a control signal line 57. Thus, the transistors 55 and 56 as switching elements are selectively turned on / off in accordance with the H level or the L level of the line 57. Therefore, the voltage + Vcc of the DC power supply 33 at the H level corresponding to the logic "1" or the ground potential at the L level corresponding to the logic "0" is derived to the line 14. Another NAND gate G37 is also configured similarly to NAND gate G27,
5, the output of the NAND gate G37 is derived.

FIG. 8 shows another detection pulse generating circuit 8.
FIG. 3 is an electric circuit diagram showing a specific configuration of FIG. The detection pulse generation circuit 8 has the same configuration as the detection pulse generation circuit 7 described above. In correspondence with the reed switch 3 of the transmitter RSW2, a line 16 is connected to the line 6 via the resistor R20.
Are connected to a connection point 58 via a resistor R21. The differential capacitor C7 is connected to the connection point 58. The capacitor C7 and the clamp resistor R22 are connected to the input terminal of the monostable circuit F15. A capacitor C8 and a resistor R22 are connected to the monostable circuit F15, and a time limit W02 (= C8 · R22) is set. The second logic circuit 62 includes a pulse leading edge forming means 63 including a NAND gate G17 and a pulse trailing edge forming means 64 including D-type flip-flops F16 and F18 and an AND gate G18.
And the first and second contacts 28, 30 of the reed switch 3.
Switching detecting means 65 for detecting conduction / interruption of the first and second contacts 2 of the reed switch 3.
A power supply means 66 is provided for supplying a current during conduction of 8, 30 to maintain a good contact state and extend the life.

The switching detecting means 65 includes a resistor R2
5, R27 and the transistor TR8. Power supply means 66 includes resistors R24 and R26 and transistor TR7.
including. The detection pulse generation circuit 8 has a configuration similar to that of the detection pulse generation circuit 7 described above, and derives a detection pulse from the line 10 according to the switching state of the reed switch 3.

Referring again to FIG. 1, outputs from NAND gates G27 and G37 forming bistable circuit F2 are as follows.
To derive a waveform-shaped detection pulse from the output connector 67 via the lines 14 and 15, the field effect transistors TR1 and TR2, which are switching elements, are connected to the ground potential of one output stage of the DC power supply 33. . The gates of the transistors TR1 and TR2 are connected to the lines 14 and 15
Connected to. Connection terminals A3, B3 of output connector 67
Are connected to the transistors TR1 and T1 via the resistors R5 and R7.
Connected to R2. The connection terminal C3 is connected to the ground potential via the resistor R6. These connection terminals A3, B3,
C3 corresponds to the connection terminals A1, B1, and C1 of the input connector 4, respectively. Connection terminal A3 of output connector 67
From B3 and C3, a detection pulse whose waveform is shaped in accordance with the switching state of the transmitter RSW2 is derived through a connection line and is given to, for example, a microcomputer or the like, and a gas meter load such as a gas usage amount is remotely located. It can be measured by performing calculations.

The detection pulse generation circuits 19 and 20 related to the transmitter RSW3 are configured in the same manner as the detection pulse generation circuits 7 and 8 described above. Bistable circuit F2
The configuration is the same as

FIG. 9 is a diagram showing the waveform of a detection pulse corresponding to the switching state of the oscillator RSW2. FIG.
(1) shows the conduction / interruption state of the first and second contacts 27 and 29 in the reed switch 2 of the transmitter RSW2, and FIG. This indicates the conducting / cutting state, and the conducting / cutting state of such reed switches 2 and 3 is obtained at a cycle corresponding to the gas usage of the gas meter. Lines 9, 10,
Accordingly, the detection pulses shown in FIGS. 9 (3) and 9 (4) are derived from the lines 14 and 15, respectively. Each of these detection pulses is derived with a time delay W01, W02 set in the monostable circuits F5, F15 from the time when the reed switches 2 and 3 are turned on. Malfunction due to noise is prevented. W01 = W02 may be satisfied.

FIG. 10 is a waveform chart for explaining the operation of detection pulse generating circuit 7. FIG. 10A shows the conduction / interruption state of the first and second contacts 27 and 29 of the reed switch 2, and FIG. 10B shows the conduction / interruption of the first and second contacts 28 and 30 of the reed switch 3. FIG. 9 shows a cut-off state, which corresponds to each of the waveforms shown in FIG. 9 (1) and FIG. 9 (2). By turning on the power, the voltage of the line 17, and thus the voltage of the connection point 35, is at the H level before the time t1, as shown in FIG. 10 (3), and the input line 36 of the monostable circuit F5 becomes H level as shown. By this power-on, the output Q of the flip-flop F5 derives an L-level output on the line 43. At this time, the output Q / of the monostable circuit F5 is as shown in FIG.
It is at the H level as indicated by 0 (6). The output Q of D-type flip-flop F6 is connected to line 51 as shown in FIG.
As shown in (7), an L-level signal is derived, and the output Q / of the output Q / leads to an H-level signal as shown in FIG. Therefore, the power supply means 41
Transistor TR5 remains off. As described above, the connection point 35 is at the H level, so that the transistor TR6 of the switching detection means 40 is also shut off. Therefore, the line 45 remains at the L level as shown in FIG.

Since the output Q of D-type flip-flop F6 is at the L level as shown in FIG. 10 (7) when the power is turned on, another D-type flip-flop F8
Is preset, and the output Q of the D-type flip-flop F8 derives an H level signal shown in FIG.

The output Q / of the monostable circuit F5 is the same as that of FIG.
When the power is turned on as shown in FIG.
1 and the line 45 is at the L level as described above, the output of the NAND gate G7 constituting the pulse leading edge forming means 38 is output to the line 9 as shown in FIG.
It is at the H level as shown by 0 (12). Thus, the AND gate G8 is connected to the line 50 as shown in FIG.
An H level signal is derived as shown in 1). FIG.
0 (13) indicates an output led to the line 14 of the bistable circuit F2, which is at the L level, and FIG. 10 (14)
The output derived from line 15 is shown at H level.
This line 14 is the reed switch 2 of the transmitter RSW2.
Is turned off, or when the reed switch 3 is conducting, it is at the L level as described above. When the reed switch 2 is conducting, the line 15 becomes L level,
At this time, the line 14 goes to the H level, and FIG.
The logic state is opposite to that of FIG.

When the reed switch 2 is turned on at time t1, the connection point 35 goes low as shown in FIG. 10 (3), whereby the capacitor C4 is shown on the line 36 and shown in FIG. 10 (4). By giving a negative differential pulse, the monostable circuit F5 starts the time counting operation of the time limit W01. As a result, the output Q of the monostable circuit F5 becomes
An H-level signal shown in FIG. 10 (5) is derived on line 43, and therefore the output Q of the D-type flip-flop F6 is output.
Derives the H-level signal shown in FIG. 10 (7) on line 51, and the output Q /
The signal at the L level shown in (8) is derived, and the transistor TR5 of the power supply means 41 is made conductive. As described above, when the connection point 35 becomes L level due to the conduction of the reed switch 2, the transistor T of the switching detection means 40
R6 is conducting. Therefore, voltage + Vcc of DC power supply 33 is applied to line 45 via transistor TR5, connection point 46 and transistor TR6, and line 45 attains H level as shown in FIG. 10 (9). At this time, the output Q / of the monostable circuit F5 is
In addition, since the signal of L level is derived as shown in FIG. 10 (6), the detection pulse derived from NAND gate G7 to line 9 becomes H as shown in FIG. 10 (12).
Remains at the level.

The monostable circuit F5 is connected to its input terminal as shown in FIG.
At the time t2 when the time limit time W01 has elapsed from the time when the output Q was set to the H level as shown in FIG. Then, the output Q of the monostable circuit F5 returns to the L level, and the output Q / derives the signal of FIG. At this time, line 45
Is at the H level as shown in FIG. 10 (9), and the output Q of the D-type flip-flop F8 is
The line 52 changes from the H level to the L level as shown in FIG. 10 (12), so that the output of the AND gate G8 changes the line 50 to the L level as shown in FIG. 10 (11). I do. Therefore, the output Q of the D-type flip-flop F6 derives an L-level signal on the line 51 as shown in FIG. When the L-level signal on line 51 is applied to D-type flip-flop F8 for presetting, its output Q is at H-level, and line 52 maintains H-level as shown in FIG. 10 (10). .

The output Q of the D-type flip-flop F6 returns to the L level as described above. At this time, the output Q / returns the line 47 to the H level as shown in FIG. 10 (8).
Therefore, the transistor TR5 of the power supply means 41 is shut off. In this way, during the period when the reed switch 2 is conducting, only during the period when the transistor TR5 is conducting,
The reed switch 2 is connected to the reed switch 2 via the resistor R15.
A current flows through the first and R19, and this current is a value suitable for keeping the contact bodies of the first and second contacts 27 and 29 of the reed switch 2 good. In this way, a longer life of the reed switch 2 is achieved.

When the transistor TR5 is cut off as described above, the L-level signal at the connection point 35 is supplied to the line 45 via the resistor R15 and the conducting transistor TR6. It becomes L level as shown in 9). This allows NAND
The gate G7 sets the line 9 to the H level. The output of AND gate G8 derives an H level on line 50, as shown in FIG.
The result is as shown in (11).

The transmitter RSW1 is in a non-detection state, that is, no magnetic field is applied, and the transmitter RSW1 is kept shut off. At this time, the detection pulse generation circuit 11
As described above, both the lines 12 and 13 are kept at the H level. Therefore, the output of the line 9 is input to the NAND gate G27 of the bistable circuit F2 via the AND gate G3. When the line 9 falls from the H level to the L level in this manner, the waveform is changed to the AND gate G3 and the line 5
3 to the NAND gate G27 to switch the bistable state, and the line 14 goes to the H level as shown in FIG. 10 (13).
It becomes L level as shown in (14).

Thereafter, at time t3, the reed switch 2 is turned off, and at time t4,
Another reed switch 3 becomes conductive. Such a series of operations is repeated. In FIG. 10, the time axis near the times t1 and t2 is shown in an enlarged manner for convenience of understanding as compared with the other parts. In the operation after time t4, another detection pulse generating circuit 8 achieves the same operation as the operation shown in FIG.

FIG. 11 is a waveform diagram for explaining the operation of detection pulse generation circuit 7 near time t2. Immediately after the output Q of the monostable circuit F5 changes from the H level to the L level at the time t2, the reed switch 2 is turned off, and the connection point 35 becomes the H level by the H level of the line 17, whereby the switching detection means It is assumed that 40 transistors TR6 are turned off. At time t2, the output Q / of the monostable circuit F5 drives the line 48 to the H level, so that the line 45 becomes
Since it is at the H level, the NAND gate G7 is connected to the line 9
From H level to L level as shown in FIG.
A waveform falling to the level is obtained. Therefore, AND gate G8 gives line 50 a waveform falling to the L level as shown in FIG. 11 (11). Therefore, D-type flip-flop F6 is cleared and its output Q is applied to line 51.
As shown in FIG. 11 (7), a signal changing to the L level is derived, and at this time, the output Q /
7 is set to the H level as shown in FIG.
At time t13 between time t11 and time t12,
When the reed switch 2 is turned off, the connection point 35 becomes H level as described above, so that the transistor TR6 of the switching detecting means 40 is turned off, and the line 45 becomes the line in FIG.
It changes to L level as shown in (9). As a result, the output of the NAND gate G7 derives a signal rising to the H level on the line 9, and the AND gate G8 derives an H level signal on the line 50 as shown in FIG.

When the line 9 changes from the H level to the L level, the stable state is switched by the operation of the bistable circuit F2, and the line 14 changes to the H level as shown in FIG. 15 changes to L level. FIG. 11 (13) of such a bistable circuit F2.
11 (14) and the change in the signals on lines 14 and 15 shown in FIG.
As shown in FIG. 11 (3), a pulse 69 which becomes high level for a short time is generated. The pulse width of the pulse 69 at the H level is, for example, on the order of μsec, is extremely short, and does not cause a malfunction of the detection pulse generation circuit 7.

FIG. 12 is a diagram showing waveforms for explaining an operation when the reed switch 2 conducts for a very short time due to a malfunction or the like and noise is mixed. The conduction / interruption states of the reed switches 2 and 3 are shown in FIGS. 12A and 12B, respectively. At time t21, the connection point 35 falls to a low level, whereby the output Q of the monostable circuit F5 rises to an H level as shown in FIG. W01 starts clocking operation. The output Q / of the monostable circuit F5 becomes L level as shown in FIG. Output Q of monostable circuit F5 is line 4
3 to the D-type flip-flop F6, the output Q of which derives an H level signal shown in FIG. 12 (7) on line 51, and the output Q / Since the level is set to the H level as shown in 8), the transistor TR5 of the power supply means 41 is turned on. As described above, due to the conduction of the reed switch 2, the transistor TR6 of the switching detection means 40 is conducting. Therefore, voltage pulse Vcc is applied to line 45 via transistor TR5, connection point 46 and transistor TR6, and line 45 attains H level as shown in FIG. 12 (9).

Within the time limit W01 of the monostable circuit F5,
When the noise which the reed switch 2 cuts off is mixed,
At this time t22, the connection point 35 returns to the H level as shown in FIG. Therefore, the transistor TR6 of the switching detection means 40 is shut off, and the line 45 returns to the L level as shown in FIG.

Thereafter, at time t23, the monostable circuit F5
12 returns to the L level as shown in FIG. 12 (5) and the output Q / returns to the H level, the rising pulse of the line 48 is applied to the clock input terminal CK of the D-type flip-flop F8. The output Q of the D-type flip-flop F8 derives the L level shown in FIG. Therefore, the output of AND gate G8 is at L level as shown in FIG.
Accordingly, the D-type flip-flop F6 is cleared, and the output Q thereof is output to the line 51 at the L level shown in FIG.
Derive the level. When the line 51 falls to the L level, the D-type flip-flop F8 is preset, and its output Q derives a waveform rising to the H level on the line 52 as shown in FIG. Line 5
When 2 goes high, the output of AND gate G8 causes line 50 to go high, as shown in FIG. 12 (11). Thus, the signal derived from NAND gate G7 to line 9 always remains at the H level as shown in FIG. 12 (12), so that the stable state of bistable circuit F2 is not switched, and line 1 is not switched.
4 remains at the L level as shown in FIG. 12 (13), and the line 15 remains at the H level as shown in FIG. 12 (14). Thus, when noise having a very short pulse width less than the time limit W01 enters the connection point 35, the detection pulse is not derived from the line 9, the line 9 remains at the H level, and the bistable circuit F
The detection pulse is not derived by switching the stable state of No. 2 so that erroneous detection of the gas usage can be avoided.

FIG. 13 is an electric circuit diagram showing a specific configuration of the detection pulse generation circuit 11 including the transmitter RSW1. One contact 24 of the transmitter RSW1, which is a reed switch, is connected to a resistor R1 and a capacitor C1 at a connection point 70. The resistor R1 is connected to the output terminal of the DC power supply 33, and is supplied with the voltage + Vcc. The capacitor C1 is connected to another output stage of the DC power supply 33,
Connected to ground potential. The other contact 2 of the transmitter RSW1
5 is a monostable circuit F1 from a line 71 via a resistor R2.
Input terminal. This line 71 is connected to a resistor R3
Grounded. A capacitor C3 and a resistor R4 are connected to the monostable circuit F1, and a time limit W03 (= C3
R4) is determined. In this way, the monostable circuit F1 starts the time limit W0 from the conduction of the contacts 24 and 25 of the transmitter RSW1.
A signal that is maintained at the H level by 3
2 is derived.

The D-type flip-flop F4 forms a frequency dividing circuit, and divides the output of the line 72 by half. This D-type flip-flop F4 has a configuration similar to that of the above-described D-type flip-flop F16. The preset input terminal PR and the clear input terminal CLR are both supplied with the voltage + Vcc, and the preset and clear operations are performed. Absent. The output of the line 72 is applied to the clock input terminal CK of the D-type flip-flop F4, and when a rising waveform is applied to the clock input terminal CK,
The logical value given to the data input terminal D is derived to one output terminal Q, and the inverted logical value of the output of one output terminal Q is derived to the other output terminal Q /. The output of the output terminal Q / is supplied to the data input terminal D via the line 73. The output Q of the D-type flip-flop F4 is supplied to one input of a NAND gate G2 which is one logic gate via a line 74, and the other output terminal Q / is connected to another logic gate from a line 75 by another logic gate. This is applied to one input of a certain NAND gate G12. Further, an output Q of the monostable circuit F1 is commonly supplied from a line 72 to the other inputs of the NAND gates G2 and G12. These NAND gates G2, G
12 are output to lines 12 and 13 and
The signal is supplied to the bistable circuit F2 via the D gates G3 and G13.

FIG. 14 is a waveform chart for explaining the operation of detection pulse generating circuit 11 shown in FIG. Before time t31, the contacts 24 and 25 of the transmitter RSW1
Is cut off, the capacitor C1 is charged, and the line 71 is at the L level by the action of the resistor R3. The voltage of the line 71 is as shown in FIG.

When the contacts 24 and 25 of the transmitter RSW1 become conductive at time t31, the electric charge of the capacitor C1 becomes
From the connection point 70, the signal flows through the transmitter RSW1 to the line 71, and a positive pulse shown in FIG. 14 (2) is generated on the line 71. Start operation. Therefore line 7
2, the time limit W03 from the output Q of the monostable circuit F1.
The signal of the H level that lasts only for a time is derived as shown in FIG. The output Q of the D-type flip-flop F4 derives on line 74 the frequency-divided signal shown in FIG. Therefore, NAND gates G2 and G12
14 (5) and FIG.
As shown in (6), a detection pulse which becomes the L level alternately at intervals is derived. Such a line 12,1
The detection pulse of No. 3 is supplied to the subsequent commonly used bistable circuit F2 by the operation of the AND gates G3 and G13.

FIG. 15 is a side view showing a state in which the gas meter load measuring device 1 shown in FIGS. FIG. 16 is a front view of the gas meter 76. The gas meter 76 is provided with a counter 78 having a mechanical structure for integrating and displaying the integrated value of the gas usage. The casing 79 of the counter 78 is made of a non-magnetic material, for example, a material such as brass. In the casing 79, FIG.
A rotating magnet piece 31 made of a permanent magnet having a horizontal axis extending to the left and right is built in, and is rotated by an angle corresponding to a predetermined gas usage and angularly displaced. The casing 81 containing the transmitter RSW2 is detachably attached to the side of the casing 79 of the counter 78. Casing 81
Reed switches 2 and 3 constituting oscillator RSW2
Is close to the rotating magnet piece 31, and its magnetic field changes the switching state. Line 82 of transmitter RSW2
Is connected to the input connector 4 of the gas meter load measuring device 1.

FIG. 17 is a side view showing a state in which the gas meter load measuring device 1 according to another embodiment of the present invention is mounted on a gas meter 83. FIG. 18 is a front view of the gas meter 83. On the front face of the gas meter 83, a counter 84 having a mechanical structure for integrating and displaying the gas usage of the membrane gas meter is mounted. The rotary magnet piece 31 is built in the lower part of the counter 84, and rotates with angular displacement for each predetermined gas consumption. Transmitter RSW2
Is provided with reed switches 2 and 3 provided close to the rotating magnet piece 31 and is housed in a casing 85 made of a nonmagnetic material, for example, brass. The gas meter load measuring device 1 is connected to the input connector 4 via the line 82 from the reed switches 2 and 3 of the transmitter RSW2. The casing of the counter 84 is also made of a non-magnetic material, for example, brass, so that the magnetic field of the rotating magnet piece 31 is detected by the reed switches 2 and 3.

FIG. 19 shows the counter 84 and the transmitter RS
FIG. 20 is a cross-sectional view showing the configuration of W2 in a simplified manner, and FIG. The power of the output shaft 86 that is angularly displaced for each predetermined gas usage amount of the gas meter 83 is transmitted to the rotary magnet piece 31 via the gear train 87. This rotating magnet piece 31 etc.
It is covered by a casing 87 made of a non-magnetic material such as brass. In the casing 85 of the transmitter RSW2, the reed switches 2 and 3 of the transmitter RSW2 are removably mounted close to and at positions corresponding to the rotating magnet pieces 31.

FIG. 21 shows a counter 84 of the gas meter 83.
FIG. 2 is a side view showing a state in which the gas meter load measuring device 1 of the present invention is detachably mounted. In this embodiment, the casing 87 provided with the rotating magnet piece 31 includes:
The gas meter load measuring device 1 is directly detachably mounted. The transmitter RSW1 built in the gas meter load measuring device 1 is arranged close to the rotating magnet piece 31 in the mounted state. Therefore, the switching state of the transmitter RSW1 changes according to the angular displacement corresponding to the gas usage of the rotating magnet piece 31. The transmitter RSW1 can be constituted by a reed switch as described above, and such a small transmitter RSW1 can be mounted on the wiring board of the gas meter load measuring device shown in FIGS. . As a result, the size of the configuration can be reduced.
The gas meter load measuring device 1 has a casing made of a non-magnetic material, for example, a synthetic resin or brass, and this casing is detachably attached to the casing 87 of the counter 84 as described above.

FIG. 22 is an electric circuit diagram showing a configuration of a transmitter RSW3 according to another embodiment of the present invention. The common contact 90 is alternately switched to the individual contacts 91 and 92 by the rotation of the rotating magnet piece 31 to conduct. These contacts 90, 91, and 92 are connected to the gas meter load measuring device 1 of the present invention.
Are connected to connection terminals C1, A1, and B1 of the input connector 4 through lead wires and the like, respectively. When one magnetic pole, for example, the N pole of the rotating magnet piece 31 is close to the transmitter RSW3, the common contact 90 is conducted to the individual contact 91 by the magnetic field of the N pole. When the other magnetic pole, for example, the south pole is close to the transmitter RSW3, the common contact 90 is conducted to the individual contact 92 by the action of the magnetic field.
By rotating the rotating magnet piece 31 in this manner, the common contact 90 is separated from the individual contacts 91 and 9 as shown in FIG.
2 is alternately switched to conduct. Such a configuration can also be implemented in the present invention.

FIG. 24 is an electric circuit diagram showing a partial configuration of another embodiment of the detection pulse generating circuit 7. In FIG. In this embodiment, the above-described resistor R1 in the input connector 4 is used.
1, R20 is omitted, and the resistor R19 is connected to the connection terminal C1. Resistance R19 is, for example, 150Ω.

FIG. 25 is an electric circuit diagram showing a part of the configuration related to the input connector 4 of still another embodiment of the present invention. In this embodiment, the resistor R19 in FIG. 4 described above is omitted, and resistors R11 and R20 are connected to the connection terminals A1 and B1, respectively. The resistors R11 and R20 are
As mentioned above, for example, it is 150Ω.

The present invention has been implemented not only for measuring the gas usage of a gas meter, but also for other applications.

The present invention is capable of the following embodiments.

(1) A transmitter RSW2 in which the first contact repeatedly conducts and cuts off the second contact, and the first contact conducts or cuts off the second contact when the transmitter is normal in response to the output of the transmitter. A monostable circuit F5 that derives an output that is shorter than a first time W1 and that lasts for a predetermined time limit W0 that exceeds a second time W2 when noise from the transmitter is generated. Logic means for deriving a detection pulse in response to an output from the circuit when the conduction or disconnection state of the first and second contacts of the transmitter exceeds the time limit W0. The detection device used.

According to the above configuration, the transmitter RSW2 is
For example, the first and second contacts are repeatedly turned on and off at time intervals corresponding to the flow rate of city gas.
The time limit W0 of the monostable circuit F5 to which SW2 is given is
A first time W when the first and second contacts are conducting or breaking
It is set to a value that is less than 1 and exceeds a relatively short second time W2 that is the pulse width of the noise (ie, W2).
2 <W0 <W1), the logic means performs a logical operation in response to the output of the oscillator RSW2 and the output having the time limit W0 of the monostable circuit F5, and conducts the first or second contact of the oscillator RSW2 or The output indicating the cutoff state is determined by the time limit W0.
(Ie, when W0 <W1), a detection pulse is derived. Thus, the output of the logic means does not include any noise from the transmitter and no other noise. Thus, by counting the number of detection pulses from the logic means, for example, the amount of gas used such as city gas can be integrated.

The above arrangement can be implemented not only for counting gas usage, but also for a wide range of other applications using transmitters.

According to the above-described configuration, when the output of the oscillator RSW2 is mixed with a noise that lasts for a very short time shorter than the time limit W0 of the monostable circuit F5, no detection pulse is generated, thereby causing an erroneous detection. Can be avoided.

(2) A transmitter RSW2 having one first contact and two second contacts, the first contact being alternately and repeatedly turned on and off to each second contact, and a first contact of the transmitter. Responsive to the output between the first contact and one of the second contacts, the first time when the first contact of the transmitter is normal to the one second contact is less than the first time W1, and the noise from the transmitter. A predetermined first time limit W exceeding a second time W2 in which
First monostable circuit F5 for deriving an output that lasts for 01
Responding to an output between a first contact of the transmitter and said one second contact and an output of a first monostable circuit,
A first logic means for deriving a first detection pulse when a conduction state or a cutoff state between a contact and the one second contact exceeds the first time limit W01; In response to the output between the two contacts, the third time W3 during which the first contact in the normal state of the transmitter is conducted to the other second contact is less than the third time W3 and the noise from the transmitter is generated. The second predetermined time limit W0 exceeding the time W4 of No. 4
A second monostable circuit F15 for deriving an output that lasts only 2
Responding to an output between a first contact of the transmitter and the other second contact and an output of a second monostable circuit;
A second logic means for deriving a second detection pulse when a conduction state or a cutoff state between the contact and the other second contact exceeds the second time limit W02, and two inputs; And a bistable circuit F2 to which the first and second detection pulses are respectively applied to switch between the two stable states and output the two stable states.

According to the above configuration, the transmitter RSW2 is
One first contact alternately and repeatedly conducts and cuts off to each of the two second contacts. For example, when the first contact is conducting to one second contact, the first contact becomes the other second contact. When the first contact is disconnected from one second contact, the first contact is electrically connected to the other second contact. This transmitter may be configured so that a state in which the first contact is interrupted by any of the two second contacts is generated. The output between the first contact of the transmitter and one of the second contacts is supplied to a first monostable circuit F5, and the first logic means mixes noise corresponding to the first and one of the second contacts. Can be avoided. Similarly, the output between the first contact of the transmitter and the other second contact is given to a second monostable circuit, and the first logic is connected to the second contact by the second logic means.
The entry of noise corresponding to the contacts is avoided.

The first and second detection pulses from the first and second logic means are applied to two respective inputs of a bistable circuit, for example an RS flip-flop, so that the two respective stable states of the bistable circuit are: The switching is performed alternately according to the state where the first contact of the transmitter is electrically connected to each second contact. In this way, for example, by counting the output of the bistable circuit, it is possible to integrate the gas usage.

For example, W0 = W01 = W02 = 150 m
sec. W1 = W3 and W2 = W4 may be satisfied.

According to the above arrangement, when noise is mixed in the output between the first contact and one second contact of the oscillator RSW2, the operation of the first monostable circuit F5 and the first logic means causes the noise to enter. When the first detection pulse is prevented from being generated by mistake, and when noise is mixed in the output between the first contact and the other second contact, the second monostable circuit F15 and the second logic means Prevents the generation of the second detection pulse. Thus, the alternating operation of the two stable states of the bistable circuit is accurately achieved without being adversely affected by noise.

(3) The bistable circuit F2 derives two outputs, one output corresponding to the one second contact, the other output corresponding to the other second contact, and the first output. The contacts are
The first logic means is connected to an output terminal of the DC power supply, the first logic means includes: a first resistor R12 connected between the one second contact and the other output of the bistable circuit; Or the second resistor R1 interposed between the other output and the first resistor R12.
1, R19, the output of the first monostable circuit, and the output of the one second contact or the connection point of the first and second resistors corresponding to conduction and cutoff between the first contact and the one second contact. And a first logic circuit that derives a first detection pulse by performing a logical operation between the output terminal of the DC power supply and the connection point of the first and second resistors as compared with the resistance value of the first resistor R12. Resistances R11 and R1 when the first and second contacts are electrically connected.
9, the second logic means includes a third resistor R21 connected between the other second contact and the one output of the bistable circuit, a first contact and a DC power supply, respectively. Or the fourth resistor R2 interposed between the one output and the third resistor R21.
0, R19, the output of the second monostable circuit, and the output of the other second contact or the connection point of the third and fourth resistors corresponding to conduction and cutoff between the first contact and the other second contact. And a second logic circuit for performing a logical operation to derive a second detection pulse, and comparing the resistance value of the third resistor R21 from the output end of the DC power supply to the connection point of the third and fourth resistors. Resistances R20 and R1 when the first and second contacts are electrically connected.
9. A detecting device using a transmitter, wherein the resistance value according to 9 is selected to be small.

According to the above-described configuration, the first contact is connected to the output terminal of the DC power supply and is, for example, grounded, and the first logic means includes the first resistor R12, the second resistors R11 and R19,
One of the outputs of the bistable circuit becomes, for example, one logical value, that is, an H level, by the conduction between the first contact of the transmitter and one of the second contacts. The voltage on the other output side of the power supply
Due to conduction between the contact and the other second contact, the other output of the bistable circuit becomes one logical value, for example, H level, and becomes the voltage of the other output terminal of the DC power supply. Second resistor R1
1, the resistance value of R19 is selected to be less than the resistance value of the first resistor R12. Therefore, when the first contact of the transmitter and one of the second contacts are in the cutoff state, that is, the other of the bistable circuit. When the output is at the H level and the first contact and one of the second contacts conduct, the output of one of the second contacts becomes the other logical value of one output terminal of the DC power supply, for example, L. Level, which causes the first logic circuit to derive a first detection pulse.

Instead of receiving the output of the one second contact, the output of the connection point of the first and second resistors may be supplied to the first logic circuit. For example, in the embodiment described later, (a) resistors R11, R19, R2
0 may be provided, but (b) the resistance R1
1, R20 may be omitted and only the resistor R19 may be provided, or (c) the resistor R19 may be omitted and the resistor R1 may be omitted.
1, only R20 may be provided. One output of the bistable circuit becomes H level due to conduction of the first contact and one second contact of the transmitter.

Next, when the first contact of the transmitter and the other second contact become conductive, the output of the other second contact becomes L level, whereby one output of the bistable circuit becomes L level, and Becomes H level. Such an operation is repeated. Instead of the output of the other second contact, a third
And the output of the connection point of the fourth resistor may be provided to the second logic circuit.

By using the first to fourth resistors, the switching state of the transmitter can be detected with a relatively simple configuration.

According to the above configuration, the conduction between the first contact of the transmitter and the one second contact causes the output of one of the second contacts or the connection point to be at the level of the output terminal of the DC power supply, for example, the ground. And the conduction between the first contact of the transmitter and the other second contact also causes the output of the other second contact or the output of the connection point to be, for example, L level.
It is possible to detect conduction and interruption between the first contact of the transmitter and each of the two second contacts with a relatively simple configuration that is forced to the level and thus uses the first to fourth resistors.

(4) The first logic circuit comprises: first switching detection means for deriving logic values corresponding to conduction and cutoff between the first contact and the one second contact, respectively, and an output of the first monostable circuit. And the output of the first switching detecting means are logically operated, the measurement of the first time limit W01 is started, and one of the conduction and the interruption between the first contact and the one second contact is established. Responding to the first pulse leading edge forming means for setting the first detection pulse to one logical value, the output of the first monostable circuit, and the output of the first switching detection means, when the first time limit W01 has elapsed, and A first pulse trailing edge forming means for setting the first detection pulse to the other logical value when the first contact and the one of the second contacts are in one of the conduction and the interruption, and the second logic circuit comprises: Conduction between one contact and the other second contact and A second switching detecting means for deriving a logical value corresponding to each of the first and second switching operations, a logical operation of an output of the second monostable circuit and an output of the second switching detecting means, and measurement of the second time limit W02 is started. And the first
A second pulse leading edge forming means for setting the second detection pulse to one logical value when one of the conduction and the interruption of the contact and the other second contact is established; 2) responding to the output of the switching detection means, when the second time limit W02 has elapsed, and when one of the conduction and the interruption of the first contact and the other of the second contact is one of the other, the second detection pulse is output to the other logic. A second pulse trailing edge forming means for converting the value into a value.

According to the above configuration, the first pulse is the first pulse.
A leading edge and a trailing edge of the first pulse are formed on the basis of the output of the switching detection means to form a first detection pulse. Similarly, the leading edge of the first pulse is formed on the basis of the output of the second switching detection means. The edge and the trailing edge form a second pulse. As described above, the leading edge and the trailing edge of the first and second detection pulses correspond to the outputs of the first and second monostable circuits and the first and second monostable circuits, respectively.
And the output of the second switching detection means, so that the first and second contacts are connected to the first and second switches.
The switching of the stable state of the bistable circuit when noise occurs when the conduction or interruption is performed for a very short period of time less than the time limits W01 and W02 is prevented, and adverse effects due to the entry of noise can be avoided.

According to the above configuration, the leading edge and the trailing edge of the first and second pulses are connected to the first and second monostable circuits and the first and second monostable circuits, respectively.
Since it is formed on the basis of the output from the second switching detecting means, the mixing of noise can be reliably avoided as described above.

(5) The gas meter is provided with the above-described detection device, and the gas meter is provided with a rotating magnet piece made of a permanent magnet that rotates with angular displacement for each predetermined amount of gas used. A gas meter load measuring device, comprising: a switching element provided in close proximity to a piece and having the first and second contacts, and turned on and off by magnetism of a rotating magnet piece.

According to the above-described configuration, for example, a reed switch can be used as the switching element, or the switching element may have a configuration in which a resistance value or the like corresponding to the strength of a magnetic field changes, and is made of a semiconductor element. The load of the gas meter can be measured by performing various calculations such as the usage amount of gas and the like, the flow rate, the integrated value of a plurality of gas meters, the state of the flow rate change over time, and the maximum flow rate.

According to the above configuration, the gas meter load such as the gas flow rate can be prevented from being erroneously detected due to noise.
It becomes possible to measure accurately.

(6) A transmitter RSW2 in which the first contact repeatedly conducts and cuts off the second contact, conduction detection means C4 and R13 for detecting conduction between the first and second contacts, and an output of the conduction detection means. A timer means F5 for responding and measuring a predetermined time limit W0 after the detection of conduction, and a predetermined voltage is applied between the first and second contacts for the time limit W0 in response to the output of the timekeeping means F5. Includes power supply means TR5 and R15 that are set to a value that allows a current suitable for maintaining a good contact state between the first and second contacts of the transmitter to flow between the first and second contacts. A detection device using a transmitter.

According to the above-described configuration, the conduction of the first and second contacts of the transmitter RSW2 is detected by the conduction detecting means, and from the time when the conduction is detected, for the time limit W0.
A voltage is applied between the first and second contacts by power supply means. This causes a current to flow between the first and second contacts,
Good contact between the first and second contacts can be achieved, poor contact can be prevented, and the life can be prolonged. The current flowing between the first and second contacts may be, for example, 0.1 mA.

The power supply has a configuration for applying a voltage between the first and second contacts, and is not configured as a current source for supplying a constant current. Even if the second contact breaks, no inconvenience such as generation of a high voltage occurs.

[0097] The clocking means F5 may be a monostable circuit, but may be realized by other configurations.

According to the above configuration, when the first and second contacts of the oscillator RSW2 are turned on, the first and second power supply means TR5 and R15 receive the time limit W0 of the time counting means F5.
If a predetermined voltage is applied between the contacts, so that the first and second contacts remain conductive for a time exceeding the time limit W0, a current flows between the first and second contacts for the time limit W0, Further, when the conduction time of the first and second contacts is shorter than the time limit W0, current flows between the first and second contacts for the conduction time, and thus the life of the transmitter RSW2 can be extended.

(7) The first contact is connected to one output terminal of the DC power supply, and the first contact R12 clamps the second contact to the voltage of the other output terminal of the DC power supply; And second resistors R11 and R19 interposed between the one output terminal of the DC power supply or the other output terminal of the DC power supply and the first resistor R12. In response to the output of F5, it conducts for the time limit W0,
A switching element TR5 connected to the other output terminal of the DC power supply; and a third element connected between the switching element TR5 and a second contact point or a connection point of the first and second resistors.
A detection device using a transmitter, comprising: a resistor R15.

According to the above configuration, when the first and second contacts of the oscillator RSW2 are cut off, the second contact is connected to the other output terminal of the DC power supply via the first resistor R12. For example, it is clamped at + Vcc. When the first and second contacts become conductive, the second contact is forced to one output terminal of the DC power supply, for example, the ground potential via the second resistors R11 and R19. , For the time limit W0. Accordingly, a current flows from the other output terminal of the DC power supply through the switching element TR5 and the third resistor R15 from the second contact point to the first contact point. Thus, a voltage corresponding to the conduction and cutoff of the first and second contacts of the transmitter RSW2 is generated at the second contact, whereby the conduction detection means can easily detect the conduction of the first and second contacts. At the same time, a voltage is applied to the second contact from the DC power supply via the switching element TR5 to supply a current. By adjusting and selecting the resistance value of the third resistor R15, a current value for maintaining a good contact state between the first and second contacts can be easily and appropriately selected.

According to the above-described configuration, voltages corresponding to the conduction / interruption of the first and second contacts of the transmitter RSW2 are obtained from the second contact.
4, R13 can easily detect the conduction / interruption of the first and second contacts of the transmitter RSW2. Moreover, according to the above-described configuration, by adjusting and selecting the resistance value of the third resistor R15, the current value for maintaining the good contact state of the first and second contacts can be easily and appropriately selected. The effect that can be achieved is achieved.

(8) The resistance value of the first resistor R12, the resistance value of the third resistor R15, and the resistance values of the second resistors R11 and R19 are selected so as to decrease in this order, and the second contact point or the connection point is selected. Switching detection means TR6, R16, R18 for level discrimination of the voltage of the switching element TR5 are provided.
In both the case of conduction and the case of disconnection, the voltage is selected to be not less than the voltage at the time of conduction of the first and second contacts and less than the voltage at the time of disconnection of the first and second contacts. A detection device using a transmitter.

According to the above-described configuration, the second resistors R11, R
19 may be (a) interposed between the first contact of the transmitter RSW2 and one output terminal of the DC power supply, and may be interposed between the second contact and the first resistor R12; ) Second
Interposed only between the contact and the first resistor R12, the first contact and the one output terminal of the DC power supply may be directly connected, or (c) the first contact and the one of the DC power supply. The second contact and the first resistor R12
May be directly connected.

According to the above-described configuration, the voltage at the second contact or the voltage at the connection point is discriminated by the switching detecting means, whereby the conduction of the first and second contacts of the oscillator RSW2 is accurately detected. be able to.

According to the above configuration, the switching detection means detects the conduction and interruption of the first and second contacts of the transmitter RSW2. Control operations and arithmetic operations can be performed.

(9) A transmitter RSW2 having one first contact and two second contacts, wherein the first contact alternately and repeatedly conducts and cuts off each second contact, and a first contact of the transmitter. Responsive to the output between the first contact and one of the second contacts, the first time when the first contact of the transmitter is normal to the one second contact is less than the first time W1, and the noise from the transmitter. A predetermined first time limit W exceeding a second time W2 in which
First monostable circuit F5 for deriving an output that lasts for 01
Responding to an output between a first contact of the transmitter and said one second contact and an output of a first monostable circuit,
A first logic means for deriving a first detection pulse when a conduction state or a cutoff state between a contact and the one second contact exceeds the first time limit W01; In response to the output between the two contacts, the third time W3 during which the first contact in the normal state of the transmitter is conducted to the other second contact is less than the third time W3 and the noise from the transmitter is generated. The second predetermined time limit W0 exceeding the time W4 of No. 4
A second monostable circuit F15 for deriving an output that lasts only 2
Responding to an output between a first contact of the transmitter and the other second contact and an output of a second monostable circuit;
A second logic means for deriving a second detection pulse when a conduction state or a cutoff state between the contact and the other second contact exceeds the second time limit W02, and two inputs; , A first and a second detection pulse are applied to each other to switch and output two stable states.
In response to the output of the first monostable circuit, to provide a predetermined voltage between the first and one of the second contacts for a time limit W01, the voltage being the first and the second one of the transmitter. A current suitable for maintaining a good contact state of the contact
And a first value determined to be a value flowing between the one second contact point.
In response to the power supply means TR5 and R15 and the output of the second monostable circuit, the first and the other second circuits are provided for a time limit W02.
A predetermined voltage is applied between the contacts, the voltage flowing between the first and the other second contacts a current suitable for maintaining good contact between the first and the other second contacts of the transmitter. A detection device using a transmitter, comprising second power supply means TR7, R24 set to a value.

According to the above configuration, the transmitter RSW2 is
One first contact alternately and repeatedly conducts and cuts off to each of the two second contacts. For example, when the first contact is conducting to one second contact, the first contact becomes the other second contact. When the first contact is disconnected from one second contact, the first contact is electrically connected to the other second contact. This transmitter may be configured so that a state in which the first contact is interrupted by any of the two second contacts is generated. The output between the first contact of the transmitter and one of the second contacts is supplied to a first monostable circuit F5, and the first logic means mixes noise corresponding to the first and one of the second contacts. Can be avoided. Similarly, the output between the first contact of the transmitter and the other second contact is given to a second monostable circuit, and the first logic is connected to the second contact by the second logic means.
The entry of noise corresponding to the contacts is avoided.

The first and second detection pulses from the first and second logic means are applied to two respective inputs of a bistable circuit, for example an RS flip-flop, so that the two stable states of the bistable circuit are: The switching is performed alternately according to the state where the first contact of the transmitter is electrically connected to each second contact. In this way, for example, by counting the output of the bistable circuit, it is possible to integrate the gas usage.

For example, W0 = W01 = W02 = 150 m
sec. W1 = W3 and W2 = W4 may be satisfied.

Further, according to the above configuration, the transmitter RSW
2 and one of the second contacts are connected to each other,
A voltage from the first power supply is applied, and a voltage from the second power supply is applied between the first contact and the other second contact when the first contact is turned on. A suitable current will be supplied to each of the two second contacts to keep them in good contact.

According to the above configuration, when noise is mixed in the output between the first contact and one second contact of the oscillator RSW2, the operation of the first monostable circuit F5 and the first logic means causes the noise to enter. When the first detection pulse is prevented from being generated by mistake, and when noise is mixed in the output between the first contact and the other second contact, the second monostable circuit F15 and the second logic means Prevents the generation of the second detection pulse. Thus, the alternating operation of the two stable states of the bistable circuit is accurately achieved without being adversely affected by noise.

Further, according to the above configuration, the voltage from the first and second power supply means is applied between the first contact and one second contact and between the first contact and the other second contact. Applied. In this way, the first contact and each of the two second contacts are supplied with a current suitable for keeping them in good contact for a long period of time, thus preventing erroneous detection and maintaining long-term maintenance. It will be easier.

(10) The transmitter has a transmitter whose first contact is repeatedly turned on and off to the second contact, a DC power supply whose first contact is connected to one output terminal, and an input terminal. Is an electric circuit F5 that receives an input signal of the polarity of the one output terminal of the DC power supply and performs an operation corresponding to the conduction of the first and second contacts; A capacitor C4 interposed therebetween and a resistor R13. One terminal of the resistor R13 is connected to the capacitor C4.
4 and an input terminal of the electric circuit F5, and the other terminal is connected to a resistor R1 connected to the other output terminal of the DC power supply.
3. A detection device using a transmitter, comprising:

According to the above configuration, the capacitor C4,
For example, between the input terminal of an electric circuit F5 such as a monostable circuit and the like, a DC voltage + Vcc is applied from the other output terminal of the DC power supply via a resistor R13, and the voltage of the other output terminal of the DC power supply is applied. Is clamped to. When the first and second contacts of the transmitter are turned on, the voltage of one output terminal of the DC power supply is applied to the terminal of the capacitor C4 on the side opposite to the electric circuit F5. As a result, a differential pulse on the L level side, which is, for example, the ground potential, of the one output terminal of the DC power supply is derived from the capacitor C4 to the input terminal of the electric circuit F5.

Even if the first and second contacts of the transmitter remain conductive due to a failure or the like, the capacitor C4
As a result, no current flows from the other output terminal of the DC power supply to the transmitter side. In this way, even when the first and second contacts remain conductive when the transmitter fails, the current does not continue to flow through those contacts, and the power of the DC power supply is not wasted. This is particularly advantageous in configurations where the DC power supply is realized by a battery.

According to the above configuration, even if the first and second contacts of the transmitter remain conductive due to a failure or the like, current does not continue to flow from the DC power supply due to the operation of the capacitor C4. In addition, unnecessary power consumption of the DC power supply is prevented.

(11) A transmitter RSW2 having one first contact and two second contacts, the first contact being alternately and repeatedly conducting to and interrupting each second contact, and the first contact being connected to one of the two contacts. A DC power supply connected to the output end, and a first input terminal;
The first input terminal is supplied with an input signal having the polarity of the one output terminal of the DC power supply, and a first time W1 during which the first contact of the transmitter is normal to the one second contact when the transmitter is normal.
Less than and the noise from the transmitter occurs
A first monostable circuit F5 that derives an output that lasts for a predetermined first time limit W01 exceeding the time W2 of the first time, an output between the first contact of the transmitter and the one second contact,
In response to the output of the monostable circuit, the conduction or cut-off state between the first contact of the transmitter and the one second contact is the first state.
When the time limit W01 is exceeded, a first logic means for deriving a first detection pulse and a second input terminal are provided. The second input terminal receives an input signal having the polarity of the one output terminal of the DC power supply. Given a normal time of the transmitter, the first contact is less than a third time W3 in which the other contact is conductive, and a fourth time W4 in which noise from the transmitter occurs.
A second monostable circuit F15 that derives an output that lasts for a predetermined second time limit W02 that exceeds a predetermined time limit, an output between a first contact of the transmitter and the other second contact, and a second monostable circuit. And a second logic means for deriving a second detection pulse when a conduction or cutoff state between the first contact of the transmitter and the other second contact exceeds the second time limit W02 in response to the output. , A first capacitor C4 interposed between the one second contact and the first input terminal, and a first resistor R13. One terminal of the first resistor R13 is connected to the first capacitor C4 and the first capacitor R4. One input terminal and the other terminal are connected to a first resistor R1 connected to the other output terminal of the DC power supply.
3, a second capacitor C7 interposed between the other second contact and the second input terminal, and a second resistor R22. One terminal of the second resistor R22 is a second capacitor C7. And a second input terminal, and the other terminal is connected to a second resistor R2 connected to the other output terminal of the DC power supply.
And a bistable circuit having two inputs, each of which is supplied with a first and a second detection pulse, respectively, and switches and outputs two stable states. The detection device used.

According to the above configuration, the transmitter RSW2 is
One first contact alternately and repeatedly conducts and cuts off to each of the two second contacts. For example, when the first contact is conducting to one second contact, the first contact becomes the other second contact. When the first contact is disconnected from one second contact, the first contact is electrically connected to the other second contact. This transmitter may be configured so that a state in which the first contact is interrupted by any of the two second contacts is generated. The output between the first contact of the transmitter and one of the second contacts is supplied to a first monostable circuit F5, and the first logic means mixes noise corresponding to the first and one of the second contacts. Can be avoided. Similarly, the output between the first contact of the transmitter and the other second contact is given to a second monostable circuit, and the first logic is connected to the second contact by the second logic means.
The entry of noise corresponding to the contacts is avoided.

The first and second detection pulses from the first and second logic means are applied to two respective inputs of a bistable circuit, for example an RS flip-flop, so that the two respective stable states of the bistable circuit are: The switching is performed alternately according to the state where the first contact of the transmitter is electrically connected to each second contact. In this way, for example, by counting the output of the bistable circuit, it is possible to integrate the gas usage.

For example, W0 = W01 = W02 = 150 m
sec. W1 = W3 and W2 = W4 may be satisfied.

Further, according to the above configuration, the first transmitter
When the contact and one of the second contacts conduct, the first capacitor C
A differential pulse having the characteristic of the voltage of one output terminal of the DC power supply is given to the first input terminal of the first monostable circuit F5 via the input terminal 4, and when the first contact and the other second contact become conductive. , The second monostable circuit F15 via the second capacitor C7.
Is supplied with a pulse having the polarity of the voltage of the one output terminal of the DC power supply. In this way, even if the first contact of the transmitter and the two second contacts remain conductive due to, for example, a failure, the first contact and the two second contacts are connected via the first or second resistors R13 and R22. It is possible to prevent current from continuing to flow through the conductive first and second contacts. Thus, unnecessary power consumption of the DC power supply can be prevented.

According to the above arrangement, when noise is mixed in the output between the first contact and one second contact of the transmitter RSW2, the operation of the first monostable circuit F5 and the first logic means causes the noise to enter. When the first detection pulse is prevented from being generated by mistake, and when noise is mixed in the output between the first contact and the other second contact, the second monostable circuit F15 and the second logic means Prevents the generation of the second detection pulse. Thus, the alternating operation of the two stable states of the bistable circuit is accurately achieved without being adversely affected by noise.

Further, according to the above configuration, the transmitter RSW
The first and second capacitors C4 and C7 reduce the wasteful power consumption of the DC power supply even if the first contact of the second and the two second contacts remain conductive due to a failure or the like. Can be prevented.

(12) (a) a transmitter RSW2 in which the first contact repeatedly conducts and cuts off the second contact;
A DC power supply having a contact connected to one output terminal; and (c) an input terminal. The input terminal is supplied with an input signal of the polarity of the one output terminal of the DC power supply and receives first and second input terminals. 2
(D) a first resistor R12 for clamping a second contact to the potential of the other output terminal of the DC power supply, (e) a first resistor R12 for measuring a predetermined time limit time W0 after the contact is turned on,
Interposed between a contact and the one output terminal of the DC power supply,
Alternatively, second resistors R11 and R19 interposed between the other output terminal of the DC power supply and the first resistor R12, and (f) power supply means connected to the other output terminal of the DC power supply. Switching element TR5 and switching element TR
5 and a second contact or a connection point of the first and second resistors, thereby providing a predetermined voltage between the first and second contacts, which voltage is applied to the first and second contacts of the transmitter. A current suitable for maintaining a good contact state of the contact
And a third resistor R15 set to a value flowing between the second contacts
In response to the outputs of the timing means F5 and F6,
(G) a capacitor interposed between the second contact or the connection point of the first and second contacts, and the input terminals of the time measuring means F5 and F6. C4, and (h) a fourth resistor R13. One terminal of the fourth resistor R13 is connected between the capacitor C4 and the input terminals of the timers F5 and F6, and the other terminal is connected to a DC power supply. And a fourth resistor R13 connected to the other output terminal of the detection device.

According to the configuration described above, when the first and second contacts of the transmitter RSW2 are cut off, the second contact is connected to the other output terminal of the DC power supply via the first resistor R12. For example, it is clamped at + Vcc. When the first and second contacts become conductive, the second contact is forced to one output terminal of the DC power supply, for example, the ground potential via the second resistors R11 and R19. , For the time limit W0. Accordingly, a current flows from the other output terminal of the DC power supply through the switching element TR5 and the third resistor R15 from the second contact point to the first contact point. Thus, a voltage corresponding to the conduction and cutoff of the first and second contacts of the transmitter RSW2 is generated at the second contact, whereby the conduction detection means can easily detect the conduction of the first and second contacts. At the same time, a voltage is applied to the second contact from the DC power supply via the switching element TR5 to supply a current. By adjusting and selecting the resistance value of the third resistor R15, a current value for maintaining a good contact state between the first and second contacts can be easily and appropriately selected.

Further, according to the above configuration, the first of the transmitters
And the second contact, through a capacitor C4, for example a time-measuring means F realized by a monostable circuit
An input signal having the polarity of the voltage of the one output terminal of the DC power supply is supplied to input terminals of F5 and F6. By the action of the capacitor C4, even if the first and second contacts of the transmitter remain conductive, the other output terminal of the DC power supply passes through the fourth resistor R13 to the second resistors R11, R19 and the transmitter. The current is prevented from being left flowing, and the unnecessary power consumption of the DC power supply is prevented.

According to the above-described configuration, voltages corresponding to the conduction / interruption of the first and second contacts of the transmitter RSW2 are obtained from the second contact.
4, R13 can easily detect the conduction / interruption of the first and second contacts of the transmitter RSW2. Moreover, according to the above-described configuration, by adjusting and selecting the resistance value of the third resistor R15, the current value for maintaining the good contact state of the first and second contacts can be easily and appropriately selected. The effect that can be achieved is achieved.

Further, according to the above configuration, the transmitter RSW
Even if the first and second contacts remain conductive, the operation of the capacitor C4 can prevent unnecessary power consumption of the DC power supply.

(13) A first oscillator RSW1 in which two contacts repeat conduction and interruption, and an output responsive to the output of the first oscillator and lasting a predetermined first time limit W03 from the conduction or interruption of the contact. , A frequency dividing circuit F4 that divides the output of the first monostable circuit by half, and responds to each output of the first monostable circuit and the frequency dividing circuit by 2 A first logic means G having two output lines and for outputting to each output line first and second detection pulses which alternate in logic value each time the first oscillator is turned on or off.
1, G2, one first contact and two second contacts, the first contact being a second transmitter RSW2 that alternately and repeatedly conducts and shuts off each second contact, and the first contact being one of And a first input terminal. The first input terminal is supplied with an input signal having the polarity of the one output terminal of the DC power supply, so that the second transmitter operates normally. A first time W1 when the first contact at the time is conducted to the one second contact;
A second time limit W01 that is less than and exceeds a second time W2 during which noise from the second transmitter occurs.
A second monostable circuit F5 that derives an output that lasts for only one time, an output between the first contact of the second transmitter and the one second contact, and an output of the second monostable circuit F5, A second logic unit for deriving a third detection pulse when a conduction or cutoff state between the first contact of the second transmitter and the one second contact exceeds the second time limit W01; The second input terminal is supplied with an input signal having the polarity of the one output terminal of the DC power supply, so that the first contact of the second transmitter in a normal state is conducted to the other second contact. A third monostable circuit F that derives an output that is shorter than the third time W3 and that lasts for a predetermined third time limit W02 that exceeds the fourth time W4 when noise from the second oscillator occurs.
15, an output between the first contact of the second transmitter and the other second contact, and an output of the third monostable circuit F15, and the first contact of the second transmitter and the other A third logic unit for deriving a fourth detection pulse when the conduction or cutoff state with the second contact exceeds the third time limit time W02, and between the one second contact and the first input terminal; An interposed first capacitor C4 and a first resistor R13. One terminal of the first resistor R13 is connected between the first capacitor C4 and the first input terminal, and the other terminal is connected to a direct current. A first resistor R13 connected to the other output terminal of the power supply; a second capacitor C7 interposed between the other second contact and the second input terminal; and a second resistor R22. 2 One terminal of the resistor R22 is connected between the second capacitor C7 and the second input terminal. Is, the other terminal, a second resistor R22 which is connected to the other output end of the DC power source, a first logic gate G3 which derives the first and third detection pulse, a second
And second logic gate G13 for deriving fourth detection pulse
And two inputs, each input being provided with the output from the first and second logic gates G3 and G13, respectively.
A bistable circuit G27 that switches and outputs each of the two stable states.
G37. A detecting apparatus using a transmitter, comprising:

According to the above configuration, the output from the first oscillator RSW1 in which the two contacts repeat conduction and cutoff is applied to the first monostable circuit F1, and the output of the first monostable circuit is divided. The frequency is divided by 1/2 by the circuit F4. Thereby, the first logic means G2 and G12 alternately change the logic values of the logic "1" and the logic "0" to the two output lines each time the two contacts of the first transmitter are turned on / off. It is changed and derived to obtain first and second detection pulses. Also one
Having two contacts and two second contacts, for example
When the first contact is electrically connected to one second contact by the output from the second transmitter RSW2 having two reed switches, the first contact is disconnected from the other second contact, and When one contact is interrupted from one second contact, it is configured to conduct to the other second contact. This transmitter may be configured so that a state in which the first contact is interrupted by any of the two second contacts is generated. The output between the first contact of the transmitter and one of the second contacts is applied to a second monostable circuit F5, and the second logic means mixes noise corresponding to the first and one of the second contacts. Can be avoided. Similarly, the output between the first contact of the transmitter and the other second contact is provided to a third monostable circuit, and the third logic means corresponds to the first contact and the other second contact. Noise contamination is avoided.

The third and fourth detection pulses from the second and third logic means are supplied to the first and second logic gates G3 and G3, respectively.
The signal is supplied to two inputs of a bistable circuit, for example, an RS flip-flop via 13. Thus, the two stable states of the bistable circuit correspond to the first contact of the second
Switching is performed alternately according to the state of conduction to the contact. In this way, for example, by counting the output of the bistable circuit, it is possible to integrate the gas usage.

For example, W01 = W02 = W03 = 150
msec. W1 = W3 and W2 = W4 may be satisfied.

Further, according to the above configuration, the outputs of these first and second oscillators RSW1 and RSW2 are applied to first and second logic gates G3 and G13. The two stable states of the bistable circuits G27 and G37 are switched by the respective outputs of the first and second logic gates G3 and G13. The outputs of the bistable circuits G27 and G37 are
For example, it can be counted by a counter to measure the gas usage and the like.

According to the above configuration, the second transmitter R
Even if the first contact of SW2 and the two second contacts become conductive due to a failure or the like, the other output terminal of the DC power supply is operated by the operation of the first and second capacitors C4 and C7. This prevents wasteful current from continuing to flow, thereby preventing power consumption of the DC power supply.

The time counting means F5 and F6 may be realized by a monostable circuit, but may be realized by other configurations.

According to the above configuration, the first transmitter RSW1
And the output associated with the second oscillator RSW2 is applied to the first and second logic gates G3 and G13 to provide the bistable circuit G
Since the two stable states 27 and G37 are switched, either one of the first and second oscillators RSW1 and RSW2 is selectively used, and the configuration after the bistable circuits G27 and G37 is used in common to use gas. It becomes possible to detect the amount and the like.

[0137]

According to the first aspect of the present invention, the outputs related to the first oscillator RSW1 and the second oscillator RSW2 are
Since the two stable states of the bistable circuits G27 and G37 are switched to the first and second logic gates G3 and G13, the first and second oscillators RSW1 and RSW2 are switched.
Are selectively used, and bistable circuits G27, G3
It becomes possible to detect the amount of gas used and the like by using the configuration after the seventh in common.

Further, according to the present invention, when noise is mixed in the output between the first contact and one second contact of the oscillator RSW2, the operation of the first monostable circuit F5 and the first logic means causes the noise to enter. When the first detection pulse is prevented from being generated by mistake, and when noise is mixed in the output between the first contact and the other second contact, the second monostable circuit F15 and the second logic means Prevents the generation of the second detection pulse. Thus, the alternating operation of the two stable states of the bistable circuit is accurately achieved without being adversely affected by noise.

According to the second aspect of the present invention, the first transmitter R
When SW1 is not detected, the first logic means continues to derive a predetermined logic value, for example, logic "1" in the later-described embodiment, from the first logic means to the first and second logic gates G3 and G13. When the first oscillator RSW1 is not used, the bistable circuit G is output by the output of the second oscillator RSW2.
The third and fourth detection pulses can be given to the two inputs 27 and G37 via the first and second logic gates G3 and G13, respectively.

According to the third aspect of the present invention, the second transmitter R
When the second oscillator RSW2 is used and the second oscillator RSW2 is used, the first oscillator RSW1 is set to the above-mentioned non-detection state, so that the bistable circuits G27 and G37 are switched according to the output of the second oscillator RSW2. The stable state can be changed or alternatively the second transmitter RSW2 can be removed,
By the output of the first oscillator RSW1, the bistable circuit G27,
The stable state of G37 can be changed. Thus, the circuit configuration can be shared, which is convenient.

According to the present invention, the first transmitter R
The frequency divider provided in association with SW1 is realized by a D-type flip-flop F4, and the first logic means
It is composed of two logic gates G2 and G12, whereby the configuration can be simplified and the present invention can be easily implemented.

[Brief description of the drawings]

FIG. 1 is a block diagram showing an overall configuration of an embodiment of the present invention.

FIG. 2 is a diagram showing a configuration of a transmitter RSW2.

FIG. 3 shows a connection terminal A1 of a connector 4 from a transmitter RSW2.
It is a figure which shows the conduction | electrical_connection and the interruption | blocking state obtained by C1.

FIG. 4 is an electric circuit diagram showing a specific configuration of a detection pulse generation circuit 7.

FIG. 5 is a diagram showing a configuration of an input terminal CK of a monostable circuit F5.

FIG. 6 shows the discrimination level V0 of the connection point 35 by the transistor TR6, the voltage V1 of the connection point 35 when the reed switch 2 is shut off, and the reed switch 2 conducting.
FIG. 9 is a diagram showing a correlation between a voltage V2 at a connection point when the transistor TR5 is conductive and a voltage V3 at the connection point 35 when the reed switch 2 is conductive and the transistor TR5 is cut off.

FIG. 7 shows a NAND gate G2 forming a bistable circuit F2.
7 is an electric circuit diagram showing a configuration of a part of an output stage connected to a line 14 of FIG.

FIG. 8 is an electric circuit diagram showing a specific configuration of another detection pulse generation circuit 8;

FIG. 9 is a diagram showing a waveform of a detection pulse corresponding to a switching state of the transmitter RSW2.

FIG. 10 is a waveform chart for explaining the operation of the detection pulse generation circuit 7;

FIG. 11 is a waveform chart for explaining the operation of detection pulse generation circuit 7 near time t2.

FIG. 12 is a diagram showing waveforms for explaining the operation when the reed switch 2 conducts for a very short time due to a malfunction or the like and noise is mixed.

FIG. 13 is an electric circuit diagram showing a specific configuration of a detection pulse generation circuit 11 including a transmitter RSW1.

FIG. 14 is a waveform chart for explaining the operation of detection pulse generation circuit 11 shown in FIG.

15 is a side view showing a state in which the gas meter load measuring device 1 shown in FIGS. 1 to 14 is detachably attached to a lower front part 77 of a membrane gas meter 76. FIG.

16 is a front view of the gas meter 76. FIG.

FIG. 17 is a side view showing a state in which a gas meter load measuring device 1 according to another embodiment of the present invention is mounted on a gas meter 83.

FIG. 18 is a front view of the gas meter 83.

FIG. 19 is a simplified cross-sectional view showing the configuration of a counter 84 and a transmitter RSW2.

FIG. 20 is a simplified cross-sectional view of the configuration of a counter 84 as viewed from the front.

FIG. 21 is a side view showing a state where a gas meter load measuring device 1 of the present invention is detachably mounted on a counter 84 of a gas meter 89 according to still another embodiment of the present invention.

FIG. 22 shows a transmitter RS according to another embodiment of the present invention.
FIG. 4 is an electric circuit diagram showing a configuration of W3.

FIG. 23 shows a transmitter RS according to another embodiment of the present invention.
It is a figure which shows the conduction | electrical_connection and the interruption | blocking state obtained from W3 to the connection terminals A1-C1 of the connector 4.

FIG. 24 is an electric circuit diagram showing a partial configuration of another embodiment of the present invention.

FIG. 25 is an electric circuit diagram showing a part of a configuration related to an input connector 4 of still another embodiment of the present invention.

[Explanation of symbols]

 DESCRIPTION OF SYMBOLS 1 Gas meter 2, 3 Reed switch 4, 18 Connector 7, 8, 11, 19, 20 Detection pulse generation circuit 21 Processing circuit 31 Rotating magnet piece 32 Rotation axis 33 DC power supply 38 Leading edge forming means 39 Trailing edge forming means 40 Switching detection Means 40 41 Power supply means 42 Transistor 55 NPN transistor 56 PNP transistor 65 Switching detection means 66 Power supply means 67 Output connector 69 Pulse 76 Membrane gas meter 78, 84 Counter 79, 81, 85, 87 Casing 83 Gas meter

Continued on the front page (72) Inventor Toru Kabayama 4-7-131 Nishiiwata, Higashi-Osaka-shi, Osaka Inside Kansai Research Laboratory, Kinmon Manufacturing Co., Ltd. (72) Takayuki Onishi 4-73-31 Nishiiwata, Higashi-Osaka-shi, Osaka No. Kansai Research Laboratories, Kansai Research Laboratories (56) References JP-A-9-311060 (JP, A) JP-A-3-239919 (JP, A) Japanese Utility Model Showa 62-3072 (JP, U) Japanese Utility Model Showa 55 -36654 (JP, U) Patent 2643119 (JP, B2) (58) Fields investigated (Int. Cl. ⁷ , DB name) G01F 15/075 G01F 3/22 G01D 5/245

Claims (4)

(57) [Claims] 1. A first oscillator RSW1 in which two contacts repeat conduction and interruption, and a first time limit W0 which is responsive to an output of the first oscillator and which is predetermined from conduction or interruption of the contact.
A first monostable circuit F1 that derives an output that lasts only 3; a frequency divider circuit F4 that divides the output of the first monostable circuit by half
A first and a second circuit which responds to each output of the first monostable circuit and the frequency divider circuit, has two output lines, and alternately changes the logical value every time the first oscillator is turned on or off. First logic means G1 and G12 for deriving two detection pulses to each output line
A second transmitter RSW2 having one first contact and two second contacts, wherein the first contact alternately and repeatedly conducts and cuts off each second contact; and a first contact of the second transmitter. Responsive to the output between the first contact and one of the second contacts, the first time when the first contact of the second transmitter is normal to the one second contact is less than a first time W1,
And a second time W2 during which noise from the second transmitter occurs.
A second monostable circuit F5 that derives an output that lasts for a predetermined second time limit W01 that exceeds a second time limit, an output between a first contact of the second transmitter and the one second contact, and a second monostable. In response to the output of the circuit F5, when the state of conduction or cutoff between the first contact of the second transmitter and the one second contact exceeds the second time limit W01, the third
Second logic means for deriving a detection pulse, and responsive to an output between the first contact of the second transmitter and the other second contact, wherein the first contact of the second transmitter in the normal state is the other first contact. Less than a third time W3 for conducting to the two contacts,
And a fourth time W4 during which noise from the second transmitter occurs.
A third monostable circuit F15 that derives an output that lasts for a predetermined third time limit W02 that exceeds a predetermined time limit, an output between a first contact of a second transmitter and the other second contact, and a third monostable circuit. In response to the output of the circuit F15, a fourth detection pulse is derived when the conduction or cutoff state between the first contact of the second transmitter and the other second contact exceeds the third time limit W02. Third logic means, and a first logic gate G for deriving first and third detection pulses
3 and a second logic gate G for deriving the second and fourth detection pulses
And bistable circuits G27 and G3 each of which receives an output from the first and second logic gates G3 and G13, respectively, and switches between two stable states for output.
7. A detection device using a transmitter, comprising: 2. The first oscillator RSW1 remains in a predetermined conducting or blocking state when it is not detected, whereby the output of the first monostable circuit F1 has a predetermined logical value, The logic means keeps deriving a predetermined logic value on the first and second output lines, whereby the first and second logic gates derive outputs corresponding to the third and fourth detection pulses. A detection device using the transmitter according to claim 1. 3. The second transmitter RSW2 includes a second transmitter and a third transmitter RSW2.
3. The detection device using a transmitter according to claim 1, wherein the detection device can be connected to and disconnected from each of the inputs of the monostable circuits F5 and F15. 4. The dividing circuit includes a D-type flip-flop F4.
The D-type flip-flop F4 has a clock input terminal CK to which an output of the first monostable circuit F1 is applied, and an output of the first monostable circuit F1 to the clock input terminal CK. At this time, the logical value given to the data input terminal D is derived to one output terminal Q, and the inverted logical value of the output of one output terminal Q is derived to the other output terminal Q / The output of the other output terminal Q / has a configuration applied to a data input terminal D. The first logic means comprises two logic gates G2 and G12, and is connected to one input of each of the logic gates G2 and G12. Is characterized in that the output of the first monostable circuit F1 is provided in common, and the other input of each of the logic gates G2 and G12 is provided with each of the output terminals Q and Q / of the D-type flip-flop F4. Detection apparatus using transmitter according to one of claims 1 to 3.