FR2608857A1 - DC/DC converter of the "forward" type with zero-current switching and two-way current operation - Google Patents
DC/DC converter of the "forward" type with zero-current switching and two-way current operation Download PDFInfo
- Publication number
- FR2608857A1 FR2608857A1 FR8617799A FR8617799A FR2608857A1 FR 2608857 A1 FR2608857 A1 FR 2608857A1 FR 8617799 A FR8617799 A FR 8617799A FR 8617799 A FR8617799 A FR 8617799A FR 2608857 A1 FR2608857 A1 FR 2608857A1
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- capacitor
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- switching
- current
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Description
CONVERTISSEUR CONTINU-CONTINU DU TPE "FORWARD" A COMMUTA
TION A COURANT NUL ET A FONCTIONNEMENT EN COURANTS BIDIREC
TIONNELS.CONTINUOUS-CONTINUOUS CONVERTER OF TPE "FORWARD" TO COMMUTA
ZERO CURRENT AND BIDIREC CURRENT OPERATION
TIONNELS.
L'invention vise à la égalisation d'un convertisseur continu-continu à faibles pertes de commutation aux fréquences élevées, qui soit de faible coût pour des puissances peu importantes, de l'ordre de la centaine de watts par exemple.The invention aims to equalize a DC-DC converter with low switching losses at high frequencies, which is of low cost for low powers, of the order of a hundred watts for example.
Elle concerne plus particulièrement un convertisseur comportant un transformateur de puissance dont l'enroulement primaire ést couplé à une source de tension continue par un organe commutateur, tandis qu'un organe à conductibilité unidirectionnelle et un condensateur sont connectés en série avec l'enroulement secondaire du transformateur, ce convertisseur étant - d'une part, du type "forward", c'est-à-dire dans lequel
les polarités sont telles que cet organe à conductibilité
unidirectionnelle soit conducteur lorsque l'organe de
commutation est conducteur, - d'autre part, dans leauel l'énergie est emmagasinée sous
forme magnétique en utilisant l'inductance de fuite du
transformateur de puissance et sous forme électrique car
le condensateur, qui constitue un circuit LC avec ladite
inductance de fuite, - enfin, dans lequel le circuit de commande de l'organe de
commutation est agencé
- d'une part, pour que l'organe de commutation soit
passant pendant des cycles successifs séparés par des
intervalles de temps et dont chacun se termine à un zéro
de courant dudit organe de commutation,
- d'autre part, pour que le condensateur, dont la tension
est unipolaire, se décharge dans la charge pendant des
fractions prédéterminées desdits cycles et sans qu'une
fraction de son énergie soit restituée à l'inductance de
fuite (ce qui supprime une cause de dissipation).It relates more particularly to a converter comprising a power transformer whose primary winding is coupled to a DC voltage source by a switching member, while a member with unidirectional conductivity and a capacitor are connected in series with the secondary winding of the transformer, this converter being - on the one hand, of the "forward" type, that is to say in which
the polarities are such that this conductive member
unidirectional be conductive when the
switching is conductive, - on the other hand, in water the energy is stored under
magnetic form using the leakage inductance of the
power transformer and in electrical form because
the capacitor, which constitutes an LC circuit with said
leakage inductance, - finally, in which the control circuit of the
switching is arranged
- on the one hand, so that the switching device is
passing through successive cycles separated by
time intervals each of which ends at zero
of current of said switching member,
- on the other hand, so that the capacitor, whose voltage
is unipolar, discharges into the charge for
predetermined fractions of said cycles and without a
fraction of its energy is returned to the inductance of
leak (which removes a cause of dissipation).
La commutation à zéro de courant supprime les pertes de commutation, tandis que le caractère unipolaire de la tension aux bornes du condensateur supprime le risque d'instabilité du montage.Switching to zero current eliminates switching losses, while the unipolar nature of the voltage across the capacitor eliminates the risk of instability of the assembly.
Un convertisseur du type qui vient d'être défini est notamment décrit dans US-A-4 415 959 déposé le 20 Mars 1981 au nom de Vinciarelli. Dans ce convertisseur, l'organe à conductibilité unidirectionnelle impose l'unidirectionnalité du courant dans les deux enroulements du transformateur et la durée de charge du condensateur est
L étant l'inductance de fuite du transformateur. Cette durée est une fonction lentement variable du courant dans la charge et les caractéristiques de sortie tension-courant du dispositif sont finalement fortement dépendantes dudit courant dans la charge ; d'où résultent un certain nombre d'inconvénients qui seront exposés plus complètement dans la suite.L being the transformer leakage inductance. This duration is a slowly variable function of the current in the load and the voltage-current output characteristics of the device are ultimately strongly dependent on said current in the load; whence result a number of drawbacks which will be explained more fully below.
L'invention se propose de s'affranchir de ces inconvénients et de réaliser un convertisseur continu-continu qui cumule les avantages inhérents aux convertisseurs du type défini ci-dessus et ceux du convertisseur forward classique à commutation forcée au blocage, grâce à la bidirectionnalité du courant dans les deux enroulements du transformateur. The invention proposes to overcome these drawbacks and to produce a DC-DC converter which combines the advantages inherent in converters of the type defined above and those of the conventional forward converter with forced switching at blocking, thanks to the bidirectionality of the current in the two windings of the transformer.
Le convertisseur suivant l'invention est principalement caractérisé par l'adjonction d'un second organe de commutation bidirectionnel - avantageusement un transistor MOS connecté en série avec l'enroulement secondaire du transformateur et le condensateur et commandé directement par la tension aux bornes dudit condensateur.The converter according to the invention is mainly characterized by the addition of a second bidirectional switching device - advantageously an MOS transistor connected in series with the secondary winding of the transformer and the capacitor and controlled directly by the voltage across said capacitor.
D'autres caractéristiques, ainsi que les avantages de l'invention, apparaltront clairement à la lumière de la description ci-après.Other characteristics, as well as the advantages of the invention, will become apparent in the light of the description below.
Au dessin annexé
La figure 1 est le schéma de principe d'un convertis
seur conforme à un mode d'exécution préféré de l'invention
La figure 2 illustre les formes d'ondes en différents
points du montage de la figure 1 ; et
La figure 3 représente les courbes caractéristiques de
sortie d'un tel montage, comparées à celles du montage
selon le brevet américain.In the attached drawing
Figure 1 is the block diagram of a convert
sister according to a preferred embodiment of the invention
Figure 2 illustrates the waveforms in different
assembly points of Figure 1; and
Figure 3 shows the characteristic curves of
output of such an assembly, compared to those of the assembly
according to the american patent.
A la figure 1, on a représenté un convertisseur continu continu du type n forward" comprenant - une source de tension continue +E ; - un transformateur de puissance ayant un enroulement
primaire L1 et un enroulement secondaire L2 ; - un organe de commutation T1 en série avec L1 entre les
deux bornes de la source ; - un premier organe à conductibilité unidirectionnelle D1 en
série avec L2 et orienté pour être passant en même temps
que T1 - un condensateur C en série avec L2 et D1 ;; - un puits de courant constant - un second organe à conductibilité unidirectionnelle D2 en
parallèle sur C et orienté pour empêcher l'inversion de la
tension aux bornes de C (L1 et L2 ayant les polarités
relatives indiquées par les points et la tension VC aux
bornes du condensateur la polarité indiquée par la flèche,
D2 devient conducteur dès que VC s'annule, empêchant ainsi VC de devenir négatif) - un circuit de commande K de l'organe de commutation - un second organe de commutation Ta en parallèle sur D1 et
apte à être commandé par la tension VC aux bornes de C.In FIG. 1, a continuous DC converter of the n forward "type has been represented comprising - a DC voltage source + E; - a power transformer having a winding
primary L1 and a secondary winding L2; - a switching device T1 in series with L1 between the
two source terminals; - a first member with unidirectional conductivity D1 in
series with L2 and oriented to be passing at the same time
that T1 - a capacitor C in series with L2 and D1 ;; - a constant current sink - a second unit with unidirectional conductivity D2 in
parallel on C and oriented to prevent inversion of the
voltage across C (L1 and L2 having the polarities
values indicated by the points and the voltage VC at
capacitor terminals the polarity indicated by the arrow,
D2 becomes conductive as soon as VC is canceled, thus preventing VC from becoming negative) - a control circuit K of the switching device - a second switching device Ta in parallel on D1 and
suitable for being controlled by the voltage VC across the terminals of C.
Le transformateur de puissance est réalisé de manière telle que son inductance de fuite secondaire L soit petite vis-àvis de la self du secondaire L2. L est, par définition, une 2 inductance fictive, égale à (LlL2-m4)/Ll, m étant l'induc- tance mutuelle entre L1 et L2. I1 doit être bien compris que des inductances réelles pourraient être ajoutées en série avec le primaire et/ou le secondaire : elles modifieraient alors la valeur de L.The power transformer is designed in such a way that its secondary leakage inductance L is small vis-à-vis the secondary choke L2. L is, by definition, a fictitious inductance, equal to (LlL2-m4) / Ll, m being the mutual inductance between L1 and L2. It must be clearly understood that real inductances could be added in series with the primary and / or secondary: they would then modify the value of L.
Avantageusement, T1 est un transistor MOS ayant une grille 91' une source sl et un drain dl. De même, T2 est un transistor MOS ayant une grille g2, une source s2 et un drain d2. La grille g1 est reliée au circuit de commande K, tandis que la grille g2 est reliée à la borne positive de C.Advantageously, T1 is a MOS transistor having a gate 91 'a source sl and a drain dl. Similarly, T2 is a MOS transistor having a gate g2, a source s2 and a drain d2. The gate g1 is connected to the control circuit K, while the gate g2 is connected to the positive terminal of C.
D1 et D2 sont des diodes. Le puits de courant constant peut en pratique être constitué par une inductance beaucoup plus grande que L, en série avec la charge aux bornes communes de C et de D2 et qui sera parcourue par un courant pratiquement constant pendant le cycle de transfert d'énergie du condensateur vers la charge.D1 and D2 are diodes. The constant current sink can in practice be constituted by an inductance much larger than L, in series with the load at the common terminals of C and D2 and which will be traversed by a practically constant current during the energy transfer cycle of the capacitor to the load.
A la figure 2, on a représenté en abscisses le temps t et en ordonnées
en (a), le courant iT1 à travers T1 (sinusolde) et la
tension VT1 aux bornes de T1
en (b), le courant iL dans l'enroulement secondaire
(sinusoide) et le courant iD2 dans D2
en (c), le courant iC dans C et la tension VC à ses bornes.In FIG. 2, the time t is shown on the abscissa and on the ordinate
in (a), the current iT1 through T1 (sinusolde) and the
voltage VT1 across T1
in (b), the current iL in the secondary winding
(sinusoid) and the current iD2 in D2
in (c), the current iC in C and the voltage VC across its terminals.
Pendant une première phase de fonctionnement qui part de l'instant t0 où le circuit de commande amorce T1, on a une croissance linéaire de iT1 et de iL et une décroissance linéaire de iD2. En effet, la tension induite au secondaire
L2 polarise D1 dans le sens passant. La tension VC reste nulle, car D2 est polarisée dans le sens passant et débite un courant iD2 égal à la différence entre IS et iL.During a first phase of operation which starts from instant t0 when the control circuit initiates T1, there is a linear growth of iT1 and of iL and a linear decrease of iD2. Indeed, the tension induced in secondary
L2 polarizes D1 in the forward direction. The voltage VC remains zero, because D2 is polarized in the forward direction and delivers a current iD2 equal to the difference between IS and iL.
A l'instant tl, iL est devenu égal à Is, si bien que 1D2 est nul et que D2 va se polariser en sens inverse. C commence alors à se charger.At time tl, iL has become equal to Is, so that 1D2 is zero and D2 will polarize in the opposite direction. C then starts to charge.
A l'instant t2, VC est chargé à une tension
le courant IL atteint sa valeur maximum
tandis que le courant iT1 atteint sa valeur maximum
1
the current IL reaches its maximum value
while the current iT1 reaches its maximum value
1
A l'instant t3, IL devient inférieur à IS et Vc atteint sa valeur maximum 2mE. En outre ic passe par zéro et change de signe.At time t3, IL becomes lower than IS and Vc reaches its maximum value 2mE. In addition ic goes through zero and changes sign.
A l'instant t4 où iL s'est annulé et change de signe, il est évident que D1 ne peut plus conduire. Par contre, T2 peut conduire dès l'instant, compris entre t2 et t4, où Vc est positive et supérieure à la tension de seuil VC0 de grille du MOS. La conduction de T2 entre t4 et t5 permet le passage d'un courant IL de signe inversé, t5 est l'instant où la tension VC devient inférieure à VCO. At the instant t4 when iL is canceled and changes sign, it is obvious that D1 can no longer drive. On the other hand, T2 can lead from the moment, comprised between t2 and t4, where Vc is positive and greater than the threshold voltage VC0 of the gate of the MOS. The conduction of T2 between t4 and t5 allows the passage of a current IL of reverse sign, t5 is the instant when the voltage VC becomes lower than VCO.
La commande du blocage de T1 par le circuit K s'effectue à l'instant du deuxième passage à zéro de iTl, qu'il est facile de faire colncider avec t5. L'expérience et le calcul montrent que la durée de conduction tCT1 de T1 est pratiquement indépendante de la valeur de Is, ce qui permet d'utiliser une bascule monostable comme circuit de commande.The blocking of T1 is controlled by circuit K is carried out at the time of the second zero crossing of iTl, which is easy to make coincide with t5. Experience and calculation show that the conduction time tCT1 of T1 is practically independent of the value of Is, which allows the use of a monostable rocker as a control circuit.
Le MOS T1 devra être choisi pour que sa diode parasite ne conduise pas de courant dans le sens inverse.The MOS T1 should be chosen so that its stray diode does not conduct current in the opposite direction.
On notera que dans le montage décrit, le MOS T1 est utilisé en mode bidirectionnel (iT1 s'inverse à l'instant t4) si bien que tout problème de recouvrement avec sa diode parasite est supprimé.It will be noted that in the assembly described, the MOS T1 is used in bidirectional mode (iT1 reverses at time t4) so that any problem of overlap with its parasitic diode is eliminated.
Le MOS T2 n'augmente pas la complexité du circuit de commande, du fait qu'il ne nécessite aucune commande propre, sa commande s'effectuant par la tension aux bornes du condensateur, ou par un diviseur capacitif si la tension globale est trop élevée.The MOS T2 does not increase the complexity of the control circuit, since it does not require any specific command, its control being effected by the voltage across the capacitor, or by a capacitive divider if the overall voltage is too high. .
Ce montage combine les avantages du convertisseur forward classique à commutation forcée au blocage à ceux du dispositif du brevet américain cité, qui sont - absence de pertes au blocage dans le commutateur primaire T11 - utilisation de l'inductance parasite de fuites, - aucune surtension au blocage, ce qui est très avantageux
dans le cas d'un découpage secteur, - très faible perturbation de la commande de grille de T1
par la commutation.This arrangement combines the advantages of the conventional forward converter with forced switching to blocking to those of the device of the cited American patent, which are - absence of blocking losses in the primary switch T11 - use of the parasitic leakage inductance, - no overvoltage at blocking, which is very advantageous
in the case of a sector breakdown, - very low disturbance of the gate control of T1
by switching.
En effet, comme le convertisseur forward classique, le montage décrit peut pratiquement fonctionner à fréquence constante.Indeed, like the conventional forward converter, the described circuit can practically operate at constant frequency.
Pour en expliquer la raison, on se réfèrera à la figure 3 dans laquelle on a représenté les caractéristiques Vs/me (Vs étant la tension moyenne de sortie) en fonction de
(IS étant le courant moyen de sortie) - en trait plein pour le montage décrit, - en pointillés pour un montage du type décrit dans le
brevet américain susvisé.To explain the reason, we will refer to Figure 3 in which we have represented the characteristics Vs / me (Vs being the average output voltage) as a function of
(IS being the average output current) - in solid lines for the assembly described, - in dotted lines for an assembly of the type described in the
aforementioned US patent.
Les courbes 1 à 9 correspondent respectivement aux valeurs respectives 0,1 ; 0,2 ; 0,3 ; 0,4 ; 0,5 ; 0,6 ; 0,7 ; 0,8 et 0,9 du rapport f/fo, f étant la fréquence de commande.Curves 1 to 9 correspond respectively to the respective values 0.1; 0.2; 0.3; 0.4; 0.5; 0.6; 0.7; 0.8 and 0.9 of the f / fo ratio, f being the control frequency.
On voit que, dans le montage antérieur, les caractéristiques de sortie sont fortement dépendantes de Is. En particulier, le fonctionnement à vide est impossible à obtenir. Pour réaliser une source d'alimentation à tension fixe et à courant compris entre O Et Int il faut donc utiliser de grandes variations de la fréquence de commande.We see that, in the previous assembly, the output characteristics are highly dependent on Is. In particular, the no-load operation is impossible to obtain. To make a power source with fixed voltage and current between O and Int, it is therefore necessary to use large variations in the control frequency.
Dans le montage décrit, les caractéristiques de sortie sont sensiblement horizontales. I1 n'y a plus de problème de fonctionnement à vide et les variations de fréquence nécessaires au maintien d'une tension fixe de sortie sont très faibles. I1 en résulte que les problèmes d'asservissement du circuit de commande sont réduits, car les fonctions de transfert à utiliser sont proches de celles des alimentations classiques. In the assembly described, the output characteristics are substantially horizontal. There is no longer any problem of no-load operation and the frequency variations necessary to maintain a fixed output voltage are very small. As a result, the problems of controlling the control circuit are reduced, because the transfer functions to be used are close to those of conventional power supplies.
Claims (5)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| FR8617799A FR2608857B1 (en) | 1986-12-19 | 1986-12-19 | CONTINUOUS-CONTINUOUS CONVERTER OF THE “FORWARD” TYPE WITH ZERO CURRENT SWITCHING AND BIDIRECTIONAL CURRENT OPERATION |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| FR8617799A FR2608857B1 (en) | 1986-12-19 | 1986-12-19 | CONTINUOUS-CONTINUOUS CONVERTER OF THE “FORWARD” TYPE WITH ZERO CURRENT SWITCHING AND BIDIRECTIONAL CURRENT OPERATION |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| FR2608857A1 true FR2608857A1 (en) | 1988-06-24 |
| FR2608857B1 FR2608857B1 (en) | 1989-05-12 |
Family
ID=9342081
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| FR8617799A Expired FR2608857B1 (en) | 1986-12-19 | 1986-12-19 | CONTINUOUS-CONTINUOUS CONVERTER OF THE “FORWARD” TYPE WITH ZERO CURRENT SWITCHING AND BIDIRECTIONAL CURRENT OPERATION |
Country Status (1)
| Country | Link |
|---|---|
| FR (1) | FR2608857B1 (en) |
Cited By (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4959765A (en) * | 1988-02-24 | 1990-09-25 | Agence Spatiale Europeenne | DC to DC converter using quasi-resonance |
| WO1990016110A1 (en) * | 1989-06-21 | 1990-12-27 | Deutsche Thomson-Brandt Gmbh | Circuit network |
| EP0429310A2 (en) * | 1989-11-22 | 1991-05-29 | Vlt Corporation | Zero-current switching forward power conversion |
| US5126931A (en) * | 1990-09-07 | 1992-06-30 | Itt Corporation | Fixed frequency single ended forward converter switching at zero voltage |
| US5231563A (en) * | 1990-09-07 | 1993-07-27 | Itt Corporation | Square wave converter having an improved zero voltage switching operation |
| US5235502A (en) * | 1989-11-22 | 1993-08-10 | Vlt Corporation | Zero current switching forward power conversion apparatus and method with controllable energy transfer |
| US5291385A (en) * | 1992-04-02 | 1994-03-01 | Vlt Corporation | Zero-current switching forward power converter operating in damped reverse boost mode |
| WO2001028079A2 (en) * | 1999-10-08 | 2001-04-19 | Lambda Electronics | Drive circuits for synchronous rectifiers |
| US6961253B1 (en) | 1999-10-08 | 2005-11-01 | Lambda Electronics | Drive circuits for synchronous rectifiers |
| CN103684415A (en) * | 2012-09-06 | 2014-03-26 | 上海航天控制工程研究所 | Highly reliable inductive load driving technology for spacecraft |
| US11705820B2 (en) | 2013-07-02 | 2023-07-18 | Vicor Corporation | Power distribution architecture with series-connected bus converter |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7269034B2 (en) | 1997-01-24 | 2007-09-11 | Synqor, Inc. | High efficiency power converter |
| WO1998033267A2 (en) | 1997-01-24 | 1998-07-30 | Fische, Llc | High efficiency power converter |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO1982003302A1 (en) * | 1981-03-20 | 1982-09-30 | Corp Vicor | Forward converter switching at zero current |
-
1986
- 1986-12-19 FR FR8617799A patent/FR2608857B1/en not_active Expired
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO1982003302A1 (en) * | 1981-03-20 | 1982-09-30 | Corp Vicor | Forward converter switching at zero current |
Non-Patent Citations (1)
| Title |
|---|
| IEEE APPLIED POWER ELECTRONICS CONFERENCE AND EXPOSITION, Conference Proceedings 1986, IEEE Power Electronics Council, New Orleans, Louisiana, 28 avril - 1er mai 1986, pages 83-84, IEEE; KWANG-HWA LIU et al.: "Secondary-side resonance for high-frequency power conversion" * |
Cited By (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4959765A (en) * | 1988-02-24 | 1990-09-25 | Agence Spatiale Europeenne | DC to DC converter using quasi-resonance |
| WO1990016110A1 (en) * | 1989-06-21 | 1990-12-27 | Deutsche Thomson-Brandt Gmbh | Circuit network |
| TR24352A (en) * | 1989-06-21 | 1991-09-01 | Thomson Brandt Gmbh | SWITCHING GUEC |
| EP0429310A2 (en) * | 1989-11-22 | 1991-05-29 | Vlt Corporation | Zero-current switching forward power conversion |
| EP0429310A3 (en) * | 1989-11-22 | 1991-10-09 | Vlt Corporation | Zero-current switching forward power conversion |
| US5235502A (en) * | 1989-11-22 | 1993-08-10 | Vlt Corporation | Zero current switching forward power conversion apparatus and method with controllable energy transfer |
| US5231563A (en) * | 1990-09-07 | 1993-07-27 | Itt Corporation | Square wave converter having an improved zero voltage switching operation |
| US5126931A (en) * | 1990-09-07 | 1992-06-30 | Itt Corporation | Fixed frequency single ended forward converter switching at zero voltage |
| US5291385A (en) * | 1992-04-02 | 1994-03-01 | Vlt Corporation | Zero-current switching forward power converter operating in damped reverse boost mode |
| WO2001028079A2 (en) * | 1999-10-08 | 2001-04-19 | Lambda Electronics | Drive circuits for synchronous rectifiers |
| WO2001028079A3 (en) * | 1999-10-08 | 2001-10-25 | Lambda Electronics | Drive circuits for synchronous rectifiers |
| US6961253B1 (en) | 1999-10-08 | 2005-11-01 | Lambda Electronics | Drive circuits for synchronous rectifiers |
| CN103684415A (en) * | 2012-09-06 | 2014-03-26 | 上海航天控制工程研究所 | Highly reliable inductive load driving technology for spacecraft |
| US11705820B2 (en) | 2013-07-02 | 2023-07-18 | Vicor Corporation | Power distribution architecture with series-connected bus converter |
Also Published As
| Publication number | Publication date |
|---|---|
| FR2608857B1 (en) | 1989-05-12 |
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