CN87101677A - Electromagnetic flowmeter - Google Patents
Electromagnetic flowmeter Download PDFInfo
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- CN87101677A CN87101677A CN87101677.XA CN87101677A CN87101677A CN 87101677 A CN87101677 A CN 87101677A CN 87101677 A CN87101677 A CN 87101677A CN 87101677 A CN87101677 A CN 87101677A
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Abstract
An electromagnetic flowmeter measures a signal voltage proportional to a flow rate to be measured, the voltage being generated between a pair of electrodes by applying a magnetic field generated by an excitation current to a fluid. In the electromagnetic flowmeter, a signal voltage generated by exciting an exciting current to electrodes includes two frequency components having frequencies higher and lower than a commercial power, the two frequency components are discriminated to obtain a first output from a higher frequency, and a second output from a lower frequency is obtained by a low-pass filter having a large time constant. Thus, a flow output is obtained by performing a predetermined operation (such as summing, zero point correction, or response correction) on the first and second outputs.
Description
The present invention relates to lean against and add the electromagnetic flowmeter that its flow is measured in a magnetic field on the fluid, relate to the electromagnetic flowmeter of the signal processing method that has improved exciting method and accompany particularly.
Up to now, the mains frequency exciting method with mains supply that will be used for excitation is used in electromagnetic flowmeter.This mains frequency exciting method has the following advantages: (a) its response with piece can reduce production costs; (b) it is insensitive to the influence of the random noise (will be referred to as " noise flows ") that results from suspending liquid or the low conductivity fluid and increase along with the increase frequency of flow.Yet the shortcoming of following this method is if flowmeter is in duty after the long duration, such as one day, has fluctuation its zero point.
This just impels to adopt to have and is mains frequency half or more low-frequency low frequency excitation method that is used for excitation.Just as known in the prior art, the advantage of low frequency excitation method is that the electromagnetic flowmeter with balanced null point can be provided.Yet low excitation frequency is near the frequency of the noise that flows, so flowmeter is just more obvious for higher flow velocity this point to the sensitivity that influences of the noise that flows.Another shortcoming is to be used for reducing flowing the damping of influence of noise with delayed response.
In addition, Electromagnetic Flow is in respect of the trend that reduces electric power in recent years, and this power economy also is necessary for providing the two-wire type electromagnetic flowmeter of electric energy and transmission signals by two lines simultaneously.In this case, reduce the electromotive force of per unit flow velocity.For example, the electromotive force in the low frequency excitation method of prior art is approximately 0.5mv/m/s(millivolt/meter per second), in the two-wire class, drop to 10 μ v/m/s(microvolt/meter per seconds).If the electromotive force that produces is than magnitude of reduction of prior art or more, the influence of the noise that flows will obviously increase, and produce the restriction to the power economy of low frequency excitation method.
There is response fast and with the mains frequency excitation, but the shortcoming of shakiness at zero point is arranged the insensitive advantage of noise that flows.
On the other hand, low frequency excitation has stable zero point, but shortcoming is the sensitivity that influences to the noise that flows.Adopt above-mentioned arbitrary exciting method all can be accompanied by to provide and have balanced null point, response but to the insensitive electromagnetic flowmeter of influence of the noise that flows fast, thus can't eliminate the obstacle of realizing power economy.
So, in view of above-mentioned prior art, fundamental purpose of the present invention provide have the variation of flow response fast, zero point stability but to the insensitive electromagnetic flowmeter of influence of the noise that flows.
Realize the primary structure of above-mentioned purpose according to the present invention, a kind of electromagnetic flowmeter is provided, it comprises: be used to provide have two kinds of different frequencies, i.e. the excitation unit of first frequency and lower second frequency; Be used for signal voltage is differentiated that above-mentioned signal voltage is encouraged by described excitation unit and produces according to flow to produce first demodulating equipment of first output signal on the basis of described first frequency; Be used on the basis of described second frequency described signal voltage is differentiated second demodulating equipment with demodulation; And have large time constant and be used for the output of described second demodulating equipment is carried out low-pass filtering to produce the low-pass filter of second output signal, thereby produce flow output signal by carrying out scheduled operation (that is, adding zero correction or response corrections) with described first and second output signals.
In the accompanying drawings:
Block diagram 1 has shown first embodiment of the present invention's excitation on the mains frequency basis;
Block diagram 2 has shown another embodiment, wherein changes the flow velocity signal feedback method of coming for the embodiment from Fig. 1;
Block diagram 3 has shown that the present invention compensates the 3rd embodiment at zero point on the basis of handling the mains frequency signal;
Block diagram 4 has shown that the present invention has simplified the 4th embodiment of structure of the embodiment of Fig. 3;
Block diagram 5 has shown the 5th embodiment of the present invention that changes signal correction point according to Fig. 4 embodiments shown;
Block diagram 6 is corresponding to Fig. 3, shown mainly by low frequency signal processing unit and response characteristic to be better than the embodiment that the former mains frequency signal processing unit constitutes;
Block diagram 7 has shown and has been better than Fig. 6 and corresponding to the embodiment of Fig. 4;
Block diagram 8 has shown the 8th embodiment with square-wave excitation;
Fig. 9 is the oscillogram of the operation of key drawing 8 embodiments shown;
Figure 10 is an oscillogram of explaining the unit-step response of embodiment shown in Figure 8;
Block diagram 11 has shown the 9th embodiment of the present invention, and the rate of change of noise is monitored and be used to the output of dual-frequency excitation output and low frequency excitation therein; Add up mutually by arbitrary ratio.
Block diagram 12 has shown the of the present invention ten embodiment, the i.e. special construction of Figure 11 embodiments shown;
Block diagram 13 has shown the 12 embodiment, and converting unit wherein is improved from the embodiment of Figure 12;
Block diagram 14 has shown the 13 embodiment of the present invention, therein the amplitude of detection noise and use it for the output signal of exchange double frequency and low frequency excitation;
Block diagram 15 has shown that the 14 embodiment of the present invention changes the distribution of amplification degree of circuit therein to prevent that amplifier or similar device are saturated because of noise;
Block diagram 16 has shown the 15 embodiment of the present invention, and it can get back to normal operating state very soon;
Block diagram 17 has shown the 16 embodiment of the present invention of using microcomputer;
Figure 18 is a clock plot of explaining the operation of Figure 17 embodiments shown;
Figure 19 is the process flow diagram that shows Signal Processing process shown in Figure 180;
Table 20 has shown the computing of the process flow diagram of Figure 19;
Figure 21 has shown the process flow diagram of the speed limit processing procedure of Figure 19;
Figure 22 is a clock plot of explaining the operation with embodiment different with the excitation waveform of the embodiment of Figure 17;
Figure 23 is the process flow diagram that shows signal processing shown in Figure 22;
Figure 24 has shown the computing of the process flow diagram of Figure 23.
With reference to its accompanying drawing the present invention is described below in conjunction with embodiment.Block diagram 1 has shown the embodiment of the present invention on the basis of mains frequency.
This embodiment is corresponding to following situation: wherein the feedback loop of electromagnetic flowmeter converter is arranged on each high and low frequency side.Reference number 10 is represented the waveguide of the transmitter of electromagnetic flowmeter, and its inside surface is lined with insulating material.The electrode that on behalf of detection signal voltage, numeral 11a and 11b use.Numeral 12 representatives are used for producing the field coil in magnetic field, and it will be added in and treat in the fluid measured.Field coil 12 is added with the mains frequency constant current from municipal power constant current source 14, and is superimposed with the about 50/8 low frequency constant current from low frequency constant current source 16.As a result, treat that fluid measured has added and have two kinds of different frequencies (be mains frequency and be its eighth frequency).
On the other hand, signal voltage detects and outputs to prime amplifier 17 by electrode 11a and 11b.Prime amplifier 17 act as the elimination common mode voltage, carry out impedance conversion and voltage signal outputed to node 19 by its output terminal 18.
At node 19, obtain output poor of prime amplifier 17 and multiplier 20, and amplify by amplifier 21.This difference makes synchronous detection by the detuner 22 of constant low-pass filter between comprising hour or sampling keeps.Direct current output after so level and smooth converts the pulse duration frequency signal with constant pulsewidth to by voltage/frequency transducer 23, the part of this signal feeds back to multiplier, a part is exported to low-pass filter 24, and smoothed therein so that it is exported V
LExport to summing junction 25.Multiplier 20 is made of for example switch.One end of this switch is defeated a low frequency comparative voltage that produces at resistance 15 two ends, thus it open or close by the output pulse of voltage/frequency transducer 23, and by its other end output voltage to node 19.On the other hand, come the low frequency comparative voltage of self-resistance 15 to be added on the detuner 22.
In addition, between the output terminal 18 and summing junction 25 of prime amplifier 17, the mains frequency signal processing unit 27 in parallel with low frequency signal processing unit 26 arranged.
Poor between the output voltage of the output voltage of the output terminal 18 that obtains prime amplifier 17 on the node 29 and multiplier 28, and amplify by amplifier 30.The output of amplifier 30 or carry out synchronous detection with the mains frequency comparative voltage that produces on the resistance 13 as reference voltage or sampling is held in level and smooth DC voltage by detuner 31.This DC voltage converts the pulse duration frequency signal with constant pulsewidth to by voltage/frequency transducer 32, and feeds back to multiplier 28.The output voltage of voltage/frequency transducer 32 is smoothed to DC voltage by low-pass filter 32, and this DC voltage is as output V
HOutput to summing junction 25 by Hi-pass filter 34.Summing junction 25 will be exported V
LAnd V
HOutput V is formed in addition
COutput to output terminal 35.
Use this structure, under the common operational circumstances that seldom flow velocity rises and falls,,, have the output V of the low frequency signal processing unit 26 of balanced null point so mains frequency signal processing unit 27 does not respond because there is Hi-pass filter 34
LOutput V as combination
CMain output.On the other hand, because there is the low-pass filter 24 of large time constant,, thereby do not show as output V so the noise that flows is weakened with suitable selection
LFluctuation.In addition, because mains frequency signal processing unit 27 has high excitation frequency, differ greatly with the frequency of the mobile noise that is present in low-frequency range, the influence that makes noise is at output V
HIn do not show.
In other words, under the normal conditions of less flow-rate fluctuation, can provide the electromagnetic flowmeter that is guaranteed balanced null point the insensitive while of influence of the noise that flows again.
Secondly, under the situation that flow rises and falls suddenly, because the large time constant of low-pass filter 24, low frequency signal processing unit 26 does not respond, and because of constant between its hour with by Hi-pass filter 34 outputs, mains frequency signal processing unit 27 responds at once, and will export V
HAs array output V
COutput.
On the other hand, be under zero the situation, not make a difference at flow velocity thereby do not produce the noise that flows.As a result, because there is Hi-pass filter 34, do not drift about the zero point of mains frequency signal processing unit 27, and its output remains zero, so have the output V of the low frequency signal processing unit 26 of balanced null point
LJust as the output V that makes up
COutput.
By the way, if the amplification degree of the amplification degree of whole low frequency signal processing unit 26 and whole mains frequency signal processing unit 27 equates substantially, if and be used for the time constant of whole low frequency signal processing unit 26 of low-pass filtering and the time constant that is used for the whole mains frequency signal processing unit 27 of high-pass filtering equates substantially, array output V then
CFor being level and smooth in the response of stablizing the unexpected fluctuation on the flow velocity.
Fig. 2 has shown second embodiment of the present invention, and it is by embodiment improvement shown in Figure 1 and next.Improved embodiment is corresponding to following situation: wherein use the feedback loop of identical ring as the sensor of electromagnetic flowmeter.In the description of being done, the part with identical function is marked with common numeral below, and their explanation will suitably be omitted.
Each constant current by low frequency constant current source 16 and municipal power constant current source 14 is added on the field coil 12 by resistance 36, so produced the comparative voltage with low frequency and mains frequency combination on resistance 36.
On the other hand, obtain output poor of prime amplifier 17 and multiplier 37 at node 19, and be entered on amplifier 21 and 30.The output of amplifier 21 has only low frequency part after by frequency divider 38 frequency divisions, and voltage input detuner 22 as a comparison, so produce the direct current flow velocity signal corresponding to low frequency excitation on the output terminal of detuner 22.This flow velocity signal is by low-pass filter 24 conduct output V
L1Output to summing junction 39.The output of amplifier 30 has only the mains frequency composition behind frequency divider 38 frequency divisions, and voltage is input to detuner 31 as a comparison, so result from the output terminal of detuner 31 corresponding to the direct current signal of mains frequency excitation.This flow velocity signal is as output V
H1, be imported into summing junction 39 by Hi-pass filter.
On summing junction 39, will export V
L1And V
H1The array output V that additive combination becomes
C1Convert pulse train to by voltage/frequency transducer 40, and feed back to multiplier 37, an output V is arranged with the constant pulsewidth of row
OOutput to output terminal 41.Multiplier is made of switch or like, and it is opened or closed by the output of voltage/frequency transducer 40, and the combination frequency comparative voltage that resistance 36 two ends are produced feeds back to node 19.
In the described in the above structure, those operations that are similar to Fig. 1 situation also can realize by the large time constant of selecting low-pass filter 24.
Fig. 3 has shown the 3rd embodiment of the present invention.In this embodiment, by use mains frequency signal processing unit 27 conduct bases, and add that thereon the low frequency zero point probe is to guarantee the stability at zero point.
The output V of the low-pass filter 33 of mains frequency signal processing unit 27
H' not only be defeated by zero correction node 42, and be defeated by low-pass filter 43.
The output of this low-pass filter 43 is added on the in-phase input end (+) of zero detection amplifier 44, and the output of low-pass filter 24 simultaneously is defeated by on the same amplifier's inverting input (-).The difference of these outputs is calculated by zero detection amplifier 44.As a result, zero detection device 44 has produced the zero signal ε that moves for 27 zero points corresponding to high-frequency signal processing unit at its output terminal
1The effect of zero correction node 42 is with output V
H' and zero signal ε
1Subtract each other, and the result that will subtract each other outputs to output terminal 35.
Low-pass filter 43 has selected large time constant so that it adapts with the time constant of the low-pass filter 24 that is selected in high value, thereby it has the response speed that equates with low-pass filter 24.
In addition, in aforementioned structure, need make amplifying unit 45 and amplifying unit 46 that common amplification degree is arranged, the former is by amplifier 21, detuner 22, and voltage/frequency transducer 23 and multiplier 20 are formed, the latter is by amplifier 30, detuner 31, and voltage/frequency transducer 32 and multiplier 28 are formed.
46 pairs of mobile noises of amplifying unit are insensitive but response is fast, in addition because it handles the mains frequency signal, so slow fluctuation is arranged its zero point.On the other hand, 45 pairs of mobile noises of amplifying unit influences sensitivity, but zero point stability.Because it handles low frequency signal, yet, because wave filter 24 has big time constant, so the output not influence of noise of flowing to low-pass filter 24.The result, if it is the difference of the output of output that is obtained by the low-pass filter 43 that large time constant is arranged by the output of amplifying unit 46 and low-pass filter 24 is calculated with zero detection amplifier 44, then 46 that produce, represent the zero signal ε that moves zero point by amplifying unit
1Can show at detecting amplifier 44 output terminal at zero point, though response is slower.
On the other hand, have the zero point of fluctuation but respond the signal of fast mains frequency signal processing unit 27 and corresponding to the zero signal ε of zero point fluctuation
1All import zero correction node 42, thereon with these signal subtractions, so on exit point 35, obtained having quick response but do not have any mobile noise and eliminated the flow velocity signal of its zero point fluctuation.
Fig. 4 has shown the 4th embodiment of the present invention.
Though amplifying unit 45 will be done consistently with 46 linearity in embodiment shown in Figure 3, in the embodiment of Fig. 4, this requirement is removed with simplified structure.
Amplifying unit 47 is by amplifier 30, detuner 31, and voltage/frequency transducer 32, multiplier 28 and zero correction node 48 constitute.Zero correction node 48 defeated output and the zero signal ε that multiplier 28 is arranged
2, and obtain the poor of them at zero correction node 48, output to node 19.
Because 53 of zero detection devices are used for suppressing zero point, on the whole as a kind of differential amplifier work, so its linearity is unessential.In addition, because common fluctuating at zero point is slowly in the mains frequency, can the smooth flow noise so the zero detection device can have slow response.
Fig. 5 has shown the 5th embodiment of the present invention.This embodiment is by shown in Figure 4 improved, as has changed zero signal ε
2The correction node.
The output of the detuner 31 of amplifying unit 54 and zero signal ε
3Be input to zero correction node 55, the signal that obtains after they subtract each other there outputs to voltage/frequency transducer 56.The amplification degree of this voltage/frequency transducer is hanked and the equating of voltage/frequency transducer 32.
Zero detection device 58 is by multiplier 57, differential amplifier 50, and detuner 22, low-pass filter 24 or the like constitutes.
Fig. 6 has shown an embodiment, wherein with a low frequency signal processing unit as its major part improving its response characteristic, this point can with Fig. 3 in compare as major part with the mains frequency signal processing unit.
The output of the low-pass filter 24 of the balanced null point of low frequency signal processing unit 26 is passed to response corrections node 59 and is added on the end points of echo probe amplifier 60.The defeated output that the mains frequency signal processing unit 27 of quick response is arranged of another end points of echo probe amplifier 60, and output poor of getting above-mentioned output and low-pass filter 24 output it to response corrections node 59 by Hi-pass filter.
The effect of response corrections node 59 is that the output of Hi-pass filter 61 and low-pass filter 24 is subtracted each other, and outputs it to output terminal 35 again.
The output of low frequency signal processing unit 26 has stable zero point but shows slow response.In contrast, the output of mains frequency signal processing unit 27 has unstable zero but shows fast response.
As a result, the output of the difference gained of the output by getting low- pass filter 24 and 33 on echo probe amplifier 60 comprises DC component, but the response compensating signal V by DC component is obtained after with Hi-pass filter 61 filtering
CTo not contain any DC component, but have high-quality zero stability and fast response.So, response corrections circuit 59 usefulness response compensating signal V
CCompensated the low-pass filter 24 of slow-response, thereby made it have response and stable zero point fast.
The embodiment that Fig. 7 has shown than the improvement of Fig. 6, it mainly is made of the low frequency signal processing unit, comparison diagram 4, it mainly is made of the mains frequency signal processing unit.
The defeated outputs that voltage/frequency transducer 23 is arranged of multiplier 62, and be used in the mains frequency comparative voltage modulation that obtains on the resistance 13 it, the input end exporting to echo probe amplifier 63 that will modulate then.Echo probe amplifier 63 calculates and output is added in modulation on the one input end and exports and be added in poor between the output of the prime amplifier 17 on another input end.The output of echo probe amplifier 63 is used in the mains frequency comparative voltage demodulation that obtains on the resistance 13 by detuner 31, thereby to the response compensating signal V of response corrections node 64 outputs corresponding to the signal voltage of mains frequency component
C'.
The low frequency output of low-pass filter 24 is added on the response corrections node 64, and with responding compensating signal V
C' proofread and correct its response, until outputing on the voltage/frequency transducer 23.If response compensating signal V
C' so be added in the inside of low frequency signal processing unit 26, then by echo probe amplifier 63, detuner 31, the amplification degree of the response detector that multiplier 62 or the like constitutes will not cause error.
Fig. 8 has shown the 8th embodiment of the present invention, and wherein excitation is realized by square wave.
The field coil 12 defeated exciting current I that have from magnetizing exciter 65
f, above-mentioned magnetizing exciter 65 constitutes with following form.
Reference voltage E
1Pass through switch SW
1Be added to amplifier Q
1In-phase input end (+) on, its output terminal is connected to transistor Q
2Base stage on.This transistor Q
2Emitter pass through resistance R
fCOM joins with public ground, it also with amplifier Q
1Inverting input (-) join.Field voltage E
SBe added in public ground COM and transistor Q
2Collector between, then switch SW between them
2And SW
3Series circuit and switch SW
4And SW
5Series circuit, the latter is in parallel with the former successively.Field coil 12 is connected on switch SW
2And SW
3Between node and switch SW
4And SW
5Between node between.These switch SW
1, SW
2And SW
5, with SW
3And SW
4Connection respectively by timing signal S
1, S
2And S
3Control.
On the other hand, signal voltage is detected and is output to prime amplifier 17 on electrode 11a and 11b.The effect of prime amplifier 17 is to eliminate common mode voltage, carries out impedance conversion and with signal voltage or pass through switch SW
7Perhaps by inverting amplifier Q
3And switch SW
8Series circuit be added to have hour between on the low-pass filter 67 of constant.
Voltage signal on node 66 and then or pass through switch SW
9Perhaps by inverting amplifier Q
4And switch SW
10Series circuit be added to have hour between on the low-pass filter 68 of constant.Switch SW
7, SW
8, SW
9And SW
10Respectively according to the timing signal S that comes self-timer 69
7, S
8, S
9And S
10Open or close.The output of the output of low-pass filter 67 and low-pass filter 68 is respectively by large time constant low-pass filter 24 and variable-gain amplifier Q
5With the series circuit of Hi-pass filter 34 in summing junction 25 additions, thereby be passed to output terminal 35 by low-pass filter 70 output signal of will suing for peace.
By the way, variable-gain amplifier Q
5Be to be used for the output voltage V of adjustment with balanced low pass filter 24
LThe output voltage V of Hi-pass filter 34
H.
In aforementioned structure, each constant so select to make by low-pass filter 24 and comprise node 66 and the low frequency loop of summing junction 25 and by Hi-pass filter 34 and comprise node 66 and summing junction 25 radio circuit transition function and be 1.In fact, by adjusting variable-gain amplifier Q
5Gain be enough to the time constant of balanced low pass filter 24 and Hi-pass filter 34 and the signal voltage on each loop of balance.
The operation of embodiment shown in Figure 8 is described below in conjunction with oscillogram shown in Figure 9.
Shown in Fig. 9 (a), timing signal S
1Repeat its on/off (ON/OFF), thereby make reference voltage E
1Be added to amplifier Q
1In-phase input end (+) go up or do not add up.On the other hand, switch SW
2And SW
5With switch SW
3And SW
4Respectively by timing signal S
2The low frequency wave and the timing signal S of (shown in Fig. 9 (b))
2The low frequency wave of (shown in Fig. 9 (c)) is alternately opened, thereby makes exciting current I
fFlow through, shown in Fig. 9 (d), low frequency wave (cycle is 2T) and high frequency waves (cycle is 2t) are arranged among the I.Composition.
Signal voltage on node 66 is by Fig. 9 (e) with the timing signal S 9(f)
7And S
8Sampling, thereby in switch SW
7Output terminal obtain the voltage shown in Fig. 9 (g).This voltage outputs to summing junction 25 by low-pass filter 67 level and smooth backs by low-pass filter 24.
In addition, the signal voltage on the node 66 is by as Fig. 9 (h) with the timing signal S 9(i)
9And S
10Timing sampling.As a result, the signal voltage shown in Fig. 9 (j) is in switch SW
9Output terminal output, its level is by variable-gain amplifier Q
5Adjust, the back outputs to summing junction 25 by Hi-pass filter 34.
After added signal voltage on the summing junction 25 is level and smooth by low-pass filter 70, export to output terminal 35.In this case, if the transition function of low-pass filter 24 is expressed as 1/(1+T
1S), the transition function of Hi-pass filter 34 is expressed as T simultaneously
2/ (1+T
2S), then select separately time constant T
1And T
2Satisfy T
1=T
2, the transition function sum that makes them is 1.
If each time constant of selecting satisfies with co-relation, then the output signal voltage V of low-pass filter 24 when the signal voltage step changes
LOutput signal voltage V with Hi-pass filter 34
HVariation will be shown in Figure 10 (a).As a result and output V
OTo not show as step shown in Figure 10 (b) changes with having error.
On the contrary, be not under 1 the situation in each transition function sum, when the signal voltage step changes, the output signal voltage V of low-pass filter 24
LOutput signal voltage V with Hi-pass filter
HVariation will be shown in Figure 10 (c).As a result and output V
O' will shown in Figure 10 (d), show as and comprise error ε
1Variation.
Say that by the way low-pass filter 24 and Hi-pass filter 34 are not limited to elementary wave filter, and can be 1 bank of filters for any its transition function sum.On the other hand, step response is not being required under the accurate situation that the transition function sum does not then need accurate adjustment.
Figure 11 has shown the 9th embodiment of the present invention, and it has utilized the advantage separately of dual-frequency excitation and low frequency excitation.
In general, entering not only has a mobile noise in the electromagnetic flowmeter, and has magnetizing exciter to bring the differential noise into to the capacitive coupling of electrode, thereby under the situation of high frequency excitation, slow (or in) fluctuating takes place.
On the contrary, the advantage of low frequency excitation is that it has stable zero point, and insensitive for the differential noise, but its shortcoming is that it has response to the noise that flows, because its frequency range belongs to the frequency range of the noise that flows.
On the other hand, as shown in Figure 8, the advantage of situation with dual-frequency excitation of two low frequencies and high frequency is that it has stable zero point and also is stable to the noise that flows, this can understand from the description of being done so far, but because it has high-frequency signal processing unit, so its shortcoming is long stability is arranged but a little less than the stability to moderate relief for the differential noise.
Signal do not have under the situation that the differential noise exists yet or only exists under the situation of differential noise both there being mobile noise, even can be obtained having the output of balanced null point by the low frequency signal processing unit processes yet.On the contrary, having under the situation of mobile noise, having the output of balanced null point even can with dual-frequency excitation side processing signals the time, obtain.In addition, when fluid flowed, mobile and differential noise all existed.As a result, even cause near zero point fluctuating (with moderate relief together), the fluctuating at these zero points just to cover and by time average by the differential noise in considerable time the zero point of dual-frequency excitation side, thereby they do not cause tangible error yet.
So the best output of the embodiment of Figure 11 is to obtain by mobile noise magnitude and the summation ratio between appropriate change lower frequency side and the double frequency side that the surveying tape lower frequency side is exported.
The signal S that comprises the suspension noise
LIn output, survey from the low-pass filter 67 of lower frequency side, and its change component Δ S
LThen draw and output to absolute value circuit 72 by Hi-pass filter 71.Absolute value circuit 72 is got the absolute value of above-mentioned change component Δ S | Δ S
L| and it is added to a end to subtracter 74 as output e Δ by low-pass filter 73.The other end of subtracter 74 is failed reference voltage E
2Thereby, the voltage difference that obtains is added to multiplier 25.Because select output e Δ to satisfy O≤e Δ≤E at this
2So, as the change component Δ S of signal S
LBe added to the voltage decreases on the multiplier 75 when becoming big.Multiplier 75 number of winning the confidence S
LOutput on the end of ratio totalizer 76 with the product of the output of subtracter 74 and with it.
On the other hand, multiplier 77 is got the array output V of summing junction 25
CWith the product of the output e Δ of low-pass filter 73, and it is added on the other end of totalizer 76.This relation can be expressed from the next:
V
O＝kV
C+（1-k）S
L
Wherein alphabetical k representative is by the ratio of output e Δ control.
Totalizer 76 will be sued for peace by the output of multiplier 76 and 77 respectively, and it is exported V as flow velocity
OOutput to output terminal 35 by low-pass filter 70.
As a result, at signal S
LChange component Δ S
LWhen becoming big, the output of low-pass filter 73 also becomes greatly, thereby the output of multiplier 75 is diminished and makes the output of multiplier 77 become big.This has reduced the ratio of low frequency output to the output of double frequency side.
Like this, according to the present invention, best output can be obtained with the ratio between the output of automatic change double frequency side and lower frequency side by the fluctuating of surveying suspension noise or similar noise at lower frequency side.
Figure 12 has shown the of the present invention ten embodiment, has wherein simplified the structure of embodiment shown in Figure 11.
The output e Δ of low-pass filter 73 is added on the input end of comparer 78, and its another input end is failed reference voltage E
3So failing has signal S
L(being low frequency signal) and array output V
CThe switch SW of (being the signal of double frequency side)
11Just controlled by the output of comparer 78.When the output e of low-pass filter 83 Δ surpasses reference voltage E
3The time, switch SW
11Get to array output V
CSide.Otherwise switch SW
11Get to low frequency signal S
LOn one side.
Figure 13 has shown the 12 embodiment of the present invention, wherein when switch open, is added with a hysteresis on the embodiment shown in Figure 12.
In this embodiment, the output of comparer 78 and its output by monostable circuit 79a be added to " or " (OR) on the input end of circuit 79b, above-mentioned OR circuit is then used its output control switch SW
11
Like this, in the time interval of the preset width of the pulse that produces by monostable circuit 79a, even the output of comparer 78 changes switch SW
11Will be in closed condition, thereby can prevent that vibration from taking place.
Figure 14 has shown the 13 embodiment of the present invention, and wherein the break-make of double frequency side and lower frequency side is to be controlled by the output level of surveying lower frequency side.
In the embodiment of Figure 11 to 13, be to remove gauge tap SW in front by the variation of surveying the lower frequency side signal
11.And in this embodiment, detection be the signal absolute value of lower frequency side.An one input end is failed reference voltage E
4The other end of comparer 80 defeated signal S arranged
L, and with its output control switch SW
11Break-make low frequency or double frequency side.As signal S
LBe higher than reference voltage E
4The time, switch SW
11Open the double frequency side to produce the output V of combination
C
Figure 15 has shown the 14 embodiment of the present invention, and the distribution of amplification degree that wherein changes circuit is saturated to prevent any amplifier that is caused by noise.
The trend of electromagnetic flowmeter is to reduce exciting power with the realization power economy, but this just descends its signal voltage because of reducing exciting power.In order to compensate this point, the trend of the enlargement factor that strengthens circuit is just arranged.On the contrary, because similar noises such as suspension noise are the constants that is independent of exciting power, so electromagnetic flowmeter will have reacting weak trend such as noises such as suspension noises.So in the present embodiment, the distribution of the enlargement factor of circuit becomes according to noise, to avoid the saturated of circuit.
Noise monitor 83 constitutes by the following method.The output of prime amplifier 17 is taken absolute value by absolute value circuit 84, and outputs to low-pass filter 85.The output of low-pass filter 85 is added to promptly that an input end is defeated to have ginseng to consider voltage E
5Comparer Q
7Another input end on, output to also that an input end is defeated a reference voltage E
6Comparer Q
8Another input end, thereby go up the level can differentiate this output.Comparer Q
7And Q
8Output be added to nondisjunction (NOR) door Q respectively
9Input end, the nondisjunction value of calculating them is with at NOR gate Q
9Output terminal produce control signal S
14By phase inverter Q
11To comparer Q
7And Q
8Output carry out anti-phase and output that obtain is added to NOR gate Q respectively
10Input end, and at NOR gate Q
10The last nondisjunction value of calculating them is to produce control signal S at output terminal
13In addition, with comparer Q
7Output as control signal S
12These control signals have detected the noise magnitude that is created in prime amplifier 17 output terminals, thereby they control each switch to change the enlargement factor of variable-gain amplifier 81 according to noise magnitude.
On the other hand, as follows, compensator-amplifier unit 82 is to constitute with variable-gain amplifier 81 similar methods.The output terminal of prime amplifier 17 passes through resistance R
i' be linked to amplifier Q
6' inverting input (-), and amplifier Q
6In-phase input end (+) be coupled on the COM of common electrical site.Output terminal and amplifier Q at prime amplifier 17
6' output terminal between in parallel: resistance R
1' and switch SW
12' series circuit; Resistance R
2' and switch SW
13' series circuit; Resistance R
3' and switch SW
14' series circuit.Switch SW
12', SW
13' and SW
14' respectively by control signal S from noise monitor
12, S
13And S
14Control.Each constant of element is chosen as and compensator-amplifier unit 82 is changed compensate the enlargement factor of variable-gain amplifier 81, and keeping total enlargement factor is constant.Like this, enlargement factor becomes according to the amplitude of noise, thus avoided that noise causes saturated.
Figure 16 has shown the 15 embodiment of the present invention, and it can be returned to normal operating state very soon.
Because dual-frequency excitation needs the low-pass filter of large time constant at its lower frequency side, so its problem is maybe to abate the noise to need considerable time when making it be returned to normal condition by up-set condition when adding power supply after entering noise.This problem has been solved by the present embodiment.
Time constant transducer 86 is made of following method.Hour between constant low-pass filter 67 output terminal and the summation end points 25 between, two end points of connecting are by switch SW
15The transistor Q of short circuit
12Capacitor C
1Be associated in transistor Q
12Output terminal and common electrical site COM between.Transistor Q
12Internal resistance by control signal S
15Control, transistor Q
12And capacitor C
1The time constant of low-pass filter 87 is changed.
Capacitor C
2Be connected on variable-gain amplifier Q
5Output terminal and summing junction 25 between.In capacitor C
2Output terminal and common electrical site COM between joining transistor Q
13, Q
13By switch SW
16Short circuit, its internal resistance is by control signal S
15Control.Transistor Q
13And capacitor C
2Constitute Hi-pass filter 88 together.
Noise monitor 89 is made of following method.The output of prime amplifier 17 both had been added to that an input end is defeated a reference voltage E
7Comparer Q
14Another input end on, be added to also that an input end is defeated a reference voltage E
8Comparer Q
15Another input end on, comparer Q
14And Q
15Output be added to OR-gate Q respectively
16Each input end on.OR-gate Q
16Output be added to an input end of comparer 17 by low-pass filter 90, another input end of comparer is defeated reference voltage E
9, output terminal is linked on the monostable circuit 91.The output of monostable circuit 91 is by phase inverter Q
18Output to after anti-phase on the low-pass filter 92.Low-pass filter 92 is by resistance R
4And capacitor C
3Constitute, and resistance R
4Two ends by diode D
1Short circuit produces control signal S with the output terminal at low-pass filter 92
15
When the output of prime amplifier 17 does not almost have noise, OR-gate Q
16Output be in low level state, comparer Q
17Output also be in low level.As a result, the output of monostable circuit 91 is in low level, but the output of low-pass filter 92, i.e. control signal S
15At high level.This state is added to transistor Q by selector switch 93
12And Q
13On, their internal resistance is remained on the high level state.
Subsequently, if surpass reference voltage E at the noise of the output terminal of prime amplifier 17
7And E
8, then high level is got in the output of low-pass filter 90.As a result, as long as there is comparer Q in noise
17Output remain on the high level.
Yet, if because noise disappears comparer Q
17Output will drop on the low level, produce pulse so monostable circuit 91 detects behind the negative edge in its output place with high level and predetermined length.This pulse is by phase inverter Q
18Be added to low-pass filter 92 after anti-phase, its output or control signal S
15Once drop to low level, be returned to high level with the speed of determining by the time constant of low-pass filter 92 then.
As a result, when noise disappears, transistor Q
12And Q
13Internal resistance once reducing then gradually and rising, quicken so be returned to stable state after noise disappears.
Power state detection device 94 constitutes by the following method.Reference letter E
10Represent power supply, its electric energy is to pass through switch SW
17Be added to resistance R
5And capacitor C
4On.In resistance R
5And capacitor C
4Between node on voltage be added to comparer Q
19An input end on, comparer Q
19Another input end defeated reference voltage E arranged
11OR-gate Q
20Defeated respectively output and the comparer Q that monostable circuit 91 is arranged of input end
19Output, and with its " or " output opens or the switch SW of shut-in time constant converting device 86
15And SW
16
Because resistance R when supply voltage is connected
5And capacitor C
4Between node be low level, so comparer Q
19Output be in high level, switch SW
15And SW
16Be in the state of " unlatching ".Yet, when passing through by resistance R
5With voltage C
4The predetermined time interval determined of time constant after, comparer Q
19Output transfer low level to, so switch SW
15And SW
16Be closed.
As a result, in the predetermined time interval that begins for the moment from power connection, the time constant of time constant transducer 86 is so short, makes the very fast recovery of normal duty.
And when noise disappeared back recovery normal operating conditions, the pulse of high level was by OR-gate Q
20Provide at interval with preset time by monostable circuit 91 and to make switch SW
15And SW
16Open.
In selector switch 93, control signal S
15And resistance R
5With capacitor C
4Between node on voltage be added to comparer Q respectively
21Input end with its output control switch SW
18This switch SW when power connection
18In 1. side, and when being in stable state, reach 2. side.
Figure 17 has shown that the present invention uses the 16 embodiment of microcomputer.
The output of prime amplifier 17 converts digital signal to by A/D converter (A/D) 95 and A/D converter (A/D) 96, and they store in the random-access memory (ram) 97 by bus 99 again.ROM (read-only memory) (ROM) 98 stores preset program and initial value.Under processor (CPU) 100 controls, according to the running program commence operation that is stored among the ROM98, the result is stored among the RAM97.
According to the running program that is stored among the ROM98, CPU100 is used for determining exciting current I by bus 99 to timing signal output port (TO) 103 outputs
F1(or I
F2) the markers of waveform.According to this markers, 103 outputs of timing signal output port are used to control the timing signal S of exciting current
22, S
23, S
24And S
25Respond these timing signals S
22, S
23, S
24And S
25, the switch SW of exciting current 104
2, SW
3, SW
4And SW
5Be open and close.
In addition, export timing signal Sh according to the timing signal output port 103 of CPU indication to A/D converter 96, so that the output of prime amplifier 17 is taken a sample.
On the other hand, according to the running program that is stored among the ROM98, CPU uses the data be stored among the RAM97 to carry out predetermined operation, and the result that will operate is stored among the RAM97, by bus 99 and D/A 105 flow velocity is outputed to output terminal 106.
In addition, below with reference to markers Figure 18, flow process Figure 19, computing Figure 20 and flow process Figure 21 describe the embodiment among Figure 17.
The system clock pulse Sh that output place of the frequency divider 102 that shows at Figure 17 obtains has the waveform shown in Figure 18 (a), and transports to CPU100.
In the step 1 of Figure 19, CPU100 exports timing signal output port 103 to target markers when the switch of excitation waveform is represented in bus 99 outputs synchronously according to the interruption markers (Figure 18 (g)) that is stored in the predetermined operation programs homologous ray clock Sh among the ROM98.
In step 2, timing signal output port 103 receives after the above-mentioned switch markers respectively with timing signal S
25(Figure 18 (b)), S
24(Figure 18 (c)), S
23(Figure 18 (d)) and S
22(Figure 18 (e)) exports to the switch SW of magnetizing exciter 104
5, SW
4, SW
3And SW
2Respond these timing signals, magnetizing exciter 104 has the exciting current I of waveform shown in Figure 18 (f) to field coil 12 outputs
F1This excitation waveform has markers and counts i=0 to 15, and it constitutes the one-period (shown in Figure 18 (i)) that repeats, and shown in Figure 18 (h), the n cycle portions of this excitation waveform is positioned at central authorities.The waveform that have excitation waveform low frequency and high frequency waveforms multiply each other.
Operation proceeds to step 3 subsequently.Step 3 to 6 corresponding to by A/ D converter 96 and 95 the input data process.
In step 3, shown in Figure 18 (j), under the control of CPU100 at each cycle and system clock pulse Sh(Figure 18 (a)) synchronously the data by A/D converter 96 input be stored in by bus 99 among the tentation data zone Hi of RAM97.
Then, operation proceeds to step 4, claims when this judges input whether number i is 0.Then, if be that "No" (NO) transition of operation is to step 6, if be "Yes" (YES) then transfer to step 5.
In step 5, by timing signal S1(Figure 18 (k) from timing signal output port 103) put on during fixed sampling, shown in Figure 18 (l), be stored in the tentation data zone of RAM97 by bus 99 by CPU100 control from the data of A/D converter 95 inputs ... L
0(n-1), L
0(n), L
0(n+1) ... or the like in, proceed to step 8 until operation.
Then, in step 7, putting on by from the fixed sampling of the timing signal (Figure 18 (k)) of timing signal output port 103 output the time, be stored in the tentation data zone of RAM97 by the control of the data of A/D converter 95 inputs such as Figure 18 (l) CPU100 that is shown in down through bus 99 ... L
1(n-1), L
1(n), L
1(n+1) ... or the like in, proceed to step 8 until operation.
In step 8, judge whether markers is counted i is odd number.If be that "Yes" then transition of operation are to step 12, if for "No" then transfer to step 9.
In step 9, the demodulation high frequency waves.For carrying out this demodulation, be stored in data Hi among the RAM97 under the control of CPU100 shown in Figure 18 (m) the time put on being stored among the ROM98 and being shown in a row high frequency demodulation e among Figure 20
HiShown in operational formula calculate, the result of computing is stored among the RAM97.By this demodulation, the electrochemical noise that is created on electrode 11a and the 11b is eliminated, and the differential noise is maintained on the constant level, thereby does not cause error.By the way, the constant A that appears among Figure 20 is expressed from the next, if tee
cExpression differential or integration constant, alphabetical Δ T simultaneously
cRepresentative graph 18(f) the running time interval shown in, then:
A＝T
c/（T
c+ΔT
c）
In step 10, carry out speed limit.This step is not indispensable, but this is described for the convenience of narration later on.The function of this operation is that significantly noise is limited in the predetermined value, since fine for the response of dual-frequency excitation high frequency side, so above-mentioned noise can be mixed.
This will describe in conjunction with Figure 21 in the back.In Figure 21, judge the upper limit of noise in steps A.Judge present operation result e at this
HiWhether greater than the operation result e that the speed limit width e is added to the front at high frequency side
Hi-2The value of last back gained.If "No", then operation judges is Zheng Chang and is transferred to step C, if be "Yes" then be transferred to step B.
At step B, with the speed limit width e
RBe added to the operation result e of front
Hi-2Last gained sum is as present value output, and its amplitude is restricted.
At step C, judge the lower limit of noise.Judge that at this whether operation result is greater than the operation result e from the front high frequency side
Hi-2In deduct the speed limit width e
RThe result.If for "No" then operation judges for normal and be transferred to step 11, if for "Yes" then be transferred to step D.
At step D, by the operation result e of front
Hi-2In deduct the speed limit width e
RThe difference of back gained is exported its amplitude as present value and also is controlled.
Transition of operation is to step 11 subsequently.At this High frequency filter F that carries out at high frequency side
Hi
For this filtering, be stored in the data e among the RAM97
HiUnder the control of CPU100, be used for being stored among the ROM98 with the filtering result of front and by the High frequency filter F of Figure 20
HiRow in the operation of operational formula, and the result of computing is stored among the RAM97.
Subsequently, operation proceeds to step 12.Judge in step 12 whether markers is counted i is 0 or 8.If for "Yes" then operate and proceed to step 13, if be "No" then arrive step 15.
In step 13, carry out the low frequency demodulation.Demodulation for this reason is stored in RAM97 ... L
0(n-1), L
0(n), L
0(n+1) or the like and ..., L
1(n-1), L
1(n), L
1(n+1) or the like the data among are used for realizing existing ROM98 and by the low frequency demodulation e of Figure 20 under the control of CPU100
LiRow shown in the operation of operational formula, and operation result existed among the RAM97.Say that by the way constant B can be expressed as in Figure 20:
B＝ΔT/（ΔT+T）
On step 14, carry out the low frequency filtering F of lower frequency side
Li
Filtering for this reason is stored in the data e among the RAM97
LoAnd e
LBUnder the control of CPU100, be stored in the low-pass filtering F that reaches among the ROM98 by Figure 20 with the filtering result of front
LiThe operation of the operational formula shown in the row, and operation result is stored among the RAM97.
In this step, judge whether markers is counted i is odd number.Move to step 16 as then operating, as be that "No" is then to step 17 for "Yes".
Carry out addition in step 16.Be stored in the F as a result of the High frequency filter among the RAM97
HiF as a result with low frequency filtering
LiBe used for being implemented under the CPU100 control be stored among the ROM98 and by the summation e of Figure 20
AThe operation of the computing formula shown in the row, and operation result is stored among the RAM97, proceed to step 18 until operation.
In step 18, wait for until the next one and interrupting, when the next one interrupts the markers arrival, re-execute flow process from step 1 to step 18.
Under the situation of the wave form varies of exciting current, signal processing operations will be described with reference to Figure 22 to 24.Because these operations are identical with the cardinal principle of Figure 17 to 22, so only do not described in conjunction with not existing together.
In Figure 22, timing signal S
22' ripple do to be different from Figure 18's.As a result, exciting current I
F2Waveform be different among Figure 18, and be get low frequency and high frequency waveforms and waveform.This has changed signal processing a little.
In the process flow diagram of Figure 23, be different from the judgement that Figure 19 part only limits to step 8, step 9,11,13 and 14 arithmetic operation and the judgement of step 15.
The operation of step 9 be shown in Figure 22 (m) the time put on and utilize the data be stored among the RAM97 to realize being stored among the ROM98 and by the high frequency demodulation e of Figure 24
HiShown operational formula, operation result deposit RAM97 in by bus 99 again.
The operation of step 11 is to utilize the data be stored among the RAM97 to realize being stored among the ROM98 and by the high-pass filtering F of Figure 24
H2' shown in operational formula, operation result deposits RAM97 in by bus 99 again.The operation of step 13 be shown in Figure 22 (n) the time put on to utilize and be stored in RAM97 ... L
0' (n-1), L
0' (n), L
0' (n+1) ... or the like and ... L
1' (n-1), L
1' (n), L
1' (n+1) data in waiting realize existing among the ROM98 and by the low frequency demodulation e of Figure 24
LiThe operational formula of ' expression, and operation result e
Li' deposit RAM97 in by bus 99 again.
The operation of step 14 is to utilize the data be stored among the RAM97 to realize existing among the ROM98 and by the low-pass filtering F of Figure 24
Li' shown in operational formula, its operation result deposits RAM97 in by bus 99 again.
In step 16, use high-pass filtering F
Hi' and low-pass filtering F
LiResults added obtain and export e
0
By the way say, do not relate to the frequency of exciting current so far in the description of being done.Yet, because electromagnetic flowmeter is handled small-signal, so these signals may be superimposed on the signal voltage from power supply.The result, as long as high frequency is not chosen in even number/one who is chosen as mains frequency on the frequency that equates with the integral multiple of mains frequency with low frequency, then eliminate by the low-pass filter of back level by the beat frequency that produces between mains frequency or its even harmonic frequency and excitation frequency.
As the top detailed description of doing, according to the present invention, by the device that constitutes constitute the output of the low frequency signal processing unit that comprises low-pass filter and comprise the output of high frequency processing unit of high pass filtering device and summing unit in one, can provide have for the fluctuating of flow response fast, zero point stability but to the insensitive electromagnetic flowmeter of fluctuating of the noise that flows.
Claims (17)
1, by apply the electromagnetic flowmeter of its flow of magnetic-field measurement to fluid, comprising:
Be used to provide have two kinds of different frequencies, i.e. the excitation unit in the magnetic field of first frequency and lower second frequency;
Being used on described first frequency basis differentiated first demodulating equipment with output signal voltage, and above-mentioned signal voltage produces by described excitation unit excitation and according to flow;
Be used for the output of described first demodulating equipment is carried out the high pass filtering device of high-pass filtering;
On the basis of described second frequency, described signal voltage is differentiated second demodulating equipment with demodulation;
Be used for the output of described second demodulating equipment is carried out the low-pass filter of low-pass filtering;
Be used for the synthetic synthesizer of algebraically is carried out in the output of described high pass filtering device and described low-pass filter.
2, according to the electromagnetic flowmeter of claim 1, further comprise:
Be used to detect the noise detection device of fluctuating of the described signal voltage of described second demodulating equipment output; And
Be used for the proportional control apparatus of summation ratio that output with described noise detection device changes the output of described synthesizer and described second demodulating equipment.
3, according to the electromagnetic flowmeter of claim 1, further comprise:
Be used for the absolute value of output of more described second demodulating equipment and the comparison means of level setting voltage; And
Switchgear, when described signal voltage was no more than predetermined level, above-mentioned switchgear was opened described second demodulating equipment, one side, and above-mentioned switchgear is then opened described synthesizer one side when described predetermined level is exceeded.
4, according to the electromagnetic flowmeter of claim 1, further comprise:
Be used for the absolute value that time of the output of more described second demodulating equipment changes and the comparison means of level setting voltage;
Switchgear, when described signal voltage is no more than predetermined level, described second demodulating equipment of above-mentioned switch open one side, above-mentioned switchgear is then opened synthesizer one side when surpassing described predetermined level.
5, according to the electromagnetic flowmeter of claim 1, further comprise:
Be installed in the lagging device of the outgoing side of described comparison means.
6, according to the electromagnetic flowmeter of claim 1, wherein said first demodulating equipment, described high pass filtering device; Described second demodulating equipment, described low-pass filter and described synthesizer lump together and utilize microcomputer to constitute arithmetic unit.
7, according to the electromagnetic flowmeter of claim 1, the transition function of wherein said high pass filtering device and described low-pass filter is made it and is about 1 by selected like this.
8, according to the electromagnetic flowmeter of claim 1, wherein described first kind of frequency of Xuan Zeing is not equal to the integral multiple of mains frequency, simultaneously second kind of frequency of Xuan Zeing even number/one that is mains frequency.
9, according to the electromagnetic flowmeter of claim 1, further comprise:
Be placed in the gain regulator that is used to adjust gain of described high pass filtering device one side or described low-pass filter side, make the output separately of described high pass filtering device and described low-pass filter can be about equally.
10, according to the electromagnetic flowmeter of claim 1, further comprise:
Be used for the variable-gain multiplying arrangement that variable-gain amplifies described signal voltage and outputs it to described first and second demodulating equipments;
Be positioned on the amplification compensation system of level behind the described synthesizer, be used for variation according to the described variable-gain device of the compensating for variations of described enlargement factor enlargement factor;
Noise detection device both had been used to detect the pace of change that is included in the noise among the described signal voltage and also had been used to detect its amplitude, made the enlargement factor that can be controlled described variable-gain multiplying arrangement and described compensation system by the output of described noise detection device.
11, according to the electromagnetic flowmeter of claim 1, further comprise:
Be associated in the speed limiting device between described first demodulating equipment and the described high pass filtering device, be used for the fluctuating of described signal voltage is limited in the predetermined fluctuating width.
12, according to the electromagnetic flowmeter of claim 1, further comprise:
Noise detection device, be used for falling into the moment output time constant control signal of predetermined allowed band to reduce the time constant of described high pass filtering device and described low-pass filter detecting the noise that is included in described signal voltage, and when getting back to normal condition, increase described time constant;
Change the time constant modifier of the time constant of described high pass filtering device and described low-pass filter with described time constant control signal.
13, according to the electromagnetic flowmeter of claim 1, further comprise:
Be used to detect the Power supply detector of the moment of energized with output time constant control signal, above-mentioned time constant control signal is reducing time constant in one period schedule time in moment of power connection; And
Change the time constant changeable device of the time constant of described high pass filtering device and described low-pass filter with described time constant control signal.
14, by apply the electromagnetic flowmeter of its flow of magnetic-field measurement to fluid, comprising:
Be used to provide have two kinds of different frequencies, i.e. the excitation unit in the magnetic field of first kind and lower second kind of frequency;
Be used on the basis of described first kind of frequency identification signal voltage and with its signal processing apparatus as first signal output, above-mentioned signal voltage produces by described excitation unit excitation and according to flow velocity;
Zero-crossing detecting device, be used to get and second kind of frequency component of the voltage of described first signal correction and described signal voltage between poor, and with detected difference as zero signal;
Be used for proofreading and correct the zero-point correction apparatus of described flow velocity signal with described zero signal.
15, by apply the electromagnetic flowmeter that its flow is measured in magnetic field to fluid, comprising:
Be used to provide have two kinds of different frequencies, i.e. the excitation unit in the magnetic field of first kind and lower second kind of frequency;
Be used for discerning on the basis of described second kind of frequency also second demodulating equipment of output signal voltage, above-mentioned signal voltage produces by described excitation unit excitation and according to flow velocity;
Be used for the output of described second demodulating equipment is carried out the low-pass filter of low-pass filtering;
Be used for first demodulating equipment with described first kind of frequency identification and the described signal voltage of demodulation;
Be used to detect the response detection and the multiplying arrangement of difference of the output of the output of described first demodulating equipment and described low-pass filter; And
The response corrections device of difference that is used for the output of calculated response compensating signal and described low-pass filter, above-mentioned response compensating signal make the output of described response detection and multiplying arrangement obtain through Hi-pass filter.
16, by apply the electromagnetic flowmeter that its flow is measured in magnetic field to fluid, comprising:
Be used to provide have two kinds of different frequencies, i.e. the excitation unit in the magnetic field of first kind of frequency and lower second kind of frequency;
Be used for discerning on the basis of described second kind of frequency also second demodulating equipment of output signal voltage, above-mentioned signal voltage produces by described excitation unit excitation and according to flow velocity;
Be used for the output of described second demodulating equipment is carried out the low-pass filter of low-pass filtering;
Be used to amplify the response detection and the multiplying arrangement of the difference of flow velocity output and described signal voltage;
Be used to respond with the output of calibration response compensating signal and described low-pass filter with the output signal relevant with described response corrections device as described flow velocity signal, the output of described response detection of above-mentioned response compensating signal demodulation on the basis of described first kind of frequency and multiplying arrangement obtains.
17, by apply the electromagnetic flowmeter that its flow is measured in magnetic field to fluid, comprising:
Be used to provide have two kinds of different frequencies, i.e. the excitation unit in the magnetic field of first kind of frequency and lower second kind of frequency;
Be used on the basis of described first kind of frequency identification signal voltage and produce first demodulating equipment of first output, above-mentioned signal voltage produces by described excitation unit excitation and according to flow velocity;
Second demodulating equipment that is used on the basis of second kind of frequency identification and the described signal voltage of demodulation;
Low-pass filter with large time constant, be used for the output of described second demodulating equipment is carried out low-pass filtering to produce second output, thereby, export described first by being produced flow velocity with second output execution scheduled operation (that is, summation, zero correction or response corrections).
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 87101677 CN1028671C (en) | 1987-03-04 | 1987-03-04 | Electromagnetic flowmeter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 87101677 CN1028671C (en) | 1987-03-04 | 1987-03-04 | Electromagnetic flowmeter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN87101677A true CN87101677A (en) | 1988-09-14 |
| CN1028671C CN1028671C (en) | 1995-05-31 |
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ID=4813587
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 87101677 Expired - Lifetime CN1028671C (en) | 1987-03-04 | 1987-03-04 | Electromagnetic flowmeter |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101893465A (en) * | 2010-06-30 | 2010-11-24 | 合肥工业大学 | A Signal Processing System of Electromagnetic Flowmeter Based on DSP |
| CN104316118A (en) * | 2014-07-10 | 2015-01-28 | 上海大学 | Electromagnetic flowmeter with variable excitation frequency |
| CN109781195A (en) * | 2019-01-21 | 2019-05-21 | 西南石油大学 | A kind of electromagnetic flowmeter system and signal extraction method based on dual-frequency excitation |
| CN110998248A (en) * | 2017-08-09 | 2020-04-10 | 代傲表计有限公司 | Measuring device for determining a fluid parameter relating to a fluid and/or a fluid flow |
-
1987
- 1987-03-04 CN CN 87101677 patent/CN1028671C/en not_active Expired - Lifetime
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101893465A (en) * | 2010-06-30 | 2010-11-24 | 合肥工业大学 | A Signal Processing System of Electromagnetic Flowmeter Based on DSP |
| CN101893465B (en) * | 2010-06-30 | 2012-07-11 | 合肥工业大学 | A Signal Processing System of Electromagnetic Flowmeter Based on DSP |
| CN104316118A (en) * | 2014-07-10 | 2015-01-28 | 上海大学 | Electromagnetic flowmeter with variable excitation frequency |
| CN104316118B (en) * | 2014-07-10 | 2018-01-02 | 上海大学 | Become the electromagnetic flowmeter of excitation frequency |
| CN110998248A (en) * | 2017-08-09 | 2020-04-10 | 代傲表计有限公司 | Measuring device for determining a fluid parameter relating to a fluid and/or a fluid flow |
| CN109781195A (en) * | 2019-01-21 | 2019-05-21 | 西南石油大学 | A kind of electromagnetic flowmeter system and signal extraction method based on dual-frequency excitation |
Also Published As
| Publication number | Publication date |
|---|---|
| CN1028671C (en) | 1995-05-31 |
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