CN118381696B - Method for designing and receiving lead-through fusion signal based on pseudorandom scrambling code modulation - Google Patents

Abstract

The application relates to a method for designing and receiving a communication fusion signal based on pseudo-random scrambling code modulation. The method comprises the following steps: the pilot frequency segment and the data segment of the time division system are designed to modulate the pseudo-random scrambling sequence on the signal waveform, the communication data transmission capacity is ensured, the capacity of high-precision measurement of signal delay and Doppler is improved, the estimated values of delay, carrier initial phase and carrier Doppler frequency deviation are utilized to compensate the delay, carrier initial phase and carrier Doppler frequency deviation of the data segment signal, the error rate of data segment message demodulation can be effectively reduced, the demodulated message is utilized as a local reference, the pilot frequency segment and the data segment signal are utilized to carry out secondary estimation, the estimated precision of delay, carrier initial phase and carrier Doppler frequency can be further improved, the error rate of data demodulation is further reduced, and the time delay and carrier Doppler frequency precision of the received signal can be improved.

Description

Design and receiving method of communication and conduction fusion signal based on pseudo-random scrambling modulation

Technical Field

The present application relates to the field of communication-conductor fusion technology, and in particular to a communication-conductor fusion signal design and receiving method based on pseudo-random scrambling code modulation.

Background Art

While transmitting communication data to users, the communication and navigation fusion system can also provide navigation, positioning and timing services. The communication data transmission function and the navigation, positioning and timing function empower and enhance each other. It has been widely used in satellite navigation, satellite communication and ground mobile communication systems, providing important guarantees for transportation, civil aviation, emergency rescue, military applications, etc.

In the global satellite navigation system, navigation positioning and timing are the main services, supplemented by partial navigation information transmission, and the continuous signal system of phase division modulation is mainly used. Taking the B1cd and B1cd signals of the Beidou-3 satellite navigation system as an example, B1cp is a continuous pilot signal, which is broadcast on the same branch; B1cd is a data signal modulated with navigation information, which is broadcast on the orthogonal branch. The navigation receiver can synchronize the delay and carrier Doppler frequency by receiving the B1cp signal, and then demodulate the telegram data on the B1cd signal. This type of signal system is conducive to the high-precision measurement of delay and Doppler frequency, but the communication transmission rate is limited.

In satellite communication systems, data transmission is the main business, supplemented by some positioning and timing services, and a discontinuous burst signal system is usually used. Taking the Iridium low-orbit communication system as an example, communication signals are usually broadcast once or repeatedly in the form of synchronization segment + data segment. Users synchronize the received signal delay and carrier Doppler frequency by matching the received synchronization segment signal, and then demodulate part of the data segment information. This type of signal system is conducive to efficient data transmission, but the measurement accuracy of delay and carrier Doppler frequency is limited.

Summary of the invention

Based on this, it is necessary to provide a design and receiving method for a conduction-conduction fusion signal based on pseudo-random scrambling code modulation that can improve the received signal delay and carrier Doppler frequency accuracy in response to the above technical problems.

A design and receiving method of a conduction-conduction fusion signal based on pseudo-random scrambling code modulation, the method comprising:

Generate an all-one pilot sequence of a first preset length and combine it with a data symbol sequence of a second preset length after channel coding, and obtain a symbol sequence of a third length in a time division multiplexing mode of first pilot and then data; perform phase mapping on the symbol sequence of the third length to obtain a symbol sequence after phase mapping;

Generate a pseudo-random scrambling sequence according to the length of the symbol sequence after phase mapping, modulate the pseudo-random scrambling sequence on the symbol sequence after phase mapping to obtain a baseband signal sequence; modulate a baseband signal corresponding to the baseband signal sequence on a carrier of a center frequency to obtain a communication-conductor fusion signal; the communication-conductor fusion signal includes a pilot segment signal and a data segment signal;

The pilot segment signal and the pre-designed pilot segment local signal are estimated according to the time-frequency and Doppler frequency joint estimation method to obtain the estimated values of the time delay, the initial phase of the carrier and the Doppler frequency deviation of the carrier; the time delay, the initial phase of the carrier and the Doppler frequency deviation of the data segment signal are compensated by using the estimated values of the time delay, the initial phase of the carrier and the Doppler frequency deviation of the carrier to obtain the compensated signal;

The scrambling code of the data segment signal is demodulated using a pseudo-random scrambling sequence to recover the original telegram symbols of the data segment. After collecting a whole frame of original telegram symbols, channel decoding is performed to recover the original telegram information. A CRC check is performed on the original telegram information to determine whether the telegram bit error rate is lower than a preset threshold. Based on the judgment result, the demodulated telegram information, the observation results of the delay, carrier initial phase and carrier Doppler frequency are output.

In one embodiment, the length of the symbol sequence of the third length is ,in, Indicates the first length, Indicates the second length.

In one embodiment, modulating a pseudo-random scrambling sequence on a phase-mapped symbol sequence to obtain a baseband signal sequence includes:

The length is The pseudo-random scrambling sequence , the modulation length is The symbol sequence On, the length is The baseband signal sequence is .

In one embodiment, modulating a baseband signal corresponding to a baseband signal sequence on a carrier of a center frequency to obtain a conduction-conduction fusion signal includes:

The baseband signal corresponding to the baseband signal sequence The modulation center frequency is The carrier wave of the conduction-conduction fusion signal is .

In one embodiment, the design process of the pilot segment local signal includes: The pseudo-random scrambling sequence , the modulation length is The symbol sequence On, the length is The baseband signal sequence is .

In one embodiment, it is determined whether the message bit error rate is lower than a preset threshold, and the message information obtained by demodulation, the observation results of the delay, the initial phase of the carrier and the Doppler frequency of the carrier are output according to the determination result, including:

Determine whether the message bit error rate is lower than a preset threshold. If the message bit error rate is higher than the preset threshold, perform channel coding on the original message information to obtain an estimated value of the original message symbol of the data segment.

Using the estimated value of the original telegram symbol of the data segment to strip the original telegram symbol of the data segment, a data segment signal without the telegram symbol is obtained;

The pilot segment signal and the data segment signal without the message symbol are jointly processed by using a pseudo-random scrambling sequence to estimate and update the estimated values of the time delay, carrier initial phase and carrier Doppler frequency deviation. The time delay, carrier initial phase and carrier Doppler frequency deviation of the data segment signal are then compensated and the original message information is recalculated until the message bit error rate of the original message information is lower than the preset threshold. The message information, the observation results of the time delay, carrier initial phase and carrier Doppler frequency are output.

The above-mentioned communication-conductor fusion signal design and receiving method based on pseudo-random scrambling code modulation, in the process of signal design, by designing the pilot segment and data segment of the time division system, modulate the pseudo-random scrambling code sequence on the signal waveform, while ensuring the communication data transmission capability, improve the ability of high-precision measurement of signal delay and Doppler; in the process of communication-conductor fusion signal reception, by first using the pilot segment signal to estimate the delay, carrier initial phase and carrier Doppler frequency, the bit error rate of data segment telegram demodulation can be effectively reduced, and then the demodulated telegram is used as a local reference, and the pilot segment and data segment signals are used for secondary estimation, which can further improve the estimation accuracy of delay, carrier initial phase and carrier Doppler frequency, and further reduce the bit error rate of data demodulation. Simulation results show that this method can achieve a delay measurement accuracy of 38.4m and a carrier Doppler measurement accuracy of 0.5Hz without significantly increasing the computational complexity, approaching the theoretical limit. Furthermore, in the entire implementation process of this article, a structure similar to that of a classical receiver is maintained, and complex operations such as matrix inversion and eigendecomposition are not involved. Therefore, the present invention is simple to implement, has a small amount of calculation, and is very convenient to implement.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG1 is a schematic flow chart of a method for designing and receiving a conduction-conduction fusion signal based on pseudo-random scrambling code modulation in one embodiment;

FIG2 is a schematic flow chart of a method for receiving a conduction-conduction fusion signal based on a pseudo-random scrambling code in one embodiment;

FIG3 is a diagram showing the relationship between the delay estimation deviation and the message demodulation bit error rate in one embodiment;

FIG4 is a diagram showing the relationship between carrier Doppler estimation deviation and message demodulation bit error rate in another embodiment;

FIG5 is a diagram showing the relationship between the message demodulation bit error rate and the delay measurement accuracy in one embodiment;

FIG6 is a graph showing the relationship between the message demodulation bit error rate and the carrier Doppler measurement accuracy in one embodiment;

FIG7 is a graph showing the relationship between the carrier-to-noise ratio of a received signal and the bit error rate of a message demodulation in one embodiment;

FIG8 is a graph showing the relationship between the carrier-to-noise ratio of a received signal and the delay measurement accuracy in one embodiment;

FIG. 9 is a diagram showing the relationship between the carrier-to-noise ratio of a received signal and the carrier Doppler measurement accuracy in one embodiment.

DETAILED DESCRIPTION

In order to make the purpose, technical solution and advantages of the present application more clearly understood, the present application is further described in detail below in conjunction with the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are only used to explain the present application and are not used to limit the present application.

In one embodiment, as shown in FIG1 , a method for designing and receiving a conduction-conduction fusion signal based on pseudo-random scrambling modulation is provided, comprising the following steps:

Step 102, generate an all-one pilot sequence of a first preset length and combine it with a data symbol sequence of a second preset length after channel coding, and obtain a symbol sequence of a third length in a time division multiplexing manner of first pilot and then data; perform phase mapping on the symbol sequence of the third length to obtain a symbol sequence after phase mapping.

The generated length is All "1" pilot sequence , and the length after channel coding is The data symbol sequence Combine them and use the time division multiplexing method of pilot first and data later to get a length of The symbol sequence Length is The symbol sequence Enter the phase mapping module. Phase mapping methods include but are not limited to BPSK, QPSK, QAM, etc. After phase mapping, the length is The symbol sequence .

Step 104, generate a pseudo-random scrambling code sequence according to the length of the symbol sequence after phase mapping, modulate the pseudo-random scrambling code sequence on the symbol sequence after phase mapping to obtain a baseband signal sequence; modulate the baseband signal corresponding to the baseband signal sequence on the carrier of the center frequency to obtain a communication-conductor fusion signal; the communication-conductor fusion signal includes a pilot segment signal and a data segment signal.

The generated length is The pseudo-random scrambling sequence , the pseudo-random scrambling sequence can be but is not limited to sequence, The scrambling sequence should have randomness and autocorrelation characteristics. The pseudo-random scrambling sequence , the modulation length is The symbol sequence On, the length is The baseband signal sequence . The baseband signal The modulation center frequency is The carrier wave of the conduction-conduction fusion signal is .

Step 106, estimate the pilot segment signal and the pre-designed pilot segment local signal according to the joint time-frequency and Doppler frequency estimation method to obtain estimated values of time delay, carrier initial phase and carrier Doppler frequency deviation; use the estimated values of time delay, carrier initial phase and carrier Doppler frequency deviation to compensate for the time delay, carrier initial phase and carrier Doppler frequency deviation of the data segment signal to obtain a compensated signal.

Step 108, using a pseudo-random scrambling sequence to demodulate the scrambling code of the data segment signal, recover the original telegram symbols of the data segment, and perform channel decoding after collecting a whole frame of original telegram symbols to recover the original telegram information; perform CRC check on the original telegram information to determine whether the telegram bit error rate is lower than a preset threshold, and output the demodulated telegram information, the observation results of the delay, the initial phase of the carrier, and the carrier Doppler frequency according to the determination result.

After the design of the communication-conduction fusion signal based on pseudo-random scrambling code modulation is completed, the communication-conduction fusion signal receiving method is designed, as shown in Figure 2. The main process is as follows:

Step 201: Input baseband received signal , including the pilot signal and data segment signal two parts of;

Step 202: Using the pilot segment local signal and pilot band signal , using a direct joint estimation method of time delay and Doppler frequency, including but not limited to early-subtraction code phase estimator and red-blue frequency shift Doppler estimator, the estimated values of time delay, carrier initial phase and carrier Doppler frequency deviation are and .

Step 203: Using the estimated values of time delay and carrier Doppler frequency and , compensation data segment signal The time delay, carrier initial phase and carrier Doppler frequency deviation are used to obtain the compensated signal .

Step 204: Using a pseudo-random scrambling sequence , demodulate the data segment signal The scrambling code is used to recover the message symbols of the data segment. .

Step 205: After collecting a whole frame of original telegram symbols, channel decoding is performed, including but not limited to convolutional codes, Turbo codes, LDPC codes, and Polar codes.

Step 206: Restore the original electronic message information.

Step 207: Based on the CRC and other verification results, determine whether the message bit error rate is lower than the threshold. If it is higher than the threshold, go to step 208; otherwise, go directly to step 211.

Step 208: Perform channel coding on the original message to obtain an estimated value of the original message symbol of the data segment. .

Step 209: Using the estimated value of the original message symbol of the data segment , strip the original telegram symbols of the data segment to obtain the data segment signal without telegram symbols .

Step 210: Using the length The pseudo-random scrambling sequence , for the pilot band signal And data segment signals without telegram symbols Perform joint processing to estimate and update the estimated values of delay, carrier initial phase and carrier Doppler frequency deviation as , and , then go to step 203.

Step 211: Output the demodulated message information, the observation results of the time delay, the initial phase of the carrier and the Doppler frequency of the carrier.

In the signal receiving process, in order to save computing resources, step 209 can be directly entered from step 204. However, since no channel decoding is performed, the error probability of the reference signal message symbols will increase, the estimation accuracy of the delay, the initial phase of the carrier and the Doppler frequency of the carrier will decrease, and the bit error rate of the final output message will increase.

In the above-mentioned communication-conductor fusion signal design and reception method based on pseudo-random scrambling code modulation, the present application modulates the pseudo-random scrambling code sequence on the signal waveform by designing the pilot segment and data segment of the time division system during the signal design process, thereby ensuring the communication data transmission capability and improving the ability of high-precision measurement of signal delay and Doppler; in the communication-conductor fusion signal reception process, by first using the pilot segment signal to estimate the delay, carrier initial phase and carrier Doppler frequency, the bit error rate of data segment telegram demodulation can be effectively reduced, and then the demodulated telegram is used as a local reference, and the pilot segment and data segment signals are used for secondary estimation, which can further improve the estimation accuracy of delay, carrier initial phase and carrier Doppler frequency, and further reduce the bit error rate of data demodulation. Simulation results show that this method can achieve a delay measurement accuracy of 38.4m and a carrier Doppler measurement accuracy of 0.5Hz without significantly increasing the computational complexity, approaching the theoretical limit. Furthermore, in the entire implementation process of this article, a structure similar to that of a classical receiver is maintained, and complex operations such as matrix inversion and eigendecomposition are not involved. Therefore, the present invention is simple to implement, has a small amount of calculation, and is very convenient to implement.

In one embodiment, the length of the symbol sequence of the third length is ,in, Indicates the first length, Indicates the second length.

In one embodiment, modulating a pseudo-random scrambling sequence on a phase-mapped symbol sequence to obtain a baseband signal sequence includes:

The length is The pseudo-random scrambling sequence , the modulation length is The symbol sequence On, the length is The baseband signal sequence is .

In one embodiment, modulating a baseband signal corresponding to a baseband signal sequence on a carrier of a center frequency to obtain a conduction-conduction fusion signal includes:

The baseband signal corresponding to the baseband signal sequence The modulation center frequency is The carrier wave of the conduction fusion signal is .

In one embodiment, the design process of the pilot segment local signal includes: The pseudo-random scrambling sequence , the modulation length is The symbol sequence On, the length is The baseband signal sequence is .

In one embodiment, it is determined whether the message bit error rate is lower than a preset threshold, and the message information obtained by demodulation, the observation results of the delay, the initial phase of the carrier and the Doppler frequency of the carrier are output according to the determination result, including:

Determine whether the message bit error rate is lower than a preset threshold. If the message bit error rate is higher than the preset threshold, perform channel coding on the original message information to obtain an estimated value of the original message symbol of the data segment.

Using the estimated value of the original telegram symbol of the data segment to strip the original telegram symbol of the data segment, a data segment signal without the telegram symbol is obtained;

The pilot segment signal and the data segment signal without the message symbol are jointly processed by using a pseudo-random scrambling sequence to estimate and update the estimated values of the time delay, carrier initial phase and carrier Doppler frequency deviation. The time delay, carrier initial phase and carrier Doppler frequency deviation of the data segment signal are then compensated and the original message information is recalculated until the message bit error rate of the original message information is lower than the preset threshold. The message information, the observation results of the time delay, carrier initial phase and carrier Doppler frequency are output.

In a specific embodiment, FIG3 is a graph showing the relationship between the delay estimation deviation and the message demodulation bit error rate of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a data segment signal length of 10 ms, a carrier-to-noise ratio of 55dB-Hz, a delay estimation deviation range of -0.4 code chips to 0.4 code chips, BPSK modulation is used, and Gaussian white noise is added to the channel. The simulation results show that when the delay estimation deviation is ±0.4 code chips, the bit error rate of the data segment signal message demodulation is approximately 0.24; when the delay estimation deviation is ±0.2 code chips, the bit error rate of the data segment signal message demodulation is approximately 0.02; when the delay estimation deviation is 0 code chips, the bit error rate of the data segment signal message demodulation is approximately .

Figure 4 is a graph showing the relationship between carrier Doppler estimation deviation and message demodulation bit error rate of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a data segment signal length of 10ms, a carrier-to-noise ratio of 55dB-Hz, a carrier Doppler frequency estimation deviation range of -30Hz to 30Hz, BPSK modulation, and Gaussian white noise added to the channel. The simulation results show that when the carrier Doppler frequency estimation deviation is ±30Hz, the bit error rate of data segment signal message demodulation is approximately 0.17; when the carrier Doppler frequency estimation deviation is ±15Hz, the bit error rate of data segment signal message demodulation is approximately ; When the carrier Doppler frequency estimation deviation is 0Hz, the bit error rate of the data segment signal message demodulation is approximately .

FIG5 is a graph showing the relationship between the message demodulation bit error rate and the delay measurement accuracy of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a data segment signal length of 10 ms, a carrier-to-noise ratio of 55dB-Hz, a data symbol bit error rate range of 1~0.1, BPSK modulation, and the addition of Gaussian white noise to the channel. The simulation results show that when the bit error rate is 0, the signal delay estimation accuracy is 72.5 m; when the bit error rate is 0.05, the signal delay estimation accuracy is 51.6 m; when the bit error rate is 0.1, the signal delay estimation accuracy is 63.4 m. Therefore, as the data segment message demodulation bit error rate increases, the accuracy of delay measurement using the data segment signal will decrease.

FIG6 is a graph showing the relationship between the demodulation bit error rate of a message and the carrier Doppler measurement accuracy of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a data segment signal length of 10ms, a carrier-to-noise ratio of 55dB-Hz, a data symbol bit error rate range of 1~0.1, BPSK modulation, and Gaussian white noise added to the channel. The simulation results show that when the bit error rate is 0, the carrier Doppler frequency estimation accuracy is 0.7Hz; when the bit error rate is 0.05, the carrier Doppler frequency estimation accuracy is 0.8Hz; when the bit error rate is 0.1, the carrier Doppler frequency estimation accuracy is 0.9 Hz. Therefore, as the demodulation bit error rate of the data segment message increases, the accuracy of carrier Doppler frequency measurement using the data segment signal will decrease.

Figure 7 is a graph showing the relationship between the carrier-to-noise ratio of the received signal and the bit error rate of the message demodulation in an embodiment of the present application. The simulation considers the symbol rate of 32KHz, the carrier-to-noise ratio range of 40~70 dB-Hz, the pilot segment signal length of 2ms, the data segment signal length of 10ms, BPSK modulation, and the addition of Gaussian white noise to the channel. First, the 2ms pilot segment signal is used to complete the initial estimation of the signal delay and the carrier Doppler frequency, and the message symbols of the 10ms data segment signal are demodulated according to the estimation results, and the error probability of the message symbols is calculated.

The simulation results show that when the received signal carrier-to-noise ratio is 45dB-Hz, the initial estimation accuracy of the signal delay is 297.2 m (0.03 code chip), the initial estimation accuracy of the carrier Doppler frequency is 24.5Hz, and the bit error rate of data segment symbol demodulation is 9.2%; when the received signal carrier-to-noise ratio is 50dB-Hz, the initial estimation accuracy of the signal delay is 166.1m (0.02 code chip), the initial estimation accuracy of the carrier Doppler frequency is 13.8Hz, and the bit error rate of data segment symbol demodulation is 1.2%; when the received signal carrier-to-noise ratio is 55dB-Hz, the initial estimation accuracy of the signal delay is 93.2m (0.01 code chip), the initial estimation accuracy of the carrier Doppler frequency is 7.9Hz, and the bit error rate of data segment symbol demodulation is 0.01%.

Figure 8 is a graph showing the relationship between the carrier-to-noise ratio of the received signal and the delay measurement accuracy of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a carrier-to-noise ratio range of 40-70dB-Hz, a pilot segment signal length of 2 ms, a data segment signal length of 10ms, BPSK modulation, and Gaussian white noise added to the channel. Based on the data segment symbol obtained by demodulation, the secondary estimation of the signal delay is completed using the 2ms pilot segment signal and the 10ms data segment signal.

The simulation results show that when the received signal carrier-to-noise ratio is 45 dB-Hz, the quadratic estimation accuracy of signal delay is 437.6 m, corresponding to the ideal value of 12 ms signal delay estimation of 120.4 m, and the theoretical value of 2 ms signal delay estimation is 297.2 m; when the received signal carrier-to-noise ratio is 50 dB-Hz, the quadratic estimation accuracy of signal delay is 72.5 m, which is close to the ideal value of 12 ms signal delay estimation, and the theoretical value of 2 ms signal delay estimation is 166.1 m; when the received signal carrier-to-noise ratio is 55 dB-Hz, the quadratic estimation accuracy of signal delay is 38.4 m, which is close to the ideal value of 12 ms signal delay estimation, and the theoretical value of 2 ms signal delay estimation is 93.2 m.

Figure 9 is a graph showing the relationship between the carrier-to-noise ratio of the received signal and the carrier Doppler measurement accuracy of an embodiment of the present application. The simulation considers a symbol rate of 32KHz, a carrier-to-noise ratio range of 40-70dB-Hz, a pilot segment signal length of 2 ms, a data segment signal length of 10ms, BPSK modulation, and Gaussian white noise added to the channel. Based on the data segment symbol obtained by demodulation, the secondary estimation of the carrier Doppler frequency is completed using the 2ms pilot segment signal and the 10ms data segment signal.

The simulation results show that when the received signal carrier-to-noise ratio is 45 dB-Hz, the quadratic estimation accuracy of the carrier Doppler frequency is 2.6 Hz, corresponding to the ideal value of 12 ms signal delay estimation of 1.7 Hz, while the theoretical value of 2 ms carrier Doppler frequency estimation is 24.5 Hz; when the received signal carrier-to-noise ratio is 50 dB-Hz, the quadratic estimation accuracy of the carrier Doppler frequency is 0.9 Hz, which is close to the ideal value of 12 ms carrier Doppler frequency estimation, while the theoretical value of 2 ms carrier Doppler frequency estimation is 13.8 Hz; when the received signal carrier-to-noise ratio is 55 dB-Hz, the quadratic estimation accuracy of the carrier Doppler frequency is 0.5 Hz, which is close to the ideal value of 12 ms carrier Doppler frequency estimation, while the theoretical value of 2 ms carrier Doppler frequency estimation is 7.8 Hz.

It should be understood that, although the various steps in the flowchart of FIG. 1 are shown in sequence according to the indication of the arrows, these steps are not necessarily executed in sequence according to the order indicated by the arrows. Unless there is a clear explanation in this article, the execution of these steps is not strictly limited in order, and these steps can be executed in other orders. Moreover, at least a portion of the steps in FIG. 1 may include a plurality of sub-steps or a plurality of stages, and these sub-steps or stages are not necessarily executed at the same time, but can be executed at different times, and the execution order of these sub-steps or stages is not necessarily to be carried out in sequence, but can be executed in turn or alternately with other steps or at least a portion of the sub-steps or stages of other steps.

The technical features of the above embodiments may be arbitrarily combined. To make the description concise, not all possible combinations of the technical features in the above embodiments are described. However, as long as there is no contradiction in the combination of these technical features, they should be considered to be within the scope of this specification.

The above-mentioned embodiments only express several implementation methods of the present application, and the descriptions thereof are relatively specific and detailed, but they cannot be understood as limiting the scope of the invention patent. It should be pointed out that, for a person of ordinary skill in the art, several variations and improvements can be made without departing from the concept of the present application, and these all belong to the protection scope of the present application. Therefore, the protection scope of the patent of the present application shall be subject to the attached claims.

Claims (6)

1. A method for designing and receiving a lead-through fusion signal based on pseudo-random scrambling code modulation is characterized by comprising the following steps:

combining the full 1 pilot frequency sequence with the first preset length with the data symbol sequence with the second preset length after channel coding, and obtaining a symbol sequence with a third length according to a time division multiplexing mode of pilot frequency and data; performing phase mapping on the symbol sequence with the third length to obtain a symbol sequence after phase mapping;

Generating a pseudo-random scrambling sequence according to the length of the symbol sequence after phase mapping, and modulating the pseudo-random scrambling sequence on the symbol sequence after phase mapping to obtain a baseband signal sequence; modulating a baseband signal corresponding to the baseband signal sequence on a carrier wave with a central frequency to obtain a lead fusion signal; the conductance fusion signal comprises a conductance band signal and a data band signal;

estimating the pilot frequency segment signals and the pre-designed pilot frequency segment local signals according to a time-frequency and Doppler frequency joint estimation method to obtain estimated values of time delay, carrier initial phase and carrier Doppler frequency deviation;

Compensating the time delay of the data section signal, the carrier initial phase and the carrier Doppler frequency deviation by using the estimated values of the time delay, the carrier initial phase and the carrier Doppler frequency deviation to obtain a compensated signal;

demodulating the scrambling code of the data segment signal of the compensated signal by using the pseudo-random scrambling code sequence, recovering to obtain the original text symbol of the data segment, collecting the original text symbol of a whole frame, then performing channel decoding, and recovering the original text information;

And performing CRC (cyclic redundancy check) on the original message information, judging whether the message error bit rate is lower than a preset threshold, and outputting observation results of the message information, the time delay, the carrier initial phase and the carrier Doppler frequency obtained by demodulation according to the judgment result.

2. The method of claim 1, wherein the third length symbol sequence has a length of N ₃=N₁+N₂, wherein N ₁ represents a first length and N ₂ represents a second length.

3. The method of claim 1, wherein modulating the pseudo-random scrambling sequence on the phase mapped symbol sequence results in a baseband signal sequence, comprising:

Modulating a pseudorandom scrambling sequence C ₅ with a length of N ₄ on a symbol sequence C ₄ with a length of N ₄ to obtain a baseband signal sequence with a length of N ₄ 。

4. The method of claim 1, wherein modulating the baseband signal corresponding to the baseband signal sequence on a carrier with a center frequency to obtain the conductance fusion signal comprises:

Modulating the baseband signal C ₆ (t) corresponding to the baseband signal sequence on a carrier wave with the center frequency of f _I to obtain a conductive fusion signal 。

5. The method of claim 1 wherein the designing of the pilot segment local signal comprises: modulating a pseudorandom scrambling sequence C ₅ with a length of N ₄ on a symbol sequence C ₁ with a length of N ₁ to obtain a baseband signal sequence with a length of N ₄ 。

6. The method of claim 1, wherein determining whether the message bit error rate is below a preset threshold, and outputting the demodulated message information, the time delay, the carrier initial phase, and the observation result of the carrier doppler frequency according to the determination result, comprises:

judging whether the message error bit rate is lower than a preset threshold, if so, performing channel coding operation on the original message information to obtain an estimated value of an original message symbol of a data segment;

Stripping the original text symbols of the data segment by using the estimated values of the original text symbols of the data segment to obtain a data segment signal without text symbols;

And carrying out joint processing on the pilot frequency segment signal and the data segment signal without the telegraph sign by utilizing the pseudo-random scrambling code sequence, estimating and updating estimated values of time delay, carrier initial phase and carrier Doppler frequency deviation, then calculating the original telegraph information again after compensating the time delay, carrier initial phase and carrier Doppler frequency deviation of the data segment signal until the telegraph error bit rate of the original telegraph information is lower than a preset threshold, and outputting observation results of the telegraph information, the time delay, the carrier initial phase and the carrier Doppler frequency.