CN118157537A - Motor operation phase compensation system and method - Google Patents

Abstract

The application relates to a motor running phase compensation system and a motor running phase compensation method, comprising a motor and a controller, wherein a stator of the motor is provided with a first armature winding and a second armature winding; the controller is internally provided with a sine wave inverter circuit and a square wave inverter circuit, the sine wave inverter circuit is connected to a first armature winding of the motor, the square wave inverter circuit is connected to a second armature winding of the motor, and when the first armature winding is used as a main driving winding, the second armature winding is used as an auxiliary adjusting winding, or when the second armature winding is used as a main driving winding, the first armature winding is used as an auxiliary adjusting winding; the controller is used for detecting the current fluctuation condition of the main driving winding after the main driving winding is controlled to form a main driving magnetic field, and controlling the auxiliary adjusting winding to form an auxiliary adjusting magnetic field only at the current fluctuation phase position in the next operation period to be input into the main driving magnetic field. The application has the effect of improving the adjusting efficiency.

Description

Motor operation phase compensation system and method

Technical Field

The application relates to the technical field of controller control methods, in particular to a motor operation phase compensation system and a motor operation phase compensation method.

Background

At present, a sine wave controller and a square wave controller are applied in the variable frequency motor industry, and the sine wave controller and the square wave controller are mainly different from each other as follows: 1. the output waveforms are different, the square wave voltage signal is output by the square wave controller, and the sine wave voltage signal is output by the sine wave controller; 2. the driving modes are different, the square wave controller adopts square wave pulses to drive the motor, and the sine wave controller adopts sine wave pulses to drive the motor; 3. the noise and vibration are different, can produce great noise and vibration when square wave controller driving motor, and the motor rotates more steadily when sine wave controller driving motor, and sound and vibration can obviously reduce. 4. The power and the efficiency are different, the sine wave controller can provide softer power output, the power is more stable and stable, and the square wave controller can adopt a high-frequency pulse mode, so that the energy loss can be reduced, and the efficiency is improved. Therefore, the application of the sine wave controller and the square wave controller in the variable frequency motor often depends on the specific requirements and the use scene of the variable frequency motor.

In view of the above related art, the inventor finds that when the sine wave controller or the square wave controller controls the motor to operate, and when the load changes, the current value of the motor fluctuates, and at present, the sine wave controller or the square wave controller only can integrally adjust the current value of the motor to adjust the magnetic field of the armature winding, so that the motor is ensured to work in a safe load range, and the efficiency of the adjustment mode is low, so that a certain improvement exists.

Disclosure of Invention

In order to improve the regulation efficiency, the application provides a motor operation phase compensation system and a motor operation phase compensation method.

The application provides a motor operation phase compensation system which adopts the following technical scheme:

A motor operation phase compensation system comprises a motor and a controller, wherein a stator of the motor is provided with a first armature winding and a second armature winding;

The controller is internally provided with a sine wave inverter circuit and a square wave inverter circuit, the sine wave inverter circuit is connected to a first armature winding of the motor, the square wave inverter circuit is connected to a second armature winding of the motor, and when the first armature winding is used as a main driving winding, the second armature winding is used as an auxiliary adjusting winding, or when the second armature winding is used as a main driving winding, the first armature winding is used as an auxiliary adjusting winding;

The controller is used for detecting the current fluctuation condition of the main driving winding after the main driving winding is controlled to form a main driving magnetic field, and controlling the auxiliary adjusting winding to form an auxiliary adjusting magnetic field only at the current fluctuation phase position in the next operation period to be input into the main driving magnetic field.

Preferably, a current detection unit, a phase conversion unit and an auxiliary adjustment unit are arranged in the controller;

The current detection unit is used for detecting current fluctuation conditions in the main driving winding and acquiring fluctuation current amplitude values;

the phase conversion unit determines a current fluctuation phase based on the current fluctuation condition detected by the current detection unit;

the auxiliary regulating unit controls an auxiliary regulating winding to form an auxiliary regulating magnetic field to be input into the main driving magnetic field only at the current fluctuation phase in the next operation period based on the fluctuation current amplitude and the current fluctuation phase.

Preferably, the winding number ratio of the main driving winding and the auxiliary adjusting winding is 4:1 or 3:1.

Preferably, the main driving winding adopts a star connection method or a triangle connection method, and the auxiliary adjusting winding adopts a star connection method or a triangle connection method.

Preferably, a waveform formula of the sine wave current generated by the sine wave inverter circuit is as follows:

The waveform formula of the square wave current generated by the square wave inverter circuit is as follows:

The motor operation phase compensation method provided by the application adopts the following technical scheme:

A motor operation phase compensation method using the motor operation phase compensation system according to the above technical solution, comprising the following steps:

the main driving winding is used for generating a main driving magnetic field;

Detecting the current fluctuation condition of the main driving winding, and acquiring the fluctuation current amplitude and the current fluctuation phase in the current operation period when the current of the main driving winding fluctuates;

Based on the fluctuating current amplitude and the current fluctuating phase, an auxiliary regulating magnetic field is formed by controlling an auxiliary regulating winding to be input into the main driving magnetic field only at the current fluctuating phase in a next operation period.

In summary, the present application includes at least one of the following beneficial technical effects:

1. When the load changes, the controller only controls the auxiliary adjusting winding to form an auxiliary adjusting magnetic field to be input into the main driving magnetic field at the current fluctuation phase position when the current of the main driving winding needs to be adjusted, so that the adjustment is completed, the current of the whole main driving winding does not need to be adjusted, and the adjustment efficiency is improved.

2. The application can realize control by only controlling the auxiliary adjusting winding to input the auxiliary adjusting magnetic field into the main driving magnetic field, and can meet the different changing demands in the load operation, thereby simplifying the design difficulty of the controller.

Drawings

Fig. 1 is a system block diagram of a motor operating phase compensation system.

Fig. 2 is a schematic distribution diagram of a first armature winding and a second armature winding.

Fig. 3 is a schematic circuit connection diagram of the inverter circuit and the stator.

Fig. 4 is a waveform schematic diagram of a sine wave current.

Fig. 5 is a schematic waveform diagram of a square wave current.

Fig. 6 is a waveform diagram of a current ripple condition.

Fig. 7 is a state diagram of case one in the first embodiment.

Fig. 8 is a state diagram of the second case in the first embodiment.

Fig. 9 is a state diagram of a case three in the first embodiment.

Fig. 10 is a state diagram of a case four in the first embodiment.

Fig. 11 is a state diagram of case five in the first embodiment.

Fig. 12 is a state diagram of case six in the first embodiment.

Fig. 13 is a flow chart of a motor operating phase compensation method.

Detailed Description

The present application is described in further detail below with reference to fig. 1-13.

Example 1

An operation phase compensation system of a motor is shown with reference to fig. 1, and comprises a motor and a controller, wherein the controller is connected with the motor, the motor comprises a stator and a rotor matched with the stator, and in the application, a first armature winding and a second armature winding are arranged on the stator, and the first armature winding and the second armature winding are copper wire windings.

Referring to fig. 2 and 3, the controller is used for realizing driving control of the motor, and a rectifying circuit, a filtering circuit and an inverter circuit which are electrically connected in sequence are arranged in the controller, the rectifying circuit is used for converting alternating current into direct current, the inverter circuit is used for converting the direct current into alternating current with adjustable frequency after noise is filtered by the filtering circuit, and the alternating current converted by the inverter circuit is input into the motor, so that the motor rotating speed is adjustable.

In the application, two groups of inverter circuits are respectively a sine wave inverter circuit and a square wave inverter circuit, the sine wave inverter circuit is connected to a first armature winding, and the square wave inverter circuit is connected to a second armature winding.

Wherein whether the first armature winding or the second armature winding is a main drive winding will be differentiated according to the motor drag load. When the load requires the motor to be driven with a sine wave current, the first armature winding is used as a main driving winding, and the second armature winding is used as an auxiliary adjusting winding.

In one embodiment, the ratio of the number of the windings of the main driving winding and the auxiliary adjusting winding is 4:1, in another embodiment, the ratio of the number of the windings of the main driving winding and the auxiliary adjusting winding is 3:1, and the number of the windings of the main driving winding and the auxiliary adjusting winding can be selected according to practical situations, and the embodiment is not particularly limited.

In this embodiment, the main driving winding adopts a star connection or a triangle connection, the auxiliary adjusting winding adopts a star connection or a triangle connection, the main driving winding and the auxiliary adjusting winding can be selected according to actual conditions by adopting a star connection or a triangle connection, and the embodiment is not particularly limited.

The connection between the first armature winding and the sine wave inverter circuit and the connection between the second armature winding and the square wave inverter circuit are described below.

Referring to fig. 2 and 3, the first armature winding has a first segment winding having two ends (U1, Z1), a second segment winding having two ends (V1, Y1), and a third segment winding having two ends (W1, X1), one end U1 of the first segment winding, one segment V1 of the second segment winding, and one end W1 of the third segment winding are connected to three output ends of the sine wave inverter circuit, respectively.

When the star connection method is adopted, the other end Z1 of the first section of winding, the other end Y1 of the second section of winding and the other end X1 of the third section of winding are connected together. When the triangle connection method is adopted, the other end Z1 of the first section winding is connected to one end V1 of the second section winding, the other end Y1 of the second section winding is connected to one end W1 of the third section winding, and the other end X1 of the third section winding is connected to U1 of the first section winding.

Similarly, the second armature winding has a first winding section, a second winding section and a third winding section, the first winding section has two ends (U2, Z2), the second winding section has two ends (V2, Y2), the third winding section has two ends (W2, X2), one end U2 of the first winding section, one section V2 of the second winding section and one end W2 of the third winding section are respectively connected to three output ends of the square wave inverter circuit.

When the star connection method is adopted, the other end Z2 of the first section of winding, the other end Y2 of the second section of winding and the other end X2 of the third section of winding are connected together. When the triangle connection method is adopted, the other end Z2 of the first section winding is connected to one end V2 of the second section winding, the other end Y2 of the second section winding is connected to one end W2 of the third section winding, and the other end X2 of the third section winding is connected to U2 of the first section winding.

The first armature winding and the second armature winding are identical in connection structure, and the second armature winding differ only in the number of windings.

In the application, the controller is used for controlling the main driving winding to form a main driving magnetic field, controlling the auxiliary adjusting winding to form an auxiliary adjusting magnetic field, and when the load changes in operation, causing the change of the impedance of the motor, so that the current of the main driving winding fluctuates, and the auxiliary adjusting magnetic field is added to the position corresponding to the current fluctuation phase of the main driving magnetic field, thereby realizing the adjustment and control of the motor.

The controller is used for detecting the current fluctuation condition of the main driving winding after controlling the main driving winding to form a main driving magnetic field, and controlling the auxiliary adjusting winding to form an auxiliary adjusting magnetic field only at the current fluctuation phase position in the next operation period to be input into the main driving magnetic field.

Specifically, a current detection unit, a phase conversion unit and an auxiliary adjustment unit are arranged in the controller. The current detection unit is used for detecting current fluctuation conditions in the main driving winding, acquiring fluctuation current amplitude values, and the phase conversion unit determines current fluctuation phases based on the current fluctuation conditions detected by the current detection unit; the auxiliary regulating unit controls the auxiliary regulating winding to form an auxiliary regulating magnetic field input into the main driving magnetic field only at the current fluctuation phase in the next operation period based on the fluctuation current amplitude and the current fluctuation phase.

The following describes how the auxiliary adjusting magnetic field plays a role in adjusting the main driving magnetic field in combination with the waveform of the sine wave current and the waveform of the square wave current. The first armature winding is used as the main drive winding and the second armature winding is used as the auxiliary regulation winding for illustration.

The sine wave inverter circuit is used for generating sine wave current, the sine wave current is input into the first armature winding, the first armature winding is used as a main driving winding, the main driving winding generates a main driving magnetic field to drive the motor to work, and referring to the waveform formula of the sine wave current shown in fig. 4, the waveform formula of the sine wave current is as follows:

The square wave inverter circuit is used for generating square wave current, the square wave current is input into the second armature winding, the second armature winding is used as an auxiliary adjusting winding, the auxiliary adjusting winding generates an auxiliary adjusting magnetic field, the auxiliary adjusting magnetic field can be added into the main driving magnetic field to adjust the working state of the motor, and referring to the figure 5, the waveform formula of the square wave is as follows:

The rotor of the motor rotates for 360 degrees, the electrical angle of the motor is p×360 degrees, p is the pole pair number, p is taken as 1 for illustration, the electrical angle of the motor works for 360 degrees, and the motor just corresponds to one running period of sine wave current. For example, the phase of the sine wave current is from 0 ° to 180 °, the rotor rotates half a turn of 180 °, which is defined as the front half-shaft of the motor, wherein the phase of the sine wave current is from 0 ° to 90 °, the rotor rotates quarter-turn of 90 °, which is defined as the front first half-shaft of the motor, and the phase of the sine wave current is from 90 ° to 180 °, the rotor rotates quarter-turn, which is defined as the front second half-shaft of the motor.

Similarly, the phase of the sine wave current is from 180 ° to 360 °, the rotor rotates half a turn 180 °, which is defined as the rear half-shaft of the motor, wherein the phase of the sine wave current is from 180 ° to 270 °, the rotor rotates quarter-turn 90 °, which is defined as the rear first half-shaft of the motor, and the phase of the sine wave current is from 270 ° to 360 °, the rotor rotates quarter-turn, which is defined as the rear second half-shaft of the motor.

When the phase of the sine wave current is respectively at 90 degrees and 270 degrees, the amplitude of the sine wave current is maximum, and the amplitude also represents the maximum torque of the motor.

Referring to fig. 6, when the motor is operated with a sine wave current, the load of the motor is changed and the impedance of the motor is changed accordingly, at this time, the controller detects the current ripple condition and acquires the ripple current amplitude and the current ripple phase in the current operation period, that is, one operation period in which the sine wave current is from 0 ° to 360 °, and the rotor of the motor rotates one turn in one operation period. Thus, the current ripple phases may occur at any of phases of 0 ° to 90 °, 90 ° to 180 °, 180 ° to 270 °, 270 ° to 360 °, respectively, in one operation cycle.

Case one: referring to fig. 7, a current ripple phase occurs at a phase of 90 ° or 270 °, and the ripple current amplitude increases, resulting in an increase in the motor maximum torque, and thus, it is necessary to reduce the sine wave current amplitude of the phase to reduce the motor maximum torque, at this time, a square wave current is input into the auxiliary adjustment winding, the amplitude direction of the square wave current is opposite to the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current coincides with the phase, whereby the auxiliary adjustment winding can generate an auxiliary adjustment magnetic field to attenuate the motor maximum torque at the sine wave current.

And a second case: referring to fig. 8, a current ripple phase occurs at a phase of 90 ° or 270 °, and the ripple current amplitude decreases, resulting in a decrease in the motor maximum torque, and thus, it is necessary to increase the sine wave current amplitude of the phase to increase the motor maximum torque, at this time, a square wave current is input to the auxiliary regulation winding, the amplitude direction of the square wave current is the same as the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current coincides with the phase, whereby the auxiliary regulation winding can generate an auxiliary regulation magnetic field to increase the motor maximum torque at the sine wave current.

And a third case: referring to fig. 9, the current ripple phase occurs at a phase between 0 ° and 90 ° and/or 180 ° and 270 °, and the ripple current amplitude increases, resulting in an increase in the motor front first half-shaft torque and/or the motor rear first half-shaft torque, and thus, it is necessary to reduce the motor front first half-shaft torque and/or the motor rear first half-shaft torque. At this time, the square wave current is input into the auxiliary adjusting winding, the amplitude direction of the square wave current is opposite to the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current is located on the current fluctuation phase, so that the auxiliary adjusting winding can generate an auxiliary adjusting magnetic field to reduce the front first half-axis torque and/or the rear first half-axis torque under the sine wave current.

Case four: referring to fig. 10, the current ripple phase occurs at a phase between 0 ° and 90 ° and/or 180 ° and 270 °, and the ripple current amplitude decreases, resulting in a decrease in the motor front first half-shaft torque and/or a decrease in the motor rear first half-shaft torque, and thus, an increase in the motor front first half-shaft torque and/or the motor rear first half-shaft torque is required. At this time, the square wave current is input into the auxiliary adjusting winding, the amplitude direction of the square wave current is the same as the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current is located on the current fluctuation phase, so that the auxiliary adjusting winding can generate an auxiliary adjusting magnetic field to increase the front first half-axis torque and/or the rear first half-axis torque under the sine wave current.

Case five: referring to fig. 11, the current ripple phase occurs at a phase between 90 ° and 180 ° and/or 270 ° and 360 °, and the ripple current amplitude increases, resulting in an increase in the motor front second half-shaft torque and/or an increase in the motor rear second half-shaft torque, and therefore, a reduction in the motor front second half-shaft torque and/or the motor rear second half-shaft torque is required. At this time, the square wave current is input into the auxiliary adjusting winding, the amplitude direction of the square wave current is opposite to the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current is located on the current fluctuation phase, so that the auxiliary adjusting winding can generate an auxiliary adjusting magnetic field to reduce the front second half-shaft torque and/or the rear second half-shaft torque under the sine wave current.

Case six: referring to fig. 12, the current ripple phase occurs at a phase between 90 ° and 180 ° and/or 270 ° and 360 °, and the ripple current amplitude decreases, resulting in an increase in the motor front second side torque and/or a decrease in the motor rear second side torque, and thus, an increase in the motor front second side torque and/or the motor rear second side torque is required. At this time, the square wave current is input into the auxiliary adjusting winding, the amplitude direction of the square wave current is the same as the amplitude direction of the sine wave current, and the maximum amplitude center of the square wave current is located on the current fluctuation phase, so that the auxiliary adjusting winding can generate an auxiliary adjusting magnetic field to increase the front second half-shaft torque and/or the rear second half-shaft torque under the sine wave current.

The fitted curves in the drawings of the specification combined in the above case one to case six are merely illustrative.

It is worth to say that how the square wave current can be regulated and controlled on the current fluctuation phase of the sine wave current is determined, the maximum amplitude center of the square wave current is mainly seen from the position of the maximum amplitude center of the square wave current, and the maximum amplitude center of the square wave current is regulated to the current fluctuation phase of the corresponding sine wave current by regulating the positions of the start angle theta 1 and the closing angle pi-theta 1 in the waveform formula of the square wave current.

At the moment, square wave current is input into the auxiliary adjusting winding, and an auxiliary adjusting magnetic field generated by the auxiliary adjusting winding is input into the main driving magnetic field, so that accurate adjustment and control of the main driving magnetic field can be realized.

Example two

The motor operation phase compensation method provided by the application adopts the following technical scheme:

Referring to fig. 13, a motor operation phase compensation method using the motor operation phase compensation system according to the above technical solution includes the following steps:

step S100, a main driving winding is used for generating a main driving magnetic field;

step S200, detecting the current fluctuation condition of the main driving winding, and acquiring the fluctuation current amplitude and the current fluctuation phase in the current operation period when the current of the main driving winding fluctuates;

Step S300, based on the fluctuating current amplitude and the current fluctuating phase, controlling the auxiliary regulating winding to form an auxiliary regulating magnetic field input into the main driving magnetic field only at the current fluctuating phase in a next operation cycle.

When the load changes, the controller only controls the auxiliary adjusting winding at the current fluctuation phase to form an auxiliary adjusting magnetic field to be input into the main driving magnetic field, so that the adjustment is completed, the current of the whole main driving winding is not required to be adjusted, and the adjustment efficiency is improved. In addition, the application can realize control by only controlling the auxiliary adjusting winding to input the auxiliary adjusting magnetic field into the main driving magnetic field, and can meet the different changing demands in the load operation, thereby simplifying the design difficulty of the controller.

The above embodiments are not intended to limit the scope of the present application, so: all equivalent changes in structure, shape and principle of the application should be covered in the scope of protection of the application.

Claims (6)

1. A motor operating phase compensation system comprising a motor and a controller, wherein a stator of the motor is provided with a first armature winding and a second armature winding;

The controller is internally provided with a sine wave inverter circuit and a square wave inverter circuit, the sine wave inverter circuit is connected to a first armature winding of the motor, the square wave inverter circuit is connected to a second armature winding of the motor, and when the first armature winding is used as a main driving winding, the second armature winding is used as an auxiliary adjusting winding, or when the second armature winding is used as a main driving winding, the first armature winding is used as an auxiliary adjusting winding;

The controller is used for detecting the current fluctuation condition of the main driving winding after the main driving winding is controlled to form a main driving magnetic field, and controlling the auxiliary adjusting winding to form an auxiliary adjusting magnetic field only at the current fluctuation phase position in the next operation period to be input into the main driving magnetic field.

2. The motor operation phase compensation system according to claim 1, wherein the controller is provided therein with a current detection unit, a phase conversion unit, and an auxiliary adjustment unit;

The current detection unit is used for detecting current fluctuation conditions in the main driving winding and acquiring fluctuation current amplitude values;

the phase conversion unit determines a current fluctuation phase based on the current fluctuation condition detected by the current detection unit;

the auxiliary regulating unit controls an auxiliary regulating winding to form an auxiliary regulating magnetic field to be input into the main driving magnetic field only at the current fluctuation phase in the next operation period based on the fluctuation current amplitude and the current fluctuation phase.

3. A motor operating phase compensation system according to claim 1 wherein the ratio of the number of windings of the main drive winding and the auxiliary regulation winding is 4:1 or 3:1.

4. The motor operating phase compensation system of claim 1 wherein the main drive winding is star or delta connected and the auxiliary trim winding is star or delta connected.

5. A motor operating phase compensation system according to claim 1 wherein,

The waveform formula of the sine wave current generated by the sine wave inverter circuit is as follows:

The waveform formula of the square wave current generated by the square wave inverter circuit is as follows:

6. a motor operation phase compensation method applying the motor operation phase compensation system according to any one of claims 1 to 5, characterized by comprising the steps of:

the main driving winding is used for generating a main driving magnetic field;

Detecting the current fluctuation condition of the main driving winding, and acquiring the fluctuation current amplitude and the current fluctuation phase in the current operation period when the current of the main driving winding fluctuates;

Based on the fluctuating current amplitude and the current fluctuating phase, an auxiliary regulating magnetic field is formed by controlling an auxiliary regulating winding to be input into the main driving magnetic field only at the current fluctuating phase in a next operation period.