CN116488641A - Frequency conversion method of W-band frequency synthesis module, W-band frequency synthesis module and system - Google Patents
Frequency conversion method of W-band frequency synthesis module, W-band frequency synthesis module and system Download PDFInfo
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- CN116488641A CN116488641A CN202310197419.XA CN202310197419A CN116488641A CN 116488641 A CN116488641 A CN 116488641A CN 202310197419 A CN202310197419 A CN 202310197419A CN 116488641 A CN116488641 A CN 116488641A
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- 101100350613 Arabidopsis thaliana PLL1 gene Proteins 0.000 claims description 25
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Classifications
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L7/00—Automatic control of frequency or phase; Synchronisation
- H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
- H03L7/07—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop using several loops, e.g. for redundant clock signal generation
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L7/00—Automatic control of frequency or phase; Synchronisation
- H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
- H03L7/08—Details of the phase-locked loop
- H03L7/085—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal
- H03L7/093—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal using special filtering or amplification characteristics in the loop
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L7/00—Automatic control of frequency or phase; Synchronisation
- H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
- H03L7/08—Details of the phase-locked loop
- H03L7/099—Details of the phase-locked loop concerning mainly the controlled oscillator of the loop
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L7/00—Automatic control of frequency or phase; Synchronisation
- H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
- H03L7/16—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop
- H03L7/18—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop using a frequency divider or counter in the loop
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L2207/00—Indexing scheme relating to automatic control of frequency or phase and to synchronisation
- H03L2207/12—Indirect frequency synthesis using a mixer in the phase-locked loop
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
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- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Physics & Mathematics (AREA)
- General Physics & Mathematics (AREA)
- Radar, Positioning & Navigation (AREA)
- Remote Sensing (AREA)
- Stabilization Of Oscillater, Synchronisation, Frequency Synthesizers (AREA)
Abstract
The invention discloses a frequency conversion method of a W-band frequency synthesizer module, the W-band frequency synthesizer module and a system, wherein the constant-temperature crystal oscillator is connected with a phase-locked loop (PLL) 1 and a phase-locked loop (PLL) 2, the phase-locked loop (PLL) 1 is sequentially connected with the 8 frequency multiplier through the DDS unit, a first radio frequency signal generating unit, a second radio frequency signal generating unit and a first frequency mixer, and the phase-locked loop (PLL) 2 is connected with the first frequency mixer; the first radio frequency signal generating unit and the second radio frequency signal generating unit have the same structure, the first radio frequency signal generating unit comprises a two-power divider, a second mixer and a band-pass filter, one output end of the two-power divider is connected with a local oscillation port of the second mixer through an amplifier, the other output end of the two-power divider is connected with an intermediate frequency port of the second mixer, and the output end of the mixer is connected with the band-pass filter. The invention can reduce broadband spurious generated by the DDS frequency source.
Description
Technical Field
The invention relates to the technical field of radars, in particular to a frequency conversion method of a W-band frequency synthesis module, the W-band frequency synthesis module and a system.
Background
Millimeter waves have the advantages of available frequency bandwidth, large information capacity, good confidentiality, small volume and the like, and are widely applied in the fields of communication, electronic countermeasure, radar, detection and the like in recent years. Particularly, V-band (50-75 GHz), E-band (60-90 GHz) and W (75-110 GHz) bands, have received much attention in communication in recent years. With the development of W-band radars and communication systems, the requirements for frequency synthesis units for generating radio frequency signals are increasing.
The scheme adopted by the current W-band frequency synthesizer module is mainly that after an L-band signal is generated by DDS (direct digital synthesis frequency source), a frequency multiplier is directly adopted to multiply the frequency to a C-band, then the frequency is moved from the C-band to an X-band in a mixing mode, and finally an 8-frequency multiplier is adopted to multiply the signal to the W-band. According to the working principle of the frequency multiplier, the spurious and phase noise degradation of the frequency multiplier follows the law of 20log (N), and the frequency generated by the DDS is usually changed to the W wave band and needs to be multiplied by more than 32 times, and according to the formula, the spurious and phase noise degradation is at least 30dB. With the DDS model that currently generally adopts: AD9915 is a column, and the narrow-band (< 500 KHz) spurious suppression can reach more than 95dBC, but the broadband (> 500 KHz) spurious suppression is only 70dBC (see figure 1), and when the frequency is converted to the W band, the broadband spurious suppression of the signal is within 40dBC, so that the signal quality is very affected.
Disclosure of Invention
In order to solve the problems, the invention provides a frequency conversion method of a W-band frequency synthesis module, which can reduce broadband spurious generated by a DDS frequency source and realize spurious reduction of W-band frequency.
In order to achieve the above purpose, the invention adopts the following technical scheme:
a W-band frequency synthesis module comprising: the device comprises a constant-temperature crystal oscillator, a phase-locked loop (PLL) 1, a phase-locked loop (PLL) 2, a Direct Digital Synthesis (DDS) unit, a first radio frequency signal generating unit, a second radio frequency signal generating unit, a first mixer and an 8 frequency multiplier;
the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2, the phase-locked loop PLL1 is connected with the 8 frequency multiplier through the DDS unit, the first radio frequency signal generating unit, the second radio frequency signal generating unit and the first frequency mixer in sequence, and the phase-locked loop PLL2 is connected with the first frequency mixer;
the first radio frequency signal generating unit and the second radio frequency signal generating unit have the same structure, the first radio frequency signal generating unit comprises a two-power divider, a second mixer and a band-pass filter, one output end of the two-power divider is connected with a local oscillation port of the second mixer through an amplifier, the other output end of the two-power divider is connected with an intermediate frequency port of the second mixer, and the output end of the mixer is connected with the band-pass filter.
And the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2 through the two power dividers.
Further, the phase-locked loop PLL1 is connected to the DDS unit sequentially through an amplifier, and the DDS unit is connected to the first radio frequency signal generating unit through a band-pass filter.
Further, the frequency of the phase-locked loop PLL1 is 3.5GHz, and the frequency range of the intermediate frequency signal output by the DDS unit is 425 MHz-550 MHz.
Further, the constant temperature crystal oscillator is characterized in that the frequency of the clock reference signal output by the constant temperature crystal oscillator is 100MHz.
The invention also provides a W-band frequency synthesizer system, which comprises the W-band frequency synthesizer module.
The invention also provides a frequency conversion method of the W-band frequency synthesis module, and the frequency conversion method of the W-band frequency synthesis module is applied to the W-band frequency synthesis module.
Further, the frequency conversion method includes the steps of:
dividing a 100MHz clock reference signal provided by a constant-temperature crystal oscillator into two paths through a two-way power divider, and respectively transmitting the two paths of clock reference signals to a phase-locked loop PLL1 and a phase-locked loop PLL2; the signal generated by the phase-locked loop PLL1 is amplified by an amplifier and then is used as a reference signal for the DDS, and the DDS generates an intermediate frequency signal IF1;
the intermediate frequency signal IF1 is distributed into two paths through a two-way power divider, wherein one path of the intermediate frequency signal IF1 is provided for a local oscillator end of a mixer to serve as a local oscillator signal LO1 after passing through an amplifier, the other path of the intermediate frequency signal IF2 is provided for an intermediate frequency port of a second mixer after passing through amplitude attenuation, the local oscillator signal LO1 and the intermediate frequency signal IF2 are synthesized into a mixed signal through the second mixer, and a mixed upper sideband signal RF1 of the mixed signal is selected through a band-pass filter;
the mixed upper sideband signal RF1 passes through the second radio frequency signal generating unit, is mixed with a local oscillation signal LO_T1 generated by the phase-locked loop PLL2 in the first mixer, and then sequentially passes through the lower sideband band-pass filter and the 8 frequency multiplier to obtain a 32 frequency multiplied radio frequency signal.
The invention has the beneficial effects that:
the invention comprises: the device comprises a constant-temperature crystal oscillator, a phase-locked loop (PLL) 1, a phase-locked loop (PLL) 2, a Direct Digital Synthesis (DDS) unit, a first radio frequency signal generating unit, a second radio frequency signal generating unit, a first mixer and an 8 frequency multiplier; the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2, the phase-locked loop PLL1 is connected with the 8 frequency multiplier through the DDS unit, the first radio frequency signal generating unit, the second radio frequency signal generating unit and the first frequency mixer in sequence, and the phase-locked loop PLL2 is connected with the first frequency mixer; the first radio frequency signal generating unit and the second radio frequency signal generating unit have the same structure, the first radio frequency signal generating unit comprises a two-power divider, a second mixer and a band-pass filter, one output end of the two-power divider is connected with a local oscillation port of the second mixer through an amplifier, the other output end of the two-power divider is connected with an intermediate frequency port of the second mixer, and the output end of the mixer is connected with the band-pass filter. The invention can reduce broadband spurious generated by the DDS frequency source and realize spurious reduction of the W-band frequency.
Drawings
Fig. 1 is a spurious distribution diagram of a conventional DDS.
Fig. 2 is a functional block diagram of the present invention.
Fig. 3 is a screenshot of the phase noise variation caused by the frequency conversion in the present invention.
Fig. 4 is a screenshot of the near-end spurious variation caused by frequency translation in the present invention.
Fig. 5 is a screenshot of the far-end spurious variation caused by frequency translation in the present invention.
Detailed Description
Referring to fig. 2, the present invention relates to a method for transforming a frequency of a W-band frequency synthesizer module, a W-band frequency synthesizer module and a system.
The W-band frequency synthesis module comprises: the device comprises a constant-temperature crystal oscillator, a phase-locked loop (PLL) 1, a phase-locked loop (PLL) 2, a Direct Digital Synthesis (DDS) unit, a first radio frequency signal generating unit, a second radio frequency signal generating unit, a first mixer and an 8 frequency multiplier; the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2, the phase-locked loop PLL1 is connected with the 8 frequency multiplier through the DDS unit, the first radio frequency signal generating unit, the second radio frequency signal generating unit and the first frequency mixer in sequence, and the phase-locked loop PLL2 is connected with the first frequency mixer; the first radio frequency signal generating unit and the second radio frequency signal generating unit have the same structure, the first radio frequency signal generating unit comprises a two-power divider, a second mixer and a band-pass filter, one output end of the two-power divider is connected with a local oscillation port of the second mixer through an amplifier, the other output end of the two-power divider is connected with an intermediate frequency port of the second mixer, and the output end of the mixer is connected with the band-pass filter.
Further, the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2 through the two power dividers. Further, the phase-locked loop PLL1 is connected to the DDS unit sequentially through an amplifier, and the DDS unit is connected to the first radio frequency signal generating unit through a band-pass filter. Further, the frequency of the phase-locked loop PLL1 is 3.5GHz, and the frequency range of the intermediate frequency signal output by the DDS unit is 425 MHz-550 MHz. Further, the constant temperature crystal oscillator is characterized in that the frequency of the clock reference signal output by the constant temperature crystal oscillator is 100MHz.
The invention is used for solving the problem of overlarge stray generated by the W-band intermediate frequency heald unit. The invention is realized by the following technical scheme: as shown in fig. 2, the frequency conversion part for converting the low frequency band into the C band is made into a twice self-mixing mode to realize the frequency conversion of the signal generated by the DDS into the C band, then the frequency is mixed into the X band through the high local oscillation signal, and finally the frequency is doubled into the W band through 8 times.
The invention will now be further described with reference to examples, figures: in the invention, as shown in fig. 2, the purpose of increasing the frequency by 4 times is achieved after the low-frequency signal is subjected to self-mixing twice by using the mixer. Firstly, a 100MHz clock reference signal provided by a constant temperature crystal oscillator is divided into two paths by a two-way power divider and is respectively sent to a phase-locked loop PLL1 and a phase-locked loop PLL2. The PLL1 generates a 3.5GHz signal, and amplifies the signal by an amplifier to make a reference signal for the DDS. The DDS generates an intermediate frequency signal IF1 (signal bandwidth 125 MHz) of 425MHz to 550MHz. The IF1 signal is distributed into two paths by a two-way power divider, wherein one path is provided for a local oscillator end of the mixer to serve as a local oscillator signal LO1 after passing through an amplifier, the other path is provided for an intermediate frequency port of the mixer to serve as an intermediate frequency signal IF2 after passing through amplitude attenuation, and the signal is used for selecting a mixed upper sideband signal RF1 by a band-pass filter after passing through the mixer. The following frequency relationship can be known from the upper sideband mixing principle:
RF1＝IF2+LO1 (1)
since during mixing the frequency of LO1 and the frequency of IF2 are both obtained after IF1 power division, the following frequency relationship is readily obtained:
LO1＝IF2＝IF1 (2)
substituting equation (2) into (1) yields the following frequency relationship:
RF1＝2*IF1 (3)
thus, after one-time mixing, an intermediate frequency signal IF2 (bandwidth 250 MHz) of 850 MHz-1100 MHz can be obtained, and the IF2 not only doubles the frequency but also doubles the working bandwidth relative to the IF 1. Similarly, after the second mixing, a frequency range is obtained: an intermediate frequency signal IF2 with a bandwidth of 500MHz ranging from 1700MHz to 2200 MHz.
Thus, the function of frequency multiplication of the intermediate frequency signal 4 output by the DDS is realized by utilizing twice frequency mixing. From the analysis of the actual measurement pictures in fig. 5, it can be seen that the broadband spurious signals of the signal output by the DDS will not be degraded, and have a suppression effect of more than 10 dB.
The IF2 and the local oscillation signal LO_T1 (13.7 GHz) generated by the PLL2 are mixed once and then pass through a lower sideband bandpass filter to obtain a radio frequency signal RF1 (bandwidth 500 MHz) of 11.5 GHz-12 GHz.
Finally, the RF1 can obtain a radio frequency signal (bandwidth 4 GHz) of 92 GHz-96 GHz after passing through an 8-frequency multiplier once.
The invention is proved to be feasible through test. As a result, the broadband spurious of the signal is reduced by more than 22dBC in the 96 GHz-92 GHz mode compared with the direct frequency doubling mode. As shown in fig. 3 to 5, it is understood from fig. 3 and 4 that the scheme of the present invention can still follow the 20log (N) rule in the degradation of the narrowband spurious signals, but in the variation of the wideband spurious signals, it is known from fig. 3 and 5 that the scheme of the present invention can not degrade the wideband spurious signals caused by the low frequency signals but can provide the wideband spurious suppression of 10dB or more.
The invention also provides a W-band frequency synthesizer system, which comprises the W-band frequency synthesizer module.
The invention also provides a frequency conversion method of the W-band frequency synthesis module, and the frequency conversion method of the W-band frequency synthesis module is applied to the W-band frequency synthesis module.
Further, the frequency conversion method includes the steps of:
dividing a 100MHz clock reference signal provided by a constant-temperature crystal oscillator into two paths through a two-way power divider, and respectively transmitting the two paths of clock reference signals to a phase-locked loop PLL1 and a phase-locked loop PLL2; the signal generated by the phase-locked loop PLL1 is amplified by an amplifier and then is used as a reference signal for the DDS, and the DDS generates an intermediate frequency signal IF1;
the intermediate frequency signal IF1 is distributed into two paths through a two-way power divider, wherein one path of the intermediate frequency signal IF1 is provided for a local oscillator end of a mixer to serve as a local oscillator signal LO1 after passing through an amplifier, the other path of the intermediate frequency signal IF2 is provided for an intermediate frequency port of a second mixer after passing through amplitude attenuation, the local oscillator signal LO1 and the intermediate frequency signal IF2 are synthesized into a mixed signal through the second mixer, and a mixed upper sideband signal RF1 of the mixed signal is selected through a band-pass filter;
the mixed upper sideband signal RF1 passes through the second radio frequency signal generating unit, is mixed with a local oscillation signal LO_T1 generated by the phase-locked loop PLL2 in the first mixer, and then sequentially passes through the lower sideband band-pass filter and the 8 frequency multiplier to obtain a 32 frequency multiplied radio frequency signal.
The above embodiments are merely illustrative of the preferred embodiments of the present invention and are not intended to limit the scope of the present invention, and various modifications and improvements made by those skilled in the art to the technical solution of the present invention should fall within the scope of protection defined by the claims of the present invention without departing from the spirit of the design of the present invention.
Claims (8)
1. A W-band frequency synthesizer module comprising: the device comprises a constant-temperature crystal oscillator, a phase-locked loop (PLL) 1, a phase-locked loop (PLL) 2, a Direct Digital Synthesis (DDS) unit, a first radio frequency signal generating unit, a second radio frequency signal generating unit, a first mixer and an 8 frequency multiplier;
the constant-temperature crystal oscillator is connected with the phase-locked loop PLL1 and the phase-locked loop PLL2, the phase-locked loop PLL1 is connected with the 8 frequency multiplier through the DDS unit, the first radio frequency signal generating unit, the second radio frequency signal generating unit and the first frequency mixer in sequence, and the phase-locked loop PLL2 is connected with the first frequency mixer;
the first radio frequency signal generating unit and the second radio frequency signal generating unit have the same structure, the first radio frequency signal generating unit comprises a two-power divider, a second mixer and a band-pass filter, one output end of the two-power divider is connected with a local oscillation port of the second mixer through an amplifier, the other output end of the two-power divider is connected with an intermediate frequency port of the second mixer, and the output end of the mixer is connected with the band-pass filter.
2. The W-band frequency synthesizer module of claim 1, wherein the thermostatic crystal oscillator is connected to the phase-locked loop PLL1 and the phase-locked loop PLL2 through a two-power divider.
3. The W-band frequency synthesizer module of claim 1, wherein the phase-locked loop PLL1 is connected to the DDS unit sequentially through an amplifier, and the DDS unit is connected to the first radio frequency signal generating unit through a band-pass filter.
4. The W-band frequency synthesizer module of claim 1, wherein the frequency of the output of the phase-locked loop PLL1 is 3.5ghz, and the frequency range of the intermediate frequency signal output by the dds unit is 425MHz to 550MHz.
5. The W-band frequency synthesizer module of claim 1, wherein the frequency of the clock reference signal output by the oven controlled crystal oscillator is 100MHz.
6. A W-band frequency synthesis system, characterized in that it comprises a W-band frequency synthesis module according to any of claims 1-5.
7. A frequency conversion method of a W-band frequency synthesis module, wherein the frequency conversion method of the W-band frequency synthesis module is applied to the W-band frequency synthesis module according to any one of claims 1 to 5.
8. The frequency conversion method of a W-band frequency synthesis module according to claim 7, wherein the frequency conversion method comprises the steps of:
dividing a 100MHz clock reference signal provided by a constant-temperature crystal oscillator into two paths through a two-way power divider, and respectively transmitting the two paths of clock reference signals to a phase-locked loop PLL1 and a phase-locked loop PLL2; the signal generated by the phase-locked loop PLL1 is amplified by an amplifier and then is used as a reference signal for the DDS, and the DDS generates an intermediate frequency signal IF1;
the intermediate frequency signal IF1 is distributed into two paths through a two-way power divider, wherein one path of the intermediate frequency signal IF1 is provided for a local oscillator end of a mixer to serve as a local oscillator signal LO1 after passing through an amplifier, the other path of the intermediate frequency signal IF2 is provided for an intermediate frequency port of a second mixer after passing through amplitude attenuation, the local oscillator signal LO1 and the intermediate frequency signal IF2 are synthesized into a mixed signal through the second mixer, and a mixed upper sideband signal RF1 of the mixed signal is selected through a band-pass filter;
the mixed upper sideband signal RF1 passes through the second radio frequency signal generating unit, is mixed with a local oscillation signal LO_T1 generated by the phase-locked loop PLL2 in the first mixer, and then sequentially passes through the lower sideband band-pass filter and the 8 frequency multiplier to obtain a 32 frequency multiplied radio frequency signal.
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