CN116192585B - Partial matched filtering signal capturing method based on scattered packet pilot frequency structure - Google Patents
Partial matched filtering signal capturing method based on scattered packet pilot frequency structure Download PDFInfo
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- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
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- H—ELECTRICITY
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- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
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- H—ELECTRICITY
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- H04L7/00—Arrangements for synchronising receiver with transmitter
- H04L7/0054—Detection of the synchronisation error by features other than the received signal transition
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- H—ELECTRICITY
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- H04L2027/0024—Carrier regulation at the receiver end
- H04L2027/0026—Correction of carrier offset
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Abstract
The invention discloses a partially matched filtering signal capturing method based on a scattered packet pilot frequency structure, which mainly solves the problem of low frequency domain capturing precision in the prior art. The implementation scheme is that 1) a local grouping pilot sequence is inserted into an encoded information sequence, the encoded information sequence is modulated and then is sent to a channel for transmission, 2) a receiving end stores a received signal into a delay register, 3) the signal in the delay register is grouped and a received grouping pilot sequence is extracted, a segmented matching filter is utilized for carrying out correlation operation on the local pilot grouping sequence and the received pilot grouping sequence, a correlation output value is subjected to FFT conversion and modulo value, the maximum value of the correlation output value is recorded, the received signal is delayed by one sampling signal, 4) the recorded maximum value sequence is compared with a set threshold value to judge a capturing result, and a timing deviation estimated value and a frequency deviation estimated value are calculated when the capturing is successful. The invention reduces the sampling rate, improves the frequency domain capturing precision, and can be used for a burst digital communication system with high-speed transmission.
Description
Technical Field
The invention belongs to the technical field of wireless communication, and particularly relates to a signal capturing method which can be used for a burst digital communication system for high-speed transmission.
Background
The acquisition of the synchronization of the signals is always an indispensable loop of the communication system, and the performance of the communication system depends to a certain extent on the speed and accuracy of the synchronization of the system to the received signals, and if the synchronization is not accurate, the received signals cannot be processed. The synchronization includes the capture and tracking of signals, the capture is used for roughly estimating the code phase and the carrier Doppler, and the fine estimation of the code phase and the carrier Doppler is well laid in the following tracking process, so the capture process is the premise and the basis of accurate synchronization.
Among the existing acquisition algorithms, the synchronous acquisition algorithm combined with the fast Fourier transform FFT is widely applied to short burst communication because of high search speed and short acquisition time, and the acquisition algorithm is used for estimating and compensating timing errors and carrier frequency offset based on time domain correlation and FFT by utilizing a section of known pilot sequence, such as Povey G J R, and the PMF-FFT synchronous acquisition algorithm based on a partial matched filter and the fast Fourier transform, which is proposed by Grant P M in "Simplified matched filter receiver designs for spread spectrumcommunications applications[J].Electronics&Communication Engineering Journal,1993,5(2):59-64.", and the basic principle is that received pilot frequency and local pilot frequency are grouped according to the same length and then are subjected to cross correlation, and peak values in the cross correlation result are selected after FFT transformation and modulo values. And when the peak value exceeds the acquisition threshold value, the acquisition is successful, and the corresponding Doppler frequency offset and code phase are obtained. Although the method is low in complexity and easy to realize, under the conditions of low pilot frequency overhead and high signal transmission rate, FFT conversion with higher points is needed to ensure the spectrum resolution, namely, the grouping is larger, so that the length of each group is too short, the anti-interference capability is greatly reduced, and good estimation accuracy cannot be ensured. If a certain packet length is required to be maintained for resisting interference, the number of packets is correspondingly reduced, so that the number of FFT points is reduced, and the frequency resolution is reduced.
Disclosure of Invention
Aiming at the defects of the prior art, the invention provides a partially matched filtering signal capturing method based on a scattered packet pilot structure, so as to improve the frequency domain capturing precision under the condition of low pilot overhead and overhigh data transmission rate.
The technical idea of the invention is that the sampling rate of the receiving end in FFT is reduced and the frequency domain capturing precision is improved by discretely inserting the grouped pilot frequency sequence into the grouped information sequence, and the implementation scheme comprises the following steps:
(1) The transmitting end transmits a baseband sampling signal:
A local pilot sequence u' is selected at the transmitting end and grouped to obtain a local grouped pilot sequence u= [ u 1u2…ui…uN ], where u i is an i-th group of local grouped pilot sequences, i=1, 2, N, N u' is the total length of the local pilot sequence, l 0 is the length of each set of pilot sequences;
Inserting a local packet pilot sequence u into the coded information sequence d to form a transmission sequence a= [ u 1 d1u2 d2…ui di…uN dN ], wherein d i is an i-th group information sequence;
modulating the transmission sequence a to obtain a baseband sampling signal s, and sending the baseband sampling signal s into a Gaussian white noise channel for transmission;
(2) The receiving end receives the signal sent by the sending end and stores the received signal r into the delay register;
(3) Dividing the signals in the delay register into N groups, and extracting a received packet pilot sequence p= [ p 1 p2…pi…pN ] from each group of received signals, wherein p i is an i-th group of received packet pilot sequences;
(4) Using the local group pilot sequence u and the received group pilot sequence p to make synchronous capture:
(4a) Storing the local grouping pilot sequence u into N segmentation matched filters PMF as coefficients of an FIR filter, and enabling the received grouping pilot sequence p to pass through the filter to obtain N relevant output values;
(4b) Performing N-point FFT (fast Fourier transform) on the N related output values, taking a modulus value, obtaining FFT conversion results Z= [ Z 1 Z2…Zi…ZN ] of the N related output values, and recording the maximum value Z max in Z and the position k max of the maximum value in Z;
(4c) The delay register performs a delay on the received signal r Time delay, wherein f s is the baseband signal sampling rate, repeating the steps (3) - (4 b) until the working times of the delay register is equal to l 0/3, and recording the maximum value Z max in Z recorded when the working times of the delay register is h as Z' h to obtain the total maximum value data sequenceh=0,1,...,l0/3;
(4D) An acquisition threshold Z 0 is set according to the channel conditions and the maximum value Z 'n in Z' is taken and compared with it:
If Z' n>Z0, then the acquisition is successful, and (4 e) is executed;
otherwise, the acquisition is regarded as failure;
(4e) According to the working times n of the delay register corresponding to Z' n, calculating to obtain a timing deviation estimated value Obtaining a frequency offset estimation value by calculating the corresponding k max
Wherein, For the sampling rate of the received packet pilot p i, Q is the over-sampling multiple, f s is the baseband signal sampling rate, l is the length of each set of pilot plus information sequence, and N is the FFT transform point number.
Compared with the prior art, the invention has the following advantages:
Aiming at the situation that the sampling rate of a baseband signal is too high in a high-speed transmission mode, compared with the prior PMF-FFT algorithm, the method can lead the equivalent sampling rate of adjacent grouped pilot sequences to be smaller, has fewer FFT operation points, reduces operation complexity, reduces the number of pilot groups, increases the grouped pilot length, improves the noise resistance and can obtain better estimation precision by inserting the pilot groups into the data frames.
Drawings
FIG. 1 is a schematic diagram of a conventional burst communication system to which the present invention is applied;
FIG. 2 is a flow chart of an implementation of the present invention;
Fig. 3 is a schematic diagram of a frame structure used in the present invention and a frame structure used in the prior art. .
Detailed Description
Embodiments and effects of the present invention are further described below with reference to the accompanying drawings.
Referring to fig. 1, the conventional burst communication system is to firstly frame a pilot sequence and an encoded information sequence at a transmitting end, then modulate the framed sequence and transmit the sequence to a channel for transmission, firstly perform timing synchronization and carrier synchronization on signals at a receiving end, and then demodulate and decode the synchronized signals to restore the transmitted information sequence.
In burst communication systems, correct signals cannot be received without timing synchronization, and large carrier frequency offset is generated on the basis of original signals due to the existence of Doppler frequency offset. If no measures are taken, the received signal is insufficient to recover the original signal, so that the communication quality of the system is lowered. The embodiment solves the problem of timing synchronization and carrier synchronization of signals at a receiving end in a burst communication system, and provides a partial matched filtering signal capturing method based on a scattered packet pilot frequency structure.
Referring to fig. 2, the implementation steps of this example are as follows:
Step 1, a transmitting end transmits a baseband sampling signal s.
(1.1) Selecting a local pilot sequence u' at a transmitting end:
u'=[u'(0)u'(1)...u'(n)...u'(Nu'-1)]
Where u ' (N) represents the nth bit in the local pilot sequence u ', n=0, 1,..n u'-1,Nu' is the length of the local pilot sequence u ', μ e {1,2,..n u' -1} and is reciprocal to N u', q is any integer. In this example, μ=1 and q=0 are taken.
(1.2) Dividing the local pilot sequence u' into N groups of equal length to obtain a local packet pilot sequence u= [ u 1 u2…ui…uN ]:
ui＝[u'((i-1)*Nu'/N+1),u'((i-1)*Nu'/N+2),…,u'(i*Nu'/N)]
where u i is the i-th group local packet pilot sequence, i=1, 2, a., N, For the number of packets, N u' is the total length of the local pilot sequence, l 0 is the length of each group of pilot sequences, x is the multiplied symbol;
(1.3) the sending end encodes the binary information sequence and divides the binary information sequence into N groups with equal length to obtain a grouped information sequence d= [ d 1 d2…di…dN ]:
di＝[d((i-1)*Nd/N+1),d((i-1)*Nd/N+2),…,d(i*Nd/N)];
Where d i is the i-th group of information sequences and N d is the total length of the encoded information sequence d.
(1.4) The transmitting end places the i-th group local grouping pilot u i in front of the coded i-th group information sequence d i to form a transmitting sequence a= [ u 1 d1 u2 d2…ui di…uN dN ];
and (1.5) modulating the transmission sequence a to obtain a baseband sampling signal s, and sending the baseband sampling signal s into a Gaussian white noise channel to be transmitted.
And step 2, the receiving end processes the received signal to obtain a received packet pilot sequence p.
(2.1) The receiving end receives the signal sent by the sending end, and the received signal r is expressed as:
r=[r(0)r(1)...r(m)...r(Nr-1)]
Where r (m) represents an m-th sample point in the received signal r, m=0, 1, & gt, N r -1, Δf is carrier frequency offset, f s is baseband signal sampling rate, N r is length of the received signal r, N r＝(Nu'+Nd) Q is an oversampling multiple, s (m) represents baseband sampled signal, w (m) represents complex gaussian random noise with mean value of zero and variance of N 0/2, N 0 is noise single-side power spectral density, and j is complex unit;
(2.2) the receiving end stores the received signal r into the delay register;
(2.3) dividing the signals in the delay register into N groups, extracting the first q·n u'/N sampling signals of each group by l= (N u'+Nd)/N, to obtain an oversampled received packet pilot sequence p ' = [ p ' 1p'2…p'i…p'N ], wherein p ' i is the i-th oversampled received packet pilot sequence, expressed as follows:
p'i＝[r((i-1)*Nr/N)r((i-1)*Nr/N+1)…r(((i-1)*Nr+Q*Nu')/N)]
Wherein N r is the length of the received signal r, N r＝(Nu'+Nd) Q, Q is the oversampling multiple, and N u' is the total length of the local pilot sequence u';
(2.3) sampling p' i from the first sampling signal every other (Q-1) point to obtain an i-th group received packet pilot sequence p i, and finally obtaining a received packet pilot sequence p= [ p 1 p2…pi…pN ], wherein i is more than or equal to 1 and less than or equal to N.
And 3, performing synchronous acquisition by using the received packet pilot sequence p= [ p 1 p2…pi…pN ] and the local packet pilot sequence u= [ u 1u2…ui…uN ].
(3.1) Multiplying the i-th group received packet pilot sequence p i by the conjugate transpose of the i-th group local packet pilot sequence u i to obtain N correlation values z:
z=[z1 z2…zi…zN]
zi＝piui *
Where z i represents the ith correlation value, u i * is the conjugate transpose of u i;
(3.2) performing N-point FFT conversion on the N related output values and taking a modulus value to obtain FFT conversion results Z of the N related output values:
Z=|FFT(z,N)|
Wherein z is all relevant values, and N is FFT conversion point number;
(3.3) record the maximum value Z max in Z and the position k max of the maximum value in Z;
(3.4) delay register to receive signal r Time delay, wherein f s is the baseband signal sampling rate, repeating the steps (2.3) to (3.3) until the number of times of operation of the delay register is equal to l 0/3, and recording the maximum value Z max in Z recorded each time as Z 'h to obtain a total maximum value data sequence Z':
Where h=0, 1..i 0/3 is the number of times the delay register is operated;
(3.5) setting a capture threshold Z 0 according to channel condition, and taking out the maximum value Z ' n in Z ' to compare with, if Z ' n>Z0, the capture is successful, and executing (3.6), otherwise, the capture is regarded as failure;
(3.6) calculating the timing deviation estimated value according to the number of times n of the operation of the delay register corresponding to Z' n Obtaining a frequency offset estimation value by calculating the corresponding k max Completing synchronous capturing;
Wherein, For the sampling rate of the received packet pilot p i, Q is the over-sampling multiple, f s is the baseband signal sampling rate, l is the length of each set of pilot plus information sequence, and N is the FFT transform point number.
The effect of the invention can be further explained by the calculation result of the frequency domain capturing precision achieved by using the PMF-FFT method for the existing frame structure and the frame structure of the invention:
1. System parameters:
one of the application scenarios of the invention is that the channel coding is turbo code, the modulation mode adopts QPSK, the pilot frequency is Chu sequence with length of 1560 bits, the data length is 11240 bits, and the number of packets is 10. The carrier frequency offset Δf=6000 Hz of the channel, the number of over-sampling points q=4, and the baseband signal sampling rate f s =51.2 Mbps.
The existing frame structure is shown in fig. 3a, where the pilot signal is placed before the data signal as a whole, and the interval length of adjacent pilot sequences is l 0.
The frame structure of the present invention is shown in fig. 3b, which divides pilot signals and data signals into 10 groups, and inserts the grouped pilot signals into the grouped data signals before the adjacent pilot sequence interval length is l.
2. Calculating the corresponding frequency spectrum resolution of two frame structures
Spectral resolution corresponding to existing frame structure:
spectral resolution corresponding to the frame structure of the present invention:
compared with the spectrum resolution corresponding to the existing frame structure, the spectrum resolution corresponding to the frame structure is improved by 8.21 times, so that better capturing precision can be achieved, and system performance can be greatly improved.
Claims (7)
1. A method for partially matched filtered signal acquisition based on a scattered packet pilot structure, comprising:
(1) The transmitting end transmits a baseband sampling signal:
A local pilot sequence u' is selected at the transmitting end and grouped to obtain a local grouped pilot sequence u= [ u 1 u2…ui…uN ], where u i is an i-th group of local grouped pilot sequences, i=1, 2, N, N u' is the total length of the local pilot sequence, l 0 is the length of each set of pilot sequences;
Inserting a local packet pilot sequence u into the coded information sequence d to form a transmission sequence a= [ u 1 d1 u2d2…ui di…uN dN ], wherein d i is an i-th group information sequence;
modulating the transmission sequence a to obtain a baseband sampling signal s, and sending the baseband sampling signal s into a Gaussian white noise channel for transmission;
(2) The receiving end receives the signal sent by the sending end and stores the received signal r into the delay register;
(3) Dividing the signals in the delay register into N groups, and extracting a received packet pilot sequence p= [ p 1 p2…pi…pN ] from each group of received signals, wherein p i is an i-th group of received packet pilot sequences;
(4) Using the local group pilot sequence u and the received group pilot sequence p to make synchronous capture:
(4a) Storing the local grouping pilot sequence u into N segmentation matched filters PMF as coefficients of an FIR filter, and enabling the received grouping pilot sequence p to pass through the filter to obtain N relevant output values;
(4b) Performing N-point FFT (fast Fourier transform) on the N related output values, taking a modulus value, obtaining FFT conversion results Z= [ Z 1 Z2…Zi…ZN ] of the N related output values, and recording the maximum value Z max in Z and the position k max of the maximum value in Z;
(4c) The delay register performs a delay on the received signal r Time delay, wherein f s is the baseband signal sampling rate, repeating the steps (3) - (4 b) until the working times of the delay register is equal to l 0/3, and recording the maximum value Z max in Z recorded when the working times of the delay register is h as Z' h to obtain the total maximum value data sequenceh=0,1,...,l0/3;
(4D) An acquisition threshold Z 0 is set according to the channel conditions and the maximum value Z 'n in Z' is taken and compared with it:
If Z' n>Z0, then the acquisition is successful, and (4 e) is executed;
otherwise, the acquisition is regarded as failure;
(4e) According to the working times n of the delay register corresponding to Z' n, calculating to obtain a timing deviation estimated value Obtaining a frequency offset estimation value by calculating the corresponding k max
Wherein, For the sampling rate of the received packet pilot p i, Q is the over-sampling multiple, f s is the baseband signal sampling rate, l is the length of each set of pilot plus information sequence, and N is the FFT transform point number.
2. The method according to claim 1, wherein the local pilot sequence u' in the step (1) is represented as follows:
u'=[u'(0)u'(1)...u'(n)...u'(Nu'-1)]
Where u ' (N) represents the nth bit in the local pilot sequence u ', n=0, 1, N u'-1,Nu' is the length of the local pilot u ', μe {1,2, N u' -1} and is reciprocal to N u', and q is any integer.
3. The method as set forth in claim 1, wherein the i-th local packet pilot sequence u i and the i-th information sequence d i in step (1) are expressed as follows:
ui＝[u'((i-1)*Nu'/N+1),u'((i-1)*Nu'/N+2),…,u'(i*Nu'/N)];
di＝[d((i-1)*Nd/N+1),d((i-1)*Nd/N+2),…,d(i*Nd/N)];
Where 1.ltoreq.i.ltoreq.N, N is the number of packets, N u' is the total length of the local pilot sequence u', and N d is the total length of the encoded information sequence d.
4. The method according to claim 1, wherein the received signal r in step (2) is represented as follows:
r=[r(0)r(1)...r(m)...r(Nr-1)]
Where r (m) represents an m-th sample point in the received signal r, m=0, 1, N r -1, Δf is carrier frequency offset, f s is baseband signal sampling rate, N r is length of the received signal r, N r＝(Nu'+Nd) Q, s (m) represents baseband sampling signal, w (m) represents complex gaussian random noise with mean value of zero and variance of N 0/2, N 0 is noise single-side power spectral density, and j is complex unit.
5. The method according to claim 1, wherein the step (3) extracts the received packet pilot sequence p from each set of received signals by:
(3a) Extracting the first q·n u'/N sampling signals from the received signal r divided into N groups, to obtain an oversampled received packet pilot sequence p ' = [ p ' 1p'2…p'i…p'N ], where p ' i is an i-th oversampled received packet pilot sequence, expressed as follows:
p'i＝[r((i-1)*Nr/N)r((i-1)*Nr/N+1)…r(((i-1)*Nr+Q*Nu')/N)]
Wherein N r is the length of the received signal r, N r＝(Nu'+Nd) Q, Q is the oversampling multiple, and N u' is the total length of the local pilot sequence u';
(3b) And taking one sampling signal from the first sampling signal at intervals of (Q-1) to obtain an i-th group of group receiving pilot sequence p i, and finally obtaining a group receiving pilot sequence p= [ p 1 p2…pi…pN ], wherein i is more than or equal to 1 and less than or equal to N.
6. The method of claim 1, wherein N correlation output values are obtained in step (4 a) as follows:
z=[z1 z2…zi…zN]
Where z i＝piui * represents the i-th correlation value, u i * is the conjugate transpose of u i, i=1, 2.
7. The method of claim 1, wherein said step (4 b) performs an N-point FFT on the N correlation output values and takes a modulus value as follows:
z= |fft (Z, N) |, where Z is all correlation values and N is the FFT transform point number.
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