CN115494464B - Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium - Google Patents
Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium Download PDFInfo
- Publication number
- CN115494464B CN115494464B CN202211067975.7A CN202211067975A CN115494464B CN 115494464 B CN115494464 B CN 115494464B CN 202211067975 A CN202211067975 A CN 202211067975A CN 115494464 B CN115494464 B CN 115494464B
- Authority
- CN
- China
- Prior art keywords
- signal
- pulse width
- compensated
- pulse
- predistortion
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 238000000034 method Methods 0.000 title claims abstract description 43
- 230000005540 biological transmission Effects 0.000 claims abstract description 36
- 230000006870 function Effects 0.000 claims description 19
- 230000015654 memory Effects 0.000 claims description 18
- 238000001914 filtration Methods 0.000 claims description 13
- 230000035485 pulse pressure Effects 0.000 claims description 12
- 238000007906 compression Methods 0.000 claims description 10
- 230000006835 compression Effects 0.000 claims description 9
- 238000004364 calculation method Methods 0.000 claims description 7
- 238000001514 detection method Methods 0.000 claims description 6
- 238000005070 sampling Methods 0.000 claims description 4
- 230000021615 conjugation Effects 0.000 claims description 3
- 230000009466 transformation Effects 0.000 claims description 3
- 238000012545 processing Methods 0.000 description 7
- 230000008569 process Effects 0.000 description 5
- IAZDPXIOMUYVGZ-UHFFFAOYSA-N Dimethylsulphoxide Chemical compound CS(C)=O IAZDPXIOMUYVGZ-UHFFFAOYSA-N 0.000 description 3
- 238000005516 engineering process Methods 0.000 description 3
- 238000003384 imaging method Methods 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 239000007787 solid Substances 0.000 description 2
- 238000001228 spectrum Methods 0.000 description 2
- 238000012360 testing method Methods 0.000 description 2
- 238000003491 array Methods 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 238000004590 computer program Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 238000010295 mobile communication Methods 0.000 description 1
- 230000003287 optical effect Effects 0.000 description 1
Classifications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/40—Means for monitoring or calibrating
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/88—Radar or analogous systems specially adapted for specific applications
- G01S13/89—Radar or analogous systems specially adapted for specific applications for mapping or imaging
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/28—Details of pulse systems
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/28—Details of pulse systems
- G01S7/282—Transmitters
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/28—Details of pulse systems
- G01S7/285—Receivers
Landscapes
- Engineering & Computer Science (AREA)
- Remote Sensing (AREA)
- Radar, Positioning & Navigation (AREA)
- Physics & Mathematics (AREA)
- Computer Networks & Wireless Communication (AREA)
- General Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Amplifiers (AREA)
Abstract
The invention discloses a predistortion compensation method of a linear frequency modulation signal, electronic equipment and a storage medium, wherein the method comprises the following steps: acquiring a linear frequency modulation signal to be compensated, and a first transmission feedback signal and a second transmission feedback signal of the linear frequency modulation signal to be compensated; respectively acquiring pulse position information of a linear frequency modulation signal to be compensated, a first transmission feedback signal and a second transmission feedback signal; respectively calculating the amplitude and the phase of a pulse width signal to be compensated, a first pulse width signal and a second pulse width signal; calculating according to the amplitudes of the first pulse width signal and the second pulse width signal to obtain the amplitude predistortion amount of the pulse width signal to be compensated; calculating according to the phase angles of the first pulse width signal and the second pulse width signal to obtain the phase angle predistortion amount of the pulse width signal to be compensated; and respectively compensating the amplitude and the phase angle of the compensation pulse width signal according to the amplitude predistortion amount and the phase angle predistortion amount to obtain a compensated linear frequency modulation signal. The method of the invention can reduce the calculated amount of predistortion compensation.
Description
Technical Field
The invention relates to the technical field of radar system integrated test and imaging processing, in particular to a predistortion compensation method for a linear frequency modulation signal, electronic equipment and a readable storage medium.
Background
When the radar system is set, in order to comprehensively compensate the influence of time-varying phase errors brought by a system receiving and transmitting channel on imaging processing, the calibration signals are generally collected and analyzed, then the phase errors and the amplitude errors of the calibration signals are extracted and reversely compensated into a transmitting signal of a frequency modulation source end, so that a basically ideal signal waveform can be obtained at a receiving end, and the compression index after processing is improved, and the process is generally called predistortion compensation.
In a high-resolution radar, an ultra-wideband chirp signal is the most commonly used radar signal based on the phase frequency characteristics of selectable time-wideband width and square law and the characteristic that the frequency spectrum characteristic is close to a rectangle, but correspondingly, the predistortion compensation of the ultra-wideband chirp signal by using an analog predistortion compensation technology or a digital predistortion compensation technology generates larger calculated amount, so that a large amount of hardware resources are consumed, and the whole system is not beneficial to develop towards miniaturization and light weight.
Disclosure of Invention
In view of this, the embodiments of the present invention provide a predistortion compensation method for a chirped signal, an electronic device, and a readable storage medium, so as to solve the problem that the calculation amount is large and the corresponding resource consumption is large when the predistortion compensation technology is used to perform predistortion compensation on the chirped signal of ultra wideband.
According to a first aspect, an embodiment of the present invention provides a predistortion compensation method for a chirp signal, including the steps of:
Acquiring a linear frequency modulation signal to be compensated, and a first transmission feedback signal and a second transmission feedback signal of the linear frequency modulation signal to be compensated; the first transmitting feedback signal is a signal fed back by the linear frequency modulation signal to be compensated after passing through the power divider, and the second transmitting feedback signal is a signal fed back by the linear frequency modulation signal to be compensated after passing through the load and the power divider;
Respectively acquiring pulse position information of a to-be-compensated linear frequency modulation signal, a first transmission feedback signal and a second transmission feedback signal, correspondingly extracting pulse width part signals of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal according to the pulse position information, and obtaining a to-be-compensated pulse width signal, a first pulse width signal and a second pulse width signal; the pulse position information includes a pulse start point and a pulse end point; the pulse end point of the linear frequency modulation signal to be compensated is the amplitude maximum value point of the signal after the linear frequency modulation signal to be compensated is subjected to pulse compression based on the matched filtering characteristic function, the pulse start point of the linear frequency modulation signal to be compensated is obtained by calculating according to the pulse end point and the pulse point number, and the pulse point number is obtained according to the pulse width; similarly, pulse position information of the first transmission feedback signal and the second transmission feedback signal is obtained;
respectively calculating the amplitude and the phase of a pulse width signal to be compensated, a first pulse width signal and a second pulse width signal;
Calculating according to the amplitudes of the first pulse width signal and the second pulse width signal to obtain the amplitude predistortion amount of the pulse width signal to be compensated;
calculating according to the phase angles of the first pulse width signal and the second pulse width signal to obtain the phase angle predistortion amount of the pulse width signal to be compensated;
And respectively compensating the amplitude and the phase angle of the pulse width signal to be compensated according to the amplitude predistortion amount and the phase angle predistortion amount to obtain a compensated linear frequency modulation signal.
Further, the predistortion compensation method of the chirp signal further comprises the following steps:
judging whether the flatness in the working frequency band of the compensated linear frequency modulation signal is smaller than a preset value;
when the flatness of the compensated linear frequency modulation signal in the working frequency band is larger than or equal to a preset value, the compensated linear frequency modulation signal is used as the linear frequency modulation signal to be compensated, and the compensation steps are repeated until the flatness of the compensated linear frequency modulation signal in the working frequency band is smaller than the preset value.
Further, the step of calculating the magnitude predistortion amount of the pulse width signal to be compensated according to the magnitudes of the first pulse width signal and the second pulse width signal includes:
Calculating the ratio of the amplitude of the second pulse width signal to the amplitude of the first pulse width signal to obtain an initial amplitude predistortion amount;
and carrying out a wrapping operation on the initial amplitude predistortion quantity to obtain the amplitude predistortion quantity of the pulse width signal to be compensated.
Further, the step of calculating the phase angle predistortion amount of the pulse width signal to be compensated according to the phase angles of the first pulse width signal and the second pulse width signal comprises the following steps:
Calculating the difference value of the phase angle of the second pulse width signal relative to the phase angle of the first pulse width signal to obtain an initial phase angle predistortion amount;
and carrying out a wrapping operation on the initial phase angle predistortion quantity to obtain the phase angle predistortion quantity of the pulse width signal to be compensated.
Further, the method is characterized in that the matched filtering characteristic function is obtained by performing left-right overturn and complex conjugation on pulse pressure coefficients with tr=0 as axes, wherein the pulse pressure coefficients are as follows: Where i denotes a complex number, kr=br/Tp denotes a modulation slope, br denotes a chirp signal bandwidth, tp denotes a pulse width, tr denotes a detection time range calculated from the pulse width and the sampling rate, and tr=0 denotes a time axis zero point corresponding to the detection time range.
Further, the specific step of pulse compressing the chirp signal to be compensated based on the matched filter characteristic function includes:
converting the linear frequency modulation signal to be compensated and the matched filtering characteristic function into a frequency domain through fast Fourier transformation, and multiplying the linear frequency modulation signal to be compensated and the matched filtering characteristic function in the frequency domain to obtain a frequency domain signal after pulse pressure;
and converting the frequency domain signal after pulse pressure back to the time domain through inverse Fourier transform.
According to a second aspect, an embodiment of the present invention provides an electronic device, including: at least one processor; and a memory communicatively coupled to the at least one processor; the memory has stored therein computer instructions which, when executed by the processor, cause the processor to perform the method of predistortion compensation of a chirp signal as described in the first aspect or any of the implementation manners of the first aspect.
According to a third aspect, an embodiment of the present invention provides a computer readable storage medium storing computer instructions for causing a computer to perform the predistortion compensation method of a chirp signal described in the first aspect or any one of the implementation manners of the first aspect.
The technical scheme provided by the invention has the following advantages:
1. The predistortion compensation method for the linear frequency modulation signal provided by the invention is characterized in that the linear frequency modulation signal involved in the predistortion compensation process is subjected to pulse compression by using a matched filtering characteristic function, continuous signals are converted into discrete points, then, the amplitude maximum value point of the signal after pulse compression is directly obtained as a pulse end point, and then, the pulse start point is obtained by calculating based on the pulse end point and the pulse point obtained according to the pulse width, so that the acquisition of the pulse position information of the linear frequency modulation signal is realized.
2. According to the predistortion compensation method for the linear frequency modulation signal, provided by the invention, the two reference signals used for predistortion compensation are respectively the first emission feedback signal and the second emission feedback signal, so that the amplitude predistortion quantity can be obtained by calculating the ratio of the amplitude of the second pulse width signal (the pulse width part signal of the second emission feedback signal) to the amplitude of the first pulse width signal (the pulse width part signal of the first emission feedback signal), and correspondingly, the amplitude of the linear frequency modulation signal to be compensated (particularly the pulse width part signal to be compensated, namely the pulse width signal to be compensated) is divided by the amplitude predistortion quantity, the amplitude predistortion compensation for the linear frequency modulation signal to be compensated can be completed, the operation is simple, and the occupation of resources and the operation time can be further reduced.
3. According to the predistortion compensation method for the linear frequency modulation signal, the two reference signals used for predistortion compensation are the first emission feedback signal and the second emission feedback signal respectively, so that the phase angle predistortion amount can be obtained by calculating the difference value of the phase angle of the second pulse width signal (pulse width part signal of the second emission feedback signal) relative to the phase angle of the first pulse width signal (pulse width part signal of the first emission feedback signal), correspondingly, the phase angle of the linear frequency modulation signal to be compensated (particularly the pulse width part signal to be compensated, namely the pulse width signal to be compensated) is subtracted by the phase angle predistortion amount, the phase angle predistortion compensation for the linear frequency modulation signal to be compensated can be completed, the operation is simple, and the occupation of resources and the operation time can be further reduced.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings that are needed in the description of the embodiments or the prior art will be briefly described, and it is obvious that the drawings in the description below are some embodiments of the present invention, and other drawings can be obtained according to the drawings without inventive effort for a person skilled in the art.
Fig. 1 is a flowchart of a predistortion compensation method for a chirp signal according to an embodiment of the present invention;
Fig. 2 is a schematic hardware structure of an electronic device according to an embodiment of the present invention.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the embodiments of the present invention more apparent, the technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention, and it is apparent that the described embodiments are some embodiments of the present invention, but not all embodiments of the present invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
In the description of the present invention, it should be noted that the terms "first," "second," and "third" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance.
Example 1
Fig. 1 shows a flowchart of a predistortion compensation method for a chirp signal according to an embodiment of the present invention, which may be performed by an FPGA, and in particular, as shown in fig. 1, the method may include the following steps:
S101: and acquiring the chirp signal to be compensated, and a first transmission feedback signal and a second transmission feedback signal of the chirp signal to be compensated.
Specifically, the first transmitting feedback signal is a signal fed back by the to-be-compensated linear frequency modulation signal after passing through the power divider only, and the second transmitting feedback signal is a signal fed back by the to-be-compensated linear frequency modulation signal after passing through the load and the power divider. Specifically, the load may be a power amplifier, a coupler, or the like.
Specifically, the chirp signal to be compensated may be generated by a chirp signal generator, based on which the chirp signal to be compensated is further transmitted and the first transmission feedback signal and the second transmission feedback signal are collected, so that the chirp signal generator further includes at least 1 transmission channel and 1 reception channel, and the chirp signal generator may be a Smart RF-301 test measurement platform, for example.
Specifically, the method is based on digital processing of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal, so that the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal obtained in the step are all RF-ADC radio frequency direct acquisition, signals (i.e. baseband signals) subjected to digital down-conversion are stored in the form of I paths and Q paths.
Specifically, in this step, signal basic parameters such as the sampling rate fs of the transmission signal, the bandwidth Br of the chirp signal, the pulse repetition period Tr, the pulse width Tp, and the in-band spectrum range RatioOfBr considered in calculating the flatness are all acquired together.
S102: pulse position information of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal is respectively obtained, pulse width part signals of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal are correspondingly extracted according to the pulse position information, and a to-be-compensated pulse width signal, a first pulse width signal and a second pulse width signal are obtained.
Specifically, the pulse position information includes a pulse start point and a pulse end point. The pulse end point of the linear frequency modulation signal to be compensated is the amplitude maximum point of the signal after the linear frequency modulation signal to be compensated is subjected to pulse compression based on the matched filtering characteristic function, the pulse start point of the linear frequency modulation signal to be compensated is calculated according to the pulse end point and the pulse point, and the pulse point is obtained according to the pulse width. Similarly, pulse position information of the first transmit feedback signal and the second transmit feedback signal is obtained.
Specifically, the matched filter characteristic function is obtained by performing left-right overturn and complex conjugation on the pulse pressure coefficient with tr=0 as an axis, wherein the pulse pressure coefficient is as follows: Where i denotes a complex number, kr=br/Tp denotes a modulation slope, br denotes a chirp signal bandwidth, tp denotes a pulse width, tr denotes a detection time range calculated from the pulse width and the sampling rate, and tr=0 denotes a time axis zero point corresponding to the detection time range.
Specifically, the specific steps of pulse compressing the chirp signal to be compensated based on the matched filter characteristic function include:
step I: and converting the linear frequency modulation signal to be compensated and the matched filtering characteristic function into a frequency domain through fast Fourier transformation, and multiplying the linear frequency modulation signal to be compensated and the matched filtering characteristic function in the frequency domain to obtain a frequency domain signal after pulse pressure.
Step II: and converting the frequency domain signal after pulse pressure back to the time domain through inverse Fourier transform.
Specifically, each signal is compressed and then converts the continuous signal of the bear into discrete points, and based on the characteristic that the delay of the signal with high matched filtering frequency through a filter is low, the maximum amplitude point of the signal after pulse compression corresponds to a pulse end point (EndPointOfTp), and then the pulse start point (StartPointOfTp) can be obtained through the known pulse width converted pulse inner point number (LengOfStandard), wherein StartPointOfTp = EndPointOfTp-LengOfStandard +1.
It should be noted that, the specific acquisition process (including the calculation process of the above-mentioned matched filter characteristic function and the pulse compression process) of the pulse position information (including the pulse start point and the pulse end point) may be executed in the same electronic device (like an FPGA) as the step S101-step S106 in the present method, or may be executed in another electronic device, and the electronic device executing the step S101-step S106 may directly acquire the pulse position information.
S103: and respectively calculating the amplitude and the phase of the pulse width signal to be compensated, the first pulse width signal and the second pulse width signal.
Specifically, the baseband-based signal can be expressed as:
Sigy=sig_i+sig_q=sig_abs_e (i*Sig_Angle), so predistortion compensation of the chirp signal to be compensated in the time domain can be done from both dimensions of amplitude sig_abs and phase sig_angle.
Specifically, the amplitude sig_abs and the phase Angle sig_angle of each signal can be obtained by integrating corresponding data of the pulse width signal to be compensated, the first pulse width signal and the second pulse width signal stored in IQ form into a signal form of a real part and an imaginary part, and then by performing modulo and phase Angle calculation.
S104: and calculating the amplitude predistortion amount of the pulse width signal to be compensated according to the amplitudes of the first pulse width signal and the second pulse width signal.
Specifically, the magnitude predistortion amount may be calculated by:
Step A: and calculating the ratio of the amplitude of the second pulse width signal to the amplitude of the first pulse width signal to obtain the initial amplitude predistortion amount. That is, the calculation formula of the initial amplitude predistortion amount Fn is as follows:
wherein SigYn _abs is the amplitude of the second pulse width signal, and sigy1_abs is the amplitude of the first pulse width signal.
And (B) step (B): and carrying out a wrapping operation on the initial amplitude predistortion quantity to obtain the amplitude predistortion quantity of the pulse width signal to be compensated. The magnitude predistortion quantity fn_envelope after the Envelope can be obtained by local maxima at 8 points, for example, and then by sample interpolation at 8/Nr sample intervals.
S105: and calculating the phase angle predistortion amount of the pulse width signal to be compensated according to the phase angles of the first pulse width signal and the second pulse width signal.
Specifically, the phase angle predistortion amount may be calculated by:
Step a: and calculating a difference value of the phase angle of the second pulse width signal relative to the phase angle of the first pulse width signal to obtain an initial phase angle predistortion amount. That is, the calculation formula of the initial phase angle predistortion amount DeltaN is as follows:
DeltaN = SigYn-Angle-sigy1-Angle, where SigYn-Angle is the phase Angle of the second pulse width signal and sigy1-Angle is the phase Angle of the first pulse width signal.
Step b: and carrying out a wrapping operation on the initial phase angle predistortion quantity to obtain the phase angle predistortion quantity of the pulse width signal to be compensated. Illustratively, the phase angle predistortion amount DeltaN _envelope after the Envelope can be obtained by local maxima at every 8 points and then by sample interpolation at 8/Nr sample intervals.
S106: and respectively compensating the amplitude and the phase angle of the compensation pulse width signal according to the amplitude predistortion amount and the phase angle predistortion amount to obtain a compensated linear frequency modulation signal.
Specifically, the amplitude sigout_abs of the compensated chirp signal is:
wherein SigYn1_abs is the amplitude of the pulse width signal to be compensated.
The phase Angle SigOut_Angle of the compensated chirp signal is:
SigOut_Angle＝SigYn1_Angle-DeltaN_Envelope，
wherein SigYn1_angle is the phase Angle of the pulse width signal to be compensated.
According to the predistortion compensation method for the linear frequency modulation signal, the linear frequency modulation signal involved in the predistortion compensation process is subjected to pulse compression by using a matched filtering characteristic function, continuous signals are converted into discrete points, then, the amplitude maximum value point of the signal after pulse compression is firstly obtained as a pulse end point, and then, the pulse start point is obtained by calculation based on the pulse end point and the pulse number obtained according to pulse width, so that the acquisition of pulse position information of the linear frequency modulation signal is realized.
As an alternative implementation manner of the embodiment of the present invention, on the basis of the one-time predistortion compensation including the above step S101 to step S106, the predistortion compensation method for a chirp signal in this embodiment may perform predistortion compensation multiple times, and specifically, as shown in fig. 1, the method further includes:
Step S107: and judging whether the flatness in the working frequency band of the compensated linear frequency modulation signal is smaller than a preset value. At this time, when the flatness in the working frequency band of the compensated linear frequency modulation signal is smaller than a preset value, the predistortion compensation is finished; and when the flatness in the working frequency band of the compensated linear frequency modulation signal is larger than or equal to a preset value, executing the step S108, and then repeatedly executing the steps S101-S107 until the flatness in the working frequency band of the compensated linear frequency modulation signal is smaller than the preset value.
For example, if the initially acquired chirp signal to be compensated has an operating bandwidth of 0GHz-1GHz, a pulse width of 20ns-200us, and a duty cycle of 1% -50%, the preset value may be set to 0.2dB.
Step S108: and taking the compensated linear frequency modulation signal as the linear frequency modulation signal to be compensated. Specifically, the compensated chirp signal may be mixed with a corresponding local oscillator signal to be used as the chirp signal to be compensated herein, and at this time, the chirp signal to be compensated needs to be transmitted after passing through the RF-DAC, so as to achieve the acquisition of the first transmission feedback signal and the second transmission feedback signal in step S101.
The predistortion compensation method for the chirp signal in the present embodiment can ensure the in-band flatness of the finally obtained compensated chirp signal by repeating predistortion compensation for the chirp signal a plurality of times.
Example 2
An embodiment of the present invention provides an electronic device, as shown in fig. 2, which may include a processor 21 and a memory 22, where the processor 21 and the memory 22 may be connected by a bus or other means, and in fig. 2, the connection is exemplified by a bus.
The processor 21 may be a central processing unit (Central Processing Unit, CPU). The Processor 21 may also be other general purpose processors, digital Signal Processors (DSP), application SPECIFIC INTEGRATED Circuits (ASIC), field-Programmable gate arrays (Field-Programmable GATE ARRAY, FPGA) or other Programmable logic devices, discrete gate or transistor logic devices, discrete hardware components, or combinations thereof.
The memory 22 is used as a non-transitory computer readable storage medium for storing a non-transitory software program, a non-transitory computer executable program, and a module, such as program instructions/modules corresponding to the predistortion compensation method for chirp signals in embodiment 1 of the present invention. The processor 21 executes various functional applications of the processor and data processing by running non-transitory software programs, instructions, and modules stored in the memory 22, that is, implements the predistortion compensation method for a chirp signal in the above-described method embodiment 1.
The memory 22 may include a storage program area that may store an operating system, at least one application program required for functions, and a storage data area; the storage data area may store data created by the processor 21, etc. In addition, the memory 22 may include high-speed random access memory, and may also include non-transitory memory, such as at least one magnetic disk storage device, flash memory device, or other non-transitory solid state storage device. In some embodiments, memory 22 may optionally include memory located remotely from processor 21, which may be connected to processor 21 via a network. Examples of such networks include, but are not limited to, the internet, intranets, local area networks, mobile communication networks, and combinations thereof.
The one or more modules are stored in the memory 22 and when executed by the processor 21 perform the predistortion compensation method of a chirp signal as in the embodiment of fig. 1.
The specific details of the electronic device may be understood correspondingly with respect to the corresponding related descriptions and effects in the embodiment shown in fig. 1, which are not repeated herein.
It will be appreciated by those skilled in the art that implementing all or part of the above-described embodiment method may be implemented by a computer program to instruct related hardware, where the program may be stored in a computer readable storage medium, and the program may include the above-described embodiment method when executed. Wherein the storage medium may be a magnetic disk, an optical disk, a Read-Only Memory (ROM), a random access Memory (Random Access Memory, RAM), a Flash Memory (Flash Memory), a hard disk (HARD DISK DRIVE, abbreviated as HDD), a Solid state disk (Solid-state-STATE DRIVE, SSD), or the like; the storage medium may also comprise a combination of memories of the kind described above.
It is apparent that the above examples are given by way of illustration only and are not limiting of the embodiments. Other variations or modifications of the above teachings will be apparent to those of ordinary skill in the art. It is not necessary here nor is it exhaustive of all embodiments. While still being apparent from variations or modifications that may be made by those skilled in the art are within the scope of the invention.
Claims (8)
1. A predistortion compensation method for a chirp signal, comprising the steps of:
Acquiring a linear frequency modulation signal to be compensated, and a first transmission feedback signal and a second transmission feedback signal of the linear frequency modulation signal to be compensated; the first transmitting feedback signal is a signal fed back by the linear frequency modulation signal to be compensated after passing through a power divider, and the second transmitting feedback signal is a signal fed back by the linear frequency modulation signal to be compensated after passing through a load and the power divider;
Respectively acquiring pulse position information of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal, correspondingly extracting pulse width part signals of the to-be-compensated linear frequency modulation signal, the first transmission feedback signal and the second transmission feedback signal according to the pulse position information, and obtaining a to-be-compensated pulse width signal, a first pulse width signal and a second pulse width signal; the pulse position information comprises a pulse starting point and a pulse ending point; the pulse end point of the linear frequency modulation signal to be compensated is the amplitude maximum point of the signal after the linear frequency modulation signal to be compensated is subjected to pulse compression based on a matched filtering characteristic function, the pulse start point of the linear frequency modulation signal to be compensated is obtained by calculation according to the pulse end point and the pulse point number, and the pulse point number is obtained according to the pulse width; similarly, pulse position information of the first transmission feedback signal and the second transmission feedback signal is obtained;
Respectively calculating the amplitude and the phase of the pulse width signal to be compensated, the first pulse width signal and the second pulse width signal;
calculating the amplitude predistortion amount of the pulse width signal to be compensated according to the amplitudes of the first pulse width signal and the second pulse width signal;
Calculating the phase angle predistortion amount of the pulse width signal to be compensated according to the phase angles of the first pulse width signal and the second pulse width signal;
And respectively compensating the amplitude and the phase angle of the pulse width signal to be compensated according to the amplitude predistortion amount and the phase angle predistortion amount to obtain a compensated linear frequency modulation signal.
2. The predistortion compensation method of a chirp signal according to claim 1, further comprising the steps of:
judging whether the flatness in the working frequency band of the compensated linear frequency modulation signal is smaller than the preset value;
And when the flatness of the compensated linear frequency modulation signal in the working frequency band is larger than or equal to the preset value, taking the compensated linear frequency modulation signal as the linear frequency modulation signal to be compensated, and repeating the compensation steps until the flatness of the compensated linear frequency modulation signal in the working frequency band is smaller than the preset value.
3. The predistortion compensation method of a chirp signal according to claim 1 or 2, characterized in that the step of calculating the magnitude predistortion amount of the pulse width signal to be compensated from the magnitudes of the first pulse width signal and the second pulse width signal comprises:
Calculating the ratio of the amplitude of the second pulse width signal to the amplitude of the first pulse width signal to obtain an initial amplitude predistortion amount;
And carrying out a wrapping operation on the initial amplitude predistortion quantity to obtain the amplitude predistortion quantity of the pulse width signal to be compensated.
4. The predistortion compensation method of a chirp signal according to claim 1 or 2, characterized in that the step of calculating the phase angle predistortion amount of the pulse width signal to be compensated from the phase angles of the first pulse width signal and the second pulse width signal comprises:
Calculating the difference value of the phase angle of the second pulse width signal relative to the phase angle of the first pulse width signal to obtain an initial phase angle predistortion amount;
and carrying out a wrapping operation on the initial phase angle predistortion quantity to obtain the phase angle predistortion quantity of the pulse width signal to be compensated.
5. The predistortion compensation method of a chirp signal according to any one of claims 1-4, wherein the matched filter characteristic function is obtained by performing left-right inversion on a pulse pressure coefficient with tr=0 as an axis and performing complex conjugation, and the pulse pressure coefficient is: Where i denotes a complex number, kr=br/Tp denotes a modulation slope, br denotes a chirp signal bandwidth, tp denotes a pulse width, tr denotes a detection time range calculated from the pulse width and the sampling rate, and tr=0 denotes a time axis zero point corresponding to the detection time range.
6. The method for predistortion compensation of a chirp signal according to claim 5, characterized in that the specific step of pulse compressing said chirp signal to be compensated based on a matched filter characteristic function comprises:
Converting the linear frequency modulation signal to be compensated and the matched filtering characteristic function into a frequency domain through fast Fourier transformation, and multiplying the linear frequency modulation signal to be compensated and the matched filtering characteristic function in the frequency domain to obtain a frequency domain signal after pulse pressure;
And converting the frequency domain signal after pulse pressure back to a time domain through inverse Fourier transform.
7. An electronic device, comprising: at least one processor; and a memory communicatively coupled to the at least one processor; wherein the memory stores instructions executable by the one processor to cause the at least one processor to perform the predistortion compensation method of a chirp signal as claimed in any one of the preceding claims 1 to 6.
8. A computer readable storage medium having stored thereon computer instructions, which when executed by a processor, implement the steps of the predistortion compensation method of a chirp signal as claimed in any one of the preceding claims 1-7.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211067975.7A CN115494464B (en) | 2022-09-01 | 2022-09-01 | Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211067975.7A CN115494464B (en) | 2022-09-01 | 2022-09-01 | Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN115494464A CN115494464A (en) | 2022-12-20 |
| CN115494464B true CN115494464B (en) | 2024-06-11 |
Family
ID=84467840
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202211067975.7A Active CN115494464B (en) | 2022-09-01 | 2022-09-01 | Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN115494464B (en) |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4968968A (en) * | 1989-11-09 | 1990-11-06 | Hughes Aircraft Company | Transmitter phase and amplitude correction for linear FM systems |
| US9784818B1 (en) * | 2013-10-04 | 2017-10-10 | National Technology & Engineering Solutions Of Sandia, Llc | Time-dependent phase error correction using digital waveform synthesis |
| CN110376607A (en) * | 2019-08-23 | 2019-10-25 | 长沙天仪空间科技研究院有限公司 | Synthetic Aperture Laser Radar system |
| KR20220060409A (en) * | 2020-11-04 | 2022-05-11 | 국방과학연구소 | Synthetic aperture radar and compensation method for synthetic aperture radar chirp signal |
| CN114966563A (en) * | 2022-05-10 | 2022-08-30 | 湖南国科锐承电子科技有限公司 | A wideband radar signal amplitude flatness compensation method |
-
2022
- 2022-09-01 CN CN202211067975.7A patent/CN115494464B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4968968A (en) * | 1989-11-09 | 1990-11-06 | Hughes Aircraft Company | Transmitter phase and amplitude correction for linear FM systems |
| US9784818B1 (en) * | 2013-10-04 | 2017-10-10 | National Technology & Engineering Solutions Of Sandia, Llc | Time-dependent phase error correction using digital waveform synthesis |
| CN110376607A (en) * | 2019-08-23 | 2019-10-25 | 长沙天仪空间科技研究院有限公司 | Synthetic Aperture Laser Radar system |
| KR20220060409A (en) * | 2020-11-04 | 2022-05-11 | 국방과학연구소 | Synthetic aperture radar and compensation method for synthetic aperture radar chirp signal |
| CN114966563A (en) * | 2022-05-10 | 2022-08-30 | 湖南国科锐承电子科技有限公司 | A wideband radar signal amplitude flatness compensation method |
Non-Patent Citations (1)
| Title |
|---|
| 基于HAF估计的超宽带LFM信号距离像频域校正;曹馨方;尹治平;孙双元;;现代雷达;20200215(第02期);全文 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN115494464A (en) | 2022-12-20 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| KR101908196B1 (en) | Frequency modulation scheme for fmcw radar | |
| CN108845296B (en) | Broadband radar radio frequency digital receiver based on microwave photons and signal acquisition and processing method | |
| EP3151495B1 (en) | Interference cancellation device and method | |
| JP5429699B2 (en) | Compression coefficient generator | |
| TWI441489B (en) | Apparatus comprising a recursive delayer and method for measuring a phase noise | |
| JP5810287B2 (en) | Radar equipment | |
| US8452245B2 (en) | Impedance measurement in an active radio frequency transmitter | |
| CN1667432B (en) | Weight function generating method, reference signal generating method, transmission signal generating apparatus, signal processing apparatus and antenna | |
| JP5369350B2 (en) | Transmission waveform generation method in pulse compression, transmission waveform generation program, and pulse compression apparatus manufactured by transmission waveform generation method | |
| US3987285A (en) | Digital matched filtering using a step transform process | |
| US8022863B1 (en) | Spatially variant apodization (SVA) filter | |
| CN107247254B (en) | A Deslope Processing Method for Nonlinear FM Signals | |
| US10237001B2 (en) | Method and measuring device for intermodulation measurement | |
| JP4080977B2 (en) | Correlation processing device, correlation processing method, pulse compression processing device, and pulse compression processing method | |
| KR100924172B1 (en) | Method of measuring variable bandwidth wireless channel and transmitter and receiver therefor | |
| Jakabosky et al. | Ultra-low sidelobe waveform design via spectral shaping and LINC transmit architecture | |
| KR101213044B1 (en) | Apparatus for pulse compression | |
| CN106842144A (en) | Parallel heterogeneous structure digital pulse compression method | |
| WO2007065639B1 (en) | Level radar frequency converter | |
| CN115642971B (en) | Simulation file generation method and automatic extraction system for nonlinear parameters of microwave module | |
| CN115494464B (en) | Predistortion compensation method for linear frequency modulation signal, electronic equipment and storage medium | |
| JP6323156B2 (en) | Image radar device | |
| US9065538B2 (en) | Transmission-reception device | |
| CN111010209A (en) | Circuit structure for realizing real-time frequency hopping communication interference suppression | |
| Le Kernec et al. | Empirical performance analysis of linear frequency modulated pulse and multitones on UWB software defined radar prototype |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |