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CN115473417B - Converter current control method and device based on hybrid logic driving - Google Patents

Converter current control method and device based on hybrid logic driving Download PDF

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Publication number
CN115473417B
CN115473417B CN202211078375.0A CN202211078375A CN115473417B CN 115473417 B CN115473417 B CN 115473417B CN 202211078375 A CN202211078375 A CN 202211078375A CN 115473417 B CN115473417 B CN 115473417B
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China
Prior art keywords
switching tube
pwm signal
level
digital quantity
overcurrent
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CN202211078375.0A
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CN115473417A (en
Inventor
毕恺韬
李建飞
罗劼
姜正茂
刘德龙
周立冬
李丹
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Sineng Electric Co ltd
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Sineng Electric Co ltd
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0038—Circuits or arrangements for suppressing, e.g. by masking incorrect turn-on or turn-off signals, e.g. due to current spikes in current mode control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/157—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention is applicable to the technical field of converter control, and provides a converter current control method and device based on hybrid logic driving, a converter topology and related equipment, wherein the method comprises the following steps: carrying out duty cycle reloading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty cycle reloading comprises the steps of correlating an original duty cycle with a first overcurrent control level to obtain an initial PWM signal; and performing mixed logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal. The method and the device can effectively reduce cost by realizing overcurrent control through software, and can effectively control the voltage of the flying capacitor when the flying capacitor three-level converter and the topology work in a pulse-by-pulse current limiting mode so as to output stable voltage.

Description

Converter current control method and device based on hybrid logic driving
Technical Field
The invention belongs to the technical field of converter control, and particularly relates to a converter current control method and device based on hybrid logic driving.
Background
Flying capacitor type three-level bidirectional power conversion topology is commonly used in an energy bidirectional flow system represented by an energy storage system to realize bidirectional power conversion. However, when an instantaneous short circuit occurs on the load side, the system current will increase dramatically, even exceeding the allowable current operating range of the power converter, severely threatening the system safety. For this purpose, in the prior art, by using pulse-by-pulse current limiting control, a hardware detection circuit, for example: and detecting current values in real time by using a current Hall device, a current divider and the like, and when the current values exceed the maximum range of the allowable operation of the system, forcibly blocking the driving signals, completely closing the switching devices and carrying out freewheeling by using the freewheeling diode. When the next switching period starts, the blocking signal of the switching device is forcedly removed, if the blocking signal is removed, the system still overflows, at the moment, the driving signal of the switching device is blocked by the vertical horse, and the switching device is forcedly closed again.
However, for the flying capacitor topology shown in fig. 1, the use of pulse-by-pulse current limit control will result in uncontrolled flying capacitor voltage due to the difference in switching timing. In FIG. 1, S a1 And S is a4 Complementary conduction, S a2 And S is a3 Complementary conduction, S a1 And S is a2 180 DEG different, S a1 And S is a2 For analysis, the turn-on timing is as shown in FIG. 2, and when the system current flows, the forced turn-off S is required a1 And S is a2 To reduce the inductor current. But at the beginning of the next cycle, S a1 The tube is to precede S a2 The tube is conductive. At this time, the current of the bus bar will flow through S a1 、C h1 、S a3 The anti-parallel diode and the inductor L form a loop, so that the flying capacitor can be charged again, and the inductor current can be increased. If the system load continues to short, the drive pulse continues to block and open for the next cycle, the flying capacitor will continue to charge, resulting in an overvoltage in the flying capacitor. If S is caused at the time of driving a1 Is delayed by S a2 Will cause the flying capacitor to go down after the pulse is blocked by 180 DEGWhen the driving signal is recovered in one switching cycle, discharging is performed. After a number of successive cycles of operation, this will result in an under-voltage flying capacitor voltage.
Disclosure of Invention
The embodiment of the invention provides a converter current control method based on hybrid logic driving, which aims to solve the problems of high hardware control cost and unstable voltage of a flying capacitor in the prior art when a three-level direct current topology of the flying capacitor works by pulse-by-pulse current limiting.
The embodiment of the invention is realized by providing a converter current control method based on hybrid logic driving, which comprises the following steps:
carrying out duty cycle reloading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty cycle reloading comprises the steps of correlating an original duty cycle with a first overcurrent control level to obtain an initial PWM signal;
and performing mixed logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
Still further, the duty cycle reloading of the switching tube of the flying capacitor three-level bidirectional converter topology includes:
acquiring the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology;
detecting whether the inductance current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value;
if the inductance current exceeds the preset current threshold, controlling the first overcurrent control level to be low in a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities;
and carrying out logic calculation on the first digital quantity and the second digital quantity, respectively associating with the original duty ratios of the first switching tube and the second switching tube, and calculating the initial PWM signals of the first switching tube and the second switching tube.
Further, the logic calculating the first digital quantity and the second digital quantity and associating the first digital quantity and the second digital quantity with the original duty ratios of the first switching tube and the second switching tube respectively, includes:
half of the second digital quantity is obtained, and the sum operation is carried out on the second digital quantity and the first digital quantity, so that an overcurrent control output quantity is obtained;
and carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube.
Still further, the calculating the initial PWM signals of the first switching tube and the second switching tube includes:
inputting the first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube;
and inputting the second reset duty ratio of the second switching tube into a second comparator for comparison to obtain a second initial PWM signal of the second switching tube.
Further, the performing hybrid logic driving on the initial PWM signal and the first and second overcurrent control levels, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal, includes:
if the inductance current exceeds the preset current threshold, the second overcurrent control level is turned to be low level, the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and the high level is recovered in the next period;
performing mixed logic operation based on a first initial PWM signal of the first switching tube, a second initial PWM signal of the second switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a first target PWM signal of the first switching tube;
and performing mixed logic operation based on the second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a second target PWM signal of the second switching tube.
Still further, the performing a hybrid logic operation based on the first initial PWM signal of the first switching transistor, the second initial PWM signal of the second switching transistor, the second digital quantity, and the second overcurrent control level that is low level at the time of overcurrent, includes:
performing an AND operation on the second initial PWM signal of the second switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the first initial PWM signal of the first switching tube;
and performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the first target PWM signal of the first switching tube.
Still further, the performing a hybrid logic operation based on the second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity, and the second overcurrent control level that is a low level at the time of overcurrent includes:
performing an AND operation on the first initial PWM signal of the first switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the second initial PWM signal of the second switching tube;
and performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the second target PWM signal of the second switching tube.
The embodiment of the invention also provides a converter current control device based on hybrid logic driving, which comprises:
the duty ratio resetting module is used for carrying out duty ratio reloading on a switching tube of the flying capacitor three-level bidirectional converter topology, and the duty ratio reloading comprises the steps of correlating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
and the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
The embodiment of the invention also provides a flying capacitor three-level converter topology, and the converter current control method based on the hybrid logic driving is adopted for overcurrent control.
The embodiment of the invention also provides electronic equipment, which comprises the flying capacitor three-level converter topology.
According to the converter current control method based on the mixed logic driving, when the over-current working condition of the flying capacitor three-level converter is detected, the original duty ratio of a switching tube of the flying capacitor three-level bidirectional converter topology is associated with a first over-current control level through the mixed logic driving, the switching tube of the flying capacitor three-level bidirectional converter topology is loaded with the duty ratio, and after the duty ratio is adjusted, the obtained target PWM signal can ensure that the output voltage of the converter is kept stable under the peak current working condition; in addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic control, the driving signal of the switching tube of the flying capacitor three-level bidirectional converter topology is subjected to state control based on the second overcurrent control level, the driving signal is blocked under the overcurrent working condition, and the voltage drift of the flying capacitor is restrained by adjusting the driving signal. Therefore, the over-current control can be realized through the mixed logic driving, so that the cost can be effectively reduced, and the flying capacitor voltage of the converter can be effectively controlled when the pulse-by-pulse current limiting work is performed, so that the stable voltage is output.
Drawings
FIG. 1 is a prior art topology of a flying capacitor three level converter;
FIG. 2 shows a switching tube S according to the prior art a1 And a switch tube S a2 A driving signal waveform diagram of (a);
FIG. 3 is a flow chart of a hybrid logic drive based inverter current control method provided by an embodiment of the present invention;
FIG. 4 is a schematic diagram of a hybrid logic drive based inverter current control method provided by an embodiment of the present invention;
FIG. 5 is a flowchart of step S301 in FIG. 3 according to an embodiment of the present invention;
FIG. 6 is a flowchart of step S302 in FIG. 3 according to an embodiment of the present invention;
FIG. 7 is a topology of a bi-directional buck-boost flying capacitor provided by an embodiment of the present invention;
fig. 8 is a block diagram of a converter current control device based on hybrid logic driving according to an embodiment of the present invention.
Detailed Description
The present invention will be described in further detail with reference to the drawings and examples, in order to make the objects, technical solutions and advantages of the present invention more apparent. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the invention.
In the prior art, pulse-by-pulse current limiting control is adopted, and hardware control cost is high through a hardware detection circuit, so that the flying capacitor voltage in the converter is not easy to control, and overvoltage or undervoltage is easy to generate. Aiming at the problem that the flying capacitor voltage is unstable when the flying capacitor three-level converter and the topology work in a pulse-by-pulse current-limiting mode, the method carries out duty ratio reloading on a switching tube of the flying capacitor three-level bidirectional converter topology, carries out mixed logic driving on an initial PWM signal, a first overcurrent control level and a second overcurrent control level, carries out state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, locks the driving signal when an overcurrent working condition fails, and inhibits the voltage drift of the flying capacitor by adjusting the driving signal. The method and the device realize overcurrent control through hybrid logic driving, so that cost can be effectively reduced, and the flying capacitor voltage of the converter can be effectively controlled when the pulse-by-pulse current limiting work is performed.
Example 1
Referring to fig. 3, fig. 3 is a flowchart of a method for controlling a converter current based on hybrid logic driving according to the present embodiment. The converter current control method based on the hybrid logic driving comprises the following steps:
s301, carrying out duty ratio reloading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty ratio reloading comprises the step of associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal.
In this embodiment, the flying capacitor three-level bidirectional converter topology is commonly used in power conversion, and the flying capacitor three-level bidirectional converter topology is shown in fig. 1, and the flying capacitor is C h1 . For convenience of explanation, in FIG. 4, the switching tube S in FIG. 1 is used a1 And S is a2 For the purposes of illustration, wherein d 1 And d 2 Switch tube S in flying capacitor three-level bidirectional converter topology a1 And S is a2 Is used for the duty cycle of the signal. F (F) od For the overcurrent fault zone bit, at F od The terminal generates the first overcurrent control level, and the first overcurrent control level is converted from a high level to a low level when the converter is overcurrent. The first overcurrent control level can be converted into digital values through two branch Data (Data conversion), and the digital values obtained through conversion are subjected to logic operation and then are compared with the original duty ratio d 1 D 2 Respectively carrying out logic association, and carrying out logic association on the original duty ratio d by the state of the first overcurrent control level 1 D 2 Duty loading is performed. The duty ratio loading is used for duty ratio adjustment, so that the original duty ratio can be reduced by one time, and the converter can be operated in a switching tube period T s The switch on time under the two-level mode operation in time is still the initial duty cycle and period you T s Can ensure the output of the converter under the peak current working conditionThe voltage remains stable. And after the duty ratio is adjusted, comparing and judging the reset duty ratio through comparators respectively, and outputting an initial PWM signal at the output end of each comparator. Under the condition that the output frequency of the control circuit is unchanged, the PWM signal, namely pulse width modulation, adjusts the duty ratio of the converter through voltage feedback, so that the purpose of stabilizing the output voltage is achieved.
S302, performing mixed logic driving on the initial PWM signal, a first overcurrent control level and a second overcurrent control level, performing state control on driving signals of a switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
Wherein, with continued reference to FIG. 4, F oc Generating a second overcurrent control level for the flag bit of the overcurrent signal, and F od Is different in that F oc The level is turned to be low after the current is detected to flow, and the level state is restored to be high in the next period; and F (F) od The level of (2) is continuously in a low level state after overcurrent until a preset maximum overcurrent operation time t oc-max After reaching, the high level is restored. F (F) oc Can ensure that the switch tube S is turned to low level under the condition of overcurrent a1 And S is a2 The driving signal of (2) is immediately blocked and the high level is recovered in the next period, and the normal working state is returned.
Specifically, the corresponding switching tubes S can be respectively a1 And S is a2 The initial PWM signal of (2) is mixed with the first overcurrent control level and the second overcurrent control level, and the mixed logic operation comprises an AND operation or an OR operation. After mixed logic operation, the corresponding switching tubes S are respectively output a1 And S is a2 Is set, is provided for the target PWM signal of (a). I.e. the final PWM signal of the converter. Wherein, PWM signal logic control can be used for signal blocking during overcurrent working condition faults by adjusting a switching tube S a1 And S is a2 Can suppress voltage drift of the flying capacitor.
In the embodiment of the invention, when the over-current working condition of the flying capacitor three-level converter is detected, the original duty ratio of the switching tube of the flying capacitor three-level bidirectional converter topology is firstly associated with the first over-current control level through mixed logic driving, the duty ratio loading is carried out on the switching tube of the flying capacitor three-level bidirectional converter topology, and the obtained target PWM signal can ensure that the converter output voltage is kept stable under the peak current working condition after the duty ratio is adjusted. In addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic driving, the driving signals of the switching tubes in the flying capacitor three-level bidirectional converter topology are subjected to state control, the driving signals can be blocked under the overcurrent working condition, and the voltage drift of the flying capacitor can be restrained by adjusting the driving signals. Therefore, the method and the device realize the overcurrent control through the hybrid logic drive, not only can effectively reduce the cost, but also can effectively control the flying capacitor voltage of the flying capacitor three-level converter topology when the pulse-by-pulse current limiting work is performed so as to output stable voltage.
Example two
On the basis of the first embodiment, referring to fig. 5, fig. 5 is a flowchart of step S301 in fig. 3 provided in this embodiment. Wherein, step S301 includes the steps of:
s501, obtaining the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology.
Wherein the first switching tube and the second switching tube can respectively correspond to the switching tube S a1 And S is a2 Can acquire a switching tube S in the flying capacitor three-level bidirectional converter topology a1 And S is a2 The original duty cycle, i.e., the duty cycle that is not adjusted, is the ratio of the on-time to the period of the drive signal.
S502, whether the inductance current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value.
Wherein the inductance is L of the flying capacitor three-level bidirectional converter topology in FIG. 1 1 During the operation of the circuit, the current i flowing through the inductor can be collected L And will induce current i L With a preset current threshold i set And comparing and judging.
And S503, if the inductance current exceeds a preset current threshold value, controlling the first overcurrent control level to be a low level in a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities.
Wherein, when the inductance current i L Exceeding a preset current threshold i set Indicating an overcurrent state, F od Transition from high to low and at maximum overcurrent run time t oc-max Is always at low level during the time until the maximum overcurrent operation time t oc-max And after the power supply reaches the power supply, the power supply is restored to the high level and is in a normal working state.
Referring to fig. 4, the first overcurrent control level is converted into a first digital quantity and a second digital quantity respectively through two paths of data, and in the digital circuit, the first digital quantity and the second digital quantity are opposite digital quantities, which means that when the first overcurrent control level is converted into a low level, the first digital quantity is 0, and the second digital quantity is 1.
S504, performing logic calculation on the first digital quantity and the second digital quantity, and correspondingly associating the first digital quantity and the second digital quantity with original duty ratios of the first switching tube and the second switching tube respectively to calculate initial PWM signals of the first switching tube and the second switching tube.
Wherein after obtaining the first digital quantity and the second digital quantity, logic AND operation can be performed first, and then the first digital quantity and the second digital quantity are respectively connected with the switch tube S a1 And S is a2 And carrying out product operation on the original duty ratio, and comparing the operation result with an initial PWM signal of the first switching tube and the second switching tube through a comparator.
Optionally, in the step 504, the logic calculating the first digital quantity and the second digital quantity specifically includes the steps of:
s5041, half of the second digital quantity is obtained, and the sum operation is carried out on the half of the second digital quantity and the first digital quantity, so that the overcurrent control output quantity is obtained.
Wherein, as shown in connection with FIG. 4, can be takenConverted 1And 2, performing a sum operation on the second digital quantity and the first digital quantity to obtain an overcurrent control output quantity based on the first overcurrent control level. Under the overcurrent condition, the first overcurrent control level is converted from a high level to a low level, the overcurrent control output quantity is 1/2 of the second digital quantity, and after the normal working state is restored, the first overcurrent control level is converted from the low level to the high level, and the overcurrent control output quantity is the first digital quantity.
S5042, carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube.
Wherein, the calculation formula for reloading the original duty ratio is shown in the following formula (1):
wherein i=1, 2, d i D is the initial duty cycle i_M To reset the duty cycle, F od_s Andrespectively the logic quantity F od The first digital quantity and the second digital quantity are obtained after data conversion.
Specifically, based on the above formula (1), the overcurrent control output is calculated as d 1 The product operation is performed to obtain a first switch tube S a1 Is set to a first reset duty cycle d 1_M And combining the overcurrent control output with d 2 The original duty ratio is subjected to product operation to obtain a second switching tube S a2 A second reset duty cycle d of (2) 2_M 。
Optionally, in the step S504, the calculating the initial PWM signals of the first switching tube and the second switching tube specifically includes the steps of:
s5043, inputting a first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube.
Wherein by switching the first switching tube S a1 Is set to a first reset duty cycle d 1_M As one input of the first comparator, the other input of the first comparator inputs a preset voltage, and after comparison, the first switch tube S can be output at the output end a1 Is a first initial PWM signal S 1_M 。
S5044, inputting a second reset duty ratio of the second switching tube into a second comparator for comparison to obtain a second initial PWM signal of the second switching tube.
Similarly, a second switch tube S a2 A second reset duty cycle d of (2) 2_M As one input of the second comparator, the other input of the second comparator inputs a preset voltage, and after comparison, the second switch tube S can be output at the output end a2 Is a second initial PWM signal S 2_M 。
In the present embodiment, by obtaining the first switching tube S in the flying capacitor three-level bidirectional converter topology a1 And a second switching tube S a2 Is d 1 And d 2 F is to F od The first overcurrent control level output by the terminal is used as an adjustment parameter of the duty ratio and is matched with the original duty ratio d 1 And d 2 And respectively performing logic calculation, reducing the duty ratio by one time, and finally realizing the resetting of the duty ratio. Resetting the duty cycle to make the converter at T s The on time of the switch under the operation of two levels in time is DT s Therefore, output voltage pulsation caused by PWM signal logic adjustment is eliminated, stable switching of output voltage under normal and fault working conditions is realized, and the output voltage of the converter under peak current working conditions is ensured to be stable. The control capability of the current of the converter is improved, and the reliability of the converter is enhanced.
Example III
On the basis of the second embodiment, referring to fig. 6, fig. 6 is a flowchart of step S302 in fig. 3 provided in this embodiment. Wherein, step S302 includes the steps of:
s601, if the inductance current exceeds a preset current threshold, the second overcurrent control level is turned to be low level, driving signals of a switching tube in the flying capacitor three-level bidirectional converter topology are blocked, and the high level is recovered in the next period.
Wherein, when the inductance current i L Exceeding a preset current threshold i set Indicating an overcurrent state, F od The high level is changed into the low level, and the low level can be used for the first switch tube S when the overcurrent is generated a1 And a second switching tube S a2 Immediately blocked and resumed in the next cycle.
S602, performing mixed logic operation based on a first initial PWM signal of the first switching tube, a second initial PWM signal of the second switching tube, a second digital quantity and a second overcurrent control level which is low in overcurrent, so as to obtain a first target PWM signal of the first switching tube.
Specifically, the method may include the steps of:
and performing AND operation on the second initial PWM signal of the second switching tube and the second digital quantity.
And performing OR operation on the calculated result after AND operation and a first initial PWM signal of the first switching tube.
And performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain a first target PWM signal of the first switching tube.
Wherein, as shown in connection with FIG. 4, the second switching tube S can be first a2 Is a second initial PWM signal S 2_M And the second digital quantity. When the AND operation is performed, if the second digital quantity is 0, the AND operation result is 0, and if the second digital quantity is 1 in the case of overcurrent, the AND operation result is S 2_M 。
Wherein, the result of the AND operation is combined with the first switch tube S a1 Is a first initial PWM signal S 1_M Performing OR operation, wherein the result of OR operation is S 1_M Or S 2_M 。
Wherein the result of OR operation is S 1_M Or S 2_M ，F oc The level is inverted to a low level after detecting that the current flows, and the level state is restored to a high level in the next cycle. Thus in the case of an overcurrent, the second overcurrent control level will be at the next cycleThe phase level state reverts to high level, i.e. F oc =1, will S 1_M Or S 2_M And F is equal to oc And operation of the first switching tube S will not occur in the next period a1 Is a first target PWM signal S of 1_F Causing an effect. That is, F when the next period has not come oc The level is turned to be low level after the current flowing is detected, so that the blocking of the driving signal can be realized; f at the next occurrence of a cycle oc Restoring to high level, unpacking the driving signal to let the first switch tube S a1 And a second switching tube S a2 The conduction is in a normal working state.
S603, performing mixed logic operation based on the second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low level during overcurrent, and obtaining a second target PWM signal of the second switching tube.
Similarly, as shown in FIG. 4, the first switching tube S is calculated according to the above a1 Is a first target PWM signal S of 1_F In the embodiment of (a), S603 specifically includes:
and performing an AND operation on the first initial PWM signal of the first switching tube and the second digital quantity.
And performing OR operation on the calculated result after AND operation and a second initial PWM signal of the second switching tube.
And performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain a second target PWM signal of the second switching tube.
Wherein the first switching tube S can be a1 Is a first initial PWM signal S 1_M And the second digital quantity. When the AND operation is performed, if the second digital quantity is 0, the AND operation result is 0, and if the second digital quantity is 1 in the case of overcurrent, the AND operation result is S 1_M . The result of the AND operation is combined with the second switch tube S a2 Is a second initial PWM signal S 2_M Performing OR operation, wherein the result of OR operation is S 2_M Or S 1_M 。F oc The level is inverted to a low level after detecting that the current flows, and the level state is restored to a high level in the next cycle. Thus, the first and second substrates are bonded together,in the case of overcurrent, the second overcurrent control level will be restored to high level in the next period of level state, i.e. F oc =1, will S 2_M Or S 1_M And F is equal to oc And operation of (c). The specific calculation formula is as follows:
in particular, when the converter is over-current1, S is known by combining the formula (2) 1_F And S is equal to 2_F The three-level converter of the flying capacitor works in a mode of converting three levels into two levels and converts the flying capacitor C h1 Bypass, cut off the switching tube S a1 To precede the second switching tube S a2 Conducting to cause flying capacitor C h1 Repeated charge and discharge loops, thereby ensuring flying capacitor C h1 The voltage is constant throughout the peak current protection period.
Let the initial duty ratio d be as shown in the following equation (3) 1 ＝d 2 =d, T under overcurrent fault conditions s The on time of the switch tube is as follows:
wherein T is s For the period of the switching tube, T s1 Is a first switching tube S a1 On-time of T s2 Is a second switching tube S a2 Is set to be on-time.
As can be seen from equation (3), under the same switching tube period, T s Unchanged, if the on time T s1 、T s2 The duty cycle of the converter is doubled.
Taking a buck mode as an example, the relationship between the input and output voltages of the flying capacitor three-level converter is shown in the following equation (4):
u 2 ＝Du 1 (4)
wherein u is 1 For the converter input voltage u 2 Is the output voltage of the transformer.
As can be seen from the formula (4), the duty ratio D is doubled, and the output voltage u of the converter 2 Will be doubled. To prevent abrupt voltage change, the duty cycle is reloaded, the initial duty cycle is reduced by one time, and the converter is operated at T s The on time of the switching tube under the operation of two levels in time is DT s Therefore, output voltage pulsation caused by logic adjustment of PWM signals is eliminated, and stable switching of output voltage under normal and fault working conditions is realized. Based on the above formula (2) and formula (3), the reset duty ratio and the target PWM signal under the normal and overcurrent protection conditions can be obtained as follows:
normal represents a Normal working condition, and Fault represents an overcurrent protection working condition.
It should be noted that the converter current control method based on hybrid logic driving provided by the embodiment of the present invention may also be used for a flying capacitor three-level converter derivative topology, such as the bidirectional buck-boost flying capacitor topology shown in fig. 7.
In this embodiment, when the over-current condition of the flying capacitor three-level converter is detected, the original duty ratio of the switching tube of the flying capacitor three-level bidirectional converter topology is associated with the first over-current control level through hybrid logic driving, the switching tube of the flying capacitor three-level bidirectional converter topology is loaded with the duty ratio, and after the duty ratio is adjusted, the obtained target PWM signal can ensure that the converter output voltage is kept stable under the peak current condition. In addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic control, the driving signal of a switching tube in the flying capacitor three-level bidirectional converter topology is subjected to state control, the driving signal can be blocked under the overcurrent working condition through the second overcurrent control level, and the voltage drift of the flying capacitor can be restrained through adjusting the driving signal. Therefore, the cost can be effectively reduced by realizing the overcurrent control through the hybrid logic drive, and the flying capacitor voltage of the flying capacitor three-level converter topology during the pulse-by-pulse current limiting operation can be effectively controlled so as to output stable voltage.
Example IV
In this embodiment, referring to fig. 8, fig. 8 is a schematic structural diagram of a converter current control device based on hybrid logic driving according to this embodiment. A hybrid logic drive based inverter current control device 800 comprising:
801. the duty ratio resetting module is used for carrying out duty ratio reloading on the switching tube of the flying capacitor three-level bidirectional converter topology, and the duty ratio reloading comprises the step of correlating the original duty ratio with a first overcurrent control level to obtain an initial PWM signal.
802. And the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on driving signals of a switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
The converter current control device based on the hybrid logic drive provided by the embodiment of the invention can realize each implementation mode of the converter current control method based on the hybrid logic drive and has the corresponding beneficial effects, and in order to avoid repetition, the description is omitted.
Example five
The embodiment provides a flying capacitor three-level converter topology, and the converter current control method based on hybrid logic driving in the embodiment is adopted for overcurrent control.
The fly capacitor three-level converter topology provided by the embodiment of the invention can realize each implementation mode of the overcurrent control method based on the hybrid logic driving converter current control method in the embodiment, and has the corresponding beneficial effects that in order to avoid repetition, the description is omitted here.
Example six
The present embodiment provides an electronic device including a flying capacitor three level converter topology in the above embodiments.
The electronic device provided by the embodiment of the invention can include a power supply device and the like, the electronic device includes a flying capacitor three-level converter topology in the fifth embodiment, and the implementation mode and the corresponding beneficial effects of the converter current control method based on hybrid logic driving in any one of the first to fourth embodiments can be realized on the flying capacitor three-level converter topology, so that any one of the first to fourth embodiments and the corresponding beneficial effects can be realized by the electronic device provided by the embodiment, and the repetition is avoided.
The terms first, second and the like in the description and in the claims or in the above-described figures, are used for distinguishing between different objects and not necessarily for describing a sequential or chronological order. Reference herein to "an embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment may be included in at least one embodiment of the present application. The appearances of such phrases in various places in the specification are not necessarily all referring to the same embodiment, nor are separate or alternative embodiments mutually exclusive of other embodiments. Those of skill in the art will explicitly and implicitly appreciate that the embodiments described herein may be combined with other embodiments.
The foregoing description of the preferred embodiments of the invention is not intended to be limiting, but rather is intended to cover all modifications, equivalents, and alternatives falling within the spirit and principles of the invention.

Claims (4)

1. The converter current control method based on the hybrid logic drive is characterized by comprising the following steps:
carrying out duty cycle reloading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty cycle reloading comprises the steps of correlating an original duty cycle with a first overcurrent control level to obtain an initial PWM signal;
performing mixed logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal;
the duty cycle reloading of the switching tube of the flying capacitor three-level bidirectional converter topology comprises the following steps:
acquiring the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology;
detecting whether the inductance current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value; when the inductance current exceeds a preset current threshold value, the inductance current is in an overcurrent state;
if the inductance current exceeds the preset current threshold, controlling the first overcurrent control level to be low in a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities;
performing logic calculation on the first digital quantity and the second digital quantity, and correspondingly associating the first digital quantity and the second digital quantity with the original duty ratios of the first switching tube and the second switching tube respectively to calculate the initial PWM signals of the first switching tube and the second switching tube;
the logic calculating the first digital quantity and the second digital quantity, and associating the first digital quantity and the second digital quantity with the original duty ratios of the first switching tube and the second switching tube respectively, includes:
half of the second digital quantity is obtained, and the sum operation is carried out on the second digital quantity and the first digital quantity, so that an overcurrent control output quantity is obtained;
carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube;
said calculating said initial PWM signals for said first and second switching tubes comprises:
inputting the first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube;
inputting the second reset duty ratio of the second switching tube into a second comparator for comparison to obtain a second initial PWM signal of the second switching tube;
the step of performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal, includes:
if the inductance current exceeds the preset current threshold, the second overcurrent control level is turned to be low level, the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and the high level is recovered in the next period;
performing mixed logic operation based on a first initial PWM signal of the first switching tube, a second initial PWM signal of the second switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a first target PWM signal of the first switching tube;
performing mixed logic operation based on a second initial PWM signal of the second switching tube, a first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a second target PWM signal of the second switching tube;
the performing a hybrid logic operation based on the first initial PWM signal of the first switching tube, the second initial PWM signal of the second switching tube, the second digital quantity, and the second overcurrent control level that is a low level when overcurrent, includes:
performing an AND operation on the second initial PWM signal of the second switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the first initial PWM signal of the first switching tube;
performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the first target PWM signal of the first switching tube;
the performing a hybrid logic operation based on the second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity, and the second overcurrent control level that is a low level when overcurrent, includes:
performing an AND operation on the first initial PWM signal of the first switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the second initial PWM signal of the second switching tube;
and performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the second target PWM signal of the second switching tube.
2. A hybrid logic drive based inverter current control device, the device comprising:
the duty ratio resetting module is used for carrying out duty ratio reloading on a switching tube of the flying capacitor three-level bidirectional converter topology, and the duty ratio reloading comprises the steps of correlating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal;
the duty cycle reloading of the switching tube of the flying capacitor three-level bidirectional converter topology comprises the following steps:
acquiring the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology;
detecting whether the inductance current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value; when the inductance current exceeds a preset current threshold value, the inductance current is in an overcurrent state;
if the inductance current exceeds the preset current threshold, controlling the first overcurrent control level to be low in a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities;
performing logic calculation on the first digital quantity and the second digital quantity, and correspondingly associating the first digital quantity and the second digital quantity with the original duty ratios of the first switching tube and the second switching tube respectively to calculate the initial PWM signals of the first switching tube and the second switching tube;
the logic calculating the first digital quantity and the second digital quantity, and associating the first digital quantity and the second digital quantity with the original duty ratios of the first switching tube and the second switching tube respectively, includes:
half of the second digital quantity is obtained, and the sum operation is carried out on the second digital quantity and the first digital quantity, so that an overcurrent control output quantity is obtained;
carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube;
said calculating said initial PWM signals for said first and second switching tubes comprises:
inputting the first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube;
inputting the second reset duty ratio of the second switching tube into a second comparator for comparison to obtain a second initial PWM signal of the second switching tube;
the step of performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal, includes:
if the inductance current exceeds the preset current threshold, the second overcurrent control level is turned to be low level, the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and the high level is recovered in the next period;
performing mixed logic operation based on a first initial PWM signal of the first switching tube, a second initial PWM signal of the second switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a first target PWM signal of the first switching tube;
performing mixed logic operation based on a second initial PWM signal of the second switching tube, a first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low in overcurrent, so as to obtain a second target PWM signal of the second switching tube;
the performing a hybrid logic operation based on the first initial PWM signal of the first switching tube, the second initial PWM signal of the second switching tube, the second digital quantity, and the second overcurrent control level that is a low level when overcurrent, includes:
performing an AND operation on the second initial PWM signal of the second switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the first initial PWM signal of the first switching tube;
performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the first target PWM signal of the first switching tube;
the performing a hybrid logic operation based on the second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity, and the second overcurrent control level that is a low level when overcurrent, includes:
performing an AND operation on the first initial PWM signal of the first switching tube and the second digital quantity;
performing OR operation on the calculated result after AND operation and the second initial PWM signal of the second switching tube;
and performing AND operation on the OR operation calculation result and the second overcurrent control level to obtain the second target PWM signal of the second switching tube.
3. A flying capacitor three-level converter topology employing hybrid logic drive based converter current control method of claim 1 for over-current control.
4. An electronic device comprising the flying capacitor three level converter topology of claim 3.
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