CN115276840B

CN115276840B - Calibration method, device and electronic device for zero intermediate frequency signal transceiver

Info

Publication number: CN115276840B
Application number: CN202210905185.5A
Authority: CN
Inventors: 张华祥; 林江涛
Original assignee: Shenzhen Sima Logic Technology Co ltd
Current assignee: Shenzhen Sima Logic Technology Co ltd
Priority date: 2022-07-29
Filing date: 2022-07-29
Publication date: 2024-12-27
Anticipated expiration: 2042-07-29
Also published as: CN115276840A

Abstract

The present application belongs to the field of signal calibration, and in particular, relates to a calibration method, device and electronic device for a zero intermediate frequency signal transceiver, the method comprising: obtaining a modulated radio frequency signal sent by a signal transmitter using a loopback link; and demodulating the radio frequency signal to obtain a baseband signal; determining the baseband spectrum information of the signal receiver according to the baseband signal; determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the DC bias information based on the baseband spectrum information; determining a first optimal compensation value for the imbalance information, and determining a second optimal compensation value for the DC bias information; calibrating the imbalance information according to the first optimal compensation value, and calibrating the DC bias information according to the second optimal compensation value. That is, the embodiment of the present application can simultaneously calibrate the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the DC bias information, thereby improving the reliability of the signal receiver.

Description

Calibration method and device of zero intermediate frequency signal transceiver and electronic equipment

Technical Field

The present application relates to the field of signal calibration, and in particular, to a method and apparatus for calibrating a zero intermediate frequency signal transceiver, and an electronic device.

Background

The existing calibration scheme for the wireless comprehensive tester uses higher-precision professional equipment (such as a high-precision spectrometer/a signal source/a power meter/an atomic clock frequency meter and the like) as a partner testing equipment, and basic calibration logic is as follows, the high-precision partner testing equipment is used as a reference, and the wireless comprehensive tester to be calibrated is adjusted to be close to the level of the high-precision partner testing equipment as much as possible. The scheme has high dependence on the accompanying and testing equipment and has higher requirements on the precision of the accompanying and testing equipment.

The other calibration scheme for the wireless comprehensive tester is self-calibration, and can calibrate the power precision and the signal quality of the equipment under the condition of no accompanying test, but the existing self-calibration scheme can only self-calibrate local oscillator leakage/direct current bias in the wireless comprehensive tester, and cannot calibrate various factors affecting the power precision and the signal quality of the wireless comprehensive tester at the same time, namely cannot reduce the influence of various factors on the reliability of the equipment at the same time.

Disclosure of Invention

The embodiment of the application provides a calibration method and device for a zero intermediate frequency signal transceiver and electronic equipment, which can improve the reliability of a signal receiver.

In a first aspect, an embodiment of the present application provides a calibration method for a zero intermediate frequency signal transceiver, where the calibration method includes:

the method comprises the steps that a signal transmitter obtains a modulated radio frequency signal sent by a loop link, demodulates the radio frequency signal and obtains a baseband signal, wherein the radio frequency signal is a single-tone signal;

determining baseband spectrum information of the signal receiver according to the baseband signal;

determining imbalance information of amplitude or angle of in-phase quadrature signals of the signal receiver, and direct current offset information based on the baseband spectrum information;

determining a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determining a second optimal compensation value of the direct current offset information based on the direct current offset information and a preset second compensation value range of the direct current offset information;

and calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, and calibrating the direct current offset information of the signal receiver according to the second optimal compensation value.

In a possible implementation manner of the first aspect, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, a deviation value between the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is less than 1/4 baseband bandwidth, and the demodulating the radio-frequency signal to obtain the baseband signal includes:

Demodulating the radio frequency signal to obtain an in-phase signal in the baseband signal, wherein the in-phase signal is:

Wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, C _Q1 represents an amplitude of local oscillation leakage of a quadrature signal of the signal transmitter, A ₁ represents an amplitude of an in-phase quadrature signal of the signal transmitter, omega ₁ represents a local oscillation frequency of the signal transmitter, omega ₂ represents a local oscillation frequency of the signal receiver, C _I1 represents an amplitude of local oscillation leakage of an in-phase signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, C _I2 representing the amplitude of local oscillator leakage of the in-phase signal of the signal receiver;

Demodulating the radio frequency signal to obtain a quadrature signal in the baseband signal, wherein the quadrature signal is:

where Q' (t) represents the quadrature signal in the baseband signal of the signal receiver, A ₂ represents the amplitude of the in-phase quadrature signal of the signal receiver, An angle representative of an in-phase quadrature signal of the signal receiver, the C _Q1、C_I1、A₁ andFor non-ideal characteristics of the signal transmitter, the C _I2、A₂ andIs a non-ideal characteristic of the signal receiver;

Based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal, obtaining the baseband signal, wherein the baseband signal is:

Wherein, Representing the baseband signal, I '(t) representing the real part of the baseband signal and jQ' (t) representing the imaginary part of the baseband signal.

Wherein the determining baseband spectrum information of the signal receiver according to the baseband signal includes:

performing fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:

Wherein, Representing baseband spectral information of the signal receiver, C _Q2 representing the amplitude of local oscillator leakage of a quadrature signal of the signal receiver, δ (ω+ω ₂-ω₁) representing the center frequency of the mono signal, δ (ω+ω ₁-ω₂) representing the image frequency of the signal receiver, δ (ω) representing the local oscillator frequency of the signal receiver, and C _Q2 being an irrational characteristic of the signal receiver.

Wherein the determining, based on the baseband spectrum information, imbalance information of an amplitude or an angle of an in-phase quadrature signal of the signal receiver, and direct current offset information includes:

based on the baseband spectrum information, the determined imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is:

Based on the baseband spectrum information, the determined direct current offset information of the in-phase and quadrature signals of the signal receiver is as follows:

[[2(C_I2+j+C_Q2)]]2πδ(ω);

wherein determining a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determining a second optimal compensation value for the dc offset information based on the dc offset information and a preset second compensation value range for the dc offset information, comprises:

determining, by using an optimization algorithm, a first compensation value range of the unbalance information Is determined by the first optimum compensation value of (a);

and determining a second optimal compensation value of [ [2 (C _I2+j+C_Q2) ] 2pi delta (omega) in a preset second compensation value range of the direct current offset information by utilizing an optimizing algorithm.

In a second aspect, an embodiment of the present application provides a calibration method for a zero intermediate frequency signal transceiver, where the calibration method includes:

based on the baseband spectrum information, imbalance information of amplitude or angle of in-phase and quadrature signals of the signal transmitter and local oscillator leakage information are determined;

Determining a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determining a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;

And calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.

In a third aspect, an embodiment of the present application provides a calibration apparatus for a zero intermediate frequency signal transceiver, where the calibration apparatus includes:

the acquisition module is used for acquiring the modulated radio frequency signal transmitted by the signal transmitter through the loop link, demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

the first determining module is used for determining baseband spectrum information of the signal receiver according to the baseband signal;

A second determining module, configured to determine, based on the baseband spectrum information, imbalance information of an amplitude or an angle of an in-phase quadrature signal of the signal receiver, and dc offset information;

A third determining module, configured to determine a first optimal compensation value of the unbalance information based on the unbalance information and a preset first compensation value range of the unbalance information, and determine a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information;

And the calibration module is used for calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value and calibrating the direct current offset information of the in-phase quadrature signal of the signal receiver according to the second optimal compensation value.

In a fourth aspect, an embodiment of the present application provides a calibration apparatus for a zero intermediate frequency signal transceiver, where the calibration apparatus includes:

The acquisition module is used for acquiring the radio frequency signal sent by the signal transmitter and demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

the second determining module is used for determining the unbalance information of the amplitude or the angle of the in-phase quadrature signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information;

A third determining module, configured to determine a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determine a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;

And the calibration module is used for calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.

In a fifth aspect, an embodiment of the present application provides an electronic device, including a memory, a processor, and a computer program stored in the memory and executable on the processor, where the processor implements the method for calibrating a zero intermediate frequency signal transceiver according to any one of the first aspects or the method for calibrating a zero intermediate frequency signal transceiver according to the second aspect when the computer program is executed.

In a sixth aspect, embodiments of the present application provide a computer readable storage medium storing a computer program which, when executed by a processor, implements a method of calibrating a zero intermediate frequency signal transceiver according to any of the first aspects or a method of calibrating a zero intermediate frequency signal transceiver according to the second aspect.

Compared with the prior art, the method has the advantages that radio frequency signals sent by a signal transmitter through a loop link are obtained, the radio frequency signals are demodulated to obtain baseband signals, baseband spectrum information of a signal receiver is determined according to the baseband signals, unbalanced information of amplitude or angle of in-phase quadrature signals of the signal receiver and direct current offset information are determined based on the baseband spectrum information, a first optimal compensation value of the unbalanced information is determined, a second optimal compensation value of the direct current offset information is determined, the unbalanced information is calibrated according to the first optimal compensation value, and the direct current offset information is calibrated according to the second optimal compensation value. The embodiment of the application can calibrate the imbalance information of the amplitude or angle of the in-phase quadrature signal and the direct current offset information of the signal receiver at the same time, thereby improving the reliability of the signal receiver.

Drawings

In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings that are needed in the embodiments or the description of the prior art will be briefly introduced below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and that other drawings can be obtained according to these drawings without inventive effort for a person skilled in the art.

Fig. 1 is a schematic diagram of an application scenario of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application;

fig. 2 is a schematic flow of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application;

FIG. 3a is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application;

FIG. 3b is an exemplary graph of power spectra before and after loop self-calibration of a signal receiver according to an embodiment of the present application;

fig. 4 is a schematic flow chart of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application;

fig. 5 is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application;

fig. 6 is a schematic structural diagram of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application;

fig. 7 is a schematic structural diagram of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application;

Fig. 8 is a schematic structural diagram of an electronic device according to an embodiment of the present application.

Detailed Description

In the following description, for purposes of explanation and not limitation, specific details are set forth such as the particular system architecture, techniques, etc., in order to provide a thorough understanding of the embodiments of the present application. It will be apparent, however, to one skilled in the art that the present application may be practiced in other embodiments that depart from these specific details. In other instances, detailed descriptions of well-known systems, devices, circuits, and methods are omitted so as not to obscure the description of the present application with unnecessary detail, and in other instances, specific details of the technology in the various embodiments may be referenced to each other and specific systems not described in one embodiment may be referenced to other embodiments.

It will be understood that the terms "comprises" and/or "comprising," when used in this specification, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.

It should also be understood that the term "and/or" as used in this disclosure refers to any and all possible combinations of one or more of the associated listed items, and includes such combinations.

Reference in the specification to "an embodiment of the application" or "some embodiments" or the like means that a particular feature, structure, or characteristic described in connection with the embodiment is included in one or more embodiments of the application. Thus, appearances of the phrases "in other embodiments," "in an embodiment of the application," "other embodiments of the application," and the like in the specification are not necessarily all referring to the same embodiment, but mean "one or more, but not all, embodiments" unless expressly specified otherwise. The terms "comprising," "including," "having," and variations thereof mean "including but not limited to," unless expressly specified otherwise.

In addition, in the description of the present application, the terms "first," "second," and the like are used merely to distinguish between descriptions and are not to be construed as indicating or implying relative importance.

The existing self-calibration scheme of the wireless comprehensive tester can calibrate the power precision and the signal quality of equipment under the condition of no accompanying test, but the existing self-calibration scheme can only self-calibrate local oscillator leakage/direct current bias in the wireless comprehensive tester, cannot calibrate various factors affecting the power precision and the signal quality of the wireless comprehensive tester at the same time, namely cannot reduce the influence of various factors on the reliability of the equipment at the same time.

In order to solve the above-mentioned defect, the inventive concept of the present application is:

When the signal receiver in the embodiment of the application performs loop self-calibration, a signal transmitter with non-ideal characteristics can transmit radio frequency signals, a signal receiver with non-ideal characteristics receives the radio frequency signals and demodulates the radio frequency signals to obtain baseband signals, local oscillation leakage information mixed with the signal transmitter in the baseband signals and imbalance information of in-phase quadrature signals, namely 1Q signals, and imbalance information mixed with the direct current offset information and 1Q signals of the signal receiver are mixed together, the signal quality is reduced.

In order to illustrate the technical scheme of the application, the following description is made by specific examples.

Referring to fig. 1, fig. 1 is a schematic diagram of an application scenario of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application, and for convenience of explanation, only a portion relevant to the present application is shown. The application scenario includes a signal transmitter 100, a signal receiver 200, and a loop link 300.

The information transmitter 100 is a zero intermediate frequency architecture transmitter, and the signal transmitter 100 is configured to modulate a radio frequency signal and then transmit the radio frequency signal to the signal receiver 200 using a transmission path (loop link 300).

The signal receiver 200 is a receiver with zero intermediate frequency architecture, after receiving a radio frequency signal, the signal receiver demodulates the radio frequency signal through a demodulator through band selection of a band-pass filter and amplification of a low noise amplifier, and performs spectrum analysis on the signal demodulated signal, and according to the spectrum analysis result, calibrates various factors affecting signal quality of the signal receiver or the signal transmitter.

Referring to fig. 2, fig. 2 is a schematic flowchart of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the application. The subject of the implementation of the method in fig. 2 may be the signal receiver in fig. 1. As shown in fig. 2, the method includes S201 to S205.

S201, a signal receiver acquires a radio frequency signal sent by a signal transmitter through a loop link, and demodulates the radio frequency signal to obtain a baseband signal.

Specifically, the radio frequency signal is a single tone signal, which is a signal with a single frequency.

In the embodiment of the application, the signal transmitter and the signal receiver share one clock source, and the relative frequency error is negligible.

In the embodiment of the application, the radio frequency signal sent by the signal transmitter can be represented by the following formula:

where-sin (omega ₁ t) is the original ideal mono signal, For non-rational character of the signal transmitter itselfDistortion caused to original ideal single-tone signal, C _I1、C_Q1、A₁,Reference may be made to other embodiments for specific meaning and are not described in detail herein.

After the signal transmitter transmits the above signals by using the loop link, the signal transmitter demodulates the radio frequency signal to obtain a baseband signal, please refer to fig. 3.

Fig. 3 is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application. The subject of the implementation of the method in fig. 3 may be the signal receiver in fig. 1. As shown in fig. 3, the method includes S301 to S303.

S301, the signal receiver demodulates the radio frequency signal to obtain an in-phase signal in the baseband signal. Specifically, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, and the deviation value of the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is smaller than 1/4 baseband bandwidth.

In the embodiment of the application, the signal receiver also has non-ideal characteristicsC_I2、C_Q2、A₂、Distortion, C _I2、C_Q2、A₂, of the original ideal single-tone signal,Reference may be made to other embodiments for specific meaning and are not described in detail herein.

The signal receiver in the embodiment of the application demodulates the radio frequency signal, and the demodulation process is as follows:

and:

In the embodiment of the application, the following steps are provided Filtering all the frequency multiplication components (using integration and difference to obtain frequency multiplication components, and then discarding) by a low-pass filter to obtain an in-phase signal in the baseband signal, wherein the in-phase signal can be expressed by the following formula:

Where I' (t) represents the in-phase signal in the baseband signal of the signal receiver, C _Q1 represents the amplitude of local oscillator leakage of the quadrature signal of the signal transmitter, A ₁ represents the amplitude of the in-phase quadrature signal of the signal transmitter, omega ₁ represents the local oscillator frequency of the signal transmitter, omega ₂ represents the local oscillator frequency of the signal receiver, C _I1 represents the amplitude of local oscillator leakage of the in-phase signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, and C _I2 represents the amplitude of local oscillator leakage of the in-phase signal of the signal receiver.

S302, the signal receiver demodulates the radio frequency signal to obtain a quadrature signal in the baseband signal.

In the embodiment of the application, the pairThe quadrature signal in the baseband signal obtained by filtering out all the frequency multiplication components (using the integration sum difference to obtain the frequency multiplication components and then discarding) through the low-pass filter can be expressed by the following formula:

where Q' (t) represents the quadrature signal in the baseband signal of the signal receiver, A ₂ represents the amplitude of the in-phase quadrature signal of the signal receiver, Angle, C _Q1、C_I1、A₁, and representative of in-phase quadrature signal of signal receiverAs a non-ideal feature of the signal transmitter, C _I2、A₂ Is a non-ideal feature of a signal receiver.

In the embodiment of the application, the non-ideal characteristics of the signal transmitter and the signal receiver are first-order small quantity, and the frequency changing along with time is far less than the local oscillation frequency.

S303, the signal receiver obtains a baseband signal based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal.

The baseband signal obtained can be expressed by the following formula:

S202, the signal receiver determines baseband spectrum information of the signal receiver according to the baseband signal.

Performing Fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, wherein the baseband spectrum information is as follows:

Wherein, Representing baseband spectral information of the signal receiver, C _Q2 representing the amplitude of local oscillator leakage of the quadrature signal of the signal receiver, δ (ω+ω ₂-ω₁) representing the center frequency of the mono signal, δ (ω+ω ₁-ω₂) representing the image frequency of the signal receiver, δ (ω) representing the local oscillator frequency of the signal receiver, C _O2 being an irrational characteristic of the signal receiver.

In the embodiment of the application, in the frequency spectrum information, the energy of the center frequency of the single-tone signal is maximum, and the peak value height is highest, and meanwhile, the energy is influenced by local oscillation leakage of the signal transmitter, direct current bias of the signal receiver and unbalanced information of IQ amplitude angles of the signal transmitter and the signal receiver.

In the embodiment of the application, in the frequency spectrum information, the image frequency of the signal receiver is only affected by the unbalanced information of the IQ amplitude angle of the signal receiver.

In the embodiment of the application, in the frequency spectrum information, the local oscillation frequency of the signal receiver is only influenced by the direct current bias of the I path and the Q path of the signal receiver.

In the embodiment of the application, the higher the spectrum resolution is, the larger the baseband bandwidth is, and the better the effect of calibrating the non-ideal characteristics is.

S203, the signal receiver determines imbalance information of amplitude or angle of in-phase quadrature signals of the signal receiver and direct current offset information based on the baseband frequency spectrum information.

Based on the baseband spectrum information, the determined imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver is:

[2(C_I2+j+C_Q2)]2πδ(ω)。

Specifically, the signal receiver may calculate a power spectral density based on the baseband spectral information.

In the embodiment of the application, the power spectral density can be calculated by the following ways:

the embodiment of the application can be concluded according to the calculated power spectrum density:

1 in the power spectrum, the peak height of the image frequency of the signal receiver is proportional to The IQ amplitude imbalance and the IQ angle imbalance of the signal receiver are decoupled from the peak height of the image frequency, and the peak height of the image frequency is lowest when the IQ amplitude imbalance and the IQ angle imbalance of the signal receiver reach the minimum simultaneously.

2 In the power spectrum, the peak value height of the local oscillation frequency of the signal receiver is proportional to C _I2 ²+C_Q2 ², which indicates that the peak value height of the local oscillation frequency is decoupled by the I-path direct current bias and the Q-path direct current bias of the signal receiver, and when the I-path direct current bias and the Q-path direct current bias reach minimum at the same time, the peak value height of the local oscillation frequency is minimum.

S204, the signal receiver determines a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determines a second optimal compensation value of the direct current offset information based on the direct current offset information and a preset second compensation value range of the direct current offset information.

Specifically, the optimization algorithm is utilized to determine in a first compensation value range of preset unbalance informationIs included.

In particular, in the embodiment of the present application,The peak height of the image frequency of the signal receiver in the power spectrum is characterized.

In some embodiments, the first compensation value range of the preset imbalance information is QDAC x IDAC E < -1024,1024 > x < -1024,1024 >, wherein QDAC and IDAC are registers on a decoding chip (DAC), and [ (1024,1024 ] x < -1024,1024] is a voltage value of a compensation circuit inside the registers.

In some embodiments, the first compensation value range of the preset imbalance information is:

The first compensation value range of the preset unbalance information is QDAC xIDAC xDAC 1 xDAC 2 epsilon < -1024,1024 > x < -1024,1024 > x < -1024,1024 > x < -1024,1024 >.

The optimizing algorithm in the embodiment of the application comprises, but is not limited to, a direction acceleration method (Powell optimizing algorithm), a conjugate gradient descent algorithm and the like, and the embodiment of the application is not limited to the method.

In the embodiment of the application, when the Powell optimizing algorithm is used for optimizing the peak value height of the mirror frequency of the signal receiver, the optimizing process has the following characteristics:

1. the one-dimensional optimizing process is iterated continuously for a plurality of times, and the direction of each one-dimensional optimizing process is determined by the results of the previous N one-dimensional optimizing processes.

2. The first N one-dimensional optimization directions need to be given and a linear independent set must be made up.

3. Under the condition that a plurality of minimum points exist in the function, only one minimum point can be found, and the global minimum point cannot be found

4. In the case of a function having a plurality of minuscule points, the points searched for are related to the initial search direction and the gradient distribution of the function.

And determining a second optimal compensation value of [2 (C _I2+j+C_Q2) ] ]2 pi delta (omega) in a second compensation value range of the preset direct current offset information by utilizing an optimizing algorithm.

Specifically, in the embodiment of the present application, [2 (C _I2+j+C_Q2) ]2δ (ω) represents the peak height of the local oscillation frequency of the signal receiver in the power spectrum.

In some embodiments the second compensation value range of the preset DC offset information is Wherein DeltaA represents the amplitude compensation value range of IQ imbalance information,And the angle compensation value range of the IQ imbalance information is represented.

In the prior art, 17 hours are needed to find the first optimal compensation point and the second optimal compensation point through traversal, and the optimizing algorithm in the application can be completed in a few seconds.

For example, when the Powell optimizing algorithm is utilized for optimizing, the optimizing process only uses 100-200 single-point measurements to find the optimal calibration point. In addition, due to universality of the Powell optimizing algorithm, the Powell optimizing algorithm can be used in the calibration process without modification, and development workload is reduced.

S205, the signal receiver calibrates the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, and calibrates the direct current offset information of the signal receiver according to the second optimal compensation value.

Specifically, by adopting the calibration method in the embodiment of the application, the calibration result of the DC offset is 5-10dB lower than that of the existing calibration scheme, and the average value of the DC offset of the existing calibration scheme is about-75 dB.

By adopting the calibration method in the embodiment of the application, the imbalance information of the IQ angle is smaller than 0.03 degrees, and the imbalance information of the IQ amplitude is smaller than 0.01dB.

The signal receiver of the embodiment of the application calibrates the unbalanced information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, so that the influence of the unbalanced information of the amplitude or angle of the in-phase quadrature signal of the signal receiver on the reliability of the equipment can be reduced, and calibrates the direct current offset information of the signal receiver according to the second optimal compensation value, so that the influence of the direct current offset information of the signal receiver on the reliability of the equipment can be reduced simultaneously.

Referring to fig. 3b, fig. 3b is an exemplary diagram of a power spectrum before and after loop self-calibration of a signal receiver according to an embodiment of the present application. In fig. 3b, a graph a represents the power spectrum before calibration and b graph b represents the power spectrum after calibration. In FIG. 3b the abscissa represents the frequency values in MHz and the ordinate represents the power spectral density values in dBm/100KHz.

In fig. 3b, the M peak in the a graph represents the peak height of the image frequency, the N peak represents the peak height of the local oscillation frequency, and the M peak and the N peak in the b graph after calibration basically disappear, that is, the calibration method in the embodiment of the application reduces the influence of the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver on the reliability of the device, and reduces the influence of the direct current bias information of the signal receiver on the reliability of the device.

In summary, the technical scheme of the application includes the steps of obtaining a radio frequency signal sent by a signal transmitter through a loop link, demodulating the radio frequency signal to obtain a baseband signal, determining baseband frequency spectrum information of a signal receiver according to the baseband signal, determining imbalance information of amplitude or angle of an in-phase quadrature signal of the signal receiver and direct current offset information based on the baseband frequency spectrum information, determining a first optimal compensation value of the imbalance information and a second optimal compensation value of the direct current offset information, calibrating the imbalance information according to the first optimal compensation value, and calibrating the direct current offset information according to the second optimal compensation value. The embodiment of the application can calibrate the imbalance information of the amplitude or angle of the in-phase quadrature signal and the direct current offset information of the signal receiver at the same time, thereby improving the reliability of the signal receiver.

Referring to fig. 4, fig. 4 is a schematic flowchart of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the application. The subject of the implementation of the method in fig. 4 may be the signal receiver in fig. 1. As shown in fig. 4, the method includes S401 to S405.

S401, the signal receiver acquires a radio frequency signal sent by the signal transmitter through the loop link, and demodulates the radio frequency signal to obtain a baseband signal.

Specifically, the radio frequency signal is a tone signal.

Where cos (ω ₂ t) is the original ideal mono signal, For non-rational character of the signal transmitter itselfDistortion caused to original ideal single-tone signal, C _I1、C_Q1、A₁,Reference may be made to other embodiments for specific meaning and are not described in detail herein.

After the signal transmitter transmits the above signals by using the loop link, the signal transmitter demodulates the radio frequency signal to obtain a baseband signal, please refer to fig. 5.

Fig. 5 is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application. The subject of the implementation of the method in fig. 5 may be the signal receiver in fig. 1. As shown in fig. 5, the method includes S501 to S503.

S501, the signal receiver demodulates the radio frequency signal to obtain an in-phase signal in the baseband signal.

Specifically, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal receiver, and the deviation value of the local oscillation frequency of the signal transmitter and the local oscillation frequency of the signal receiver is smaller than 1/4 baseband bandwidth. In the embodiment of the application, the signal receiver also has non-ideal characteristicsC_I2、C_Q2、A₂、Distortion, C _I2、C_Q2、A₂, of the original ideal single-tone signal,Reference may be made to other embodiments for specific meaning and are not described in detail herein.

The demodulation of the signal receiver in the embodiment of the present application for demodulating the radio frequency signal may refer to other embodiments, which are not described herein.

In the embodiment of the application, the following steps are providedFiltering all the frequency multiplication components (using integration and difference to obtain frequency multiplication components, and then discarding) by a low-pass filter to obtain an in-phase signal in the baseband signal, wherein the in-phase signal can be expressed by the following formula:

where I' (t) represents the in-phase signal in the baseband signal of the signal receiver, A ₁ represents the amplitude of the in-phase quadrature signal of the signal transmitter, C _I1 represents the amplitude of local oscillator leakage of the in-phase signal of the signal transmitter, w ₁ represents the local oscillator frequency of the signal transmitter, w ₂ represents the local oscillator frequency of the signal receiver, C _Q1 represents the amplitude of local oscillator leakage of the quadrature signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, and C _I2 represents the amplitude of local oscillator leakage of the in-phase signal of the signal receiver.

S502, the signal receiver demodulates the radio frequency signal to obtain a quadrature signal in the baseband signal.

In the embodiment of the application, the pairFiltering all the frequency multiplication components (using integration and difference to obtain frequency multiplication components, and then discarding) by a low-pass filter to obtain orthogonal signals in the baseband signal, wherein the orthogonal signals can be represented by the following formula:

wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, Representing the angle of the in-phase quadrature signal of the signal receiver,Representing the angle of the in-phase quadrature signal of the signal receiver, C _Q2 is the non-rational characteristic of the signal receiver, C _Q1、C_I1、A₁ andAs a non-ideal feature of the signal transmitter, C _I2、C_Q2 Is a non-ideal feature of a signal receiver.

S503, the signal receiver obtains a baseband signal based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal.

The baseband signal obtained can be expressed by the following formula:

S402, the signal receiver determines baseband spectrum information of the signal receiver according to the baseband signal.

Wherein, Represents baseband spectral information of the signal receiver, delta (ω) represents a center frequency of the mono signal, delta (ω -2 (ω ₁-ω₂)) represents an image frequency of the signal transmitter, and delta (ω - ω ₁+ω₂) represents a local oscillator frequency of the signal transmitter.

In the embodiment of the application, in the frequency spectrum information, the image frequency of the signal transmitter is only affected by the unbalanced information of the IQ amplitude angle of the signal receiver.

In the embodiment of the application, in the frequency spectrum information, the local oscillation frequency of the signal transmitter is only influenced by local oscillation leakage of the I path and the Q path of the signal receiver.

S403, the signal receiver determines the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information.

Based on the baseband spectrum information, the determined imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter is:

Based on the baseband spectrum information, the local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter is determined as follows:

[(C_I1-jC_Q1)]2πδ(ω-ω₁+ω₂)。

1 in the power spectrum, the peak height of the image frequency of the signal transmitter is proportional to Indicating that the IQ amplitude imbalance and IQ angle imbalance of the signal transmitter are decoupled from the peak height of the image frequency, which is lowest when the IQ amplitude imbalance and IQ angle imbalance of the signal transmitter are simultaneously minimized.

2 In the power spectrum, the peak value height of the local oscillation frequency of the signal transmitter is proportional to C _I2 ²+C_Q2 ², which indicates that the peak value heights of the local oscillation frequency of the I-path local oscillation leakage and the Q-path local oscillation leakage of the signal transmitter are decoupled, and when the I-path local oscillation leakage and the Q-path local oscillation leakage reach minimum at the same time, the peak value heights of the local oscillation frequency are minimum.

S404, the signal receiver determines a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determines a third optimal compensation value of the local oscillation leakage information based on the local oscillation leakage information and a preset third compensation value range of the local oscillation leakage information.

Determining, by using an optimization algorithm, a first compensation value range of preset unbalance information Is included.

And determining a third optimal compensation value of [ (C _I1-jC_Q1)]2πδ(ω-ω₁+ω₂) in a third compensation value range of the preset local oscillator leakage information by utilizing an optimizing algorithm.

Specifically, the specific method of S404 is the same as that of S204, and will not be described here again.

S405, the signal receiver calibrates the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrates the local oscillator leakage information of the signal transmitter according to the third compensation value.

Specifically, the signal receiver according to the embodiment of the application calibrates the unbalanced information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, so that the influence of the unbalanced information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter on the reliability of the device can be reduced, and calibrates the local oscillator leakage information of the signal transmitter according to the third optimal compensation value, so that the influence of the local oscillator leakage information of the signal transmitter on the reliability of the device can be reduced at the same time.

In summary, the technical scheme of the application includes the steps of obtaining a radio frequency signal sent by a signal transmitter through a loop link, demodulating the radio frequency signal to obtain a baseband signal, determining baseband frequency spectrum information of a signal receiver according to the baseband signal, determining imbalance information of amplitude or angle of an in-phase quadrature signal of the signal transmitter and local oscillator leakage information based on the baseband frequency spectrum information, determining a first optimal compensation value of the imbalance information and a third optimal compensation value of the local oscillator leakage information, calibrating the imbalance information according to the first optimal compensation value, and calibrating the local oscillator leakage information according to the third optimal compensation value. The embodiment of the application can calibrate the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter and the local oscillator leakage information at the same time, thereby improving the reliability of the signal receiver.

Furthermore, the technical scheme of the application does not need additional accompanying measurement equipment or depends on other special hardware equipment, and can realize the calibration of the signal transmitter and the signal receiver only by connecting the signal transmitter and the signal receiver through a loop link, thereby further improving the calibration efficiency, and the scheme has low cost and is easy to popularize.

Furthermore, the technical scheme of the application utilizes the optimizing algorithm to calibrate, and has high calibration precision and high calibration speed.

It should be understood that the sequence number of each step in the foregoing embodiment does not mean that the execution sequence of each process should be determined by the function and the internal logic, and should not limit the implementation process of the embodiment of the present application.

Referring to fig. 6, fig. 6 is a schematic structural diagram of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application, where the device includes:

The acquiring module 61 is configured to acquire a modulated radio frequency signal sent by the signal transmitter through the loop link, and demodulate the radio frequency signal to obtain a baseband signal, where the radio frequency signal is a single tone signal.

The first determining module 62 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.

A second determining module 63, configured to determine imbalance information of amplitude or angle of in-phase quadrature signals of the signal receiver, and dc offset information based on the baseband spectrum information.

The third determining module 64 is configured to determine a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determine a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information.

The calibration module 65 is configured to calibrate the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, and calibrate the dc offset information of the signal receiver according to the second optimal compensation value.

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, the deviation value of the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is less than 1/4 of the baseband bandwidth, the obtaining module 61 is further configured to demodulate the radio-frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:

Where I' (t) represents the in-phase signal in the baseband signal of the signal receiver, C _Q1 represents the amplitude of local oscillator leakage of the quadrature signal of the signal transmitter, A ₁ represents the amplitude of the in-phase quadrature signal of the signal transmitter, omega ₁ represents the local oscillator frequency of the signal transmitter, omega ₂ represents the local oscillator frequency of the signal receiver, C _I1 represents the amplitude of local oscillator leakage of the in-phase signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, and C _I2 represents the amplitude of local oscillator leakage of the in-phase signal of the signal receiver;

Demodulating the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is:

where Q' (t) represents the quadrature signal in the baseband signal of the signal receiver, A ₂ represents the amplitude of the in-phase quadrature signal of the signal receiver, CQ1, CI1, A1 and CQ1 represent angles of in-phase and quadrature signals of a signal receiverAs a non-ideal feature of the signal transmitter, CI2, A2 andIs a non-ideal characteristic of a signal receiver;

Based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal, a baseband signal is obtained, and the baseband signal is:

The first determining module 62 is further configured to perform fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:

Wherein, Representing baseband spectral information of the signal receiver, C _Q2 representing the amplitude of local oscillator leakage of the quadrature signal of the signal receiver, δ (ω+ω ₂-ω₁) representing the center frequency of the mono signal, δ (ω+ω ₁-ω₂) representing the image frequency of the signal receiver, δ (ω) representing the local oscillator frequency of the signal receiver, C _Q2 being an irrational characteristic of the signal receiver.

The second determining module 63 is further configured to determine, based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver, where the imbalance information is:

[2(C_I2+j+C_Q2)]2πδ(ω);

wherein the third determining module 64 is further configured to determine, using an optimization algorithm, a first compensation value range of the preset unbalance information Is determined by the first optimum compensation value of (a);

And determining a second optimal compensation value of [2 (C _I2+j+C_Q2) ] 2pi delta (omega) in a second compensation value range of the preset direct current offset information by utilizing an optimizing algorithm.

Referring to fig. 7, fig. 7 is a schematic structural diagram of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application, where the device includes:

The acquiring module 71 is configured to acquire a modulated radio frequency signal sent by the signal transmitter through the loop link, and demodulate the radio frequency signal to obtain a baseband signal, where the radio frequency signal is a tone signal.

The first determining module 72 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.

The second determining module 73 is configured to determine, based on the baseband spectrum information, imbalance information of an amplitude or an angle of an in-phase quadrature signal of the signal transmitter, and local oscillation leakage information.

A third determining module 74, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a third optimal compensation value of the local oscillation leakage information based on the local oscillation leakage information and a preset third compensation value range of the local oscillation leakage information.

The calibration module 75 is configured to calibrate the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value.

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal receiver, the local oscillation frequency of the signal transmitter and the local oscillation frequency of the signal receiver are smaller than 1/4 of the baseband bandwidth, and the obtaining module 71 is further configured to demodulate the radio-frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:

where I' (t) represents the in-phase signal in the baseband signal of the signal receiver, A ₁ represents the amplitude of the in-phase quadrature signal of the signal transmitter, C _I1 represents the amplitude of local oscillator leakage of the in-phase signal of the signal transmitter, omega ₁ represents the local oscillator frequency of the signal transmitter, omega ₂ represents the local oscillator frequency of the signal receiver, C _Q1 represents the amplitude of local oscillator leakage of the quadrature signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, and C _I2 represents the amplitude of local oscillator leakage of the in-phase signal of the signal receiver;

wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, Representing the angle of the in-phase quadrature signal of the signal receiver,Representing the angle of the in-phase quadrature signal of the signal receiver, C _Q2 is the non-rational characteristic of the signal receiver, C _Q1、C_I1、A₁ andAs a non-ideal feature of the signal transmitter, C _I2、C_Q2 Is a non-ideal characteristic of a signal receiver;

The first determining module 72 is further configured to perform fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:

Wherein the second determining module 72 is further configured to determine, based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter as follows:

[(C_I1-jC_Q1)]2πδ(ω-ω₁+ω₂)。

Wherein the third determining module 73 is further configured to determine, using an optimization algorithm, a first compensation value range of the preset unbalance information Is determined by the first optimum compensation value of (a);

and determining a second optimal compensation value of [ (C _I1-jC_Q1)]2πδ(ω-ω₁+ω₂) in a third compensation value range of the preset local oscillator leakage information by utilizing an optimizing algorithm.

It will be apparent to those skilled in the art that, for convenience and brevity of description, only the above-described division of the functional units and modules is illustrated, and in practical application, the above-described functional distribution may be performed by different functional units and modules according to needs, i.e. the internal structure of the apparatus is divided into different functional units or modules to perform all or part of the above-described functions. The functional units and modules in the embodiment may be integrated in one processing unit, or each unit may exist alone physically, or two or more units may be integrated in one unit, where the integrated units may be implemented in a form of hardware or a form of a software functional unit. In addition, the specific names of the functional units and modules are only for distinguishing from each other, and are not used for limiting the protection scope of the present application. The specific working process of the units and modules in the above system may refer to the corresponding process in the foregoing method embodiment, which is not described herein again.

As shown in fig. 8, an electronic device 200 is further provided according to an embodiment of the present application, which includes a memory 21, a processor 22, and a computer program 23 stored in the memory 21 and executable on the processor 22, where the processor 22 implements the calibration method of the zero intermediate frequency signal transceiver of the above embodiment or implements the calibration method of the zero intermediate frequency signal transceiver of the above embodiment when executing the computer program 23.

The Processor 22 may be a central processing unit (Central Processing Unit, CPU), but may also be other general purpose processors, digital signal processors (DIGITAL SIGNAL Processor, DSP), application SPECIFIC INTEGRATED Circuit (ASIC), field-Programmable gate array (Field-Programmable GATE ARRAY, FPGA) or other Programmable logic device, discrete gate or transistor logic device, discrete hardware components, or the like. A general purpose processor may be a microprocessor or the processor may be any conventional processor or the like.

The memory 21 may be an internal storage unit of the electronic device 200. The memory 21 may also be an external storage device of the electronic device 200, such as a plug-in hard disk, a smart memory card (SMART MEDIA CARD, SMC), a Secure Digital (SD) card, a flash memory card (FLASH CARD) or the like, which are provided on the electronic device 200. Further, the memory 21 may also include both an internal storage unit and an external storage device of the electronic device 200. The memory 21 is used to store computer programs and other programs and data required by the electronic device 200. The memory 21 may also be used to temporarily store data that has been output or is to be output.

The embodiment of the application also provides a computer readable storage medium, wherein the computer readable storage medium stores a computer program, and the calibration method of the zero intermediate frequency signal transceiver of the embodiment is realized when the computer program is executed by a processor.

The embodiment of the application provides a computer program product which, when run on a mobile terminal, enables the mobile terminal to execute the calibration method of the zero intermediate frequency signal transceiver of the embodiment.

The integrated units, if implemented in the form of software functional units and sold or used as stand-alone products, may be stored in a computer readable storage medium. Based on such understanding, the present application may implement all or part of the flow of the method of the above-described embodiments, and may be implemented by a computer program to instruct related hardware, where the computer program may be stored in a computer readable storage medium, and the computer program may implement the steps of the method embodiments described above when executed by a processor. Wherein the computer program comprises computer program code, which may be in the form of source code, object code, executable files or in some intermediate form, etc. The computer readable storage medium may include at least any entity or device capable of carrying computer program code to a camera device/electronic apparatus, a recording medium, a computer memory, a read-only memory (ROM), a random access memory (random access memory, RAM), an electrical carrier signal, a telecommunications signal, and a software distribution medium. Such as a U-disk, removable hard disk, magnetic or optical disk, etc. In some jurisdictions, computer-readable storage media may not be electrical carrier signals and telecommunications signals in accordance with legislation and patent practice.

In the foregoing embodiments, the descriptions of the embodiments are emphasized, and in part, not described or illustrated in any particular embodiment, reference is made to the related descriptions of other embodiments.

Those of ordinary skill in the art will appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, or combinations of computer software and electronic hardware. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the solution. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present application.

The units described as separate units may or may not be physically separate, and units shown as units may or may not be physical units, may be located in one place, or may be distributed over a plurality of network units. Some or all of the units may be selected according to actual needs to achieve the purpose of the embodiment of the present application.

The foregoing embodiments are merely for illustrating the technical solution of the present application, but not for limiting the same, and although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those skilled in the art that the technical solution described in the foregoing embodiments may be modified or substituted for some of the technical features thereof, and that these modifications or substitutions should not depart from the spirit and scope of the technical solution of the embodiments of the present application and should be included in the protection scope of the present application.

Claims

1. A method of calibrating a zero intermediate frequency signal transceiver, the method comprising:

determining baseband spectrum information of a signal receiver according to the baseband signal;

Calibrating imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, and calibrating direct current offset information of the signal receiver according to the second optimal compensation value;

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, the deviation value of the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is smaller than 1/4 baseband bandwidth, the demodulation of the radio-frequency signal to obtain a baseband signal comprises the following steps:

2. The method of calibrating according to claim 1, wherein said determining baseband spectral information of said signal receiver from said baseband signal comprises:

3. The calibration method according to claim 2, wherein the determining of the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver, and the dc offset information based on the baseband spectrum information, comprises:

[2(C_I2+j+C_Q2)]2πδ(ω)。

4. A calibration method according to claim 3, wherein determining a first optimal compensation value for the unbalance information based on the unbalance information and a preset first compensation value range for the unbalance information, and determining a second optimal compensation value for the dc offset information based on the dc offset information and a preset second compensation value range for the dc offset information, comprises:

and determining a second optimal compensation value of [2 (C _I2+j+C_Q2) |delta (omega) in a preset second compensation value range of the direct current offset information by utilizing an optimizing algorithm.

5. A method of calibrating a zero intermediate frequency signal transceiver, the method comprising:

Calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value;

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal receiver, the deviation value of the local oscillation frequency of the signal transmitter and the local oscillation frequency of the signal receiver is smaller than 1/4 baseband bandwidth, the demodulation of the radio-frequency signal to obtain a baseband signal comprises the following steps:

where I' (t) represents the in-phase signal in the baseband signal of the signal receiver, A ₁ represents the amplitude of the in-phase quadrature signal of the signal transmitter, C _I1 represents the amplitude of local oscillator leakage of the in-phase signal of the signal transmitter, w ₁ represents the local oscillator frequency of the signal transmitter, w ₂ represents the local oscillator frequency of the signal receiver, C _Q1 represents the amplitude of local oscillator leakage of the quadrature signal of the signal transmitter, Representing the angle of the in-phase quadrature signal of the signal transmitter, and C _I2 represents the amplitude of local oscillator leakage of the in-phase signal of the signal receiver;

6. A calibration device for a zero intermediate frequency signal transceiver, the calibration device comprising:

The calibration module is used for calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal receiver according to the first optimal compensation value, and calibrating the direct current offset information of the in-phase quadrature signal of the signal receiver according to the second optimal compensation value;

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, and the deviation value of the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is smaller than 1/4 baseband bandwidth;

the obtaining module is further configured to demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:

7. A calibration device for a zero intermediate frequency signal transceiver, the calibration device comprising:

The calibration module is used for calibrating the imbalance information of the amplitude or angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value;

The center frequency of the single-tone signal is the same as the local oscillation frequency of the signal receiver, and the deviation value of the local oscillation frequency of the signal transmitter and the local oscillation frequency of the signal receiver is smaller than 1/4 baseband bandwidth;

8. An electronic device comprising a memory, a processor and a computer program stored in the memory and executable on the processor, the processor implementing a method of calibrating a zero intermediate frequency signal transceiver according to any of claims 1 to 5 when the computer program is executed.

9. A computer readable storage medium storing a computer program, characterized in that the computer program, when executed by a processor, implements a method of calibrating a zero intermediate frequency signal transceiver according to any of claims 1 to 5.