CN115201650B - Shortwave power amplifier drain valley voltage detection circuit and voltage regulation method - Google Patents
Shortwave power amplifier drain valley voltage detection circuit and voltage regulation method Download PDFInfo
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Abstract
The invention discloses a drain trough voltage detection circuit of a shortwave power amplifier and a voltage regulation method, which comprise a drain input port, a direct current detection network, an alternating current negative pressure detection network, an addition amplifier and a detection output port, wherein the drain input port is respectively connected to the input ends of the direct current detection network and the alternating current negative pressure detection network, the output end of the direct current detection network and the output end of the alternating current negative pressure detection network are connected to one input end of the addition amplifier, and the output end of the addition amplifier is connected to the detection output port. The invention realizes the detection and collection of the trough voltage of the drain electrode of the power amplifier tube, provides an adjustment basis for an automatic drain electrode supply voltage adjustment system, and further improves the efficiency of the power amplifier under the condition of load mismatch.
Description
[ Field of technology ]
The invention belongs to the technical field of radio frequency circuits, and particularly relates to a drain electrode trough voltage detection circuit of a shortwave power amplifier and a voltage regulation method.
[ Background Art ]
Short wave power amplifiers are an indispensable device in short wave communication, electronic countermeasure and probe transmitters, providing the necessary radio frequency output power for the system.
The short wave frequency range covers 2 MHz-30 MHz, and is close to 4 octaves, the transmitting equipment belongs to a typical broadband system, the power amplifier always faces severe load conditions, the typical load standing wave ratio can reach more than 2.5, and the reflection phase angle is distributed in a range of 360 degrees.
Serious load mismatch can lead to uncontrolled performance of the power amplifier technology, one of which is efficiency degradation. The low efficiency can lead to the heat consumption to increase on the one hand, raise the power tube core temperature, reduce the reliability, even lead to the power tube damage, on the other hand can increase the system power consumption, increase running cost.
Fig. 1 (a) shows the drain efficiency of a typical power amplifier circuit at a load standing wave ratio of 2.5, with different reflection phase angles. It can be seen that as load conditions change, the drain efficiency drops from 65% to below 30%, increasing the heat consumption by a factor of approximately 5.
The main technical scheme for coping with load mismatch is to increase design margin and adopt automatic protection measures. Obviously, the design margin is large, so that excessive redundancy is caused, the miniaturization and the light weight of equipment are not facilitated, the automatic protection measures are only to prevent the equipment from being damaged under extreme conditions, the power amplification performance can not be fundamentally improved, and if the design margin is insufficient, frequent shutdown protection is caused, so that the normal work is influenced. Both of these measures cannot avoid an increase in the running cost.
The method for adjusting the power supply voltage can also be used for solving the problem of efficiency reduction caused by load mismatch. According to the working principle of the power tube, one of the mechanisms causing the efficiency reduction of the power amplifier circuit is that the alternating voltage swing of the drain electrode of the power tube is reduced due to the load change, and the dynamic range under the current direct current power supply condition is not fully used. Fig. 1 (b) and 1 (c) show the voltage waveforms at the drain of the power tube at the highest and lowest efficiencies, respectively. The waveform shows that under the condition of high efficiency, the voltage trough value reaches 0V and has a longer time duty ratio, and under the condition of low efficiency, the trough voltage minimum point is 6V, a larger falling space is provided, the trough duration time is short, and the efficiency can be improved under the condition that the signal quality is not affected by reducing the direct current supply voltage of the drain electrode. Experiments have shown that under the conditions shown in fig. 1 (c), the drain efficiency increases from 26% to 40% after the voltage drops from 48V to 36V.
The adjustment of the supply voltage needs to be automatically performed according to the load change, so that the method has engineering practicability. Although the technology of testing the load vector reflection coefficient of the power amplifier is not hindered, the implementation complexity is relatively high, the measuring point is generally at the outlet of the transmitter, and for a high-power transmitter, a longer radio frequency path exists from the output port of the transmitter to the drain electrode of the power amplifier, and a complicated calibration flow is needed.
At present, no related trough voltage detection circuit exists, and no automatic voltage adjustment system based on trough voltage exists. Therefore, it is necessary to provide a new short-wave power amplifier drain valley voltage detection circuit and voltage adjustment method to solve the above-mentioned technical problems.
[ Invention ]
The invention provides a drain electrode trough voltage detection circuit of a shortwave power amplifier, which realizes detection and acquisition of trough voltage of a drain electrode of a power amplifier tube, provides an adjustment basis for an automatic drain electrode supply voltage adjustment system, and further improves efficiency of the power amplifier under a load mismatch condition.
The drain trough voltage detection circuit of the shortwave power amplifier comprises a drain input port, a direct current detection network, an alternating current negative pressure detection network, an addition amplifier and a detection output port, wherein the drain input port is respectively connected to the input ends of the direct current detection network and the alternating current negative pressure detection network, the output end of the direct current detection network and the output end of the alternating current negative pressure detection network are connected to one input end of the addition amplifier, and the output end of the addition amplifier is connected to the detection output port.
Further, the direct current detection network includes two series connection voltage dividing resistors R1 and resistor R2, one end of the resistor R1 is connected with the drain input port, one end of the resistor R2 is grounded, and the terminal of the resistor R1 and the resistor R2 connected with each other forms the output end of the direct current detection network.
Further, the direct current detection network further comprises an operational amplifier N1, a terminal for connecting the resistor R1 and the resistor R2 is connected to the positive input end of the operational amplifier N1, the negative input end of the operational amplifier N1 is connected with the output end of the operational amplifier N1 to form a follower, and the output end of the operational amplifier N1 forms the output end of the direct current detection network.
Further, the alternating current negative pressure detection network comprises a blocking capacitor C1, a resistor R3, a resistor R4, a detection diode D1, a capacitor C2 and a resistor R5, wherein the drain input port is connected to one end of the blocking capacitor C1, the other end of the blocking capacitor C1 is connected with one end of the resistor R3, the resistor R3 is connected with the resistor R4 in series and then grounded, a terminal for connecting the resistor R3 with the resistor R4 is connected with the negative electrode of the detection diode D1, the positive electrode of the detection diode D1 is respectively connected with the capacitor C2 and the resistor R5, the capacitor C2 and the resistor R5 are connected with the ground in parallel, and the positive electrode of the detection diode D1 forms the output end of the alternating current negative pressure detection network.
Further, the alternating current negative pressure detection network further comprises an operational amplifier N2, the positive electrode of the detection diode D1 is connected with the positive input end of the operational amplifier N2, the negative input end of the operational amplifier N2 is connected with the output end of the operational amplifier N2 to form a follower, and the output end of the operational amplifier N2 forms the output end of the alternating current negative pressure detection network.
Further, the alternating current negative pressure detection network comprises a blocking capacitor C1, a resistor R3, a resistor R4, a detection diode D1 and a capacitor C2, wherein the drain input port is connected to one end of the blocking capacitor C1, the other end of the blocking capacitor C1 is connected with one end of the resistor R3, the resistor R3 is connected with the resistor R4 in series and then grounded, a terminal of the resistor R3, which is connected with the resistor R4, is connected with the negative electrode of the detection diode D1, the positive electrode of the detection diode D1 is connected with one end of the capacitor C2, the connection end of the detection diode D forms the output end of the alternating current negative pressure detection network, and the other end of the capacitor C2 is connected with the output end of the direct current detection network.
Furthermore, the alternating current negative pressure detection network further comprises a capacitor C5 and a capacitor C6, the resistor R3 is connected with the capacitor C5 in parallel, and the resistor R4 is connected with the capacitor C6 in parallel.
Further, the summing amplifier is provided with two input ends and one output end, and comprises an operational amplifier N3, a resistor R6 and a resistor R7, wherein the two input ends of the summing amplifier are respectively connected to the positive input end of the operational amplifier N3 through the resistor R6 and the resistor R7, the negative input end of the operational amplifier N3 is grounded through a resistor R8 and is connected with the output end of the operational amplifier N3 through a resistor R9, and the output end of the operational amplifier N3 forms the detection output end of the detection circuit and is connected to the detection output port.
Further, the drain input port is located at a root position on the printed circuit board near the drain of the power transistor and is electrically connected with the drain of the power transistor.
Another objective of the present invention is to provide a method for adjusting a drain dc supply voltage of a short-wave power amplifier, which correspondingly adjusts the drain dc supply voltage of the power amplifier according to the drain valley voltage value of the power amplifier detected by the detection circuit.
Compared with the prior art, the short wave power amplifier drain valley voltage detection circuit and the voltage regulation method have the advantages that whether the dynamic range of the power tube is full or not can be obtained by measuring the alternating current valley voltage value of the drain electrode of the power tube, and further whether the current power supply voltage is proper or not can be directly reflected, the basis is provided for automatic regulation of the direct current power supply voltage of the drain electrode of the power tube, the implementation process is greatly simplified, the drain electrode of the power tube is input into a direct current detection network and an alternating current negative voltage detection network, the output voltage of the direct current detection network is in direct proportion to the direct current voltage of the drain electrode through resistance voltage division, filtering and buffering, the alternating current negative voltage detection network is connected with the input of an addition amplifier through a detection diode, the drain voltage detection value is obtained after the two detection voltages are added and amplified, the direct current and the alternating current component of the drain electrode are separately detected, the alternating current negative voltage detection circuit is optimized, the detection precision and the detection efficiency of the drain voltage of the power amplifier is improved, the circuit is simple and convenient to realize, the direct current negative voltage detection network is distributed nearby, the voltage detection network can obtain the negative voltage peak voltage of the negative voltage of the drain electrode through resistance voltage, and the full or not, and the full power supply voltage can be accurately regulated according to the drain voltage detection circuit.
[ Description of the drawings ]
FIG. 1 (a) shows that the drain efficiency of a short-wave power amplifier changes with the reflection phase (the frequency is 30 MHz) when the load standing wave ratio is 2.5;
FIG. 1 (b) shows the drain voltage waveform at the highest efficiency;
FIG. 1 (c) is the drain voltage waveform at the lowest efficiency;
FIG. 2 is a functional block diagram of an embodiment of the present invention;
FIG. 3 is one of the circuit schematic diagrams of an embodiment of the present invention;
FIG. 4 is a second schematic circuit diagram of an embodiment of the present invention;
FIG. 5 is a third schematic circuit diagram of an embodiment of the present invention;
Fig. 6 is a schematic view of an installation position of an embodiment of the present invention.
[ Detailed description ] of the invention
Embodiment one:
The schematic block diagram of the embodiment is shown in fig. 2, and the circuit comprises a drain input port 1, a direct current detection network 2, an alternating current negative pressure detection network 3, an addition amplifier 4 and a detection output port 5. The output end of the direct current detection network 2 is connected with one input end of the summing amplifier 4, the output end of the alternating current negative pressure detection network 3 is connected with the other input end of the summing amplifier 4, and the output end of the summing amplifier 4 serves as the detection output end of the drain trough voltage detection circuit of the shortwave power amplifier.
The schematic circuit diagram of this embodiment is shown in fig. 3. The direct current detection network 2 comprises a voltage dividing circuit formed by connecting resistors R1 and R2 in series, a filter capacitor C3 and an follower formed by an operational amplifier N1 and an output filter capacitor C4, wherein one end of the voltage dividing resistor R1 is connected with a drain input port 1, the other end of the voltage dividing resistor R1 is connected with the resistor R2 in series and grounded, the filter capacitor C3 is connected with the resistor R2 in parallel, a terminal of the resistor R1, which is connected with the resistor R2, is connected with the positive input end of the operational amplifier N1, the output end of the operational amplifier N1 is connected with the negative input end of the operational amplifier N1, one end of the filter capacitor C4 is connected with the output end of the operational amplifier N1, the other end of the filter capacitor C4 is grounded, and the output end of the operational amplifier N1 forms the output end of the direct current detection network 2.
In another embodiment, referring to fig. 4, the dc detection network 2 includes a voltage dividing circuit formed by connecting resistors R1 and R2 in series and a filter capacitor C3, wherein one end of the voltage dividing resistor R1 is connected to the drain input port 1, the other end is connected to the resistor R2 in series, the filter capacitor C3 is connected in parallel with the resistor R2, and terminals of the resistor R1 and the resistor R2 connected to each other form an output end of the dc detection network 2.
In this embodiment, referring to fig. 3, the ac negative pressure detection network 3 includes a blocking capacitor C1, a series voltage dividing resistor R3 and a resistor R4, a detection diode D1, a filter composed of a capacitor C2 and a resistor R5, and a follower composed of an operational amplifier N2. One end of a blocking capacitor C1 is connected with a drain electrode input port 1, the other end of the blocking capacitor C1 is connected with a divider resistor R3, the other end of the divider resistor R3 is connected with a divider resistor R4 in series and then grounded, a terminal for connecting the divider resistor R3 with the resistor R4 is connected with the negative electrode of a detection diode D1, the positive electrode of the detection diode D1 is respectively connected with a capacitor C2 and a resistor R5, the capacitor C2 and the resistor R5 are connected with each other in parallel, the positive electrode of the detection diode D1 is also connected with the positive input end of an operational amplifier N2, the negative input end of the operational amplifier N2 is connected with the output end of the operational amplifier N2 to form a follower, and the output end of the operational amplifier N2 forms an output end of an alternating current negative pressure detection network 3.
In another embodiment, referring to fig. 4, the ac negative pressure detection network 3 includes a blocking capacitor C1, a series voltage dividing resistor R3 and a resistor R4, a detection diode D1, and a filter composed of a capacitor C2 and a resistor R5. One end of the blocking capacitor C1 is connected with the drain electrode input port 1, the other end of the blocking capacitor C is connected with the divider resistor R3, the other end of the divider resistor R3 is connected with the divider resistor R4 in series and then grounded, a terminal for connecting the divider resistor R3 and the resistor R4 with each other is connected with the negative electrode of the detection diode D1, the positive electrode of the detection diode D1 is respectively connected with the capacitor C2 and the resistor R5, the capacitor C2 and the resistor R5 are connected in parallel, and the positive electrode of the detection diode D1 forms an output end of the alternating current negative voltage detection network 3.
In yet another embodiment, referring to fig. 5, the ac negative pressure detection network 3 includes a blocking capacitor C1, a series voltage dividing resistor R3, a resistor R4, a detection diode D1 and a capacitor C2, wherein one end of the blocking capacitor C1 is connected to the drain input port 1, the other end is connected to the voltage dividing resistor R3, the other end of the voltage dividing resistor R3 is connected to the voltage dividing resistor R4 in series and then grounded, a terminal of the voltage dividing resistor R3 connected to the resistor R4 is connected to the negative electrode of the detection diode D1, the positive electrode of the detection diode D1 is connected to one end of the capacitor C2, the connection end forms an output end of the ac negative pressure detection network 3, and the other end of the capacitor C2 is connected to the output end of the dc detection network 2.
The alternating current negative pressure detection network 3 further comprises a capacitor C5 and a capacitor C6, wherein a resistor R3 is connected with the capacitor C5 in parallel, and a resistor R4 is connected with the capacitor C6 in parallel.
In this embodiment, the summing amplifier circuit 4 includes an input resistor R6 and an input resistor R7, an operational amplifier N3, and a feedback voltage dividing resistor R8 and a feedback voltage dividing resistor R9, one end of the input resistor R6 is connected to an output end of the ac negative pressure detection network 3 (an output end of the operational amplifier N2, or a positive electrode of the detection diode D1, or a connection end of the detection diode D1 and the capacitor C2), the other end is connected to a positive input end of the operational amplifier N3, one end of the input resistor R7 is connected to an output end of the dc detection network 2 (an output end of the operational amplifier N1, or a terminal where the resistor R1 and the resistor R2 are connected to each other), the other end is connected to a positive input end of the operational amplifier N3, the feedback voltage dividing resistor R9 is connected between the output end and a negative input end of the operational amplifier N3, and one end of the feedback voltage dividing resistor R8 is connected to a negative input end of the operational amplifier N3, and the other end is grounded.
The output terminal of the operational amplifier N3 serves as a detection output terminal of the detection circuit of the present embodiment, and is connected to the detection output port 5.
The working principle of the embodiment is as follows:
the voltage V d (t) at the drain input port is:
Vd(t)＝Vd0+Va(t+nT),
Where n is an integer, T is the radio frequency signal period, V d0 is the DC component, and V a (T) is the AC waveform. The valley value V val of the drain voltage is:
Vval＝min0≤t≤T{Vd(t)}＝Vd0+min0≤t≤T{Va(t)}
In the dc detection network 2, after the drain voltage is divided by the resistor R1 and the resistor R2, the ac component is filtered by the filter capacitor C3, so as to obtain a dc detection voltage V sd as follows:
In the AC negative pressure detection network 3, the capacitor C1 isolates the DC component, so that the resistors R3 and R4 divide the voltage to obtain the AC voltage The detection diode D1 conducts the negative pressure in the waveform of V a1 (T), charges the filter capacitor C2 to make the capacitor C2 negative voltage to the ground, and selects the filter time constant tau=C2.R5 > > T composed of the capacitor C2 and the resistor R5, the capacitor C2 keeps the lowest voltage of V a1 (T), and the output voltage V sa of the detection diode D1 is as follows:
The summing amplifier 4 sums and amplifies V sd、Vsa and outputs the resultant voltage V s as follows:
Selecting component parameter values, and meeting the following conditions:
Then
I.e. the detected output voltage is proportional to the valley voltage value. The scaling factor can be adjusted by selecting the resistor R9 and the resistor R8.
When the specific implementation shown in fig. 5 is adopted, the difference from the working principle of this embodiment is that after the input resistor R6 and the resistor R7 of the summing amplifier 4 are connected in series, the filter resistor is equivalent to the output end of the detection diode D1, so that the time constant τ= (r6+r7) C2 of the filter should be ensured to be τ > > T. The detection output result of the detection circuit shown in fig. 5 is the same as that of the embodiment, and the detection circuit shown in fig. 5 omits an operational amplifier N2 and a filter resistor R5 on one hand, so that the circuit is simplified, and on the other hand, as one end of a filter capacitor C2 is connected with the direct current detection output, the loop voltage difference of a detection diode D1 is increased, so that the conduction of the detection diode D1 is more sufficient, the sensitivity of the detection diode D1 is increased, and the influence caused by junction voltage drop is reduced.
Fig. 6 is a schematic diagram of a layout position of the circuit of the present embodiment. The detection circuit of the embodiment is designed and manufactured on a printed circuit board 52, a power tube 51 to be detected and the printed circuit board 52 are arranged on the surface of a metal substrate 53, a drain electrode pin 511 of the power tube 51 is connected with a microstrip line 54 on the upper layer of the printed circuit board 52, a cavity 57 is processed on the metal substrate 53 below an output transformer 56, and the microstrip line 54 is connected to the back surface of the printed circuit board 52 at a position close to the root of the drain electrode pin 511 through a metallized via hole 55 and is arranged in the cavity 57. The detection circuit of this embodiment is disposed on the back side of the printed circuit board 52 and corresponds to the location of the cavity 57, and the drain input is connected to the metallized via 55.
In the frequency range of 2-30 mhz, the embodiment of the invention selects r6=r7=20kΩ, c2=560 pf, r3=r1=20kΩ, r8=r9=10kΩ, the detection diode D1 is a schottky diode, and the operational amplifier is of a general type. And (3) taking the trough detection output voltage as a reference, and adjusting the power supply voltage of the power amplifier, wherein under the test condition shown in fig. 1, the minimum efficiency of the power amplifier reaches more than 40%.
The method and the device can be used for obtaining whether the dynamic range of the power tube is full or not under the current load condition by measuring the alternating current trough voltage value of the drain electrode of the power tube, further, whether the current power supply voltage is proper or not can be directly reflected, the basis is provided for automatic adjustment of the direct current power supply voltage of the drain electrode of the power tube, the implementation process is greatly simplified, the drain electrode of the power tube is input into a direct current detection network and an alternating current negative pressure detection network, the output voltage of the direct current detection network is in direct current voltage proportional to the drain electrode through resistor voltage division, filtering and buffering, the alternating current negative pressure detection network adopts a detection diode after a direct current capacitor is isolated, the output of the direct current detection network and the alternating current negative pressure detection network are connected with the input of an addition amplifier, the drain trough voltage detection value is obtained after the two detection voltages are added and amplified, the direct current and the alternating current components of the drain electrode are separately detected, the alternating current negative pressure detection circuit is optimized, the detection accuracy and the detection efficiency of the drain voltage of the power amplifier are improved, the circuit is simple and convenient to implement, the circuit can be distributed nearby the drain electrode of the power tube, the structure is compact, the structure is convenient, and the implementation is accurate, and the automatic measurement of the voltage of the drain voltage of the power tube is obtained according to whether the dynamic range of the power supply is full or not.
What has been described above is merely some embodiments of the present invention. It will be apparent to those skilled in the art that various modifications and improvements can be made without departing from the spirit of the invention.
Claims (8)
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| CN208369533U (en) * | 2018-07-18 | 2019-01-11 | 航天恒星科技有限公司 | A kind of broadband high-efficiency power amplifier |
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| JP2005079967A (en) * | 2003-09-01 | 2005-03-24 | Seiko Epson Corp | High frequency power amplifier and wireless communication device using the same |
| CN103329626B (en) * | 2011-11-29 | 2016-01-20 | 叶军 | LED drive circuit and LED drive chip |
| RU2550561C1 (en) * | 2013-12-05 | 2015-05-10 | Федеральное государственное казенное военное образовательное учреждение высшего профессионального образования "Военный учебно-научный центр Военно-Морского Флота "Военно-морская академия имени Адмирала Флота Советского Союза Н .Г. Кузнецова" | Wide-band short wave power amplifier |
| CN107085132B (en) * | 2017-05-18 | 2019-09-17 | 东南大学 | A kind of high-precision detection of negative pressure circuit under positive voltage power supply |
| CN108761284B (en) * | 2018-05-18 | 2024-07-05 | 北京华峰测控技术股份有限公司 | Drain leakage current test circuit and method in field effect transistor breakdown voltage characteristics |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN102636684A (en) * | 2012-04-24 | 2012-08-15 | 安徽华祝电气技术有限公司 | Alternating voltage peak moment detection circuit |
| CN103648219A (en) * | 2013-12-19 | 2014-03-19 | 上海莱托思电子科技有限公司 | Light-emitting diode (LED) switch constant-current driving circuit |
| CN208369533U (en) * | 2018-07-18 | 2019-01-11 | 航天恒星科技有限公司 | A kind of broadband high-efficiency power amplifier |
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