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CN114598172B - Rectifying device suitable for wireless power transmission system and control method - Google Patents

Rectifying device suitable for wireless power transmission system and control method Download PDF

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Publication number
CN114598172B
CN114598172B CN202210497810.7A CN202210497810A CN114598172B CN 114598172 B CN114598172 B CN 114598172B CN 202210497810 A CN202210497810 A CN 202210497810A CN 114598172 B CN114598172 B CN 114598172B
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signal
voltage
current
pwm
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CN114598172A (en
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柯光洁
许叶葳
陈乾宏
张斌
温振霖
徐立刚
任小永
张之梁
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Jiangsu Zhanxin Semiconductor Technology Co ltd
Nanjing University of Aeronautics and Astronautics
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Jiangsu Zhanxin Semiconductor Technology Co ltd
Nanjing University of Aeronautics and Astronautics
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

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  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Rectifiers (AREA)
  • Dc-Dc Converters (AREA)

Abstract

本发明公开一种适用于无线电能传输系统的整流装置及控制方法，该无线电能传输系统的整流装置包括：非接触变压器副边绕组、副边补偿网络、整流电路、滤波电路、负载和控制单元。本发明的控制方法通过检测副边绕组侧电流，有效避免了现有技术因采样整流电路输入电流i 2 高频谐波含量过高，畸变严重导致的采样相位偏移和过零信号不唯一问题，从而避免了过零点检测不准确以及多个过零信号带来的误判、同步失败问题，优化了可控开关管驱动同步控制的稳定性，使控制方法更加简单、准确且便于设计。

Figure 202210497810

The invention discloses a rectification device and a control method suitable for a wireless power transmission system. The rectification device of the wireless power transmission system comprises: a non-contact transformer secondary winding, a secondary compensation network, a rectification circuit, a filter circuit, a load and a control unit . The control method of the present invention effectively avoids the problems of sampling phase offset and non-unique zero-crossing signal caused by the high-frequency harmonic content of the input current i 2 of the sampling rectifier circuit and serious distortion caused by the detection of the secondary winding side current in the prior art , so as to avoid the inaccurate zero-crossing detection and the misjudgment and synchronization failure caused by multiple zero-crossing signals, optimize the stability of the synchronous control of the controllable switch tube drive, and make the control method simpler, more accurate and easier to design.

Figure 202210497810

Description

Rectifying device suitable for wireless power transmission system and control method
Technical Field
The invention relates to a rectifying device and a control method suitable for a wireless power transmission system, and belongs to the field of wireless power transmission.
Background
The Wireless Power Transfer (WPT) greatly increases the safety, convenience and reliability of the charging system due to the characteristic of no contact between an electric energy sending end and a receiving end, and has higher practical value and potential economic benefit in the fields of biomedicine, foreign matter detection, underwater Power supply, electric vehicle charging and the like.
In practical applications, wireless charging systems are often required to meet different output power requirements. For example, in the electric automobile industry, the national standard of wireless charging of electric automobiles in China is divided into multiple stages from 3.7 kilowatts to 11 kilowatts, and the change of the large-power stage range reflects the large equivalent load change of the electric automobiles in the whole charging process. In order to maintain high-efficiency transmission all the time during charging, a controllable rectifying circuit can be usually introduced to control the equivalent impedance by adjusting the conduction angle, so as to realize impedance matching.
In order to realize zero voltage switching-on of a controllable switching tube in a rectifying circuit, a common method is to obtain an input current signal of a rectifying bridge through a current-voltage conversion circuit, and drive the switching tube through a DSP controller after band-pass filtering, phase compensation and zero-crossing comparison processing. However, when the secondary side is compensated by the LCC or LCL, the input current waveform of the rectifying circuit is seriously distorted due to the low impedance characteristic of the system under the higher harmonic wave, and the harmonic wave content is very high. Under the working condition, the influence of harmonic waves on the phase of a current zero crossing point cannot be ignored, and meanwhile, the distortion of the waveform can enable a plurality of zero crossing points to exist in a current signal in one switching period, so that the complexity of signal processing is increased, and the reliability of a system is influenced. Therefore, how to guarantee the simplicity and stability of the control method while considering the harmonic influence becomes an urgent problem to be solved in the prior art.
Disclosure of Invention
In order to solve the problems in the prior art, the invention provides a control method for realizing the synchronous drive control of a controllable switching tube by detecting the current phase of a secondary winding of a non-contact transformer, which can avoid the problems of phase shift and non-unique zero-crossing signals in the current sampling process, reduce harmonic interference, be beneficial to the optimization of system control and ensure that the charging process is more stable.
Another object of the present invention is to provide a rectifying device suitable for a wireless power transmission system, which implements the above control method.
The technical scheme of the invention is as follows:
a driving synchronization method for a controllable switch tube of a rectification circuit in a wireless power transmission system comprises the following steps: the non-contact transformer secondary winding, the secondary compensation network, the rectifying circuit, the filter circuit, the load and the control unit are characterized in that the control unit comprises a winding current sampling circuit, a current-voltage conversion circuit, a signal processing circuit, a PWM (pulse width modulation) module and a driving circuit, and the method comprises the following steps:
step 1: detecting secondary winding current flowing through non-contact transformeri s And generates a voltage signal in phase with the current-voltage conversion circuitv a ；
Step 2: voltage signal is processed by signal processing circuitv a Conversion to secondary winding currenti s Square wave signal of same phasev b And applying the square wave signalv b The synchronous signal input is used as a synchronous signal input of the PWM module;
and step 3: the PWM modulation module is used for modulating the square wave signalv b Fundamental component of input voltage of rectifier circuitv 2_1 Generating a PWM signal ePWM;
and 4, step 4: and the driving circuit (6e) receives the PWM signal ePWM and outputs the driving voltage required by the controllable switching tube in the rectifying circuit (3) to realize the driving synchronization and zero voltage switching-on of the controllable switching tube.
Specifically, the PWM signal modulation process in step 3 is:
for the case that the rectification circuit (3) is a semi-controlled bridge active rectification circuit, the PWM modulation module (6d) outputs two PWM signals ePWM1 and ePWM2, and outputs two driving voltages after passing through the driving circuit (6e)v gq1 Andv gq2 driving voltagev gq1 With respect to the synchronization signalv b The rising edge of (A) is centrosymmetric; driving voltagev gq2 With respect to the synchronization signalv b Is centrosymmetric along the falling edge of the driving voltagev gq1 And withv gq2 The phase difference is 180 degrees;
for the case that the rectification circuit (3) is a fully-controlled bridge active rectification circuit, the PWM modulation module (6d) outputs four PWM signals ePWM1, ePWM2, ePWM3 and ePWM4, and four driving voltages are output after passing through the driving circuit (6e)v gq1 、v gq2 、v gq3 Andv gq4 driving voltagev gq1 With respect to the synchronization signalv b The rising edge of (A) is centrosymmetric; driving voltagev gq2 With respect to the synchronization signalv b Is centrosymmetric along the falling edge of the driving voltagev gq1 And withv gq2 The phase difference is 180 degrees, and the phase difference is,v gq3 is composed ofv gq1 The complementary signal of (a) to (b), v gq4 is composed ofv gq2 The complementary signal of (a);
for the case that the rectifying circuit (3) is a controllable half-bridge active rectifying circuit, when the upper tube is an uncontrolled diode and the lower tube is a controllable switching tube, the PWM modulation module (6d) outputs a PWM signal ePWM2, and a driving voltage is output after passing through the driving circuit (6e)v gq2 ，v gq2 With respect to the synchronization signalv b The rising edge of (A) is centrosymmetric; when the upper and lower arms of the bridge arm are controllable switch tubes, the PWM modulation module (6d) outputs two PWM signals ePWM1 and ePWM2, and outputs two driving voltages after passing through the driving circuit (6e)v gq1 Andv gq2 driving voltagev gq2 With respect to the synchronization signalv b Has a central symmetry of the rising edge of the driving voltagev gq1 Is composed ofv gq2 The complementary signal of (1).
Furthermore, the PWM signal modulation process also comprises the step that the output sampling module collects the output voltage or the output current or the output power of the system and outputs a voltage signalv d And the PWM modulation module is provided with the PWM. The PWM modulation module is based on the output sampling module (output voltage signal)v d And controlling the duty ratio of the PWM signal ePWM.
The rectifying device for realizing the driving synchronization method is suitable for a wireless power transmission system and comprises the following steps:
the device at least comprises a non-contact transformer secondary winding, a secondary compensation network, a rectifying circuit, a filter circuit, a load and a control unit. The control unit comprises a current sampling circuit, a current-voltage conversion circuit, a signal processing circuit, a PWM (pulse-width modulation) module, a driving circuit and an output sampling module, and the rectifying circuit comprises a controllable switching tube.
Specifically, the winding current sampling circuit is used for detecting a current signal flowing through a secondary winding of the non-contact transformer, the current-voltage conversion circuit is used for converting the current signal acquired by the winding current sampling circuit into a voltage signal, and after the phase information of the voltage signal is extracted by the signal processing circuit, a square wave signal is output to the PWM modulation module. The PWM modulation module compares the system output voltage or current or power sampled by the output sampling module with a reference voltage or current or power, and adjusts the duty ratio of the output PWM signal according to the comparison result so as to enable the output voltage or current or power of the filter circuit to track the set voltage reference value or current reference value or power reference value. Meanwhile, the PWM module collects edge signals of square waves output by the signal processing circuit as synchronous signals and generates PWM signals according to the phase relation and the duty ratio of the fundamental wave component of the input voltage of the rectifying circuit and the secondary winding current of the non-contact transformer. And finally, the driving circuit converts the PWM signal output by the PWM modulation module into the driving voltage of a controllable switching tube in the rectifying circuit, and controls the controllable switching tube to realize driving synchronization and zero voltage switching-on.
Specifically, the secondary side compensation network may employ LCC compensation, including compensating inductanceL 1 Compensating capacitorC 1 And compensation capacitorC 2 In which the secondary winding of the non-contact transformer and the compensation capacitorC 1 Compensating inductanceL 1 Sequentially connected, compensating capacitorsC 2 Parallel connected to secondary winding of non-contact transformer and compensation capacitorC 1 Series branchTwo ends of the way. Compensation capacitorC 2 And compensation inductanceL 1 The following expression is satisfied:
Figure DEST_PATH_IMAGE001
whereinωIs the operating angular frequency;
the secondary compensation network can also adopt LCL compensation, including compensation inductanceL 2 And compensation capacitorC 3 In which the secondary winding of the non-contact transformer and the compensation inductorL 2 Series, compensating capacitorC 3 And the two ends of the secondary winding of the non-contact transformer are connected in parallel. Compensation capacitorC 3 And compensation inductanceL 2 The following expression is satisfied:
Figure 834648DEST_PATH_IMAGE002
whereinωIs the operating angular frequency.
The rectifying circuit can adopt a semi-controlled bridge type active rectifying circuit or a fully-controlled bridge type active rectifying circuit or a controllable semi-bridge type active rectifying circuit. In particular, the rectifier circuit may employ an uncontrolled diode and/or a controllable switching tube.
Specifically, the current sampling mode of the winding current sampling circuit may be an ac hall or a current transformer, and the signal processing circuit may include a signal amplifying circuit, a filter circuit, a phase compensation circuit, a detection circuit, a zero-crossing comparison circuit, and a correction circuit.
Compared with the prior art, the invention has the following beneficial effects:
the driving synchronization method of the controllable switch tube of the invention samples the non-contact transformer secondary winding current which is approximately sinei s Effectively avoids the input current of the sampling rectification circuit in the prior arti 2 The problems of sampling phase shift and non-unique zero-crossing signals caused by overhigh high-frequency harmonic content and serious distortion are solved, thereby avoiding the problems of inaccurate zero-crossing point detection and erroneous judgment and synchronization failure caused by a plurality of zero-crossing signals, and optimizing the drive synchronization of the controllable switch tubeThe stability of control makes the control method simpler, more accurate and convenient to design.
Meanwhile, the invention can realize zero voltage switching-on ZVS of the controllable switching tube while realizing the driving synchronization of the controllable switching tube, reduce the switching loss of the wireless power transmission system under high frequency, improve the efficiency of the converter and meet the application requirements of the wireless power transmission system on high reliability and high efficiency.
Drawings
FIG. 1 is a schematic diagram of a conventional synchronous rectification apparatus in a wireless power transmission system;
FIG. 2a is a simulated waveform diagram of a prior art synchronous rectification device operating in a multi-harmonic environment;
FIG. 2b is a waveform diagram of a driving signal of a conventional synchronous rectification device, which is actually measured and extended when the synchronous rectification device operates in a multi-harmonic environment;
FIG. 2c is a waveform diagram of the driving signal loss occurring when the conventional synchronous rectification device operates in a multi-harmonic environment;
FIG. 3 is a schematic diagram of a synchronous rectification apparatus employing an LLC compensation network and a half-controlled bridge active rectification circuit in accordance with the present invention;
FIG. 4 is a waveform diagram of input current and voltage of a rectifier circuit;
FIG. 5 is a schematic diagram illustrating the modulation principle of PWM signals in the driving synchronization method of the controllable switch tube according to the present invention;
FIG. 6 is a schematic diagram of a synchronous rectification apparatus employing an LCL compensation network and a half-controlled bridge active rectification circuit according to the present invention;
FIG. 7 is a schematic diagram of a synchronous rectification apparatus employing an LCC compensation network and a fully controlled bridge active rectification circuit according to the present invention;
FIG. 8 is a schematic diagram of a synchronous rectification apparatus of the present invention employing an LCC compensation network and a controllable half-bridge active rectification circuit;
FIG. 9 is a schematic diagram of the modulation process of the PWM signal duty ratio control in the driving synchronization method of the controllable switch tube according to the present invention;
FIG. 10 is a schematic diagram of an exemplary apparatus for verification using a bilateral LCC compensation network and a half-controlled bridge active rectifier circuit according to the present invention;
fig. 11 is a waveform diagram actually obtained in an experiment according to the first verification example of the present invention.
Detailed Description
The technical solution of the present invention will be described in detail with reference to the accompanying drawings. It should be noted that the embodiments and features of the embodiments of the present application may be arbitrarily combined with each other without conflict.
Principle analysis:
the operation mode of the rectifier circuit 3 of the present invention is described with reference to fig. 3 and 4 as an example:
in fig. 3, the rectifying device suitable for the wireless power transmission system includes a secondary winding 1 of the non-contact transformer, a secondary compensation network 2, a rectifying circuit 3, a filter circuit 4, a load 5, and a control unit 6. The secondary compensation network 2 adopts LCC compensation network, the rectification circuit 3 is a semi-controlled bridge type active rectification circuit, and the two lower tubes are controllable switching tubesQ 1 、Q 2 。
Fig. 4 is a simulated waveform of input voltage and current of the rectifier circuit 3, in which,v 2 is the input voltage of the rectifying circuit,v 2_1 Is the fundamental component of the input voltage of the rectifier circuit,i 2 Is the input current of the rectifying circuit,i 2_1 Is the fundamental component of the input current to the rectifier circuit,V bat for the voltage across the dc load 5,v gq1 、v gq2 is two controllable switch tubesQ 1 、Q 2 The driving voltage of (a) is set,v 2_1 andi 2_1 can pass through the pairv 2 Andi 2 and performing Fourier decomposition to obtain the target.
Within one waveform period, the rectifying circuit 3 has 6 working modes, which are respectively:
1) mode 1[ 2 ]t 0 Before one]: in thatt 0 Before the moment, the controllable switch tubeQ 1 、Q 2 Are all conducted, the output of the resonant cavity is short-circuited,v 2 = 0。 i 2 >0, throughQ 1 、Q 2 And (4) circulating.
2) Modal 2[ 2 ]t 0 – t 1 ]：t 0 At the moment of time, the time of day,Q 1 the power is turned off and the power is turned off,i 2 to giveQ 1 The junction capacitor of (1) is charged rapidly whenQ 1 The voltage at both ends rises toV bat Time, diodeD 1 Is conducted, willv 2 Is clamped toV bat At this timei 2 Warp beamD 1 、Q 2 The water flows through the water tank and the water tank,Q 2 operating as a synchronous rectifier. Due to the fact thatQ 1 The off-current is large during this periodQ 1 The junction capacitance charging time is very short and negligible. Within this mode of operation,i 2 first decrease, then increase, then decrease.
3) Mode 2[ 2 ]t 1 – t 2 ]：t 1 At the moment of time, the time of day,i 2 resonates to zero and then flows in reverse.i 2 For feedingQ 1 The junction capacitance of the first and second electrodes is discharged,v 2 and decreases. In thatt 2 At the moment of time, the time of day,v 2 the amplitude is reduced to zero and,Q 1 the reverse parallel diode is conducted and can be switched on at zero voltageQ 1 。
4) In thatt 3 At the moment of time, turn offQ 2 The rectifier bridge begins operation in the other half cycle, the same principle as before.
Control principle and defects of the prior art:
as shown in FIG. 1, the conventional synchronous rectification device using LLC compensation network and semi-controlled bridge active rectification circuit samples the input current of the rectification circuit through the control uniti 2 Generating a drive signal at its zero crossing to control a controllable switching tubeQ 1 、Q 2 Input current to rectifying circuiti 2 And (6) synchronizing. However, such an input current using a rectifier circuiti 2 The method for directly synchronizing the driving signals has certain defects in the LCC or LCL compensation topology, and the LCC compensation topology is taken as an example for explanation:
first, as shown in fig. 2a, 2b, 2c and 4, due to the high-order LCC topologyLow impedance characteristic under higher harmonic, input current of rectifier circuiti 2 The waveform distortion is serious, and the harmonic content is very high. Under the working condition, the influence of harmonic waves on the phase of the current zero crossing point cannot be ignored. If the band-pass filter is still used to filter out the high-frequency noise, it will inevitably affecti 2 The phase of the zero crossing point, resulting in inaccurate zero crossing point detection. Secondly, the waveform distortion also causes one switching cyclei 2 There are a number of negative to positive zero crossings, as shown in FIG. 2a, wherev gq2 Is composed ofQ 2 The synchronization signal of (2). At this moment, in order to achieve correct synchronization, the control unit is required to discriminate an effective pulse rising edge signal first, filter out a redundant signal, and then perform synchronization, so that the complexity of signal processing is greatly increased, and meanwhile, a large synchronization delay is brought, and misjudgment and synchronization failure are easily caused. Finally, if the control unit misjudges the synchronization pulse, the pulse width of the driving signal may be lost or prolonged, as shown in fig. 2b and 2 c. In the context of figure 2b of the drawings,v d2 the square wave signal is output after zero-crossing comparison. When in usev d2 When it is set highv gq1 When it should be set low, and it can be seen from fig. 2b that this is due to multiple zerosv d2 A slight falling edge makesv gq1 The high at this low time causes the drive signal to be prolonged and the current to flowi 2 Three times the normal value in one cycle; for the same reason, in FIG. 2cv gq2 The low at the instant this high is supposed to cause the loss of the drive signal. The wrong driving synchronization signal can affect the working state of the resonant unit, resulting ini 2 Wave form disorder, even brought abouti 2 The multiple of the amplitude rises, which is fatal to the system reliability.
The first embodiment is as follows:
the embodiment provides a rectifying device suitable for a wireless power transmission system, as shown in fig. 3, which includes a non-contact transformer secondary winding 1, a secondary compensation network 2, a rectifying circuit 3, a filter circuit 4, a load 5, and a control unit 6. Wherein is not connectedThe secondary winding 1, the secondary compensation network 2, the rectifying circuit 3, the filter circuit 4 and the load 5 of the thixotropic transformer are sequentially cascaded, specifically, the control unit 6 comprises a winding current sampling circuit 6a, a current-voltage conversion circuit 6b, a signal processing circuit 6c, a PWM (pulse width modulation) module 6d, a driving circuit 6e and an output sampling module 6f, the rectifying circuit 3 comprises a controllable switch tubeQ 1 、Q 2 。
The following describes a specific application scheme of the present embodiment with reference to fig. 3 as a main circuit structure and fig. 4 to 5. As shown in fig. 3, the secondary compensation network 2 adopts an LCC compensation network, a non-contact transformer secondary winding 1 and a compensation capacitorC 1 Compensating inductanceL 1 Sequentially connected, compensating capacitorsC 2 Is connected in parallel with a secondary winding 1 of the non-contact transformer and a compensation capacitorC 1 Resonant frequency of system operation at both ends of series branchωThe rectification circuit 3 is a semi-controlled bridge type active rectification circuit, and the two lower tubes are controllable switching tubesQ 1 、Q 2 Connected to a drive circuit 6e of the control unit 6, and the output end of the half-controlled bridge active rectification circuit 3 is connected to the filter circuitC o 4 to supply power to the load R5. A current sampling circuit 6a in the control unit 6 collects the current of the secondary winding through a Hall current sensori s The signal processing circuit 6c is composed of an extremely fast comparator, a digital isolator, an inverter, an analog comparator, a buffer, a monostable multivibrator and other elements, and the PWM module 6d adopts a DSP of TMS320F28335 type.
The winding current sampling circuit 6a is used for detecting the current flowing through the secondary winding of the non-contact transformeri s The current-voltage conversion circuit 6b is used for converting the current signal collected by the winding current sampling circuit 6a into a voltage signalv a Extracted in the signal processing circuit 6cv a After the phase information of (2), outputting a square wave signalv b To DSP6 d. The DSP6d compares the system output voltage sampled by the output sampling module 6f, and when the acquired output voltage is greater than the voltage threshold set in the DSP6d, the DSP6d increases the size of the duty ratio adjustable region; when the output voltage is collectedWhen the voltage is smaller than the voltage threshold set in the DSP, the DSP6d may reduce the size of the duty ratio adjustable region to control the constant voltage output, where the duty ratio adjustable region is shown in fig. 5Q 1 、Q 2 The shaded area of (d). Meanwhile, the DSP6d applies the square wave signal inputted from the signal processing circuit 6cv b As a synchronous signal and based on the secondary winding current of the contactless transformeri s And fundamental component of input voltage of rectifier circuitv 2_1 Outputs PWM signals ePWM1 and ePWM2 and outputs two paths of driving voltages after passing through a driving circuit 6ev gq1 Andv gq2 ，v gq1 with respect to the synchronization signalv b The rising edge of (a) is symmetrical at the center,v gq2 with respect to the synchronization signalv b Is centrosymmetric along the falling edge. Wherein the secondary winding currenti s Fundamental component of input current of phase advance rectification circuiti 2_1 Phase 90 degree, rectifier circuit input current fundamental componenti 2_1 And fundamental component of input voltage of rectifier circuitv 2_1 In-phase, i.e. square-wave edge signalsv b The falling edge and the rising edge of the rectifier circuit respectively correspond to the fundamental wave component of the input voltage of the rectifier circuitv 2_1 The peak value and the valley value of the peak value,v gq1 andv gq2 respectively with respect to fundamental component of input voltage of rectifying circuitv 2_1 The valley value and the peak value are symmetrical, and the phase synchronization between the driving signal and the input current of the rectifying circuit is realized.
As can be seen from FIG. 4, the capacitance C is compensated for by the parallel connection 2 Existence of a rectifying circuit input currenti 2 The distortion is serious, the high-frequency harmonic content is very high, the problems of non-uniqueness of sampling phase shift and zero-crossing signals occur, and the method is not suitable for being used as a synchronous reference of controllable rectification driving. And as shown in FIG. 5, the secondary winding current is detected in the present inventioni s In which the secondary winding current flows due to the frequency-selective action of the LC networki s The waveform is approximate to sine, so that the problem of inaccurate zero crossing point detection caused by distorted current phase deviation and the problems of misjudgment and synchronization failure caused by a plurality of zero crossing signals can be effectively avoided, the driving signal required by the controllable switching tube can be accurately and reliably generated, the method is simple and accurate, the optimization of system control is facilitated, and the application requirements of a wireless power transmission system on high reliability and high efficiency are met.
Example two:
for example, as shown in fig. 6, the invention is suitable for a rectifying device of a wireless power transmission system, the secondary compensation network 2 adopts an LCL compensation network, and the secondary winding 1 and the compensation capacitor of the non-contact transformerC 3 Connected in parallel and then connected with a compensation inductorL 2 The resonant frequency of the system operation is connected to the input end of the semi-controlled bridge rectifier circuit 3 in seriesωThe rectification circuit 3 is a semi-controlled bridge type active rectification circuit, and the two lower tubes are controllable switching tubesQ 1 、Q 2 Connected to a drive circuit 6e of the control unit 6, and the output end of the half-controlled bridge active rectification circuit 3 is connected to the filter circuitC o 4 to supply power to the load R5. A current sampling circuit 6a in the control unit 6 collects the current of the secondary winding through a Hall current sensori s The signal processing circuit 6c is composed of an extremely fast comparator, a digital isolator, an inverter, an analog comparator, a buffer, a monostable multivibrator and other elements, and the PWM module 6d adopts a DSP of TMS320F28335 type.
The winding current sampling circuit 6a is used for detecting the current flowing through the secondary winding of the non-contact transformeri s The current-voltage conversion circuit 6b is used for converting the current signal collected by the winding current sampling circuit 6a into a voltage signalv a Extracted in the signal processing circuit 6cv a After the phase information, outputting a square wave signalv b To DSP6 d. The DSP6d compares the system output voltage sampled by the output sampling module 6f, and when the acquired output voltage is greater than the voltage threshold set in the DSP6d, the DSP6d increases the size of the duty ratio adjustable region; when the collected output voltage is less than the voltage threshold set in the DSPWhen the value is positive, the DSP6d reduces the size of the duty ratio adjustable region to control the constant voltage output, the duty ratio adjustable region is shown in FIG. 5Q 1 、Q 2 The shaded area of (d). Then, the DSP6d applies the square wave signal inputted from the signal processing circuit 6cv b As a synchronous signal and based on the secondary winding current of the contactless transformeri s Fundamental component of input voltage of rectifier circuitv 2_1 Outputs PWM signals ePWM1 and ePWM2 and outputs two paths of driving voltages after passing through a driving circuit 6ev gq1 Andv gq2 ，v gq1 with respect to the synchronization signalv b The rising edge of (a) is symmetrical at the center,v gq2 with respect to the synchronization signalv b Is centrosymmetric. Wherein the secondary winding currenti s Fundamental component of input current of phase advance rectification circuiti 2_1 Phase 90 degree, fundamental component of input current of rectifying circuiti 2_1 Fundamental component of input voltage of rectifier circuitv 2_1 In-phase, i.e. square-wave edge signalsv b The falling edge and the rising edge of the first half-bridge respectively correspond to the fundamental wave component of the input voltage of the rectifier circuitv 2_1 The peak value and the valley value of the peak value,v gq1 andv gq2 respectively with respect to fundamental component of input voltage of the rectifier circuitv 2_1 The valley value and the peak value are symmetrical, and the phase synchronization between the driving signal and the input current of the rectifying circuit is realized.
Example three:
for example, as shown in fig. 7, the invention is suitable for a rectifying device of a wireless power transmission system, the secondary compensation network 2 adopts an LCC compensation network, and the secondary winding 1 of a non-contact transformer and a compensation capacitorC 1 Compensating inductanceL 1 Sequentially connected, compensating capacitorsC 2 Is connected in parallel with the secondary winding 1 of the non-contact transformer and the compensation capacitorC 1 Resonant frequency of system operation at both ends of series branchωSatisfy that the rectification circuit 3 is a full-control bridge type active rectifierThe two lower tubes of the flow circuit are controllable switch tubesQ 1 、Q 2 Two upper tubes are controllable switch tubesQ 3 、Q 4 Connected with a drive circuit 6e of the control unit 6, the output end of the full-control bridge type active rectification circuit 3 and the filter circuitC o 4 to supply power to the load R5. A current sampling circuit 6a in the control unit 6 collects the current of the secondary winding through a Hall current sensori s The signal processing circuit 6c is composed of an extremely fast comparator, a digital isolator, an inverter, an analog comparator, a buffer, a monostable multivibrator and other elements, and the PWM module 6d adopts a DSP of TMS320F28335 type.
The winding current sampling circuit 6a is used for detecting the current flowing through the secondary winding of the non-contact transformeri s The current-voltage conversion circuit 6b is used for converting the current signal collected by the winding current sampling circuit 6a into a voltage signalv a Extracted in the signal processing circuit 6cv a After the phase information, outputting a square wave signalv b To the PWM modulation block 6 d. The PWM module 6d compares the system output voltage sampled by the output sampling module 6f, and when the acquired output voltage is greater than a voltage threshold value set in the PWM module 6d, the PWM module 6d increases the size of a duty ratio adjustable area; when the collected output voltage is smaller than the voltage threshold set in the DSP, the PWM modulation module 6d may reduce the size of the duty ratio adjustable region to control the constant voltage output, the duty ratio adjustable region being the controllable switching tube in fig. 5Q 1 、Q 2 The shaded area of (d). Then, the PWM modulation module 6d modulates the square wave signal inputted from the signal processing circuit 6cv b As a synchronous signal and based on the secondary winding current of the contactless transformeri s Fundamental component of input voltage to the rectifying circuit 3v 2_1 The output PWM signals ePWM1, ePWM2, ePWM3 and ePWM4 output four driving voltages after passing through the driving circuit 6ev gq1 、v gq2 、v gq3 Andv gq4 ，v gq1 with respect to the synchronization signalv b The rising edge of (2) is centrosymmetric;v gq2 with respect to the synchronization signalv b The falling edge of (a) is symmetrical at the center,v gq1 andv gq2 the phase difference is 180 degrees, and the phase difference is,v gq3 is composed ofv gq1 The complementary signal of (a) to (b),v gq4 is composed ofv gq2 The complementary signal of (1). Wherein the secondary winding currenti s Fundamental component of input current of phase lead rectifying circuiti 2_1 Phase 90 degree, rectifier circuit input current fundamental componenti 2_1 Fundamental component of input voltage of rectifier circuitv 2_1 In-phase, i.e. square-wave edge signalsv b The falling edge and the rising edge of the rectifier circuit respectively correspond to the fundamental wave component of the input voltage of the rectifier circuitv 2_1 The peak and valley of (i.e. thev gq1 With respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The valley value of the light-emitting diode is symmetrical,v gq2 with respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The peak value of the driving signal and the input current of the rectifying circuit are symmetrical, so that the driving signal and the input current of the rectifying circuit are realizedi 2 Phase synchronization between them.
Example four:
in this embodiment, as shown in fig. 8, in the rectifying device of the wireless power transmission system, the secondary compensation network 2 adopts an LCC compensation network, and the secondary winding 1 of the non-contact transformer and the compensation capacitorC 1 Compensating inductanceL 1 Sequentially connected, compensating capacitorsC 2 Is connected in parallel with the secondary winding 1 of the non-contact transformer and the compensation capacitorC 1 Resonant frequency of system operation at both ends of series branchωThe rectifier circuit 3 is a controllable half-bridge active rectifier circuit, and the upper and lower bridge arms are controllable switching tubesQ 1 、Q 2 Connected to a drive circuit 6e of the control unit 6, the output of the controllable half-bridge active rectifier circuit 3 and the filter circuitC o 4 to supply power to the load R5. Control unitThe current sampling circuit 6a in 6 collects the current of the secondary winding through a Hall current sensori s The signal processing circuit 6c is composed of an extremely fast comparator, a digital isolator, an inverter, an analog comparator, a buffer, a monostable multivibrator and other elements, and the PWM module 6d adopts a DSP of TMS320F28335 type.
The winding current sampling circuit 6a is used for detecting the current flowing through the secondary winding of the non-contact transformeri s The current-voltage conversion circuit 6b is used for converting the current signal collected by the winding current sampling circuit 6a into a voltage signalv a Extracted in the signal processing circuit 6cv a After the phase information of (2), outputting a square wave signalv b To the PWM modulation block 6 d. The PWM module 6d compares the system output voltage sampled by the output sampling module 6f, and when the acquired output voltage is greater than a voltage threshold value set in the PWM module 6d, the PWM module 6d increases the size of a duty ratio adjustable area; when the collected output voltage is smaller than the voltage threshold set in the DSP, the PWM modulation module 6d may reduce the size of the duty ratio adjustable region to control the constant voltage output, where the duty ratio adjustable region is shown in fig. 5Q 1 、Q 2 The shaded area of (d). Then, the PWM modulation module 6d modulates the square wave signal inputted from the signal processing circuit 6cv b As a synchronous signal and based on the secondary winding current of the contactless transformeri s Fundamental component of input voltage of rectifier circuitv 2_1 Outputs PWM signals ePWM1 and ePWM2 and outputs two paths of driving voltages after passing through a driving circuit 6ev gq1 Andv gq2 ，v gq2 with respect to the synchronization signalv b The rising edge of (a) is symmetrical at the center,v gq1 is composed ofv gq2 The complementary signal of (1). Wherein the secondary winding currenti s Fundamental component of input current of phase advance rectification circuiti 2_1 Phase 90 degree, rectifier circuit input current fundamental componenti 2_1 Fundamental component of input voltage of rectifier circuitv 2_1 In-phase, i.e. square-wave edge signalsv b The falling edge and the rising edge of the rectifier circuit respectively correspond to the fundamental wave component of the input voltage of the rectifier circuitv 2_1 The peak value and the valley value of the peak value, v gq2 with respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The valley value of (A) is symmetrical;v gq1 is composed ofv gq2 Of complementary signals, i.e.v gq1 With respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The peak value of the driving signal and the input current of the rectifying circuit are symmetrical, so that the driving signal and the input current of the rectifying circuit are realizedi 2 Phase synchronization between them.
Example five:
the embodiment provides a driving synchronization method for a controllable switching tube of a rectifying device suitable for a wireless power transmission system, which mainly comprises the following operations:
step 1: detecting current flowing through secondary winding of non-contact transformeri s And generates a voltage signal in phase with the current-voltage conversion circuit 6bv a ；
Step 2: through the signal processing circuit 6cv a Is converted intoi s Square wave signal of same phasev b And will bev b As the synchronous signal input of the PWM modulation module 6 d;
and step 3: according to the square wave signal by the PWM module 6dv b Fundamental component of input voltage of rectifier circuitv 2_1 Generates the PWM signal ePWM based on the phase relationship of the output sampling module 6fv d Controlling the duty ratio of the PWM signal ePWM to regulate and control the required output parameters;
and 4, step 4: the ePWM is output to a driving circuit 6e to provide a driving voltage required by a controllable switch tube in the rectifying circuit 3v gq And meanwhile, zero voltage switching-on of the controllable switching tube is realized.
Wherein the signal processing circuit 6c is to be connected tov a Is converted intoi s In-phase squareWave signalv b The process of (2) is as follows:
when the voltage signalv a When the output voltage is larger than zero, a square wave signal is outputv b (ii) a When voltage signalv a When the output signal is less than zero, the output signal is stoppedv b 。
Wherein, the PWM module 6d is based on square wave signalv b Fundamental component of input voltage of rectifier circuitv 2_1 The modulation principle for generating a PWM signal is as follows:
first, when the secondary compensation topology is the LCC compensation network as shown in FIG. 3, the compensation capacitorC 2 And compensation inductanceL 1 The following expression should be satisfied:
Figure DEST_PATH_IMAGE003
whereinωIs the operating angular frequency;
when the secondary side compensation topology is the LCL compensation network as shown in FIG. 6, the compensation capacitorC 3 And compensation inductanceL 2 The following expression should be satisfied:
Figure 817647DEST_PATH_IMAGE004
whereinωIs the operating angular frequency.
When the secondary side compensation topology is LCC or LCL compensation network and the working angular frequency satisfies the above expression, the secondary side winding current is as shown in FIG. 5i s Fundamental component of input current of phase advance rectification circuiti 2_1 Phase 90 degree, fundamental component of input current of rectifying circuiti 2_1 Fundamental component of input voltage of rectifier circuitv 2_1 In-phase, i.e. secondary winding currenti s Fundamental component of input voltage of phase-lead rectifying circuitv 2_1 Phase 90 degrees, i.e. square-wave edge signalsv b The falling edge and the rising edge of the rectifier circuit correspond to the peak value and the valley value of the fundamental wave component of the input voltage of the rectifier circuit respectively.
For the case that the rectification circuit 3 is a half-controlled bridge active rectification circuit, the PWM modulation module 6d outputs two PWM signals ePWM1 and ePWM2, and outputs two driving voltages after passing through the driving circuit 6ev gq1 And withv gq2 ，v gq1 With respect to the synchronization signalv b The rising edge of (a) is symmetrical at the center,v gq2 with respect to the synchronization signalv b Is centrosymmetric along the falling edge. Namely, it isv gq1 Andv gq2 respectively with respect to fundamental component of input voltage of the rectifier circuitv 2_1 The valley value and the peak value of the driving signal are symmetrical, so that the driving signal and the input current of the rectifying circuit are realizedi 2 Phase synchronization between them.
For the case that the rectification circuit (3) is a fully-controlled bridge type active rectification circuit, the PWM modulation module (6d) outputs PWM signals ePWM1, ePWM2, ePWM3 and ePWM4 and outputs four driving voltages after passing through the driving circuit (6e)v gq1 、v gq2 、v gq3 Andv gq4 ，v gq1 with respect to the synchronization signalv b The rising edge of (A) is centrosymmetric;v gq2 with respect to the synchronization signalv b The falling edge of (a) is symmetrical along the center,v gq1 andv gq2 the phase difference is 180 degrees, and the phase difference is,v gq3 is composed ofv gq1 The complementary signal of (a) to (b), v gq4 is composed ofv gq2 The complementary signal of (a); namely thatv gq1 With respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The valley value of the light-emitting diode is symmetrical,v gq2 with respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The peak value of the driving signal and the input current of the rectifying circuit are symmetrical, so that the driving signal and the input current of the rectifying circuit are realizedi 2 Phase synchronization between them.
For the case that the rectification circuit (3) is a controllable half-bridge active rectification circuit, when the upper tube is an uncontrolled diode and the lower tube is a controllable tube, the PWM adjustsThe system module (6d) outputs a PWM signal ePWM2, and outputs a driving voltage after passing through the driving circuit (6e)v gq2 ，v gq2 With respect to the synchronization signalv b The rising edge of (A) is centrosymmetric; when the upper and lower arms of the bridge arm are controllable, the PWM modulation module (6d) outputs two PWM signals ePWM1 and ePWM2, and outputs two driving voltages after passing through the driving circuit (6e)v gq1 And withv gq2 ，v gq2 With respect to the synchronization signalv b The rising edge of (a) is symmetrical at the center,v gq1 is composed ofv gq2 The complementary signal of (1). Namely, it isv gq2 With respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The valley value of the steel is symmetrical; v gq1 with respect to the fundamental component of the input voltage of the rectifier circuitv 2_1 The peak value of the driving signal and the input current of the rectifying circuit are symmetrical, so that the driving signal and the input current of the rectifying circuit are realizedi 2 Phase synchronization between them.
It can be seen from the above description of the principles that the technical solution of the present invention skillfully applies the current in the compensation networki s And current (D)i 2 By detecting the phase relationship betweeni s Implementation and detectioni 2 The same effect, and no current need to be consideredi 2 The problem of higher harmonic waves in the wireless power transmission system greatly simplifies the complexity of the existing synchronous rectification control method in the wireless power transmission system, and improves the stability of the system.
The modulation process of PWM signal duty cycle control is explained with reference to fig. 5 and 9:
the modulation process of the ePWM2 is described by taking the rectifying circuit 3 as a semi-controlled bridge active rectifier, the PWM module 6d adopts an up-counting mode, and the PWM module 6d samples the system output voltage as an example.
As can be seen from fig. 5 and 9, after the device starts to operate, the base count register TBCT is loaded to the set initial value and starts to count up, and when the counter value does not reach the comparison register set value CMP2A, the TBCT starts to count upR continues counting up, when the counter value reaches a comparison register set value CMP2A, a PWM signal ePWM2 is set high, then TBCTR continues counting up, when the counter value does not reach a comparison register set value CMP2B, the TBCTR continues counting up, when the counter value reaches a comparison register set value CMP2B, a PWM signal ePWM2 is set low, and ePWM2 correspondingly generates a controllable switch tubeQ 2 Driving synchronous voltage ofv gq2 . The TBCTR continues to count up until the TBCTR count reaches a set threshold, and when the TBCTR count reaches the set threshold, the time base counter register TBCTR is forcibly loaded to a set initial value and starts to count up, and the above counting operation is repeated. In any of the above processes, if the PWM modulation module 6d receives the external synchronization signalv b The time base counter register TBCTR is forced to load to a set initial value and starts counting up, and the above counting operation is repeated.
The PWM signal modulation process also comprises the following parallel operations:
firstly, judging whether the output voltage acquired by the output sampling module 6f is greater than a voltage threshold set in the PWM modulation module 6d, if the output voltage is greater than the voltage threshold set in the PWM modulation module 6d, the PWM modulation module 6d increases the size of the duty ratio adjustable region, that is, the value of CMP2A is reduced and the value of CMP2B is increased; otherwise, whether the output voltage acquired by the output sampling module 6f is smaller than the voltage threshold set in the PWM modulation module 6d is judged, and if the acquired output voltage is smaller than the voltage threshold set in the PWM modulation module 6d, the PWM modulation module 6d decreases the size of the duty ratio adjustable region, that is, increases the value of CMP2A and decreases the value of CMP 2B; if the collected output voltage is not less than the voltage threshold set in the PWM modulation module 6d, that is, the output voltage is equal to the voltage threshold set in the PWM modulation module 6d, the output sampling module 6f continues to sample the output voltage at the load end without any change with respect to CMP2A or CMP 2B.
In the above control process, the variation amounts of CMP2A and CMP2B start to gradually increase or decrease by taking the unit count value 1 as a step, and the duty ratio adjustable region is shown in fig. 5Q 2 Has a minimum value of 0.5 and a maximum value according to the factThe actual demand does not exceed 1. The ePWM1 signal and other PWM signal generation processes in the form of rectification circuit can be seen in the implementation process.
It should be noted that, since the method of this embodiment may be implemented by a circuit according to the first embodiment, other implementation processes of the method of this embodiment may refer to corresponding contents of the first embodiment, and are not described herein again.
It can be seen from the above embodiments that, in the technical solution of the present application, the secondary winding current is sampled to approximate sinei s Effectively avoiding the input current due to the rectifying circuiti 2 The problems of sampling phase shift and non-unique zero-crossing signals caused by overhigh high-frequency harmonic content and serious distortion are solved, the problems of inaccurate zero-crossing point detection and misjudgment and synchronization failure caused by a plurality of zero-crossing signals are solved, the stability of the driving synchronization control of the controllable switching tube is optimized, and the control method is simpler, more accurate and more convenient to design. Moreover, the technical scheme of the application can also realize ZVS of the controllable switching tube, improve conversion efficiency and meet the application requirements of high reliability and high efficiency of the wireless power transmission system.
Verification example one:
as shown in FIG. 10, in the rectifier device suitable for the wireless power transmission system of the present invention, the LCC compensation network is used as the primary compensation network, and the primary winding and the compensation capacitor of the non-contact transformerC p1 Compensating inductanceL p1 Sequentially connected, compensating capacitorsC p2 Parallel connection between primary winding of non-contact transformer and compensation capacitorC p1 The secondary compensation network at two ends of the series branch adopts LCC compensation network, non-contact transformer secondary winding and compensation capacitorC 1 Compensating inductanceL 1 Sequentially connected, compensating capacitorsC 2 Parallel connected to secondary winding of non-contact transformer and compensation capacitorC 1 Two ends of the series branch circuit are respectively provided with a half-controlled bridge type active rectifying circuit and two lower tubes which are controllable switching tubesQ 1 、Q 2 Output end of semi-controlled bridge type active rectification circuit and filter circuitC o Is connected withThe load R supplies power and the control unit is as described for the example control unit. And testing by adopting the driving synchronization method of the controllable switching tube in the fifth embodiment.
Wherein the transformer parameter isL p = 46.69μH，L s = 36.37 muH, coupling coefficient of 0.146 and compensation network parameters ofL p1 = 18.1μH,C p1 = 122.2nF, C p2 = 194.1nF, L 1 = 17.2μH, C 1 = 180.8nF, C 2 = 204.2nF, primary side inverter tubeS 1 、S 2 、S 3 、S 4 Model number of C2M0025120D, rectifier diodeD 1 、D 2 Model number of C3D30065D, controllable switch tubeQ 1 、Q 2 Model number of SCH2080 KE.
FIG. 11 shows experimental waveforms of this example, the resonant frequency of the system operation is 85kHz, and the input voltagev in =275V, output voltagev bat =410V, load R =103 Ω,v 1 and withi 1 The primary side inverter bridge outputs voltage and current,v 2 andi 2 the input voltage and the input current of the secondary side rectifier bridge are obtained. When the controllable switch tubeQ 1 、Q 2 When the switch-on is carried out at the same time, the rectifier bridge is short-circuited,v 2 = 0V; when the controllable switch tubeQ 1 Switching-on, controllable switch tubeQ 2 When the power is turned off, the power is turned on,v 2 is negative pressure; when controllable switch tubeQ 2 Switching-on, controllable switch tubeQ 1 When the power is turned off, the power is turned on,v 2 is a positive pressure, and is,v 2 the rising edge and the falling edge of the waveform correspond to the turn-off and turn-on processes of the two switching tubes. According tov 2 The falling edge of the waveform andi 2 phase relationship between, i.e. switching tube on-process andi 2 the synchronization of the zero crossing process shows that the technical scheme of the invention can realize the drive synchronization control of the controllable switching tube, and the problem of drive signal and current waveform disorder caused by a plurality of signal zero crossing points does not occur.
While passing through FIG. 11v 2 The falling edge of the waveform can also be seen inv 2 During the transition from positive to zero voltage, the currenti 2 Resonant negative, currenti 2 Switch tubeQ 1 The junction capacitance of (a) is discharged,v 2 the voltage at the two ends is smoothly reduced to a zero voltage state, and the cliff-broken voltage sudden change does not occur, so that the voltage at the two ends can be seen inv 2 The switch tube is not switched on before the voltage at two ends is reduced to zeroQ 1 . When in usev 2 After the voltage at both ends is reduced to zero, the currenti 2 Through a switch tubeQ 1 After that, the switching tube is switched onQ 1 Namely, zero voltage turn-on is realized. In the same way, the switch tubeQ 2 Zero voltage turn-on is also achieved.
The experimental verification proves that the technical scheme of the invention can accurately and reliably generate the driving signal required by the controllable switching tube, the method is simple and accurate, the optimization of system control is facilitated, and the application requirements of a wireless electric energy transmission system on high reliability and high efficiency are met.
It will be understood by those skilled in the art that all or part of the steps of the above methods may be implemented by a program instructing relevant hardware, and the program may be stored in a computer-readable storage medium, such as a read-only memory, a magnetic or optical disk, and the like. Alternatively, all or part of the steps of the above embodiments may be implemented by using one or more integrated circuits. Accordingly, each module/unit in the above embodiments may be implemented in the form of hardware, and may also be implemented in the form of a software functional module. The present application is not limited to any specific form of hardware or software combination.
The above description is only a preferred example of the present invention, and is not intended to limit the scope of the present invention. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the protection scope of the present invention.

Claims (9)

1.无线电能传输系统中整流电路可控开关管的驱动同步方法，该无线电能传输系统的整流装置包括：非接触变压器副边绕组(1)、副边补偿网络(2)、整流电路(3)、滤波电路(4)、负载(5)和控制单元(6) ，其特征在于，所述控制单元(6)包括绕组电流采样电路(6a)、流压转换电路(6b)、信号处理电路(6c)、PWM调制模块(6d)及驱动电路(6e)，所述副边补偿网络(2)采用LCC补偿网络或LCL补偿网络，该方法包括以下步骤：1. A method for driving and synchronizing a controllable switch tube of a rectifier circuit in a wireless power transmission system, the rectifier device of the wireless power transmission system comprising: a non-contact transformer secondary winding (1), a secondary compensation network (2), a rectifier circuit (3) ), a filter circuit (4), a load (5) and a control unit (6), characterized in that the control unit (6) includes a winding current sampling circuit (6a), a current-voltage conversion circuit (6b), and a signal processing circuit (6c), a PWM modulation module (6d) and a drive circuit (6e), the secondary side compensation network (2) adopts an LCC compensation network or an LCL compensation network, and the method includes the following steps: 步骤1：检测非接触变压器的副边绕组电流i s ，并经流压转换电路(6b)生成与其同相的电压信号v a ；Step 1: Detect the secondary winding current is of the non-contact transformer, and generate a voltage signal va in phase with the current through the current-voltage conversion circuit (6b ) ; 步骤2：通过信号处理电路(6c)将电压信号v a 转换为与副边绕组电流i s 同相的方波信号v b ，并将方波信号v b 作为PWM调制模块(6d)的同步信号输入；Step 2: Convert the voltage signal va into a square wave signal vb in phase with the secondary winding current is through the signal processing circuit ( 6c ) , and input the square wave signal vb as the synchronization signal of the PWM modulation module ( 6d) ; 步骤3：PWM调制模块(6d)根据方波信号v b 与整流电路输入电压基波分量v 2_1的相位关系产生PWM信号ePWM；Step 3: the PWM modulation module (6d) generates the PWM signal ePWM according to the phase relationship between the square wave signal v b and the fundamental wave component v 2_1 of the input voltage of the rectifier circuit; 步骤4：驱动电路(6e)接收PWM信号ePWM，并输出整流电路(3)中可控开关管所需的驱动电压，实现可控开关管的驱动同步及零电压开通。Step 4: The drive circuit (6e) receives the PWM signal ePWM, and outputs the drive voltage required by the controllable switch in the rectifier circuit (3), so as to realize the drive synchronization and zero-voltage turn-on of the controllable switch. 2.根据权利要求1所述的无线电能传输系统中整流电路可控开关管的驱动同步方法，其特征在于：步骤3中，PWM信号调制过程如下：2. the drive synchronization method of rectifier circuit controllable switch tube in the wireless power transmission system according to claim 1, is characterized in that: in step 3, PWM signal modulation process is as follows: 对于整流电路(3)为半控桥式有源整流情况，PWM调制模块(6d) 输出两路PWM信号ePWM1和ePWM2，经驱动电路(6e)后输出两路驱动电压v gq1与v gq2，驱动电压v gq1的正向脉冲关于同步信号v b 的上升边沿中心对称；驱动电压v gq2的正向脉冲关于同步信号v b 的下降边沿中心对称，驱动电压v gq1与v gq2相差180度相位；In the case where the rectifier circuit (3) is a half-controlled bridge type active rectifier, the PWM modulation module (6d) outputs two PWM signals ePWM1 and ePWM2, and outputs two drive voltages v gq 1 and v gq 2 after the driving circuit (6e). , the forward pulse of the driving voltage v gq 1 is symmetric about the center of the rising edge of the synchronizing signal v b ; the forward pulse of the driving voltage v gq 2 is symmetric about the center of the falling edge of the synchronizing signal v b , the driving voltages v gq 1 and v gq 2 180 degrees out of phase; 对于整流电路(3)为全控桥式有源整流情况，PWM调制模块(6d) 输出四路PWM信号ePWM1、ePWM2、ePWM3及ePWM4，经驱动电路(6e)后输出四路驱动电压v gq1、v gq2、v gq3及v gq4，驱动电压v gq1的正向脉冲关于同步信号v b 的上升边沿中心对称；驱动电压v gq2的正向脉冲关于同步信号v b 的下降边沿中心对称，驱动电压v gq1与v gq2相差180度相位，驱动电压v gq3为v gq1的互补信号，驱动电压v gq4为v gq2的互补信号；In the case where the rectifier circuit (3) is a fully-controlled bridge type active rectifier, the PWM modulation module (6d) outputs four PWM signals ePWM1, ePWM2, ePWM3 and ePWM4, and outputs four driving voltages v gq 1 after the driving circuit (6e). , v gq 2 , v gq 3 and v gq 4 , the positive pulse of the driving voltage v gq 1 is centrally symmetric with respect to the rising edge of the synchronizing signal v b ; the positive pulse of the driving voltage v gq 2 is symmetric with respect to the falling edge of the synchronizing signal v b The center is symmetrical, the driving voltage v gq 1 and v gq 2 are 180 degrees out of phase, the driving voltage v gq 3 is the complementary signal of v gq 1 , and the driving voltage v gq 4 is the complementary signal of v gq 2 ; 对于整流电路(3)为可控半桥有源整流情况，当上管为不控二极管下管为可控开关管时，PWM调制模块(6d)输出一路PWM信号ePWM2，经驱动电路(6e)后输出驱动电压v gq2，驱动电压v gq2的正向脉冲关于同步信号v b 的上升边沿中心对称；当桥臂上、下管均为可控开关管时，PWM调制模块(6d) 输出两路PWM信号ePWM1和ePWM2，经驱动电路(6e)后输出两路驱动电压v gq1与v gq2，驱动电压v gq2的正向脉冲关于同步信号v b 的上升边沿中心对称，驱动电压v gq1为v gq2的互补信号。For the case where the rectifier circuit (3) is a controllable half-bridge active rectifier, when the upper tube is an uncontrolled diode and the lower tube is a controllable switch tube, the PWM modulation module (6d) outputs a PWM signal ePWM2, which is passed through the driving circuit (6e) After outputting the driving voltage v gq 2 , the positive pulse of the driving voltage v gq 2 is centrally symmetric with respect to the rising edge of the synchronization signal v b ; when the upper and lower tubes of the bridge arm are both controllable switches, the PWM modulation module (6d) outputs The two PWM signals ePWM1 and ePWM2 output two driving voltages v gq 1 and v gq 2 after passing through the driving circuit (6e) . v gq 1 is the complementary signal of v gq 2 . 3.根据权利要求2所述的无线电能传输系统中整流电路可控开关管的驱动同步方法，其特征在于：所述副边补偿网络(2)采用LCC补偿网络，包括补偿电感L 1、补偿电容C 1与补偿电容C 2，其中所述非接触变压器副边绕组(1)与补偿电容C 1、补偿电感L 1依次连接，补偿电容C 2并联在非接触变压器副边绕组(1)与补偿电容C 1串联支路的两端，补偿电容C 2与补偿电感L 1满足如下表达式：3. The drive synchronization method for the controllable switch tube of the rectifier circuit in the wireless power transmission system according to claim 2, wherein the secondary side compensation network (2) adopts an LCC compensation network, comprising a compensation inductance L 1 , a compensation Capacitor C 1 and compensation capacitor C 2 , wherein the non-contact transformer secondary winding (1) is connected to the compensation capacitor C 1 and the compensation inductance L 1 in sequence, and the compensation capacitor C 2 is connected in parallel with the non-contact transformer secondary winding ( 1 ) and the compensation inductance L 1 . The two ends of the series branch of the compensation capacitor C 1 , the compensation capacitor C 2 and the compensation inductance L 1 satisfy the following expression:
Figure 520489DEST_PATH_IMAGE001
，其中ω为工作角频率；
Figure 520489DEST_PATH_IMAGE001
, where ω is the working angular frequency; 或者，所述副边补偿网络(2)采用LCL补偿网络，包括补偿电感L 2与补偿电容C 3，其中所述非接触变压器副边绕组(1)与补偿电感L 2串联，补偿电容C 3并联在所述非接触变压器副边绕组(1)两端，补偿电容C 3与补偿电感L 2满足如下表达式：Alternatively, the secondary side compensation network (2) adopts an LCL compensation network, including a compensation inductance L 2 and a compensation capacitor C 3 , wherein the non-contact transformer secondary winding (1) is connected in series with the compensation inductance L 2 , and the compensation capacitor C 3 Connected in parallel at both ends of the secondary winding (1) of the non-contact transformer, the compensation capacitor C 3 and the compensation inductance L 2 satisfy the following expressions:
Figure 69282DEST_PATH_IMAGE002
，其中ω为工作角频率。
Figure 69282DEST_PATH_IMAGE002
, where ω is the working angular frequency. 4.根据权利要求1所述的无线电能传输系统中整流电路可控开关管的驱动同步方法，其特征在于：步骤3中PWM信号调制过程，还包括由输出采样模块(6f)采集系统输出电压或输出电流或输出功率，并输出电压信号v d 给所述PWM调制模块(6d)；所述PWM调制模块(6d)根据方波信号v b 和电压信号v d 控制PWM信号ePWM的相位和占空比大小。4. the drive synchronization method of the controllable switch tube of the rectifier circuit in the wireless power transmission system according to claim 1, is characterized in that: in step 3, the PWM signal modulation process, also comprises collecting the system output voltage by the output sampling module (6f) Or output current or output power, and output voltage signal vd to described PWM modulation module ( 6d ); Described PWM modulation module ( 6d ) controls the phase and occupation of PWM signal ePWM according to square wave signal vb and voltage signal vd . Empty ratio size. 5.一种适用于无线电能传输系统的整流装置，用于实现1-4之一所述无线电能传输系统中整流电路可控开关管的驱动同步方法，至少包括非接触变压器副边绕组(1)、副边补偿网络(2)、整流电路(3)、滤波电路(4)、负载(5)和控制单元(6)，所述非接触变压器副边绕组(1)、副边补偿网络(2)、整流电路(3)、滤波电路(4)与负载(5)依次连接，所述整流电路(3)包括可控开关管，其特征在于：所述控制单元(6)包括绕组电流采样电路(6a)、流压转换电路(6b)、信号处理电路(6c)、PWM调制模块(6d)及驱动电路(6e)，其中：5. A rectifier device suitable for a wireless power transmission system, for realizing a drive synchronization method for a controllable switch tube of a rectifier circuit in the wireless power transmission system described in one of 1-4, comprising at least a non-contact transformer secondary winding (1 ), secondary side compensation network (2), rectifier circuit (3), filter circuit (4), load (5) and control unit (6), the non-contact transformer secondary side winding (1), secondary side compensation network ( 2), the rectifier circuit (3), the filter circuit (4) and the load (5) are connected in sequence, the rectifier circuit (3) includes a controllable switch tube, and it is characterized in that: the control unit (6) includes a winding current sampling A circuit (6a), a current-voltage conversion circuit (6b), a signal processing circuit (6c), a PWM modulation module (6d) and a drive circuit (6e), wherein: 所述绕组电流采样电路(6a)用于检测流过所述非接触变压器副边绕组的电流信号；The winding current sampling circuit (6a) is used to detect the current signal flowing through the secondary winding of the non-contact transformer; 所述流压转换电路(6b)用于将检测的非接触变压器副边绕组电流信号转换为电压信号；The current-voltage conversion circuit (6b) is used to convert the detected current signal of the secondary winding of the non-contact transformer into a voltage signal; 所述信号处理电路(6c)用于提取所述电压信号的相位信息，并输出方波信号给PWM调制模块(6d)；The signal processing circuit (6c) is used to extract the phase information of the voltage signal, and output a square wave signal to the PWM modulation module (6d); 所述PWM调制模块(6d)采集所述方波信号的边沿信号作为同步信号，并根据非接触变压器副边绕组电流信号与所述整流电路(3)输入电压基波分量的相位关系以及占空比大小，产生PWM信号；The PWM modulation module (6d) collects the edge signal of the square wave signal as a synchronization signal, and according to the phase relationship between the current signal of the secondary winding of the non-contact transformer and the fundamental wave component of the input voltage of the rectifier circuit (3) and the duty cycle than the size, generate a PWM signal; 所述驱动电路(6e)用于将所述PWM信号转换为整流电路(3)中可控开关管的驱动电压，控制可控开关管实现驱动同步及零电压开通。The driving circuit (6e) is used for converting the PWM signal into a driving voltage of the controllable switch tube in the rectifier circuit (3), and controlling the controllable switch tube to realize driving synchronization and zero-voltage turn-on. 6.根据权利要求5所述适用于无线电能传输系统的整流装置，其特征在于：所述控制单元(6)还包括输出采样模块(6f)，用于采集系统输出电压或输出电流或输出功率，并输出给所述PWM调制模块(6d)，控制PWM信号的相位关系和占空比大小。6. The rectifier device suitable for a wireless power transmission system according to claim 5, wherein the control unit (6) further comprises an output sampling module (6f) for collecting system output voltage or output current or output power , and output to the PWM modulation module (6d) to control the phase relationship and duty ratio of the PWM signal. 7.根据权利要求6所述适用于无线电能传输系统的整流装置，其特征在于：所述整流电路(3)为半控桥式有源整流电路或全控桥式有源整流电路或可控半桥有源整流电路；7. The rectifier device suitable for a wireless power transmission system according to claim 6, wherein the rectifier circuit (3) is a half-controlled bridge type active rectifier circuit or a fully controlled bridge type active rectifier circuit or a controllable bridge type active rectifier circuit. Half-bridge active rectifier circuit; 对于整流电路(3)为半控桥式有源整流情况，整流电路包括第一桥臂与第二桥臂，其中第一桥臂与第二桥臂的两个下管均为可控开关管，第一桥臂与第二桥臂的两个上管均为不控二极管；For the case where the rectifier circuit (3) is a half-controlled bridge type active rectifier, the rectifier circuit includes a first bridge arm and a second bridge arm, wherein the two lower tubes of the first bridge arm and the second bridge arm are controllable switch tubes , the two upper tubes of the first bridge arm and the second bridge arm are both uncontrolled diodes; 对于整流电路(3)为全控桥式有源整流情况，整流电路包括第一桥臂与第二桥臂，其中第一桥臂与第二桥臂的两个下管及两个上管均为可控开关管；In the case where the rectifier circuit (3) is a fully-controlled bridge type active rectifier, the rectifier circuit includes a first bridge arm and a second bridge arm, wherein the two lower tubes and the two upper tubes of the first bridge arm and the second bridge arm are both is a controllable switch tube; 对于整流电路(3)为可控半桥有源整流情况，整流电路的下管为可控开关管，上管为不控二极管或可控开关管。In the case where the rectifier circuit (3) is a controllable half-bridge active rectifier, the lower tube of the rectifier circuit is a controllable switch tube, and the upper tube is an uncontrolled diode or a controllable switch tube. 8.根据权利要求7所述适用于无线电能传输系统的整流装置，其特征在于：所述绕组电流采样电路(6a)的电流采样方式为交流霍尔或电流互感器。8. The rectifier device suitable for a wireless power transmission system according to claim 7, characterized in that: the current sampling method of the winding current sampling circuit (6a) is an AC Hall or a current transformer. 9.根据权利要求7所述的装置，其特征在于：所述信号处理电路(6c)包括信号放大电路、滤波电路、相位补偿电路、检波电路、过零比较电路及校正电路。9. The device according to claim 7, wherein the signal processing circuit (6c) comprises a signal amplification circuit, a filter circuit, a phase compensation circuit, a detection circuit, a zero-cross comparison circuit and a correction circuit.
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