CN114374401A - Automatic gain control radio frequency receiver - Google Patents
Automatic gain control radio frequency receiver Download PDFInfo
- Publication number
- CN114374401A CN114374401A CN202111556952.8A CN202111556952A CN114374401A CN 114374401 A CN114374401 A CN 114374401A CN 202111556952 A CN202111556952 A CN 202111556952A CN 114374401 A CN114374401 A CN 114374401A
- Authority
- CN
- China
- Prior art keywords
- amplifier
- linearity
- value
- low
- radio frequency
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
- H04B1/12—Neutralising, balancing, or compensation arrangements
- H04B1/123—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G3/00—Gain control in amplifiers or frequency changers
- H03G3/20—Automatic control
- H03G3/30—Automatic control in amplifiers having semiconductor devices
- H03G3/3036—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04W—WIRELESS COMMUNICATION NETWORKS
- H04W52/00—Power management, e.g. Transmission Power Control [TPC] or power classes
- H04W52/04—Transmission power control [TPC]
- H04W52/52—Transmission power control [TPC] using AGC [Automatic Gain Control] circuits or amplifiers
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Superheterodyne Receivers (AREA)
- Circuits Of Receivers In General (AREA)
Abstract
The application relates to an automatic gain control radio frequency receiver, which comprises a wiring terminal for receiving radio frequency signals, wherein the wiring terminal is connected with a low noise amplifier, the low noise amplifier is connected with a voltage-current converter, the voltage-current converter is respectively connected with two mixers, each mixer is connected with a transimpedance amplifier, each transimpedance amplifier is connected with a low-pass filter, each low-pass filter is connected with a variable gain amplifier, each variable gain amplifier is connected with a digital-to-analog converter, and the two digital-to-analog converters are jointly connected with a processing control module; the low-noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier are used for coarsely and finely adjusting gain coefficients; the processing control module is used for calculating the frequency of the radio frequency signal and controlling the low noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier to adjust the gain coefficient. The method and the device can realize the adjustment of a wider gain coefficient adjustment range and high precision.
Description
Technical Field
The present application relates to the field of radio frequency technologies, and in particular, to an automatic gain controlled radio frequency receiver.
Background
The radio frequency receiver is a device which can receive radio frequency signals from a long distance and then perform inverse modulation to restore the radio frequency signals to an electric information source. Currently, radio frequency receivers are widely used in a variety of fields such as vehicle monitoring, remote control, and telemetry. Radio frequency receivers are mainly classified into superheterodyne receivers, zero intermediate frequency receivers, and near-zero intermediate frequency receivers.
The zero intermediate frequency receiver has the advantages of easiness in integration, small size and low power consumption, is greatly influenced by direct current offset, and has poor noise and linearity. Specifically, when the phase difference between two local oscillation signals is not exactly 90 °, two signals are overlapped, which may cause distortion and cause a higher error rate, and further may cause baseband I/Q signal mismatch. Similarly, gain mismatch also causes degradation in receiver performance. Therefore, in the process of manufacturing the zero intermediate frequency receiver, the requirement on the performance of the radio frequency receiver is generally higher, and not only the low-noise amplification gain range is wide enough and thin enough, but also the wide-range high-adjustment precision automatic gain control is achieved.
Disclosure of Invention
In order to enable wide-range high-precision automatic gain control, the application provides an automatic gain control radio frequency receiver.
The radio frequency receiver with automatic gain control adopts the following technical scheme:
an automatic gain control radio frequency receiver comprises a receiving terminal for receiving radio frequency signals, wherein the receiving terminal is connected with a low noise amplifier, the low noise amplifier is connected with a voltage-current converter, the voltage-current converter is respectively connected with two mixers, each mixer is connected with a transimpedance amplifier, each transimpedance amplifier is connected with a low-pass filter, each low-pass filter is connected with a variable gain amplifier, each variable gain amplifier is connected with a digital-to-analog converter, and the two digital-to-analog converters are commonly connected with a processing control module;
the phase difference of the local oscillation signals accessed by the two frequency mixers is 90 degrees;
the low-noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier are all used for roughly adjusting the gain coefficient;
another variable gain amplifier is used for fine adjustment of the gain coefficient;
the processing control module is also respectively connected with the low-noise amplifier, the voltage-current converter, the mixer, the transimpedance amplifier and the variable gain amplifier, and is used for calculating the frequency value of the radio-frequency signal and controlling the low-noise amplifier, the voltage-current converter, the mixer, the transimpedance amplifier and the variable gain amplifier to adjust the gain coefficient.
By adopting the technical scheme, the low noise amplifier, the voltage-current converter, the mixer, the transimpedance amplifier and the variable gain amplifier can carry out coarse adjustment on the gain coefficient, and have a certain adjustment range respectively, the other variable gain amplifier can carry out fine adjustment, the low noise amplifier, the voltage-current converter, the mixer, the transimpedance amplifier and the variable gain amplifier can be combined to form a wide-range gain coefficient by adjusting, and the variable gain amplifier can carry out fine adjustment, so that the wide gain coefficient adjustment range is realized, and meanwhile, high-precision adjustment can be realized.
Optionally, the gain steps of the low-noise amplifier, the voltage-to-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier for coarse adjustment of the gain coefficient are at least 2 dB;
the gain step of the variable gain amplifier for fine tuning the gain factor is 1 dB.
By adopting the technical scheme, the gain coefficients of the low-noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier for roughly adjusting the gain coefficient can be adjusted to obtain the gain coefficient which is closer to the target gain coefficient, and then the gain coefficient of the variable gain amplifier for finely adjusting the gain coefficient is adjusted to achieve the target gain coefficient so as to realize high-precision adjustment.
Optionally, the power amplifier further comprises two peak detection modules, wherein the two peak detection modules are respectively connected to the output ends of the two transimpedance amplifiers, and are used for detecting a peak value of the output voltage of the transimpedance amplifier and outputting a peak detection signal;
and the processing control module is connected with the peak detection module and is used for reducing the gain coefficients of the low-noise amplifier, the voltage-current converter, the frequency mixer and the transimpedance amplifier when the voltage value reflected by the received peak detection signal exceeds a threshold value.
By adopting the technical scheme, the gain coefficients of the low-noise amplifier, the voltage-current converter, the mixer and the transimpedance amplifier are adjusted to be low, so that the saturation of the later stage can be avoided.
Optionally, the system further comprises two bandwidth calibration modules, and the two bandwidth calibration modules are respectively connected to the output ends of the two low-pass filters.
By adopting the technical scheme, the problems of signal distortion and the like are prevented.
Optionally, the apparatus further includes an orthogonal offset calibration module, where the orthogonal offset calibration module is respectively connected to the two mixers.
By adopting the technical scheme, the quadrature imbalance calibration module can calibrate the phase difference between the I signal and the Q signal, and prevent the two paths of signals from overlapping to further form distortion.
Optionally, the digital frequency mixer further comprises two dc offset calibration modules, and the two dc offset calibration modules are respectively connected to the two frequency mixers and used for compensating for dc leakage generated by the frequency mixers.
By adopting the technical scheme, when the radio frequency signal and the local oscillator signal are mixed, the local oscillator signal may enter the radio frequency port, and the radio frequency signal may also enter the local oscillator port, so that the self-mixing generates a direct current component, and the direct current component can influence the mixed frequency signal, so that part of direct current offset can be eliminated through the direct current offset calibration module.
Optionally, the system further comprises a check group and two linearity detection modules, wherein the two linearity detection modules are respectively connected to the two mixers, and are used for detecting linearity and outputting a linearity detection signal;
the processing control module is respectively connected with the two linearity detection modules and is also used for controlling the check group to be accessed to and replace a group of frequency mixers, trans-impedance amplifiers, low-pass filters, variable gain amplifiers and digital-to-analog converters with abnormal linearity when the linearity value reflected by any received linearity detection signal exceeds a preset linearity range;
the check group comprises the frequency mixer, the trans-impedance amplifier, the low-pass filter, the variable gain amplifier, the digital-to-analog converter and the linearity detection module.
By adopting the technical scheme, the check group can replace one abnormal group of the mixer, the transimpedance amplifier, the low-pass filter, the variable gain amplifier and the digital-to-analog converter when the receiver is abnormal so as to position the abnormality and further ensure the accuracy of the frequency of the radio-frequency signal received by the receiver.
Optionally, the processing control module is configured to:
obtaining a linearity value exceeding a preset linearity range before accessing a check group, and recording the linearity value as an original linearity value;
determining the frequency value of the radio frequency signal according to the mixing signals output by the two digital-to-analog converters, and recording the frequency value as a frequency detection value;
after accessing the check group, acquiring a linearity value of the check group, and recording the linearity value as a check linearity value;
determining the frequency value of the radio frequency signal according to the mixing signals output by the two digital-to-analog converters, and recording the frequency value as a frequency check value;
judging whether the frequency check value is the same as the frequency detection value or not, if so, adjusting and recording a parameter which enables the check linearity value to be in a preset linearity range, and outputting the parameter;
if not, an alarm signal is output.
By adopting the technical scheme, when the frequency check value is the same as the frequency detection value, the replaced frequency mixer, the transimpedance amplifier, the low-pass filter, the variable gain amplifier and the digital-to-analog converter are not abnormal, the setting of parameters added in the frequency mixing process is problematic, and when the frequency check value is different from the frequency detection value, the replaced frequency mixer, the transimpedance amplifier, the low-pass filter, the variable gain amplifier and the digital-to-analog converter are abnormal, a worker can be reminded of maintaining in time through alarming.
In summary, the present application includes at least one of the following beneficial technical effects:
1. the low noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier are all arranged to be capable of roughly adjusting gain coefficients and have a certain adjusting range, the other variable gain amplifier is capable of finely adjusting, the low noise amplifier, the voltage-current converter, the mixer, the trans-impedance amplifier and the variable gain amplifier are adjusted to be capable of combining to form a wide-range gain coefficient, and the variable gain amplifier can be finely adjusted, so that the wide adjusting range of the gain coefficient is realized, and meanwhile, high-precision adjustment can be realized;
2. the peak value detection module can detect the peak value of the current output by the transimpedance amplifier, and when the peak value exceeds a threshold value, the gain coefficients of the low-noise amplifier, the voltage-current converter, the mixer and the transimpedance amplifier are adjusted to avoid the saturation of the later stage;
3. by setting the check group, the abnormal group of the mixer, the transimpedance amplifier, the low-pass filter, the variable gain amplifier and the digital-to-analog converter can be replaced when the receiver is abnormal, so that the abnormality is positioned, and the accuracy of the frequency of the radio-frequency signal received by the receiver is further ensured.
Drawings
Fig. 1 is a circuit diagram of an automatic gain controlled rf receiver according to an embodiment of the present application.
Fig. 2 is a schematic diagram of a control system of an automatic gain controlled rf receiver according to an embodiment of the present application.
Description of reference numerals: 1. a receiving terminal; 2. a low noise amplifier; 3. a voltage-to-current converter; 4. a mixer; 41. an orthogonal offset calibration module; 42. a direct current offset calibration module; 43. a linearity detection module; 5. a transimpedance amplifier; 51. a peak detection module; 6. a low-pass filter; 61. a bandwidth calibration module; 7. a variable gain amplifier; 8. a digital-to-analog converter; 9. a processing control module; 10. and (5) checking the group.
Detailed Description
In order to make the objects, technical solutions and advantages of the present application more apparent, the present application is further described in detail below with reference to fig. 1-2 and the embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
The embodiment of the application discloses an automatic gain control radio frequency receiver. Referring to fig. 1 and 2, the automatic gain controlled radio frequency receiver includes a receiving terminal 1, a low noise amplifier 2, a voltage-current converter 3, a mixer 4, a transimpedance amplifier 5, a low pass filter 6, a variable gain amplifier 7, a digital-to-analog converter 8, and a processing control block 9. The radio frequency receiver has the advantages of wide and thin low-noise amplification gain range and wide-range high-adjustment-precision automatic gain control.
The receiving terminal 1 is used for receiving a radio frequency signal, and may be a receiving antenna.
The low noise amplifier 2 is connected to the receiving terminal 1 and amplifies the radio frequency signal. Because the noise coefficient generated by the low-noise amplifier 2 is low, the radio-frequency signal with low noise coefficient can be obtained after the low-noise amplifier 2 amplifies the radio-frequency signal.
The voltage-current converter 3 is connected to the low-noise amplifier 2, and is configured to convert the radio-frequency signal in the form of voltage into the radio-frequency signal in the form of current to drive the mixer 4 to mix the radio-frequency signals.
In consideration of the problem of image interference generated during the mixing process, in the present application, two mixers 4 are provided to perform I/Q demodulation, while reducing the complexity of the system.
The two mixers 4 are respectively connected to the voltage-to-current converter 3, and are configured to mix the radio frequency signal with the local oscillator signal to obtain a mixed frequency signal. It should be noted that the phase difference between the local oscillator signals accessed by the two mixers 4 must be 90 °, otherwise, the Q signal mixes into the I signal and interferes with the I signal, and the I signal also mixes into the Q signal and interferes with the Q signal, and further, the overlapping of the two signals may cause signal distortion and increase the error rate. In a specific example, the phase of one local oscillator signal is 0 ° or 180 °, and the phase of the other local oscillator signal is 90 ° or 270 °. Preferably, in order to ensure that the two local oscillation signals can be orthogonal exactly, the two local oscillation signals are preferably a sine signal and a cosine signal.
It can be appreciated that in an actual demodulation process, the quadrature accuracy of the two local oscillator signals may vary with process and temperature conditions. Therefore, in order to alleviate the signal distortion and error problems caused by the overlapping of two signals, two quadrature imbalance calibration modules 41 are further included.
The two quadrature imbalance calibration modules 41 are respectively connected to the two mixers 4, and are configured to calibrate the two local oscillation signals when a phase difference between the two local oscillation signals is not 90 °. Preferably, the quadrature offset calibration module 41 is QEC.
It should also be noted that, in addition to the phase difference between the two local oscillation signals in the I/Q demodulation process, the demodulation process may be affected, and there may also be interference between the radio frequency signal and the local oscillation signal. Specifically, a part of the local oscillator signals may leak to the radio frequency port, and correspondingly, a part of the radio frequency signals may also leak to the local oscillator port, which causes a self-mixing condition in a mixing process, thereby generating a direct current leakage condition.
To this end, the rf receiver of the present application further includes a dc offset calibration module 42. Two dc offset calibration modules 42 are provided. The two dc offset calibration modules 42 are respectively connected to the two mixers 4 for compensating the dc leakage generated by the mixers 4.
Accordingly, two transimpedance amplifiers 5 are also provided. The two transimpedance amplifiers 5 are respectively connected with the two mixers 4 and used for converting the current into voltage, and then amplifying and outputting the voltage. The amplification of the noise signal can be effectively suppressed while amplifying the signal. Furthermore, the present application can also partially eliminate the dc offset by injecting a controllable current into the input terminal of the transimpedance amplifier 5.
The low-pass filters 6 are provided in two. The two low-pass filters 6 are respectively connected to the two transimpedance amplifiers 5, and are used for eliminating interference of high-frequency components in the mixed signal.
The variable gain amplifiers 7 are provided in two. The two variable gain amplifiers 7 are respectively connected with the two low pass filters 6, and are used for amplifying the mixing signals only with low frequency components by a certain factor, wherein the amplification factor can be adjusted according to actual needs.
Two digital-to-analog converters 8 are also provided. Two digital-to-analog converters 8 are connected to the two variable gain amplifiers 7, respectively.
The processing control module 9 is respectively connected with the two digital-to-analog converters 8, receives the two paths of mixing signals only with low-frequency components, and obtains the frequency value of the radio-frequency signal according to the two paths of mixing signals only with low-frequency components.
Up to this point, the function of the radio frequency receiver has been substantially realized by the above-described receiving terminal 1, low noise amplifier 2, voltage-to-current converter 3, mixer 4, transimpedance amplifier 5, low-pass filter 6, variable gain amplifier 7, digital-to-analog converter 8, and processing control block 9.
It can be appreciated that low noise amplifier 2, voltage to current converter 3, mixer 4, transimpedance amplifier 5 and variable gain amplifier 7 are all configured with corresponding gain coefficients. By setting different gain coefficients for the noise amplifier, the voltage-to-current converter 3, the mixer 4, the transimpedance amplifier 5 and the variable gain amplifier 7, an adjustable wide range gain coefficient can be obtained.
Further, the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, the transimpedance amplifier 5, and one variable gain amplifier 7 are used for coarse adjustment of the gain factor, and the other variable gain amplifier 7 is used for fine adjustment of the gain factor.
Specifically, the gain steps of the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, the transimpedance amplifier 5, and the variable gain amplifier 7 for coarse gain factor adjustment are at least 2 dB. In the present application, the gain factor of the low noise amplifier 2 is set to-18 dB, -12dB, 0dB, 12dB, 18dB, and 24 dB; the gain coefficient steps of the voltage-current converter 3, the mixer 4 and the transimpedance amplifier 5 are-6 dB, 0dB, 3dB, 6dB, 9dB, 12dB, 15dB, 18dB, 21dB and 24 dB; the gain factor steps of the variable gain amplifier 7 for coarse adjustment of the gain factor are 0dB, 6dB, 12dB and 18 dB.
The gain step of the variable gain amplifier 7 for fine adjustment of the gain factor is 1dB, and the adjustment range of the gain factor is 0dB to 5dB in the present application.
When the gain coefficients of the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, the transimpedance amplifier 5 and the variable gain amplifier 7 are all set at the highest gear, the radio frequency receiver of the present application can obtain the maximum gain coefficient, which is 81 dB.
When the receiver receives a weak useful signal, the receiver is easily interfered by a strong interference signal of a high-frequency loop at both sides of a receiving frequency, so that the nonlinear device is saturated, and further nonlinear distortion is generated to block communication, and even cause the performance of the receiver to be reduced, therefore, the radio frequency receiver further comprises a peak detection module 51.
The peak detection modules 51 are provided in two. The two peak detection modules 51 are respectively connected to the output ends of the two transimpedance amplifiers 5, and are configured to detect a peak of the output voltage of the transimpedance amplifier 5 and output a peak detection signal. Preferably, the peak detection module 51 is a digital peak detector.
The processing control module 9 is further connected to the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, the transimpedance amplifier 5, and the peak detection module 51, respectively, to receive the peak detection signal, and is configured to control the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, and the transimpedance amplifier 5 to adjust the gain coefficient when the voltage value reflected by the received peak detection signal exceeds the threshold, so as to reduce the gain coefficient of the low noise amplifier 2, the voltage-to-current converter 3, the mixer 4, and the transimpedance amplifier 5, and further avoid saturation of the subsequent stage. Of course, the processing control module 9 is also connected to the two variable gain amplifiers 7 for controlling the two variable gain amplifiers 7 to adjust the gain factor.
The radio frequency receiver of the present application further comprises a bandwidth calibration module 61. The bandwidth calibration module 61 is provided with two. The two bandwidth calibration modules 61 are respectively connected to the output ends of the two low-pass filters 6, and are used for calibrating the bandwidth of the low-pass filters 6, so that the filtered mixed signal with only low-frequency components is more accurate.
For the rf receiver, the linearity is also an important index to show the performance. Therefore, in order to obtain a high-linearity radio frequency receiver, the linearity can be judged.
Specifically, the linearity of the rf receiver is determined by a plurality of parameters, and the present application further includes a linearity detecting module 43.
The two linearity detecting modules 43 are provided, and the two linearity detecting modules 43 are respectively connected to the two mixers 4 and are used for detecting the linearity of the mixers 4 and outputting a linearity detecting signal. Linearity can be measured by 1dB compression point, second order intermodulation point and third order intermodulation point. The specific measurement method is a conventional technical means of those skilled in the relevant field, and is not described in detail in this application.
It will be appreciated that when the linearity is not within the target range, this may be due to unreasonable settings of other parameters, and of course there may be faults in the mixers 4, transimpedance amplifier 5, low pass filter 6, variable gain amplifier 7, digital-to-analog converter 8 and linearity detection module 43 on the I and Q channels, and therefore a check group 10 is also provided. The calibration group 10 includes a mixer 4, a transimpedance amplifier 5, a low pass filter 6, a variable gain amplifier 7, a digital-to-analog converter 8, a peak detection module 51, a bandwidth calibration module 61, a quadrature offset calibration module 41, a dc offset calibration module 42, and a linearity detection module 43, and is connected in the same manner as mentioned above.
The processing control module 9 is respectively connected to the two linearity detecting modules 43 to receive the linearity detecting signals, and is further configured to control the check group 10 to access and replace the group of mixers 4, the transimpedance amplifier 5, the low-pass filter 6, the variable gain amplifier 7, and the digital-to-analog converter 8 with abnormal linearity when a linearity value reflected by any one of the received linearity detecting signals exceeds a preset linearity range, so as to further determine the reason for the abnormal linearity. Therein, the mixer 4, the transimpedance amplifier 5, the low-pass filter 6, the variable gain amplifier 7 and the digital-to-analog converter 8 of the check group 10 are considered to be fault-free.
The specific processing procedure of the processing control module 9 for the case of the linearity abnormality is as follows:
firstly, before accessing the check group 10, a linearity value exceeding a preset linearity range is obtained and recorded as an original linearity value. Meanwhile, the frequency value of the radio frequency signal is determined according to the mixing signal which is obtained from the two digital-to-analog converters 8 and only has the low frequency component, and the frequency value is recorded as a frequency detection value.
Then, after accessing the check group 10, a linearity value of the check group 10 is obtained and recorded as a check linearity value. Meanwhile, the frequency value of the radio frequency signal is determined according to the mixing signal which is obtained from the two digital-to-analog converters 8 and only has the low frequency component, and the frequency value is recorded as a frequency check value.
And then, judging whether the frequency check value is the same as the frequency detection value, if so, adjusting and recording a parameter which enables the check linearity value to be in a preset linearity range so as to output, and if not, outputting an alarm signal.
It should be noted that when the frequency verification value is the same as the frequency detection value, since the verification group 10 has no fault, the group of mixer 4, transimpedance amplifier 5, low-pass filter 6, variable gain amplifier 7 and digital-to-analog converter 8 corresponding to the original linearity value has no fault, i.e. the abnormality of the original linearity value is caused by the abnormality of the relevant parameter. Therefore, the related parameters are adjusted in the calibration group 10, so that the calibration linearity value is within the preset linearity range, and the parameters at this time are recorded for output. Further, the parameters of the group of mixer 4, transimpedance amplifier 5, low pass filter 6, variable gain amplifier 7 and digital-to-analog converter 8 corresponding to the original linearity value are adjusted to the same values as the recorded parameters, so that the linearity within the preset linearity range can be obtained, and further the radio frequency receiver with higher linearity can be obtained.
When the frequency check value is different from the frequency detection value, it indicates that the group of the mixer 4, the transimpedance amplifier 5, the low-pass filter 6, the variable gain amplifier 7 and the digital-to-analog converter 8 corresponding to the original linearity value have faults and need to be repaired or replaced, and at this time, an alarm signal is output to remind an operator to check. The specific maintenance mode may be to sequentially replace the mixer 4, the transimpedance amplifier 5, the low-pass filter 6, the variable gain amplifier 7, and the digital-to-analog converter 8, and when the frequency detection value is the same as the frequency check value after replacement, the fault location is successfully located.
In the present application, the processing control module 9 is an MCU, wherein the preset linearity range can be adaptively designed according to actual needs.
The implementation principle of the automatic gain control radio frequency receiver in the embodiment of the application is as follows: the low noise amplifier 2, the voltage-current converter 3, the mixer 4, the trans-impedance amplifier 5 and one variable gain amplifier 7 are all arranged to be capable of carrying out coarse adjustment on a gain coefficient, and each variable gain amplifier has a certain adjustment range, and the other variable gain amplifier 7 is arranged to be capable of carrying out fine adjustment. By adjusting the low-noise amplifier 2, the voltage-current converter 3, the mixer 4, the transimpedance amplifier 5 and the variable gain amplifier 7 to different gain coefficient steps, the gain coefficient can be changed in a 1dB gain stepping mode, and the effect of adjusting the gain coefficient in a wide range and with high precision is achieved. Meanwhile, the problems of direct current loss, nonlinear distortion and the like can be solved.
The foregoing is a preferred embodiment of the present application and is not intended to limit the scope of the application in any way, and any features disclosed in this specification (including the abstract and drawings) may be replaced by alternative features serving equivalent or similar purposes, unless expressly stated otherwise. That is, unless expressly stated otherwise, each feature is only an example of a generic series of equivalent or similar features.
Claims (8)
1. An automatic gain controlled radio frequency receiver, characterized by: the radio frequency signal receiving device comprises a receiving terminal (1) for receiving a radio frequency signal, wherein the receiving terminal (1) is connected with a low-noise amplifier (2), the low-noise amplifier (2) is connected with a voltage-current converter (3), the voltage-current converter (3) is respectively connected with two mixers (4), each mixer (4) is connected with a trans-impedance amplifier (5), each trans-impedance amplifier (5) is connected with a low-pass filter (6), each low-pass filter (6) is connected with a variable gain amplifier (7), each variable gain amplifier (7) is connected with a digital-to-analog converter (8), and the two digital-to-analog converters (8) are connected with a processing control module (9) together;
the phase difference of the local oscillation signals accessed by the two frequency mixers (4) is 90 degrees;
the low-noise amplifier (2), the voltage-current converter (3), the mixer (4), the trans-impedance amplifier (5) and the variable gain amplifier (7) are all used for roughly adjusting a gain coefficient;
another variable gain amplifier (7) is used for fine adjustment of the gain coefficient;
the processing control module (9) is further connected to the low noise amplifier (2), the voltage-current converter (3), the mixer (4), the transimpedance amplifier (5) and the variable gain amplifier (7) respectively, and is configured to calculate a frequency value of the radio frequency signal, and control the low noise amplifier (2), the voltage-current converter (3), the mixer (4), the transimpedance amplifier (5) and the variable gain amplifier (7) to adjust a gain coefficient.
2. The automatic gain controlled radio frequency receiver of claim 1, wherein: the gain steps of the low-noise amplifier (2), the voltage-current converter (3), the mixer (4), the trans-impedance amplifier (5) and the variable gain amplifier (7) for coarse adjustment of the gain coefficient are at least 2 dB;
the gain of the variable gain amplifier (7) for fine tuning the gain factor is stepped by 1 dB.
3. The automatic gain controlled radio frequency receiver of claim 2, wherein: the two peak value detection modules (51) are respectively connected with the output ends of the two transimpedance amplifiers (5) and are used for detecting the peak value of the output voltage of the transimpedance amplifier (5) and outputting a peak value detection signal;
the processing control module (9) is connected with the peak detection module (51) and is used for reducing the gain coefficients of the low noise amplifier (2), the voltage-current converter (3), the mixer (4) and the transimpedance amplifier (5) when the voltage value reflected by the received peak detection signal exceeds a threshold value.
4. The automatic gain controlled radio frequency receiver of claim 3, wherein: the device also comprises two bandwidth calibration modules (61), and the two bandwidth calibration modules (61) are respectively connected with the output ends of the two low-pass filters (6).
5. The automatic gain controlled radio frequency receiver of claim 4, wherein: the frequency mixer further comprises an orthogonal offset calibration module (41), wherein the orthogonal offset calibration module (41) is respectively connected with the two frequency mixers (4).
6. The automatic gain controlled radio frequency receiver of claim 5, wherein: the direct current offset calibration circuit further comprises two direct current offset calibration modules (42), wherein the two direct current offset calibration modules (42) are respectively connected with the two mixers (4) and are used for compensating direct current leakage generated by the mixers (4).
7. The automatic gain controlled radio frequency receiver of claim 6, wherein: the device also comprises a check group (10) and two linearity detection modules (43), wherein the two linearity detection modules (43) are respectively connected with the two mixers (4) and are used for detecting linearity and outputting a linearity detection signal;
the processing control module (9) is respectively connected with the two linearity detection modules (43), and is further used for controlling the check group (10) to be connected to and replace a group of mixers (4), transimpedance amplifiers (5), low-pass filters (6), variable gain amplifiers (7) and digital-to-analog converters (8) with abnormal linearity when the linearity value reflected by any received linearity detection signal exceeds a preset linearity range;
the check group (10) comprises the mixer (4), a transimpedance amplifier (5), a low-pass filter (6), a variable gain amplifier (7), a digital-to-analog converter (8) and a linearity detection module (43).
8. The automatic gain controlled radio frequency receiver of claim 7, wherein: the process control module (9) is configured to:
obtaining a linearity value exceeding a preset linearity range before accessing a check group (10), and recording as an original linearity value;
determining the frequency value of the radio frequency signal according to the mixing frequency signals output by the two digital-to-analog converters (8), and recording the frequency value as a frequency detection value;
after accessing the check group (10), acquiring a linearity value of the check group (10), and recording as a check linearity value;
determining the frequency value of the radio frequency signal according to the mixing frequency signals output by the two digital-to-analog converters (8), and recording the frequency value as a frequency check value;
judging whether the frequency check value is the same as the frequency detection value or not, if so, adjusting and recording a parameter which enables the check linearity value to be in a preset linearity range, and outputting the parameter;
if not, an alarm signal is output.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111556952.8A CN114374401B (en) | 2021-12-18 | 2021-12-18 | Automatic gain control radio frequency receiver |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111556952.8A CN114374401B (en) | 2021-12-18 | 2021-12-18 | Automatic gain control radio frequency receiver |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN114374401A true CN114374401A (en) | 2022-04-19 |
| CN114374401B CN114374401B (en) | 2024-08-09 |
Family
ID=81139457
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202111556952.8A Active CN114374401B (en) | 2021-12-18 | 2021-12-18 | Automatic gain control radio frequency receiver |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN114374401B (en) |
Citations (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020193958A1 (en) * | 2001-06-15 | 2002-12-19 | Underbrink Paul A. | System using adaptive circuitry to improve performance and provide linearity and dynamic range on demand |
| CN101895266A (en) * | 2010-07-20 | 2010-11-24 | 上海全波通信技术有限公司 | Mixed-signal automatic gain control system and control method thereof |
| CN202750081U (en) * | 2012-06-11 | 2013-02-20 | 桂林电子科技大学 | Software defined radio receiver comprising multi-level automatic gain control modules |
| CN104283574A (en) * | 2013-07-10 | 2015-01-14 | 清华大学 | software radio receiver circuit |
| CN106788511A (en) * | 2016-12-30 | 2017-05-31 | 北京时代民芯科技有限公司 | A kind of wideband radio receiver |
| CN107026665A (en) * | 2015-12-23 | 2017-08-08 | 英特尔公司 | Real-time obstacle adaptive wideband wireless receiver for low-power operation |
| CN107276621A (en) * | 2017-06-01 | 2017-10-20 | 博流智能科技（南京）有限公司 | Take into account the receiver AGC system and method for plurality of application scenes |
| CN109756240A (en) * | 2019-01-25 | 2019-05-14 | 广州全盛威信息技术有限公司 | Wireless communication receiver and gain control method with gain control |
| CN112653486A (en) * | 2020-12-10 | 2021-04-13 | 北京时代民芯科技有限公司 | Broadband radio frequency transceiver capable of expanding receiving channel bandwidth |
| CN113267718A (en) * | 2021-07-19 | 2021-08-17 | 成都市克莱微波科技有限公司 | Power amplifier testing method and device and computer readable storage medium |
-
2021
- 2021-12-18 CN CN202111556952.8A patent/CN114374401B/en active Active
Patent Citations (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020193958A1 (en) * | 2001-06-15 | 2002-12-19 | Underbrink Paul A. | System using adaptive circuitry to improve performance and provide linearity and dynamic range on demand |
| CN101895266A (en) * | 2010-07-20 | 2010-11-24 | 上海全波通信技术有限公司 | Mixed-signal automatic gain control system and control method thereof |
| CN202750081U (en) * | 2012-06-11 | 2013-02-20 | 桂林电子科技大学 | Software defined radio receiver comprising multi-level automatic gain control modules |
| CN104283574A (en) * | 2013-07-10 | 2015-01-14 | 清华大学 | software radio receiver circuit |
| CN107026665A (en) * | 2015-12-23 | 2017-08-08 | 英特尔公司 | Real-time obstacle adaptive wideband wireless receiver for low-power operation |
| CN106788511A (en) * | 2016-12-30 | 2017-05-31 | 北京时代民芯科技有限公司 | A kind of wideband radio receiver |
| CN107276621A (en) * | 2017-06-01 | 2017-10-20 | 博流智能科技（南京）有限公司 | Take into account the receiver AGC system and method for plurality of application scenes |
| CN109756240A (en) * | 2019-01-25 | 2019-05-14 | 广州全盛威信息技术有限公司 | Wireless communication receiver and gain control method with gain control |
| CN112653486A (en) * | 2020-12-10 | 2021-04-13 | 北京时代民芯科技有限公司 | Broadband radio frequency transceiver capable of expanding receiving channel bandwidth |
| CN113267718A (en) * | 2021-07-19 | 2021-08-17 | 成都市克莱微波科技有限公司 | Power amplifier testing method and device and computer readable storage medium |
Non-Patent Citations (2)
| Title |
|---|
| 周嘉业: "射频接收机中自动增益控制电路的研究与设计", 《中国优秀硕士学位论文全文数据库（信息科技辑）》, no. 12, 15 December 2009 (2009-12-15) * |
| 李江全: "《计算机控制技术项目教程》", vol. 2, 30 June 2019, 机械工业出版社, pages: 233 - 235 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN114374401B (en) | 2024-08-09 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US8571149B2 (en) | Direct conversion RF transceiver for wireless communication | |
| CA2093638C (en) | High dynamic range closed loop automatic gain control circuit | |
| US6646449B2 (en) | Intermodulation detector for a radio receiver | |
| EP2055013B1 (en) | Adaptive predistortion for controlling an open loop power amplifier | |
| US8705595B2 (en) | Digital output power measurement in radio communication systems | |
| US8761708B2 (en) | Direct conversion receiver and calibration method thereof | |
| US20030002452A1 (en) | System and method for power control calibration and a wireless communication device | |
| US8121571B2 (en) | Method for second intercept point calibration based on opportunistic reception | |
| EP2713507B1 (en) | FET RF power detector | |
| US6771941B2 (en) | Transmission power control apparatus of base station of mobile communication network | |
| CN113328763B (en) | Carrier power control method and device and radio remote unit | |
| US8019309B2 (en) | Method and system for a second order input intercept point (IIP2) calibration scheme | |
| CN114374401B (en) | Automatic gain control radio frequency receiver | |
| CN216013630U (en) | System for realizing automatic calibration of frequency spectrograph power under condition of adapting to ADC linear characteristic | |
| CN113466774A (en) | System and method for realizing automatic calibration of frequency spectrograph power under condition of adapting to ADC linear characteristic | |
| CN113098548A (en) | Transmitting link, transmitting link calibration method, device and digital transceiver | |
| US6931242B2 (en) | Down converter using C/N ratio correcting circuit of base station for mobile communication network | |
| CN112731276B (en) | Phase-controllable double-channel direction finding device and method | |
| CN116015488B (en) | Receiving gain compensation circuit and receiving gain compensation method of radio frequency chip | |
| US20240106477A1 (en) | Receiver path for a measurement device and measurement device comprising such a receiver path | |
| TW202404278A (en) | Transceiver apparatus having self-calibration mechanism and self-calibration method thereof | |
| Tietze et al. | Transmitters and Receivers |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |