CN113471684A - Patch antenna - Google Patents
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- CN113471684A CN113471684A CN202010241006.3A CN202010241006A CN113471684A CN 113471684 A CN113471684 A CN 113471684A CN 202010241006 A CN202010241006 A CN 202010241006A CN 113471684 A CN113471684 A CN 113471684A
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- 230000005684 electric field Effects 0.000 description 9
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- 230000010287 polarization Effects 0.000 description 3
- 230000007423 decrease Effects 0.000 description 2
- 238000011161 development Methods 0.000 description 2
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- 238000001465 metallisation Methods 0.000 description 2
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- 239000002356 single layer Substances 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 1
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
- H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/48—Earthing means; Earth screens; Counterpoises
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
- H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
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Abstract
The invention relates to the technical field of antennas, and discloses a patch antenna, which comprises: the dielectric substrate, electrically conductive ground plate and electrically conductive paster. The conductive patch and the conductive grounding plate are respectively positioned on the first surface and the second surface of the dielectric substrate; the patch antenna is provided with a plurality of through holes, and the through holes sequentially penetrate through the conductive patch, the dielectric substrate and the conductive grounding plate. The plurality of through holes are metalized through holes or a plurality of short-circuit columns are arranged in the plurality of through holes respectively, two ends of each short-circuit column are connected with the conductive patch and the conductive grounding plate respectively, and the plurality of through holes are distributed on the circumference with the radius of R1. The patch antenna enables the resonant frequency of the first resonant mode and the resonant frequency of the second resonant mode to be close to each other by adjusting R1 and the number N of the plurality of through holes. Therefore, two resonance modes are realized by adopting dual-mode radiation, and high gain of the antenna is realized while low profile and wide bandwidth are realized.
Description
Technical Field
The invention relates to the technical field of antennas, in particular to a patch antenna.
Background
In recent decades, with the rapid development of wireless communication technology, systems such as personal communication and wireless local area network have made higher demands on portability of wireless terminal devices. The antenna is an essential component of a system terminal, and is endowed with multi-band and multi-functional performance. As various multimedia services enter wireless communication systems, the space available on the mobile terminal device to accommodate the antenna will become more and more limited. In military affairs, in order to enhance the maneuverability and concealment of equipment in future electronic combat, a high-performance multifunctional small-sized integrated antenna will become the development trend of antenna technology. In this context, multi-frequency, multi-mode, multi-polarization antennas have been developed. The multi-frequency multi-mode multi-polarization antenna has the significance that a plurality of working frequency bands, a plurality of working modes and even a plurality of polarization modes are integrated into a simple antenna by designing a new antenna model so as to avoid using a plurality of different antennas. Therefore, the cost of the terminal equipment is greatly reduced, and the system space is also saved.
The microstrip antenna has the advantages of small volume, light weight, low profile, easy conformal, low cost, easy integration with a circuit and the like, and is widely applied to the civil and military communication fields of wireless communication, remote sensing, aerospace and the like. At present, many reports of realizing multi-frequency, multi-mode and multi-polarization by using microstrip antennas exist at home and abroad. However, these methods still need to be improved in terms of increasing the size of the antenna, destroying the low-profile characteristics of the antenna, operating at integer frequency multiplication of the limited main mode frequency band, and having a complex structure that is not easy to adjust. In addition, most of the multifunctional antennas only have single multi-frequency, multi-mode or multi-polarization characteristics, and a complete theoretical system is not formed.
The omnidirectional antenna has the characteristics of being broadcast, being capable of covering omnidirectional angles and being used in many occasions. The method is widely applied to airplanes, missiles, high-speed rails and civil communication. As civil communication equipment becomes more integrated and commonalized; the appearance of the traditional antenna is abrupt when the speed of the aircraft is faster and faster, and the requirement of high-speed aerodynamic appearance is difficult to meet.
The traditional omnidirectional antenna is mainly realized in two forms, one is a microstrip antenna, the impedance of the traditional omnidirectional antenna is widened by adopting a double-layer suspension structure of a radiation mode or by improving the feed structure (electromagnetic coupling feed), adding parasitic units (branches or loading) and other technologies, and the traditional omnidirectional antenna has the advantages of low section, but has the problems of complex structure and easy distortion of a directional diagram. The other type is a monopole antenna, top loading or lossy loading is adopted to realize the low profile of the antenna, lossy matching is at the cost of sacrificing gain, the top loading is difficult to realize the real low profile, the advantage is wide bandwidth, and the disadvantage is high profile. It is difficult to realize a high gain of the antenna while simultaneously realizing a low profile and a wide bandwidth.
Disclosure of Invention
In order to solve the above-described problems, the present invention provides a patch antenna that can realize a high gain of the antenna while realizing a low profile and a wide bandwidth.
According to the present invention, there is provided a patch antenna operating in a first resonance mode and a second resonance mode and including:
a dielectric substrate;
a conductive ground plate;
the conductive patch and the conductive grounding plate are respectively positioned on the first surface and the second surface of the dielectric substrate; the patch antenna is provided with a plurality of through holes, and the through holes sequentially penetrate through the conductive patch, the dielectric substrate and the conductive grounding plate;
the through holes are all metalized through holes or a plurality of short-circuit columns are respectively arranged in the through holes, two ends of each short-circuit column are respectively connected with the conductive patch and the conductive grounding plate, and the through holes are distributed on the circumference with the radius of R1;
the patch antenna enables the resonant frequency of the first resonant mode and the resonant frequency of the second resonant mode to be close to each other by adjusting R1 and the number N of the through holes.
Preferably, the first resonant mode is a TM01 mode and the second resonant mode is a TM02 mode.
Preferably, the resonant frequency of the first resonant mode is determined according to R1 and the number N of the plurality of through holes.
Preferably, the conductive patch is circular in shape, and the resonant frequency of the second resonant mode is determined by R1, the radius R2 of the conductive patch, and the dielectric constant ε of the dielectric substraterTo be determined.
Preferably, the center of the circle with the radius of R1 is the same as the center of the conductive patch, and the radius of the conductive patch R2 is larger than R1.
Preferably, each of the through-holes has a circular or polygonal sectional shape.
Preferably, the conductive grounding plate is circular, the dielectric substrate is circular, and the diameter of the conductive grounding plate is equal to the diameter of the dielectric substrate.
Preferably, the cross-sectional height of the patch antenna is 0.024 λ, where λ is a free space wavelength corresponding to a central frequency point of an operating band of the patch antenna.
Preferably, the surface of the conductive ground plate, which is far away from the dielectric substrate, is provided with a radio frequency connector, and the radio frequency connector is used for feeding the patch antenna; the inner conductor of the radio frequency connector is connected with the conductive patch, and the outer conductor of the radio frequency connector is connected with the conductive grounding plate.
Preferably, each through hole has a circular or polygonal cross-sectional shape, and the dielectric substrate has a circular or polygonal cross-sectional shape.
The invention has the beneficial effects that:
1. the radiating patch in the patch antenna provided by the invention selects the circular metal patch and realizes dual-mode radiation of two resonance modes in a mode of metalizing the through hole or loading the conformal metal column, and the stability of a directional diagram is realized through mode selection and ingenious excitation;
2. the height of the patch antenna is 0.024f, and the patch antenna has the advantages of miniaturization and low profile;
3. the antenna is obtained by adopting a single-layer dielectric substrate through an etching process, has a simple and reliable structure and is easy to produce in batches;
4. the invention adopts the circular patch antenna with dual-mode radiation, effectively widens the bandwidth of the antenna, can calculate the radius R1 of the circumference where the central connecting line of the loading through hole is located and the number N of the plurality of through holes through the coaxial resonant cavity model and the sector model, has strong innovation, and widens the application range of the patch antenna based on the dual-mode radiation.
Drawings
The above and other objects, features and advantages of the present invention will become more apparent from the following description of the embodiments of the present invention with reference to the accompanying drawings.
Fig. 1 is a perspective view of a patch antenna provided according to an embodiment of the present invention.
Fig. 2 is a top view of the patch antenna shown in fig. 1.
Fig. 3 is a side view of the patch antenna shown in fig. 1.
Fig. 4 shows a radiation gain diagram of the patch antenna in fig. 1 in a horizontal direction of the TM02 mode.
Fig. 5 shows a schematic diagram of a metal patch structure of the patch antenna in fig. 1.
Fig. 6 shows a schematic diagram of a sector structure of the patch antenna of fig. 5 cut at an angle phi.
Fig. 7 shows a graph of the voltage standing wave ratio of the patch antenna of fig. 1.
Fig. 8 shows a gain profile of the patch antenna of fig. 1 at Phi 90 °/270 °, and a frequency of 0.9f 0.
Fig. 9 shows a gain profile of the patch antenna of fig. 1 at Phi 0 °/180 ° and a frequency of 0.9f 0.
Fig. 10 shows a gain profile of the patch antenna of fig. 1 at Phi 90 °/270 °, and a frequency of 1.12f 0.
Fig. 11 shows a gain profile of the patch antenna of fig. 1 at Phi 0 °/180 ° and a frequency of 1.12f 0.
Detailed Description
To facilitate an understanding of the invention, the invention will now be described more fully with reference to the accompanying drawings. Preferred embodiments of the present invention are shown in the drawings. The invention may, however, be embodied in different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete.
Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this invention belongs. The terminology used herein in the description of the invention is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention.
The present invention will be described in detail below with reference to the accompanying drawings.
Fig. 1 is a perspective view of a patch antenna provided according to an embodiment of the present invention, fig. 2 is a top view of the patch antenna shown in fig. 1, and fig. 3 is a side view of the patch antenna shown in fig. 1.
Referring to fig. 1, fig. 2 and fig. 3, an embodiment of the invention provides a patch antenna 100, which includes: a conductive patch 10, a dielectric substrate 20 and a conductive ground plate 30. The conductive patch 10 is a metal patch and the conductive ground plate 30 is a metal ground plate.
The conductive patch 10 and the conductive ground plate 30 are located on the first surface and the second surface of the dielectric substrate 20, respectively. The conductive patch 10 is centrosymmetric with respect to the central axis of the dielectric substrate 20, and the conductive ground plate 30 is coaxially disposed with the conductive patch 10.
The patch antenna 100 has a plurality of through holes 50, and the plurality of through holes 50 sequentially penetrate through the conductive patch 10, the dielectric substrate 20, and the conductive ground plate 30.
In a first alternative embodiment, the plurality of vias 50 are all metallized vias.
Or in a second alternative embodiment, a plurality of shorting posts are respectively disposed in the plurality of through holes 50 and both ends of each shorting post are respectively connected to the conductive patch 10 and the conductive ground plate 30. Each short-circuit column is a metal column.
The plurality of through holes 50 are distributed on a circumference having a radius R1. In a specific embodiment of the present invention, the plurality of through holes 50 are evenly distributed on a circumference having a radius R1.
The patch antenna 100 operates in a first resonant mode and a second resonant mode. In the embodiment of the present invention, the first resonant mode is a TM01 mode, and the second resonant mode is a TM02 mode.
The patch antenna 100 makes the resonance frequency of the first resonance mode (for example, TM01 mode) and the resonance frequency of the second resonance mode (for example, TM02 mode) close to each other by adjusting the number N of R1 and the plurality of through holes. In this embodiment, that the resonance frequency of the first resonance mode and the resonance frequency of the second resonance mode are close to each other may mean that a difference between the resonance frequency of the first resonance mode and the resonance frequency of the second resonance mode is small, for example, the difference is 0.01Hz, 0.001Hz, or 0.0001Hz, or the like.
The resonant frequency of the first resonant mode (e.g., TM01 mode) is determined according to R1 and the number N of the plurality of vias. Wherein the plurality of through holes 50 are evenly distributed on a circumference with a radius R1.
The conductive patch 10 is circular in shape. The resonant frequency of the second resonant mode (e.g., TM02 mode) depends on the R1, the radius R2 of the conductive patch 10, and the dielectric constant ε of the dielectric substrate 20rTo be determined. Since the patch antenna 100 has two resonance modes (TM01 mode and TM02 mode), the bandwidth of the patch antenna 100 is effectively increased.
Wherein the introduction of a shorting post (e.g., a metal post) or a metalized via 50 within the via 50 causes the equivalent inductance of the antenna to change and excite the TM01 mode. And since the plurality of through holes 50 are distributed on the circumference of radius R1, the radius of the circular conductive patch 10 is R2; the circular conductive structure formed by the radius R1 and the radius R2 changes the capacitance distribution of the antenna, so that a new resonant mode TM02 is excited, and the frequency band of the antenna is widened.
In the embodiment of the invention, the center of the circle with the radius of R1 is the same as the center of the conductive patch 10, and the radius R2 of the conductive patch 10 is greater than R1.
Specifically, the conductive ground plate 30 has a circular shape, the dielectric substrate 20 has a circular shape, and the diameter of the conductive ground plate 30 is equal to the diameter of the dielectric substrate 20.
In the present embodiment, each through-hole 50 has a circular cross-sectional shape. In other embodiments, the cross-sectional shape of each through-hole 50 is polygonal.
In the embodiment of the present invention, the cross-sectional shape of the dielectric substrate 20 is circular. In other embodiments, the cross-sectional shape of the dielectric substrate 20 is polygonal.
The surface of the conductive ground plate 30 away from the dielectric substrate 20 is provided with a radio frequency connector 40, and the radio frequency connector 40 is used for feeding the patch antenna 100; the inner conductor of the radio frequency connector 40 is connected to the conductive patch 10 and the outer conductor of the radio frequency connector 40 is connected to the conductive ground plate 30.
In the embodiment of the present invention, the cross-sectional height of the patch antenna 100 is 0.024 λ, where λ is a free space wavelength corresponding to a central frequency point of an operating frequency band of the patch antenna 100. In contrast, the conventional antenna in the prior art has a cross-sectional height of 0.23 λ; the patch antenna 100 in the embodiment of the present invention has a low profile with respect to the conventional antenna.
In the present embodiment, the circular conductive patch 10 is adopted, so that the patch antenna 100 selects the TM02 mode, the directional pattern thereof is apple-shaped, the coverage space is large, and the antenna has good omni-directionality in the horizontal direction, as shown in fig. 4, which can meet the requirements of the antenna coverage space and polarization.
Therefore, the omnidirectional antenna requires that the azimuth plane realizes 360-degree coverage, namely, the electric field and the magnetic field are symmetrical around the normal direction, the rectangular patch antenna is difficult to find two modes of electric field and magnetic field which are symmetrical around the normal direction at the same time, and the circular patch antenna 100 designed by the invention can achieve the symmetry of the electric field and the magnetic field in the normal direction by selecting the TM02 mode, thereby meeting the requirement of a directional diagram.
It is known that the guided wave propagating on the antenna transmission line depends on the cut-off wave number kcGenerally, there are 3 cases:
in the latter two cases, the former means that the guided wave has neither longitudinal electric field nor longitudinal magnetic field, but only transverse electric and magnetic fields, called transverse electromagnetic wave, which is a mode that cannot exist in a metal waveguide; the latter is not possible in a metal waveguide made of a smooth conductor, but only in modes that are possible with certain impedance walls, such as in a dielectric waveguide. To for
The situation of (2) is divided into two cases: ezNot equal to 0, and HzThe wave which is 0 is called magnetic field pure transverse wave, called TM wave for short; e z0, and HzWaves with a magnetic field component other than 0 are called electric field pure transverse waves, TE waves for short.
The law for the transverse distribution of the circular waveguide with respect to the field is: in the radial direction R is the bezier function or derivative distribution thereof; is a trigonometric function distribution along the angular direction phi for TMnmMode, n represents the number of periods in which the field varies along the circumference (from 0 to 2 pi) or the number of half-waves over which the field is distributed along the circumference, and m represents the number of zeros (or the maximum number) other than 0 experienced by the field along the radius (R from 0 to a). For TM in circular waveguidenmCutoff wavelength λ of modecTMnmThis can be obtained by the following equation:
v in formula (1)nmIs the nth root of the first derivative of the m-th order Bessel function, and a is the radius of the longitudinal section of the circular waveguide.
In the present embodiment, the through hole 50 disposed coaxially with the central axis of the circular conductive patch 10 changes the distributed inductance on the conductive ground plate of the antenna by means of short circuit through metallization or loading of the conformal metal pillar, so as to excite the patch antenna 30 in the TM01 mode, thereby effectively increasing the bandwidth. As described above, the plurality of symmetrical through holes 50 coaxially disposed on the central axis of the circular conductive patch 10, the conductive patch 10 disposed on the first surface of the dielectric substrate 20 and the conductive ground plate 30 disposed on the second surface of the dielectric substrate 20 form a circular coaxial resonant cavity, and the TM01 mode is excited to form a dual resonant point, thereby effectively increasing the bandwidth.
In the present embodiment, the dielectric substrate 20 is circular, and has a diameter less than or equal to 0.62 λ, as shown in fig. 2, and the cross-sectional height of the patch antenna 100 is less than or equal to 0.024 λ, as shown in fig. 3, where λ is a free space wavelength corresponding to a central frequency point of the operating band of the antenna. The patch antenna 100 has the advantages of small size and low profile.
The radiation pattern of a circular patch antenna is complex, including: TE11, TE01, TM11, TM01, and the like. The conventional circular patch antenna generally adopts a TM11 mode and a TE11 mode, and has a high Q value (quality factor), a narrow bandwidth, and a biased feeding, which makes it difficult to realize a wide bandwidth. Because of the omnidirectional directional pattern, the electric field and the magnetic field are required to be symmetrical around the normal direction, and the electric field and the magnetic field characteristics of the TM01 and TM02 modes can meet the design requirements, the patch antenna 100 designed by the invention works in the TM01 and TM02 modes.
The resonant frequency of the TM02 mode can be determined by matching the radius R2 of the circular conductive patch 10, the radius R1, and the dielectric constant epsilon of the dielectric substrate 20rSpecifically, the calculation is as follows:
initial value determination of (one) R1 and R2 values
The cross-sectional shape of the through-hole 50 is circular, and the plurality of through-holes 50 are evenly distributed on a circumference having a radius R1.
R2＝3.8117/k02 (2)
3.8117 in equation (2) is the variable value at which the derivative function of the first order Bessel function of the TM02 mode field component becomes zero, also called the eigenvalue, k, of the TM02 mode02Is the cut-off wavenumber, k, in the TM02 mode02The value of (c) can be calculated according to the following equation (3):
wherein, c is 3 x 108(m/s), f1 is the resonant frequency, ε, in the TM02 moderIs the dielectric constant of the dielectric substrate 20.
The electric field of TM02 mode appears in the short-circuit face along the radial direction of circular metal patch, and the antenna structure that adopts the mode of metallized through-hole or loading conformal metal post to form in the position that appears the short-circuit face, under the electric field and the magnetic field condition that do not influence TM02 mode guided wave, can encourage the TM01 mode of antenna, increase impedance bandwidth. The radius of the circle where the center of the loading position of each metalized through hole or short-circuit pillar (e.g., metal pillar) is located, i.e., the value of R1, is specifically:
R1＝2.4048/k02 (4)
2.4048 in equation (4) is the variable value of zero after the first order Bezier function of the TM01 mode field component becomes the origin, also called the eigenvalue of the TM01 mode.
(II) optimization of R1 and R2 values
In this coaxial cavity model, since the position of the metalized via or the loading shorting bar (e.g., metal bar) is at the short-circuited face of the TM02 mode, the number thereof has little influence on the TM02 mode. Combining the formulas (2), (3) and (4), it can be seen that the resonant frequency f1 of the TM02 mode decreases with the increase of R1 when R2 is unchanged.
Specifically, in the formula (3) for calculating the resonant frequency of TM02 mode:
wherein f1 is the resonant frequency in TM02 mode; j (χ) in equation (6) is a first-type bessel function, and J' (χ) is a derivative function thereof; since the bezier function has: j'0(χ)+J1The property of (χ) ═ 0, so the root of the first order bessel function is equal to the root of the derivative of the zeroth order bessel function, and is used to find the zero value of the first class bessel function. Y (χ) is a bezier function of the second type, Y' (χ) is its derivative function; to find the zero value of the bessel function of the second kind. J'0(x) and Y'0(χ) is the derivative of the zeroth order function of the respective functions, availableRespectively calculating the zero value, χ, of its first order function curve02Is the second zero value of its first order function, i.e., the second root of eigen equation (6).
It should be noted that, in the TM02 model, the content of the definitions of the first bessel function and the second bessel function, and their function derivatives and zero values may refer to Pozar D M, microwave engineering (third edition), beijing, electronic industry publishers, 2007.271-273, which is not described herein again.
Influence of the number N of (III) metallized vias 50 or the number N of shorting pillars (e.g., metal pillars) on the two-mode resonant frequency
The resonant frequency for the TM01 mode of a circular patch antenna can be viewed as N included angles with radius R1
The sector model of (a), wherein,
or
The upper and lower surfaces of the sector are Perfect Electric Conductor (PEC) surfaces, and the front, rear, and right surfaces of the sector are Perfect Magnetic Conductor (PMC) surfaces, as shown in fig. 5 and 6. The PEC and PMC correspond to symmetric boundary conditions, and in this embodiment, the cross-sectional shapes of the metal patch 10 and the dielectric substrate 20 are both circular, and the light source (with a certain polarization) also satisfies symmetry at normal incidence, which corresponds to a periodic boundary.
For TM01The resonant frequency f2 of the mode is specifically:
k in formula (7)01Is TM01Cutoff wave number in mode, said k01Is obtained by the following equations (8) and (9):
k01＝χ01*R1 (8)
J'v(χ01)＝0 (9)
in formula (9), J (χ) is a first seebeck function, and J' (χ) is a derivative function thereof; chi shape01Is the first zero value of the function curve of order (v +1) of said function, i.e. the first root of the eigen equation (9) of the circular sector, and the value of the variable v in the eigen equation (9) is obtained according to the following equations (10) and (11):
φ＝2π/N (11)
where N is the number of the plurality of through holes 50, and N is an integer multiple of 2.
Combining the formulas (7), (8), (9), (10) and (11) to obtain TM01The value of the resonant frequency f2 in the mode, and as the number N of vias increases, the effective circuit path in TM01 mode decreases and the resonant frequency f2 increases.
It should be noted that, the definition of the bezier function of the first kind and the derivative and zero value of the function in the TM01 model can be referred to Pozar D M, microwave engineering (third edition), beijing, electronic industry press, 2007.271-273, which is not described herein again.
In the circular patch antenna 100 provided by the present invention, the radius R1 of the circumference where the center lines of the plurality of through holes 50 are located and the number N of the through holes can be adjusted to make the resonant frequencies of the TM01 mode and the TM02 mode close to each other, and further make the difference between the resonant frequency f2 of the TM01 mode and the resonant frequency f1 of the TM02 mode smaller, for example, the difference is 0.01Hz, 0.001Hz, or 0.0001 Hz. Thereby widening the bandwidth of the patch antenna 100 (i.e., thereby forming a wideband) to meet the impedance characteristics requirements of the patch antenna 100 in the operating bandwidth.
The position of the loading through hole is calculated through the coaxial resonant cavity model and the sector model, and the antenna structure with stable gain effect and bandwidth is obtained through parameter optimization, so that the aim of reducing simulation data volume is fulfilled, and meanwhile, the application range of the patch antenna based on dual-mode radiation is widened.
It should be noted that the patch antenna of the present invention can be applied to a communication system with multiple frequency bands, and can be implemented by parameters (e.g. R1, R2, N, and epsilon) in the antenna structurer) The selection optimization of the method can obtain good impedance matching and directional gain within the corresponding working bandwidth.
FIG. 7 is a graph showing the voltage standing wave ratio of the patch antenna in FIG. 1, as shown in FIG. 7, the center frequency of the patch antenna is f0, and the voltage standing wave ratio of the patch antenna is not more than 2 in the frequency range of 0.9f 0-1.12 f 0.
Fig. 8 and 9 show gain graphs of the patch antenna 100 in fig. 1 at Phi 90 °/270 ° and Phi 0 °/180 °, and at a frequency of 0.9f0, respectively, in fig. 8, the patch antenna 100 has a main lobe radiation power of 3.56dB at a maximum in the direction Phi 90 °/270 °, i.e., in the XOZ plane, a main lobe width of 48.3 °, and a side lobe level of-7.4 dB in the direction Phi 90 °/270 ° at a frequency of 0.9f0, i.e., in the YOZ plane, and in fig. 9, the patch antenna 100 has a main lobe radiation power of 3.37dB at a maximum in the direction Phi 0 °/180 °, i.e., in the YOZ plane, a main lobe radiation power of 37dB, a direction of 37 °, and a main lobe width of 48.3, and a side lobe level of-7.3 dB in the frequency of 0.9f 0.
Fig. 10 and 11 show gain graphs of the patch antenna in fig. 1 at Phi 90 °/270 ° and Phi 0 °/180 °, and at a frequency of 1.12f0, respectively, in fig. 10, the patch antenna has a main lobe radiation power of 5.21dB at a maximum in a direction of Phi 90 °/270 °, i.e., in the XOZ plane, a main lobe radiation power of 34 ta, a main lobe width of 43.8 °, and a side lobe level of-10.3 dB in a direction of Phi 90 °/270 ° at a frequency of 1.12f0, and in fig. 9, the patch antenna has a main lobe radiation power of 5.13dB at a maximum in a direction of Phi 0 °/180 °, i.e., in the YOZ plane, a main lobe width of 34 °, a main lobe width of 43.8 °, and a side lobe level of-10.3 dB in a frequency of 1.12f 0.
The simulation results show that the frequency bandwidth of the patch antenna 100 of embodiment 1 is 20.2%, the maximum gain in the whole bandwidth reaches 5.21dB, a stable edge-ray pattern exists in the bandwidth, and the cross polarization levels of the E-plane and the H-plane are relatively low.
In addition, the patch antenna 100 provided by the embodiment of the invention adopts a single-layer dielectric substrate, and the process adopts etching and metallization through holes or loading short-circuit columns, so that the patch antenna is simple and reliable in structure and easy to produce in batches.
It should be noted that in the description of the present invention, it is to be understood that the terms "upper", "lower", "inner", and the like, indicate orientation or positional relationship, are only for convenience of describing the present invention and simplifying the description, but do not indicate or imply that the referenced components or elements must have a particular orientation, be constructed and operated in a particular orientation, and thus should not be construed as limiting the present invention.
Further, in this document, the contained terms "include", "contain" or any other variation thereof are intended to cover a non-exclusive inclusion, so that a process, a method, an article or an apparatus including a series of elements includes not only those elements but also other elements not explicitly listed or inherent to such process, method, article or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
Finally, it should be noted that: it should be understood that the above examples are only for clearly illustrating the present invention and are not intended to limit the embodiments. Other variations and modifications will be apparent to persons skilled in the art in light of the above description. And are neither required nor exhaustive of all embodiments. And obvious variations or modifications of the invention may be made without departing from the scope of the invention.
Claims (10)
1. A patch antenna, comprising:
a dielectric substrate;
a conductive ground plate;
the conductive patch and the conductive grounding plate are respectively positioned on the first surface and the second surface of the dielectric substrate; the patch antenna is provided with a plurality of through holes, and the through holes sequentially penetrate through the conductive patch, the dielectric substrate and the conductive grounding plate;
the through holes are all metalized through holes or a plurality of short-circuit columns are respectively arranged in the through holes, two ends of each short-circuit column are respectively connected with the conductive patch and the conductive grounding plate, and the through holes are distributed on the circumference with the radius of R1;
the patch antenna enables the resonant frequency of the first resonant mode of the patch antenna and the resonant frequency of the second resonant mode of the patch antenna to be close to each other by adjusting the number N of the R1 and the through holes.
2. A patch antenna according to claim 1, wherein: the first resonant mode is a TM01 mode and the second resonant mode is a TM02 mode.
3. A patch antenna according to claim 1, wherein: the resonant frequency of the first resonant mode is determined according to R1 and the number N of the plurality of vias.
4. A patch antenna according to claim 1, wherein: the conductive patch is circular in shape, and the resonant frequency of the second resonant mode is determined by R1, the radius R2 of the conductive patch, and the dielectric constant ε of the dielectric substraterTo be determined.
5. A patch antenna according to claim 4, wherein: the circle center of the circle with the radius of R1 is the same as the circle center of the conductive patch, and the radius of the conductive patch R2 is larger than R1.
6. A patch antenna according to claim 1, wherein: the cross-sectional shape of each through hole is circular or polygonal.
7. A patch antenna according to claim 1, wherein: the conductive grounding plate is circular, the dielectric substrate is circular, and the diameter of the conductive grounding plate is equal to that of the dielectric substrate.
8. A patch antenna according to claim 1, wherein: the cross-sectional height of the patch antenna is 0.024 lambda, wherein lambda is the free space wavelength corresponding to the central frequency point of the working frequency band of the patch antenna.
9. A patch antenna according to claim 1, wherein: the surface of the conductive grounding plate, which is far away from the dielectric substrate, is provided with a radio frequency connector, and the radio frequency connector is used for feeding the patch antenna; the inner conductor of the radio frequency connector is connected with the conductive patch, and the outer conductor of the radio frequency connector is connected with the conductive grounding plate.
10. A patch antenna according to claim 1, wherein: the cross section of each through hole is circular or polygonal, and the cross section of the dielectric substrate is circular or polygonal.
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|---|---|---|---|
| CN202010241006.3A CN113471684A (en) | 2020-03-31 | 2020-03-31 | Patch antenna |
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| Application Number | Priority Date | Filing Date | Title |
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| CN202010241006.3A CN113471684A (en) | 2020-03-31 | 2020-03-31 | Patch antenna |
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| CN113471684A true CN113471684A (en) | 2021-10-01 |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN118508061A (en) * | 2024-05-21 | 2024-08-16 | 南通大学 | Double-frequency-band and three-frequency-band horizontal omnidirectional antenna |
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| CN105186116A (en) * | 2015-07-16 | 2015-12-23 | 广东顺德中山大学卡内基梅隆大学国际联合研究院 | Wideband monopole microstrip antenna |
| CN108808232A (en) * | 2018-06-06 | 2018-11-13 | 深圳市深大唯同科技有限公司 | A kind of dual-band and dual-polarization paster antenna in biradial direction |
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| CN108808232A (en) * | 2018-06-06 | 2018-11-13 | 深圳市深大唯同科技有限公司 | A kind of dual-band and dual-polarization paster antenna in biradial direction |
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| CN118508061A (en) * | 2024-05-21 | 2024-08-16 | 南通大学 | Double-frequency-band and three-frequency-band horizontal omnidirectional antenna |
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