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CN112887230A - Channel estimation method of space-time block coding MSK system under flat fading channel - Google Patents

Channel estimation method of space-time block coding MSK system under flat fading channel Download PDF

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CN112887230A
CN112887230A CN202110022932.6A CN202110022932A CN112887230A CN 112887230 A CN112887230 A CN 112887230A CN 202110022932 A CN202110022932 A CN 202110022932A CN 112887230 A CN112887230 A CN 112887230A
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training sequence
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CN112887230B (en
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张学达
孙锦华
张春晖
郑浩然
刘玉涛
魏萌
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Xidian University
CETC 54 Research Institute
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0204—Channel estimation of multiple channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/10—Frequency-modulated carrier systems, i.e. using frequency-shift keying
    • H04L27/106—M-ary FSK

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Abstract

本发明公开了一种平坦衰落信道下空时块编码MSK系统的信道估计方法，主要解决现有STBC‑MSK系统中平坦衰落信道响应估计不精确、接收机复杂度较高的问题。其实现方案是：1)将发送端产生的初始比特序列分为多个数据块；2)在数据块尾部添加相位连续符号得到预调制序列；3)将预调制序列分解为调幅脉冲信号得到调制信号；4)对调制信号进行STBC编码，并添加训练序列得到发射信号；5)将发射信号通过平坦衰落信道到达接收端；6)在接收端计算训练序列可信度变量，并分段估计信道响应。本发明在提高信道估计精度的同时降低了复杂度，可用于空时块编码下最小频移键控STBC‑MSK系统中信号的传输。

Figure 202110022932

The invention discloses a channel estimation method for a space-time block coding MSK system under a flat fading channel, which mainly solves the problems of inaccurate response estimation and high receiver complexity in the existing STBC-MSK system. The implementation scheme is: 1) dividing the initial bit sequence generated by the transmitting end into multiple data blocks; 2) adding phase-continuous symbols at the end of the data blocks to obtain a pre-modulation sequence; 3) decomposing the pre-modulation sequence into amplitude modulation pulse signals to obtain modulation 4) Perform STBC coding on the modulated signal, and add a training sequence to obtain the transmitted signal; 5) Send the transmitted signal to the receiving end through a flat fading channel; 6) Calculate the reliability variable of the training sequence at the receiving end, and estimate the channel in sections response. The present invention reduces the complexity while improving the channel estimation accuracy, and can be used for signal transmission in the minimum frequency shift keying STBC-MSK system under space-time block coding.

Figure 202110022932

Description

Channel estimation method of space-time block coding MSK system under flat fading channel
Technical Field
The invention belongs to the technical field of communication, and particularly relates to a channel estimation method which can be used for signal transmission in a minimum frequency shift keying STBC-MSK system under space-time block coding.
Background
The minimum frequency shift keying (MSK) modulation mode is a modulation mode which is very advantageous under a nonlinear band-limited channel. The phase is continuous, phase jump can not occur during symbol switching, so that the side lobe of the power spectrum is attenuated quickly, the power spectrum is mainly concentrated in the main lobe, the interference of the side lobe on signals of adjacent frequency bands is small, and the utilization efficiency of the frequency band is high. Meanwhile, the phase carries transmission bit information, so that the system performance is insensitive to the attenuation of the signal amplitude.
M.P Fitz and X.Zhang put forward a space-time trellis coding (STTC) coding mode in 2003, which is applied to an MIMO-CPM system, and constructs a coding mode under the condition of Rayleigh flat fading channel, and in addition, the two people also put forward a calculation method for measuring the symmetric information rate of the MIMO system performance as the lower bound of the channel capacity, and a joint channel estimation algorithm and a data detection method aiming at soft output. Space-time trellis coding, however, introduces greater complexity to the system receiver.
Shenli introduces a predistortion circuit for processing aiming at the nonlinearity of a channel of the MIMO system, and researches a symbol timing synchronization method of the MIMO-CPM system. In forestry, chenghandong et al, further extend the OST-CPM coding method of g.y.wang to any number of antennas, and prove from the aspect of rank criterion that the OST-CPM system has complete diversity gain, and further research the non-coherent demodulation algorithm of the OST-CPM system, but these methods do not discuss the problem of CPM signal phase continuity during coding, and the phase discontinuity may affect the orthogonality of the transmitted signal on the transmitting antennas, so that the signal may be subject to self-interference during transmission, which affects the system receiving error performance.
G.y.wang et al propose an orthogonal-like construction method similar to Alamouti orthogonal space-time coding, which can use orthogonal space-time coding continuous phase modulation OST-CPM transmitted by two antennas to combat flat fading channels. But the construction method thereof increases the channel estimation complexity, and the STBC-MSK system can estimate the flat fading channel at the receiving end of the system and reduce the calculation complexity due to the characteristic of the coding block. The beam-Han-Sai researches the STBC-MSK coding structure and carries out channel estimation at the receiving end, but the channel estimation method adopts integral average, so that the channel response precision is low and the system error code performance is poor.
Disclosure of Invention
The invention aims to provide a channel estimation method of a space-time block coding MSK system under a flat fading channel aiming at the defects of the prior art so as to improve the channel response precision and the system error code performance.
The technical idea of the invention is as follows: the initial bit sequence is processed in a blocking mode at a sending end, a phase return-to-zero symbol is added, amplitude modulation pulse decomposition is carried out, STBC coding is carried out, and a training sequence credibility variable is introduced to a receiving end to carry out sectional estimation on channel response.
According to the above thought, the implementation steps of the invention include the following:
(1) randomly generating a data frame with length of L bits at a transmitting end of a space-time coding minimum frequency shift keying STBC-MSK system
Figure BDA0002889302550000021
Duration per bit of Ts；
(2) The data frame is partitioned into two transmitting antennas to obtain the data frame of each antenna
Figure BDA0002889302550000022
Has a length of
Figure BDA0002889302550000023
Dividing the data frame on each antenna into three sub-data blocks
Figure BDA0002889302550000024
Calculating phase continuation symbols d from the three sub-data blocks respectivelyxAdding phase continuous symbols to the tail of each subdata block to obtain the 1 st antenna premodulation data block
Figure BDA0002889302550000025
Figure BDA0002889302550000025
2 nd antenna premodulation data block
Figure BDA0002889302550000026
(3) For the pre-modulated data block after adding phase continuous symbols
Figure BDA0002889302550000027
And
Figure BDA0002889302550000028
amplitude modulation pulse decomposition is carried out to obtain modulation signals s on two antennasm,1(t)、sm,2(t)；
(4) Modulating signals s on two antennasm,1(t)、sm,2(t) the heads are each added with a length LcpTo obtain sm1(t)、sm2(t); and to sm1(t)、sm2(t) performing STBC coding to obtain a transmission signal s on the 1 st antenna1(t) and the transmitted signal s on the 2 nd antenna2(t)；
(5) Transmitting signal s on the 1 st transmitting antenna1(t) adding a training sequence p before1(t), obtaining the transmitting signal s with training sequence on the 1 st transmitting antennap1(t) transmitting signal s on the 2 nd transmitting antenna2(t) adding a training sequence p before2(t), obtaining the transmitting signal s with training sequence on the 2 nd transmitting antennap2(t) wherein p1(t)、p2(t) all have a length of Lp；
(6) Two pieces are transmittedTransmitting signal s with training sequence on antennap1(t) and sp2(t) obtaining a receiving signal r (t) on a receiving antenna at a receiving end through a flat fading channel;
r(t)＝h1sp1(t)+h2sp2(t)+n(t)
h1for the 1 st transmitting antenna to receiving antenna flat fading channel response, h2Flat fading channel response for the 2 nd transmit antenna to the receive antenna;
(7) using training sequence of received signal r (t) on receiving antenna to make channel estimation:
(7a) dividing the training sequence p (t) on the received signal into
Figure BDA0002889302550000031
Segment interval with duration of 2TsCalculating the confidence level delta of the nth section of the training sequence p (t) on the received signali,n：
Figure BDA0002889302550000032
Figure BDA0002889302550000033
(7b) The reliability δ obtained from (7a)i,nTraining sequence p in (1) and (5)1(t)、p2And (t) calculating the average channel response estimated value from the ith transmitting antenna to the receiving antenna according to the received signal r (t) in (t) and (6)
Figure BDA0002889302550000034
Figure BDA0002889302550000035
Compared with the prior art, the invention has the following advantages:
firstly, the method comprises the following steps: because the invention introduces the pulse amplitude decomposition before the STBC coding of the signal, the complexity of the receiving end is reduced compared with the prior Viterbi demodulation while approaching the CPM signal as much as possible, the realization is simple, and the simulation result shows that the signal decomposed by the amplitude modulation pulse is completely consistent with the signal generated by the original MSK modulation, and the energy is not lost after the approach.
Secondly, the method comprises the following steps: the invention combines the STBC block coding requirement and the CPM signal characteristic to add the phase continuous symbol, maintains the MSK signal phase continuity, and simultaneously reduces the reduction of the frequency spectrum utilization rate caused by adding the phase continuous symbol to the maximum extent.
Thirdly, the method comprises the following steps: when the invention estimates the flat fading channel by using the training sequence, the channel estimation is more accurate because the training sequence credibility is introduced to take weighted average for the received training sequence segmental estimation, and the channel fading factor obtained by estimation is used for restoring the transmitted signal at the receiving end, so that the signal-to-noise ratio of the improved channel estimation is improved by 0.2dB compared with the signal-to-noise ratio when the bit error rate of the existing channel estimation reaches 10 e-6.
Drawings
FIG. 1 is a diagram of a MIMO-MSK system scenario for use with the present invention;
FIG. 2 is a flow chart of an implementation of the present invention;
FIG. 3 is a time comparison of the present invention with a prior art channel estimation;
FIG. 4 is a graph comparing an AM pulse decomposition modulated signal of the present invention with a conventional MSK modulated signal;
fig. 5 is a comparison of error performance curves of the channel estimation of the present invention and the existing channel estimation algorithm.
Detailed Description
Embodiments and effects of the present invention will be further described below with reference to the accompanying drawings.
Referring to fig. 1, an application scenario of this example is a MIMO-MSK system model, where the system includes a transmitting end and a receiving end, and a flat fading channel is used as a channel. Wherein:
the transmitting end sequentially adds phase continuous symbols, amplitude modulation pulse decomposition and STBC coding to a binary data bit sequence, adds a cyclic prefix and finally adds a training sequence to form a transmitting signal;
at a receiving end, performing channel estimation by using the received signal;
referring to fig. 2, the specific implementation steps of this example are as follows:
step 1, generating a transmitted modulation signal.
(1.1) constructing a randomly generated binary bit sequence data frame at a transmitting end
Figure BDA0002889302550000041
Duration per bit of TsThe bit sequence
Figure BDA0002889302550000042
The length L is 3994 bits,
Figure BDA0002889302550000043
expressed as:
Figure BDA0002889302550000044
wherein d ishTo represent
Figure BDA0002889302550000045
The h-th bit;
(1.2) data frame constructed by (1.1)
Figure BDA0002889302550000046
Performing block processing with length of each block being Ld1997, cyclic prefix length LcpGet 400 data frame on the 1 st transmitting antenna
Figure BDA0002889302550000047
Data frame on 2 nd transmitting antenna
Figure BDA0002889302550000048
Then will be
Figure BDA0002889302550000049
Are respectively divided into three sub data blocks：
Figure BDA00028893025500000410
Figure BDA00028893025500000411
Wherein, the 1 st sub-data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000412
in the formula diTo represent
Figure BDA00028893025500000413
The ith bit in the bit, i is more than or equal to 1 and less than or equal to Lcp-1；
The 2 nd sub data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000414
in the formula djTo represent
Figure BDA00028893025500000415
Middle j-th bit, Lcp≤j≤Ld-Lcp+1；
The 3 rd sub-data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000416
in the formula dkTo represent
Figure BDA00028893025500000417
Middle k bit, Ld-Lcp+2≤k≤Ld；
The 1 st sub-data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000051
in the formula dlTo represent
Figure BDA0002889302550000052
Middle L bit, Ld+1≤l≤Ld+Lcp-1；
The 2 nd sub data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000053
in the formula dmTo represent
Figure BDA0002889302550000054
M-th bit, Ld+Lcp≤m≤2Ld-Lcp+1；
The 3 rd sub-data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000055
in the formula dnTo represent
Figure BDA0002889302550000056
Middle nth bit 2Ld-Lcp+2≤n≤2Ld；
(1.3) calculating the phase continuation symbol dxPhase continuation symbol at tail of ith sub-data block on nth transmitting antenna
Figure BDA0002889302550000057
Figure BDA0002889302550000058
Wherein
Figure BDA0002889302550000059
For the L bit, L, of the ith sub-data block on the nth transmitting antennan,iThe length of the ith sub-data block on the nth transmitting antenna is obtained;
(1.4) addition of dxThe pre-modulated data sequence on the 1 st transmitting antenna
Figure BDA00028893025500000510
And a firstPre-modulated data sequence on 2 transmitting antennas
Figure BDA00028893025500000511
The following were used:
Figure BDA00028893025500000512
Figure BDA00028893025500000513
(1.5) carrying out pulse amplitude decomposition on the premodulation data added with the phase continuous symbols to obtain the 1 st antenna modulation signal sm,1(t) and 2 nd antenna modulation signal sm,2(t) are respectively represented as follows:
Figure BDA00028893025500000514
Figure BDA00028893025500000515
wherein
Figure BDA00028893025500000516
Denotes the modulation index, Lo＝Ld+ 3-2000 denotes the modulation signal length,
Figure BDA00028893025500000517
to represent
Figure BDA00028893025500000518
The upper i-th bit of the data,
Figure BDA00028893025500000519
to represent
Figure BDA00028893025500000520
Upper ith bit, c0(t) isThe shape function, expressed as follows:
Figure BDA0002889302550000061
(1.6) the tail length of the modulation signal on the first transmitting antenna is LcpCopying 400 data as cyclic prefix to the head of the 1 st transmitting antenna modulation signal to obtain a modulation signal s added with the cyclic prefixm1(t)：
Figure BDA0002889302550000062
Modulating the 2 nd transmitting antenna with the tail length of LcpThe data is copied to the head of the modulation signal of the 2 nd transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm2(t)：
Figure BDA0002889302550000063
(1.7) adding the cyclic prefix to the 1 st transmitting antennam1(t) and modulated signal s with cyclic prefix added to 2 nd transmitting antennam2(t) space-time block coding to obtain the transmission signal s on the 1 st transmitting antenna1(t) and the transmission signal s on the 2 nd transmitting antenna2(t)，s1(t)、s2(t) are respectively represented as follows:
s1(t)＝[sm1(t) sm2(t)]
Figure BDA0002889302550000064
and 2, adding training sequences to the transmitting signals of the two transmitting antennas.
(2.1) the lengths produced are all LpDuration of Tp＝LpTsThe 1 st transmitting antenna transmits a training sequence p of signals1(t) and training sequence p of the 2 nd transmitting antenna transmitting signal2(t), the training sequence in this example is:
[1,-1,1,-1,...,1,-1]，Lp＝100；
(2.2) transmitting the signal s at the 1 st transmitting antenna1(t) and 2 nd transmitting antenna transmitting signal s2Before (t), the training sequences generated in (2.1) are added respectively to obtain a transmitting signal s with the training sequences on the 1 st transmitting antennap1(t) and the transmitted signal s with training sequence on the 2 nd transmitting antennap2(t)：
sp1(t)＝[p1(t) s1(t)]
sp2(t)＝[p2(t) s2(t)]。
Step 3, obtaining a receiving signal r (t) on a receiving antenna
Transmitting signal s with training sequence on the 1 st transmitting antennap1(t) flat fading channel response h to receive antenna via the 1 st transmit antenna1Reaches a receiving antenna to obtain a signal h after fading channel response1sp1(t)；
Transmitting signal s with training sequence on 2 nd transmitting antennap2(t) flat fading channel response h to receive antenna via 2 nd transmit antenna2Reaches a receiving antenna to obtain a signal h after fading channel response2sp2(t)；
The receiving antenna superposes the signals of the two transmitting antennas after the flat fading channel response to obtain a receiving signal r (t);
r(t)＝h1sp1(t)+h2sp2(t)+n(t)
wherein n (t) is additive white Gaussian noise.
And 4, the receiving end obtains the received signal and estimates the channel.
In an emulated system, the experienced fading channel response h1、h2Unknown and not directly measurable, but the receiving signal after the flat fading channel can be obtained on the receiving antenna of the receiving end, and the receiving signal can be utilizedTraining sequence p (t) and training sequence p of transmitting signal on ith transmitting antennai(t) estimating the fading channel response, which is achieved as follows:
(4.1) dividing the training sequence p (t) on the received signal into
Figure BDA0002889302550000071
Segment interval with duration of 2TsCalculating the reliability delta between the n-th segments of the training sequence p (t) on the received signali,n：
Figure BDA0002889302550000072
Figure BDA0002889302550000073
Wherein p isi(t) is the training sequence of the nth interval on the ith transmitting antenna, and p (t) is the training sequence of the nth interval on the receiving signal;
(4.2) calculating the estimated channel response of the ith transmitting antenna to the receiving antenna under the condition of neglecting the influence of noise
Figure BDA0002889302550000074
Figure BDA0002889302550000075
Wherein L ispFor the length of the transmit-end training sequence, pi(T) is the training sequence on the ith transmit antenna, r (T) is the received signal on the receive antenna, TsFor each duration of a bit of the data stream,
Figure BDA0002889302550000081
is the conjugate of the training sequence on the ith transmit antenna.
The effects of the present invention can be further illustrated by the following simulations:
firstly, setting simulation system parameters
MATLAB R2020a simulation software is used, the MIMO-MSK system is a double-transmitting single-receiving system, and the length of original data of a transmitting end is 3994 bits; the training sequence length is 100 bits, the cyclic prefix length is 400 bits, and the duration of each bit is 2 x 10 e-7.
The multipath channel parameters apply flat fading to the signal using the comm.
Second, simulation content
Simulation 1, comparing the running time of the channel estimation of the present invention with the existing STBC coding channel estimation system under the conditions of signal-to-noise ratio of 1dB, 2dB, 3dB, 4dB, 5dB, 6dB, the result is shown in FIG. 3.
As can be seen from fig. 3, the existing channel estimation running time exceeds the channel estimation algorithm of the present invention by 30% in the case of a signal-to-noise ratio of 5dB, and exceeds the estimation algorithm running time of the present invention by 40% in the case of 6dB, indicating that the estimation time of the present invention is short.
Simulation 2 compares the am-pwm signal with the existing MSK signal under the condition of a signal-to-noise ratio of 6dB, and the result is shown in fig. 4. It can be seen from fig. 4 that the two modulation signals are completely identical, which indicates that the modulation signal obtained after the decomposition of the amplitude modulation pulse of the present invention has no loss of energy with the original MSK modulation signal.
Simulation 3, comparing the error code performance of the channel estimation method of the invention and the existing channel estimation method on the MIMO-MSK system under the condition of the signal-to-noise ratio of 1dB to 12dB, the result is shown in FIG. 5.
As can be seen from FIG. 5, the error code performance of the channel estimation of the invention is better than that of the existing channel estimation algorithm, when the signal-to-noise ratio is 10dB, the signal-to-noise ratio is improved by 0.2dB when the error code rate of the channel estimation of the invention reaches 10e-6 compared with the existing channel estimation, which shows that the channel response estimated by the invention is more accurate.

Claims (9)

1.一种基于平坦衰落信道下空时块编码MSK系统的信道估计方法，其特征在于，包括如下：1. a channel estimation method based on a space-time block coding MSK system under a flat fading channel, is characterized in that, comprises as follows: (1)在空时编码最小频移键控STBC-MSK系统发送端随机生成的一个长度L比特的数据帧
Figure FDA0002889302540000011
每比特持续时间为Ts；(1) A data frame of length L bits randomly generated by the transmitter of the minimum frequency shift keying STBC-MSK system in space-time coding
Figure FDA0002889302540000011
The duration of each bit is T s ; (2)将数据帧分块到两根发射天线，得到每根天线的数据帧
Figure FDA0002889302540000012
长度为
Figure FDA0002889302540000013
再把每根天线上的数据帧分为三个子数据块
Figure FDA0002889302540000014
并在每个子数据块尾部计算并添加相位连续符号dx，得到第1根天线预调制数据块
Figure FDA0002889302540000015
第2根天线预调制数据块
Figure FDA0002889302540000016
(2) Divide the data frame into two transmitting antennas to obtain the data frame of each antenna
Figure FDA0002889302540000012
length is
Figure FDA0002889302540000013
Then divide the data frame on each antenna into three sub-data blocks
Figure FDA0002889302540000014
And calculate and add the phase continuous symbol d x at the end of each sub-data block to obtain the first antenna pre-modulation data block
Figure FDA0002889302540000015
2nd antenna premodulation block
Figure FDA0002889302540000016
 (3)对添加相位连续符号后的预调制数据块
Figure FDA0002889302540000017
和
Figure FDA0002889302540000018
进行调幅脉冲分解，得到两根天线上的调制信号sm,1(t)、sm,2(t)；(3) For the premodulated data block after adding phase continuous symbols
Figure FDA0002889302540000017
and
Figure FDA0002889302540000018
Perform AM pulse decomposition to obtain modulated signals s m,1 (t) and s m,2 (t) on the two antennas; (4)在两根天线上的调制信号sm,1(t)、sm,2(t)头部分别添加长度为Lcp的循环前缀，得到sm1(t)、sm2(t)；并对sm1(t)、sm2(t)进行STBC编码，得到第1根天线上的发射信号s1(t)和第2根天线上的发射信号s2(t)；(4) Add a cyclic prefix of length L cp to the modulated signals s m,1 (t) and s m,2 (t) on the two antennas, respectively, to obtain s m1 (t) and s m2 (t) ; And carry out STBC coding on s m1 (t), s m2 (t), obtain the transmission signal s 1 (t) on the 1st antenna and the transmission signal s 2 (t) on the 2nd antenna; (5)在第1根发射天线上的发射信号s1(t)前加入训练序列p1(t)，得到第1根发射天线上带有训练序列的发射信号sp1(t)，在第2根发射天线上的发射信号s2(t)前加入训练序列p2(t)，得到第2根发射天线上带有训练序列的发射信号sp2(t)，其中p1(t)、p2(t)的长度均为Lp；(5) Add the training sequence p 1 (t) before the transmit signal s 1 (t) on the first transmit antenna to obtain the transmit signal s p1 (t) with the training sequence on the first transmit antenna. The training sequence p 2 (t) is added before the transmit signal s 2 (t) on the two transmit antennas, and the transmit signal sp 2 (t) with the training sequence on the second transmit antenna is obtained, where p 1 (t), The lengths of p 2 (t) are all L p ; (6)将两根发射天线上带有训练序列的发射信号sp1(t)和sp2(t)通过平坦衰落信道，在接收端得到接收天线上的接收信号r(t)；(6) Pass the transmit signals sp1 (t) and sp2 (t) with the training sequence on the two transmit antennas through the flat fading channel, and obtain the receive signal r(t) on the receive antenna at the receiving end; r(t)＝h1sp1(t)+h2sp2(t)+n(t)r(t)=h 1 s p1 (t)+h 2 s p2 (t)+n(t) h1为第1根发射天线到接收天线上的平坦衰落信道响应，h2为第2根发射天线到接收天线上的平坦衰落信道响应，n(t)为加性高斯白噪声；h 1 is the flat fading channel response from the first transmitting antenna to the receiving antenna, h 2 is the flat fading channel response from the second transmitting antenna to the receiving antenna, and n(t) is additive white Gaussian noise; (7)利用接收天线上接收信号r(t)的训练序列进行信道估计：(7) Use the training sequence of the received signal r(t) on the receiving antenna to estimate the channel: (7a)将接收信号上的训练序列p(t)分为
Figure FDA0002889302540000021
段区间，每段区间持续时间为2Ts，计算接收信号上训练序列p(t)第n段区间的可信度δi,n：(7a) Divide the training sequence p(t) on the received signal into
Figure FDA0002889302540000021
segment interval, the duration of each segment is 2T s , calculate the reliability δ i,n of the nth segment interval of the training sequence p(t) on the received signal:
Figure FDA0002889302540000022
Figure FDA0002889302540000022
 p(t)＝r(t)2(n-1)Ts≤t＜2nTs
Figure FDA0002889302540000023
p(t)=r(t)2(n-1)T s ≤t<2nT s
Figure FDA0002889302540000023
 (7b)根据(7a)得到的可信度δi,n以及(5)中的训练序列p1(t)、p2(t)和(6)中的接收信号r(t)，计算第i根发射天线到接收天线上平均信道响应估计值
Figure FDA0002889302540000024
(7b) According to the reliability δ i,n obtained in (7a) and the received signals r(t) in the training sequences p 1 (t), p 2 (t) and (6) in (5), calculate the first Average channel response estimates from i transmit antennas to receive antennas
Figure FDA0002889302540000024
Figure FDA0002889302540000025
Figure FDA0002889302540000025
 2.根据权利要求1所述方法，其中(1)中的数据帧
Figure FDA0002889302540000026
是一个二进制随机序列，长度L＝3994。2. The method according to claim 1, wherein the data frame in (1)
Figure FDA0002889302540000026
is a binary random sequence with length L=3994. 3.根据权利要求1所述方法，其中(2)中的三个子数据块，长度分别为L1＝Lcp-1、L2＝Ld-2Lcp+2、L3＝Lcp-1，其中Lcp为循环前缀长度。3. The method according to claim 1, wherein the three sub-data blocks in (2) are L 1 =L cp -1, L 2 =L d -2L cp +2, L 3 =L cp -1 respectively , where L cp is the cyclic prefix length. 4.根据权利要求1所述方法，其中(2)中每个子数据块尾部添加的相位连续符号dxn,i通过下式确定：4. The method according to claim 1, wherein the phase continuous symbol d xn,i added at the end of each sub-data block in (2) is determined by the following formula:
Figure FDA0002889302540000027
Figure FDA0002889302540000027
 其中
Figure FDA0002889302540000028
为第n根发射天线上第i个子数据块的第l位比特，Ln,i为第n根发射天线上第i个数据块的长度。in
Figure FDA0002889302540000028
is the l-th bit of the i-th sub-data block on the n-th transmit antenna, and L n,i is the length of the i-th data block on the n-th transmit antenna. 5.根据权利要求1所述的方法，其中(3)中得到的第1根天线调制信号sm,1(t)和第2根天线调制信号sm,2(t)分别表示如下：5. The method according to claim 1, wherein the first antenna modulation signal s m,1 (t) and the second antenna modulation signal s m,2 (t) obtained in (3) are respectively expressed as follows:
Figure FDA0002889302540000031
Figure FDA0002889302540000031
Figure FDA0002889302540000032
Figure FDA0002889302540000032
 其中
Figure FDA0002889302540000033
表示调制指数，Lo＝Ld+3表示调制信号长度，
Figure FDA0002889302540000034
表示
Figure FDA0002889302540000035
上第i位比特，
Figure FDA0002889302540000036
表示
Figure FDA0002889302540000037
上第i位比特，c0(t)为成形函数，表示如下：in
Figure FDA0002889302540000033
represents the modulation index, L o =L d +3 represents the length of the modulated signal,
Figure FDA0002889302540000034
express
Figure FDA0002889302540000035
the i-th bit above,
Figure FDA0002889302540000036
express
Figure FDA0002889302540000037
On the i-th bit, c 0 (t) is the shaping function, which is expressed as follows:
Figure FDA0002889302540000038
Figure FDA0002889302540000038
 6.根据权利要求1所述的方法，其中(4)中在两个调制信号头部添加长度为Lcp的循环前缀，实现如下：6. The method according to claim 1, wherein in (4), a cyclic prefix with a length of L cp is added to the two modulated signal headers, and the implementation is as follows: 将第1根发射天线调制信号尾部长度为Lcp的数据作为循环前缀复制到第1根发射天线调制信号头部，得到添加循环前缀的调制信号sm1(t)：Copy the data whose tail length is L cp of the modulated signal of the first transmit antenna as a cyclic prefix to the head of the modulated signal of the first transmit antenna, and obtain the modulated signal s m1 (t) with a cyclic prefix added:
Figure FDA0002889302540000039
Figure FDA0002889302540000039
 将第2根发射天线调制信号尾部长度为Lcp的数据作为循环前缀复制到第2根发射天线调制信号头部,得到添加循环前缀的调制信号sm2(t)：Copy the data whose tail length is L cp of the modulated signal of the second transmit antenna as a cyclic prefix to the head of the modulated signal of the second transmit antenna to obtain the modulated signal s m2 (t) with a cyclic prefix added:
Figure FDA00028893025400000310
Figure FDA00028893025400000310
 其中，Lo＝Ld+3表示调制信号长度。Wherein, L o =L d +3 represents the length of the modulated signal. 7.根据权利要求1所述的方法，其中(4)中第1根天线上的发射信号s1(t)、第2根天线上发射信号s2(t)，分别表示如下：7. The method according to claim 1, wherein in (4), the transmitted signal s 1 (t) on the first antenna and the transmitted signal s 2 (t) on the second antenna are respectively represented as follows: s1(t)＝[sm1(t) sm2(t)]s 1 (t)=[s m1 (t) s m2 (t)]
Figure FDA0002889302540000041
Figure FDA0002889302540000041
 8.根据权利要求1所述的方法，其中(5)中两个发射信号训练序列p1(t)、p2(t)的内部结构均为[1,-1,1,-1,...,1,-1]，其长度Lp为50≤Lp≤1000的偶数。8. The method according to claim 1, wherein the internal structures of the two transmission signal training sequences p 1 (t) and p 2 (t) in (5) are both [1,-1,1,-1,. ..,1,-1], whose length L p is an even number of 50≤L p ≤1000. 9.根据权利要求1所述的方法，其中(5)中第1根天线上的带有训练序列的发射信号sp1(t)和第2根天线上的带有训练序列的发射信号sp2(t)分别表示如下：9. The method according to claim 1, wherein in (5) the transmitted signal sp1 (t) with the training sequence on the first antenna and the transmitted signal sp2 with the training sequence on the second antenna (t) are represented as follows: sp1(t)＝[p1(t) s1(t)]s p1 (t)=[p 1 (t) s 1 (t)] sp2(t)＝[p2(t) s2(t)]s p2 (t)=[p 2 (t) s 2 (t)] 其中s1(t)为第1根天线上的发射信号，s2(t)为第2根天线上发射信号，p1(t)为第1根天线上的训练序列，p2(t)为第2根天线上的训练序列。where s 1 (t) is the transmitted signal on the first antenna, s 2 (t) is the transmitted signal on the second antenna, p 1 (t) is the training sequence on the first antenna, and p 2 (t) is the training sequence on the second antenna.
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