CN112736946A - Dead-zone compensation method and device for energy storage converter based on quasi-resonant controller - Google Patents
Dead-zone compensation method and device for energy storage converter based on quasi-resonant controller Download PDFInfo
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- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for AC mains or AC distribution networks
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
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Abstract
本发明涉及电力电子技术领域，具体提供了一种基于准谐振控制器的储能变流器死区补偿方法及装置，旨在解决储能变流器的自适应、高精度死区补偿的技术问题。包括：基于负载侧三相交流电压信号对应的d/q轴电压分量，利用基波控制器和准谐振控制器获取电压调制信号；将所述电压调制信号作为SVPWM模块的输入，得到所述SVPWM模块输出的储能变流器的开关管驱动信号；该方案实现了储能变流器自适应、高精度的死区补偿，从而提高变流器控制性能和带载能力。
The invention relates to the technical field of power electronics, and specifically provides a method and device for dead zone compensation of an energy storage converter based on a quasi-resonant controller, aiming at solving the self-adaptive and high-precision dead zone compensation technology of the energy storage converter question. Including: using the fundamental wave controller and the quasi-resonant controller to obtain a voltage modulation signal based on the d/q axis voltage component corresponding to the three-phase AC voltage signal on the load side; using the voltage modulation signal as the input of the SVPWM module to obtain the SVPWM The switch tube driving signal of the energy storage converter output by the module; this scheme realizes the self-adaptive and high-precision dead zone compensation of the energy storage converter, thereby improving the control performance and load capacity of the converter.
Description
Technical Field
The invention relates to the field of power electronics, in particular to a dead-time compensation method and device for an energy storage converter based on a quasi-resonant controller.
Background
The continuous and reliable supply of energy, which is the power for the operation of industrial society, is a great problem in the development of society. With the popularization and the use of new energy, various distributed power supplies such as wind power and photovoltaic power are connected to a power grid, and the ratio of new energy power generation in the total generated energy is increased continuously. In order to solve the problem of new energy consumption and optimize an energy structure, the energy storage system is adopted to convert redundant electric energy into energy in other forms for storage. The energy storage converter is used as an interface between a direct current side battery and an alternating current side power grid/load, realizes the bidirectional energy flow and auxiliary functions, and is a key and core device of the whole energy storage system.
In the control of the energy storage converter, in order to prevent the upper and lower switching tubes of the converter from being directly connected, in-phase control signals are usually set to be in a complementary state, and meanwhile, dead time setting is usually introduced on software in consideration of delay of on-off actions of an IGBT. Although the dead time protects the switching tube, the command voltage cannot strictly modulate the output voltage. In particular, the voltage signal is caused to contain 6 times and multiples of the ripple component, which affects the control system of the energy storage converter.
Currently, the dead zone compensation methods applied more are mainly divided into two categories: one is a time compensation method, which judges whether the on-time of the switching tube is prolonged or shortened by judging the current polarity flowing through the switching tube, and then directly adjusts the on-time and off-time of the pulse signal; the other method is a voltage compensation method, wherein a sector is determined according to the current polarity, and then corresponding voltage compensation quantity is superposed on the amplitude of the modulation wave. However, these methods have two major disadvantages:
1) dead zone compensation is carried out in an open-loop mode, and self-adaptive dead zone compensation cannot be realized due to the limitation of a modulation mode and the influence of dead zone time setting;
2) on one hand, the compensation process depends on current polarity judgment, and on the other hand, the compensation quantity is an estimated average value, so that high-precision dead zone compensation cannot be realized.
Disclosure of Invention
In order to overcome the above drawbacks, the present invention is proposed to provide a dead-time compensation method and apparatus for an energy storage converter based on a quasi-resonant controller, which solves or at least partially solves the technical problem of adaptive, high-precision dead-time compensation of the energy storage converter.
In a first aspect, a dead-time compensation method for a quasi-resonant controller-based energy storage converter is provided, and the dead-time compensation method for the quasi-resonant controller-based energy storage converter comprises the following steps:
acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
and taking the voltage modulation signal as the input of an SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module.
Preferably, the obtaining of the voltage modulation signal by using the fundamental wave controller and the quasi-resonant controller based on the d-axis voltage component and the q-axis voltage component corresponding to the load-side three-phase ac voltage signal includes:
taking a d/q axis voltage component corresponding to the three-phase alternating voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
respectively taking d/q axis voltage components corresponding to the three-phase alternating voltage signal at the load side as the input of n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
converting the superposed voltage components output by the fundamental wave controller and the superposed voltage components output by the n quasi-resonant controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
Further, the mathematical model of the quasi-resonant controller is as follows:
in the above formula, udxD-axis voltage component, u, output for the x-th quasi-resonant controllerqxQ-axis voltage component, K, output for the x-th quasi-resonant controllerrxFor the x-th quasi-resonant controller coefficient, ωcxIs the cut-off frequency, ω, of the x-th quasi-resonant controlleroFor the fundamental frequency, x ∈ [1, n ]]，udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqAnd s is a Laplace operator, and is a q-axis voltage component corresponding to the three-phase alternating voltage signal on the load side.
Preferably, the fundamental wave controller is composed of a current loop regulator and a voltage loop regulator.
Further, the mathematical model of the current loop regulator is calculated as follows:
the mathematical model calculation for the voltage loop regulator is as follows:
in the above formula, id1D-axis component, i, of the output of the voltage-loop regulatorq1Q-axis component, K, of the output of the voltage loop regulatorupIs the proportional term coefficient, K, of the voltage loop regulatoruiFor the integral term coefficient, u, of the voltage loop regulatordrefFor d-axis of voltage-loop regulatorGiven value of quantity uqrefFor setting the q-component of the voltage-loop regulator, udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqQ-axis voltage component u corresponding to three-phase AC voltage signal on load sided1D-axis component, u, being output from fundamental controllerq1Q-axis component, K, output of fundamental controlleripIs the current loop proportional term coefficient, KiiIs a current loop integral term coefficient, idrefSetting value i for d-axis component of current loop regulatorqrefAnd (4) setting a value for the q-axis component of the current loop regulator, wherein s is a Laplace operator.
Further, before the obtaining of the voltage modulation signal by the fundamental wave controller and the quasi-resonant controller based on the d/q axis voltage component corresponding to the load side three-phase alternating-current voltage signal, the method further includes:
and transforming the load side three-phase alternating voltage signal into a d-q coordinate system synchronously rotating with the fundamental voltage to obtain a d/q axis voltage component corresponding to the load side three-phase alternating voltage signal.
In a second aspect, a quasi-resonant controller-based energy storage converter dead-time compensation device is provided, which includes:
the acquisition module is used for acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
and the driving signal generation module is used for taking the voltage modulation signal as the input of the SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module.
Preferably, the obtaining module includes:
the first generating unit is used for taking a d/q axis voltage component corresponding to the three-phase alternating-current voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
the second generating unit is used for respectively taking d/q axis voltage components corresponding to the three-phase alternating-current voltage signals on the load side as the input of the n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
the third generating unit is used for converting the superposed voltage components output by the fundamental wave controller and the voltage components output by the n quasi-resonance controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
Preferably, the apparatus further comprises:
the device comprises an abd/dq conversion module, a fundamental voltage conversion module and a control module, wherein the abd/dq conversion module is used for converting a load side three-phase alternating voltage signal into a d-q coordinate system synchronously rotating with the fundamental voltage to obtain a d/q axis voltage component corresponding to the load side three-phase alternating voltage signal.
In a third aspect, a storage device is provided, wherein a plurality of program codes are stored in the storage device, and the program codes are suitable for being loaded and executed by a processor to execute the dead-zone compensation method for the energy storage converter based on the quasi-resonant controller in any one of the above technical solutions.
In a fourth aspect, a control device is provided, which comprises a processor and a storage device, wherein the storage device is adapted to store a plurality of program codes, and the program codes are adapted to be loaded and run by the processor to execute the dead-zone compensation method of the quasi-resonant controller based energy storage converter according to any one of the above technical solutions.
One or more technical schemes of the invention at least have one or more of the following beneficial effects:
in the embodiment, firstly, a voltage modulation signal is obtained by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side; then, the voltage modulation signal is used as the input of an SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module; the scheme is based on a fundamental wave controller and a quasi-resonance controller, and a control loop adopts a closed-loop mode to perform dead-zone compensation on the converter, so that the dead-zone compensation is not influenced by the limitation of a modulation mode and the dead-zone time setting, and the self-adaptive compensation can be realized;
furthermore, an additional hardware detection circuit or a complex current polarity judgment algorithm is not needed in the compensation process, a filter is not needed, the compensation quantity is automatically calculated according to the voltage ripple deviation, and therefore the compensation method has high compensation precision and can be applied to the application occasions of the voltage source type converter, the high-precision dead-zone compensation of the energy storage converter is realized, and the control performance and the loading capacity of the converter are improved.
Drawings
FIG. 1 is a schematic flow chart of main steps of a dead-time compensation method of an energy storage converter based on a quasi-resonant controller according to an embodiment of the invention;
fig. 2 is a schematic view of an application scenario of an embodiment related to the technical solution of the present invention;
FIG. 3 is a block diagram of a quasi-resonant controller according to an embodiment of the present invention;
FIG. 4 is a simulated waveform diagram of dead-time compensation using a conventional algorithm-voltage compensation method according to an embodiment of the present invention;
FIG. 5 is a simulated waveform diagram for dead-zone compensation according to the embodiment of the present invention;
FIG. 6 is a harmonic frequency spectrum diagram of the output voltage of the energy storage converter without dead-zone compensation according to an embodiment of the present invention;
FIG. 7 is a voltage spectrum diagram of dead-zone compensation by voltage compensation according to an embodiment of the present invention;
FIG. 8 is a graph of a voltage spectrum for dead-zone compensation according to an embodiment of the present invention;
fig. 9 is a main structural block diagram of a dead-zone compensation device of a storage converter based on a quasi-resonant controller according to an embodiment of the invention.
Detailed Description
The following describes embodiments of the present invention in further detail with reference to the accompanying drawings.
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
In order to solve the problem that the existing method is difficult to realize self-adaption and high-precision dead zone compensation of the energy storage converter, the embodiment provides the dead zone compensation method of the energy storage converter based on the quasi-resonant controller, which can be applied to the application occasions of the voltage source type converter, and realizes self-adaption and high-precision dead zone compensation of the energy storage converter, thereby improving the control performance and the loading capacity of the converter.
In the embodiment of the invention, referring to fig. 1, fig. 1 is a schematic flow chart of main steps of a dead-zone compensation method of an energy storage converter based on a quasi-resonant controller according to an embodiment of the invention. As shown in fig. 1, the dead-time compensation method for the energy storage converter based on the quasi-resonant controller in the embodiment of the present invention mainly includes the following steps:
step S101: converting the three-phase alternating voltage signal at the load side into a d-q coordinate system synchronously rotating with fundamental voltage to obtain a d/q axis voltage component corresponding to the three-phase alternating voltage signal at the load side;
step S102: acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
step S103: the voltage modulation signal is used as the input of an SVPWM module to obtain a switching tube driving signal of an energy storage converter output by the SVPWM module;
in the present embodiment, the step S101 may be implemented by an abd/dq converter;
in one embodiment, the mathematical model of the abd/dq converter may be as follows:
in the above formula, t isEnergy converter operating time, omegarIs the fundamental voltage angular frequency, ua、ub、ucAre three-phase AC voltage signals u on the load side, respectivelydD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqA q-axis voltage component corresponding to the three-phase alternating current voltage signal at the load side;
in this embodiment, the step S102 may be implemented by using the following processes:
taking a d/q axis voltage component corresponding to the three-phase alternating voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
respectively taking d/q axis voltage components corresponding to the three-phase alternating voltage signal at the load side as the input of n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
converting the superposed voltage components output by the fundamental wave controller and the superposed voltage components output by the n quasi-resonant controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
In one embodiment, the mathematical model of the quasi-resonant controller is as follows:
in the above formula, udxD-axis voltage component, u, output for the x-th quasi-resonant controllerqxQ-axis voltage component, K, output for the x-th quasi-resonant controllerrxFor the x-th quasi-resonant controller coefficient, ωcxIs the cut-off frequency, ω, of the x-th quasi-resonant controlleroFor the fundamental frequency, x ∈ [1, n ]]，udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqAnd s is a Laplace operator, and is a q-axis voltage component corresponding to the three-phase alternating voltage signal on the load side.
In one embodiment, the fundamental controller is comprised of a current loop regulator and a voltage loop regulator.
The mathematical model calculation formula of the current loop regulator is as follows:
the mathematical model calculation for the voltage loop regulator is as follows:
in the above formula, id1D-axis component, i, of the output of the voltage-loop regulatorq1Q-axis component, K, of the output of the voltage loop regulatorupIs the proportional term coefficient, K, of the voltage loop regulatoruiFor the integral term coefficient, u, of the voltage loop regulatordrefFor setting the d-axis component of the voltage-loop regulatorqrefFor setting the q-component of the voltage-loop regulator, udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqQ-axis voltage component u corresponding to three-phase AC voltage signal on load sided1D-axis component, u, being output from fundamental controllerq1Q-axis component, K, output of fundamental controlleripIs the current loop proportional term coefficient, KiiIs a current loop integral term coefficient, idrefSetting value i for d-axis component of current loop regulatorqrefAnd (4) setting a value for the q-axis component of the current loop regulator, wherein s is a Laplace operator.
It should be noted that, although the foregoing embodiments describe each step in a specific sequence, those skilled in the art will understand that, in order to achieve the effect of the present invention, different steps do not necessarily need to be executed in such a sequence, and they may be executed simultaneously (in parallel) or in other sequences, and these changes are all within the protection scope of the present invention.
Based on the above solution, the present invention provides an application scenario of an embodiment related to the technical solution of the present invention, referring to fig. 2, which is a diagramThe application scenario diagram of an embodiment related to the technical solution of the present invention includes two parts, namely a hardware loop and a control loop. The hardware loop contains an energy storage battery UdcThe bridge arm-side three-phase current transformer comprises a voltage source type converter, a current transformer, an output LC filter, a voltage transformer and a load, wherein the voltage source type converter is composed of a three-phase bridge type fully-controlled power electronic device, the current transformer collects three-phase current signals at a bridge arm side, the voltage transformer collects three-phase voltage signals at a load side, and the load can be a resistor, a capacitor, an inductor or a nonlinear load. The control loop is divided into two parts of fundamental wave control and harmonic wave control, and the fundamental wave controller consists of a current loop regulator and a voltage loop regulator. The given value of the voltage loop regulator is a voltage target control value udqrefThe feedback value is a three-phase voltage signal u collected by the voltage transformeroThe position voltage is regulated by adopting a proportional integral regulator (PI), and the PI expression is as follows:
wherein, KupIs the proportional term coefficient, K, of the voltage loop regulatoruiIs the voltage loop regulator integral term coefficient.
Further, the mathematical model of the voltage loop regulator is calculated as follows:
the given value of the current loop is the output value i of the voltage loop regulatordqrefAnd the feedback value is a three-phase current signal i acquired by the current transformerLAnd a proportional integral regulator (PI) is also adopted for position current regulation, and the PI expression is as follows:
further, the mathematical model of the current loop regulator is calculated as follows:
in the above formula, id1D-axis component, i, of the output of the voltage-loop regulatorq1Q-axis component, K, of the output of the voltage loop regulatorupIs the proportional term coefficient, K, of the voltage loop regulatoruiFor the integral term coefficient, u, of the voltage loop regulatordrefFor setting the d-axis component of the voltage-loop regulatorqrefFor setting the q-component of the voltage-loop regulator, udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqQ-axis voltage component u corresponding to three-phase AC voltage signal on load sided1D-axis component, u, being output from fundamental controllerq1Q-axis component, K, output of fundamental controlleripIs the current loop proportional term coefficient, KiiIs a current loop integral term coefficient, idrefSetting value i for d-axis component of current loop regulatorqrefAnd (4) setting a value for the q-axis component of the current loop regulator, wherein s is a Laplace operator.
In this embodiment, the number of times of a pulsating component contained in a three-phase ac voltage signal on the load side is 12, and therefore, the harmonic control is constituted by 2 quasi-resonant controllers, the given value is 0, the three-phase voltage signal collected by the voltage transformer is fed back, and the output is a 6-time and 12-time harmonic modulation signal. And after the harmonic modulation signal and the fundamental modulation signal are superposed, a switching tube trigger signal is obtained through SVPWM.
Fig. 3 is a block diagram of a quasi-resonant controller. The input signal is uinThe output signal is uout，KrFor controller gain, ωcTo cut-off frequency, ωnFor the resonant frequency, ω if the 6 th harmonic is to be suppressedn＝6ωoIf the 12 th harmonic is to be suppressed, then ωn＝12ωo. As can be seen from the figure, the control system contains a frequency ωnS-domain model of the sinusoidal signal, it is thus possible to achieve a corresponding frequency of ω in a given signalnWithout dead-beat tracking of the sinusoidal signal. Quasi-resonance controllerThe transfer function of (a) is:
specifically, in the present embodiment, the d-q axis voltage component u is converted intod、uqRespectively as the input of the first quasi-resonance controller and the second quasi-resonance controller to obtain the output component u of the first quasi-resonance controller and the second quasi-resonance controllerd1、ud2、uq1、uq2：
The mathematical model of the quasi-resonant controller is as follows:
in the above formula, udxD-axis voltage component, u, output for the x-th quasi-resonant controllerqxQ-axis voltage component, K, output for the x-th quasi-resonant controllerrxFor the x-th quasi-resonant controller coefficient, ωcxIs the cut-off frequency, ω, of the x-th quasi-resonant controlleroFor the fundamental frequency, x ∈ [1, n ]]，udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqAnd s is a Laplace operator, and is a q-axis voltage component corresponding to the three-phase alternating voltage signal on the load side.
Superposing the output components of the first quasi-resonance controller and the second quasi-resonance controller with the output component of the fundamental wave controller, and transforming to an alpha-beta static coordinate system to obtain a voltage modulation signal uα、uβ；
Voltage modulated signal uα、uβAnd the output of the energy storage converter is the three-phase alternating voltage after dead zone compensation.
It should be noted that the number of quasi-resonant controllers depends on the dominant harmonic component in the loop, and if the dominant harmonic is 6 th, only the first quasi-resonant controller is needed.
The embodiment of the invention is specifically illustrated by taking a 500kW energy storage converter as an example. The rated power of the energy storage converter is 500kW, the input voltage of the direct current side is 650V, the voltage of the output line is 380V, the switching frequency is 3200Hz, the fundamental wave frequency is 50Hz, the inductance value of the output filter is 0.1mH, and the capacitance value is 80 uF.
Fig. 4 is a simulation waveform of dead-time compensation by using a conventional algorithm-voltage compensation method, which includes voltage compensation amount and 6 th harmonic component from top to bottom. The energy storage converter is put into 500kW load at the moment of 0.01s, dead zone compensation is not carried out at the moment, and the voltage contains obvious 6 th harmonic component. Dead zone compensation was performed at time 0.1s, and it was found that the 6 th harmonic component was attenuated to some extent, but the harmonic component was not yet complete. This is because the compensation amount of the voltage compensation method has a sawtooth shape, and the 6 th harmonic component has a sinusoidal shape, which do not completely match.
Fig. 5 is a simulation waveform for performing dead-zone compensation by using the technical scheme of the present invention, and the dead-zone compensation is performed at 0.1s, so that the voltage compensation amount is a sinusoidal amount, and thus the 6 th harmonic component is attenuated to a minimum value within 0.02 s. Comparing with fig. 4, it is proved that the method of the present patent can adaptively compensate the harmonic component caused by the dead zone effect.
Fig. 6 is a spectrum diagram of harmonic waves of the output voltage of the energy storage converter when no dead zone compensation is performed, the voltage THD exceeds 5%, and the main harmonic components are 5, 7, 11 and 13 times as can be seen from the spectrum diagram. Fig. 7 is a voltage spectrum diagram of dead zone compensation by using a voltage compensation method, wherein the THD is reduced to 3.91%, and meanwhile, the harmonics of 5, 7 and 11 are attenuated to a certain degree, while the harmonic of 13 is almost unchanged. Fig. 8 is a voltage spectrum diagram when dead-zone compensation is performed by using the technical scheme of the invention, the THD is reduced to 2.89%, and meanwhile, 5 th, 7 th, 11 th and 13 th harmonics are attenuated to a large extent. Comparing fig. 6-8, it can be known that the harmonic component caused by the dead zone effect can be compensated with high precision by using the technical solution of the present invention.
Based on the same inventive concept, an embodiment of the present invention further provides a dead-zone compensation apparatus for an energy storage converter based on a quasi-resonant controller, referring to fig. 9, fig. 9 is a main structural block diagram of the dead-zone compensation apparatus for an energy storage converter based on a quasi-resonant controller according to an embodiment of the present invention. As shown in fig. 9, the energy storage converter dead-time compensation apparatus based on the quasi-resonant controller in the embodiment of the present invention mainly includes an abd/dq conversion module, an acquisition module, and a driving signal generation module. In some embodiments, one or more of the abd/dq conversion module, the acquisition module, and the drive signal generation module may be combined together into one module.
In some embodiments, the apparatus includes an abd/dq conversion module for transforming a load-side three-phase ac voltage signal into a d-q coordinate system rotating synchronously with a fundamental voltage to obtain a d/q axis voltage component corresponding to the load-side three-phase ac voltage signal;
the acquisition module is used for acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
and the driving signal generation module is used for taking the voltage modulation signal as the input of the SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module.
Specifically, the obtaining module includes:
the first generating unit is used for taking a d/q axis voltage component corresponding to the three-phase alternating-current voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
the second generating unit is used for respectively taking d/q axis voltage components corresponding to the three-phase alternating-current voltage signals on the load side as the input of the n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
the third generating unit is used for converting the superposed voltage components output by the fundamental wave controller and the voltage components output by the n quasi-resonance controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
In this embodiment, the mathematical model of the quasi-resonant controller is as follows:
in the above formula, udxD-axis voltage component, u, output for the x-th quasi-resonant controllerqxQ-axis voltage component, K, output for the x-th quasi-resonant controllerrxFor the x-th quasi-resonant controller coefficient, ωcxIs the cut-off frequency, ω, of the x-th quasi-resonant controlleroFor the fundamental frequency, x ∈ [1, n ]]，udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqAnd s is a Laplace operator, and is a q-axis voltage component corresponding to the three-phase alternating voltage signal on the load side.
In this embodiment, the fundamental controller is composed of a current loop regulator and a voltage loop regulator.
Wherein, the mathematical model calculation formula of the current loop regulator is as follows:
the mathematical model calculation for the voltage loop regulator is as follows:
in the above formula, id1D-axis component, i, of the output of the voltage-loop regulatorq1Q-axis component, K, of the output of the voltage loop regulatorupIs the proportional term coefficient, K, of the voltage loop regulatoruiFor the integral term coefficient, u, of the voltage loop regulatordrefFor setting the d-axis component of the voltage-loop regulatorqrefFor setting the q-component of the voltage-loop regulator, udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqQ-axis voltage component u corresponding to three-phase AC voltage signal on load sided1D-axis component, u, being output from fundamental controllerq1Q-axis component, K, output of fundamental controlleripIs the current loop proportional term coefficient, KiiIs a current loop integral term coefficient, idrefSetting value i for d-axis component of current loop regulatorqrefAnd (4) setting a value for the q-axis component of the current loop regulator, wherein s is a Laplace operator.
It will be understood by those skilled in the art that all or part of the flow of the method according to the above-described embodiment may be implemented by a computer program, which may be stored in a computer-readable storage medium and used to implement the steps of the above-described embodiments of the method when the computer program is executed by a processor. Wherein the computer program comprises computer program code, which may be in the form of source code, object code, an executable file or some intermediate form, etc. The computer-readable medium may include: any entity or device capable of carrying said computer program code, media, usb disk, removable hard disk, magnetic diskette, optical disk, computer memory, read-only memory, random access memory, electrical carrier wave signals, telecommunication signals, software distribution media, etc. It should be noted that the computer readable medium may contain content that is subject to appropriate increase or decrease as required by legislation and patent practice in jurisdictions, for example, in some jurisdictions, computer readable media does not include electrical carrier signals and telecommunications signals as is required by legislation and patent practice.
Furthermore, the invention also provides a storage device. In one embodiment of the storage device according to the present invention, the storage device may be configured to store a program for executing the quasi-resonant controller based dead-time compensation method of the above method embodiment, and the program may be loaded and executed by a processor to implement the quasi-resonant controller based dead-time compensation method of the energy storage converter. For convenience of explanation, only the parts related to the embodiments of the present invention are shown, and details of the specific techniques are not disclosed. The storage device may be a storage device apparatus formed by including various electronic devices, and optionally, a non-transitory computer-readable storage medium is stored in the embodiment of the present invention.
Furthermore, the invention also provides a control device. In an embodiment of the control apparatus according to the present invention, the control apparatus includes a processor and a storage device, the storage device may be configured to store a program for executing the quasi-resonant controller based energy storage converter dead zone compensation method of the above method embodiment, and the processor may be configured to execute a program in the storage device, the program including but not limited to a program for executing the quasi-resonant controller based energy storage converter dead zone compensation method of the above method embodiment. For convenience of explanation, only the parts related to the embodiments of the present invention are shown, and details of the specific techniques are not disclosed. The control device may be a control device apparatus formed including various electronic apparatuses.
As will be appreciated by one skilled in the art, embodiments of the present application may be provided as a method, system, or computer program product. Accordingly, the present application may take the form of an entirely hardware embodiment, an entirely software embodiment or an embodiment combining software and hardware aspects. Furthermore, the present application may take the form of a computer program product embodied on one or more computer-usable storage media (including, but not limited to, disk storage, CD-ROM, optical storage, and the like) having computer-usable program code embodied therein.
The present application is described with reference to flowchart illustrations and/or block diagrams of methods, apparatus (systems), and computer program products according to embodiments of the application. It will be understood that each flow and/or block of the flow diagrams and/or block diagrams, and combinations of flows and/or blocks in the flow diagrams and/or block diagrams, can be implemented by computer program instructions. These computer program instructions may be provided to a processor of a general purpose computer, special purpose computer, embedded processor, or other programmable data processing apparatus to produce a machine, such that the instructions, which execute via the processor of the computer or other programmable data processing apparatus, create means for implementing the functions specified in the flowchart flow or flows and/or block diagram block or blocks.
These computer program instructions may also be stored in a computer-readable memory that can direct a computer or other programmable data processing apparatus to function in a particular manner, such that the instructions stored in the computer-readable memory produce an article of manufacture including instruction means which implement the function specified in the flowchart flow or flows and/or block diagram block or blocks.
These computer program instructions may also be loaded onto a computer or other programmable data processing apparatus to cause a series of operational steps to be performed on the computer or other programmable apparatus to produce a computer implemented process such that the instructions which execute on the computer or other programmable apparatus provide steps for implementing the functions specified in the flowchart flow or flows and/or block diagram block or blocks.
Finally, it should be noted that: the above embodiments are only for illustrating the technical solutions of the present invention and not for limiting the same, and although the present invention is described in detail with reference to the above embodiments, those of ordinary skill in the art should understand that: modifications and equivalents may be made to the embodiments of the invention without departing from the spirit and scope of the invention, which is to be covered by the claims.
Claims (11)
1. A dead-time compensation method for an energy storage converter based on a quasi-resonant controller is characterized by comprising the following steps:
acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
and taking the voltage modulation signal as the input of an SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module.
2. The method of claim 1, wherein the obtaining the voltage modulation signal using a fundamental controller and a quasi-resonant controller based on d-axis voltage components and q-axis voltage components corresponding to the load-side three-phase alternating voltage signal comprises:
taking a d/q axis voltage component corresponding to the three-phase alternating voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
respectively taking d/q axis voltage components corresponding to the three-phase alternating voltage signal at the load side as the input of n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
converting the superposed voltage components output by the fundamental wave controller and the superposed voltage components output by the n quasi-resonant controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
3. The method of claim 2, wherein the mathematical model of the quasi-resonant controller is as follows:
in the above formula, udxD-axis voltage component, u, output for the x-th quasi-resonant controllerqxQ-axis voltage component, K, output for the x-th quasi-resonant controllerrxFor the x-th quasi-resonant controller coefficient, ωcxIs the cut-off frequency, ω, of the x-th quasi-resonant controlleroFor the fundamental frequency, x ∈ [1, n ]]，udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqAnd s is a Laplace operator, and is a q-axis voltage component corresponding to the three-phase alternating voltage signal on the load side.
4. The method of claim 1, wherein the fundamental controller is comprised of a current loop regulator and a voltage loop regulator.
5. The method of claim 4, wherein the mathematical model of the current loop regulator is calculated as follows:
the mathematical model calculation for the voltage loop regulator is as follows:
in the above formula, id1D-axis component, i, of the output of the voltage-loop regulatorq1Q-axis component, K, of the output of the voltage loop regulatorupIs the proportional term coefficient, K, of the voltage loop regulatoruiFor the integral term coefficient, u, of the voltage loop regulatordrefFor setting the d-axis component of the voltage-loop regulatorqrefFor setting the q-component of the voltage-loop regulator, udD-axis voltage component u corresponding to three-phase AC voltage signal on load sideqQ-axis voltage component u corresponding to three-phase AC voltage signal on load sided1D-axis component, u, being output from fundamental controllerq1Q-axis component, K, output of fundamental controlleripIs the current loop proportional term coefficient, KiiIs a current loop integral term coefficient, idrefSetting value i for d-axis component of current loop regulatorqrefAnd (4) setting a value for the q-axis component of the current loop regulator, wherein s is a Laplace operator.
6. The method according to any one of claims 1-5, wherein before the obtaining the voltage modulation signal using the fundamental controller and the quasi-resonant controller based on the d/q-axis voltage components corresponding to the load-side three-phase alternating voltage signal, further comprises:
and transforming the load side three-phase alternating voltage signal into a d-q coordinate system synchronously rotating with the fundamental voltage to obtain a d/q axis voltage component corresponding to the load side three-phase alternating voltage signal.
7. An energy storage converter dead zone compensation device based on a quasi-resonant controller is characterized by comprising:
the acquisition module is used for acquiring a voltage modulation signal by using a fundamental wave controller and a quasi-resonance controller based on a d/q axis voltage component corresponding to a three-phase alternating voltage signal at a load side;
and the driving signal generation module is used for taking the voltage modulation signal as the input of the SVPWM module to obtain a switching tube driving signal of the energy storage converter output by the SVPWM module.
8. The apparatus of claim 7, wherein the acquisition module comprises:
the first generating unit is used for taking a d/q axis voltage component corresponding to the three-phase alternating-current voltage signal at the load side as the input of a fundamental wave controller to obtain a voltage component output by the fundamental wave controller;
the second generating unit is used for respectively taking d/q axis voltage components corresponding to the three-phase alternating-current voltage signals on the load side as the input of the n quasi-resonance controllers to obtain voltage components output by the n quasi-resonance controllers;
the third generating unit is used for converting the superposed voltage components output by the fundamental wave controller and the voltage components output by the n quasi-resonance controllers into an alpha-beta static coordinate system to obtain the voltage modulation signal;
where N is N/6, where N is the number of times of a ripple component included in the load-side three-phase ac voltage signal.
9. The apparatus of claim 7, wherein the apparatus further comprises:
the device comprises an abd/dq conversion module, a fundamental voltage conversion module and a control module, wherein the abd/dq conversion module is used for converting a load side three-phase alternating voltage signal into a d-q coordinate system synchronously rotating with the fundamental voltage to obtain a d/q axis voltage component corresponding to the load side three-phase alternating voltage signal.
10. A storage device having a plurality of program codes stored therein, wherein the program codes are adapted to be loaded and run by a processor to perform the method of any of claims 1 to 6 for dead-time compensation of a quasi-resonant controller based energy storage converter.
11. A control apparatus comprising a processor and a storage device adapted to store a plurality of program codes, wherein said program codes are adapted to be loaded and run by said processor to perform the method of dead-time compensation of a quasi-resonant controller based energy storage converter according to any of claims 1 to 6.
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| CN114172179A (en) * | 2021-11-22 | 2022-03-11 | 贵州电网有限责任公司 | Energy storage converter dead zone compensation method based on disturbance observer |
| CN115309091A (en) * | 2022-10-09 | 2022-11-08 | 深圳市源广浩电子有限公司 | Equipment load automatic adjusting method and system based on Internet of things and storage medium |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN114172179A (en) * | 2021-11-22 | 2022-03-11 | 贵州电网有限责任公司 | Energy storage converter dead zone compensation method based on disturbance observer |
| CN115309091A (en) * | 2022-10-09 | 2022-11-08 | 深圳市源广浩电子有限公司 | Equipment load automatic adjusting method and system based on Internet of things and storage medium |
| CN115309091B (en) * | 2022-10-09 | 2022-12-20 | 深圳市源广浩电子有限公司 | Equipment load automatic adjustment method and system based on Internet of things and storage medium |
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