CN112039319A - Drive circuit and drive method - Google Patents
Drive circuit and drive method Download PDFInfo
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- CN112039319A CN112039319A CN202010813834.XA CN202010813834A CN112039319A CN 112039319 A CN112039319 A CN 112039319A CN 202010813834 A CN202010813834 A CN 202010813834A CN 112039319 A CN112039319 A CN 112039319A
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- 238000000034 method Methods 0.000 title claims abstract description 17
- 230000002457 bidirectional effect Effects 0.000 claims abstract description 338
- 238000004146 energy storage Methods 0.000 claims abstract description 206
- 239000003990 capacitor Substances 0.000 claims abstract description 187
- 238000005070 sampling Methods 0.000 claims description 75
- 230000001939 inductive effect Effects 0.000 claims description 14
- 230000002441 reversible effect Effects 0.000 claims description 11
- 230000007423 decrease Effects 0.000 claims description 10
- 238000010586 diagram Methods 0.000 description 25
- 230000001276 controlling effect Effects 0.000 description 8
- 230000001965 increasing effect Effects 0.000 description 5
- 230000008859 change Effects 0.000 description 3
- 230000008569 process Effects 0.000 description 3
- 238000013459 approach Methods 0.000 description 2
- 230000005540 biological transmission Effects 0.000 description 2
- 230000003750 conditioning effect Effects 0.000 description 2
- 230000003247 decreasing effect Effects 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000000630 rising effect Effects 0.000 description 2
- 230000003044 adaptive effect Effects 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 238000001914 filtration Methods 0.000 description 1
- 230000007246 mechanism Effects 0.000 description 1
- 229910044991 metal oxide Inorganic materials 0.000 description 1
- 150000004706 metal oxides Chemical class 0.000 description 1
- 230000000737 periodic effect Effects 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 239000004065 semiconductor Substances 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J1/00—Circuit arrangements for DC mains or DC distribution networks
- H02J1/14—Balancing the load in a network
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/34—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering
- H02J7/345—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering using capacitors as storage or buffering devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/06—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider
- H02M3/07—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/1566—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with means for compensating against rapid load changes, e.g. with auxiliary current source, with dual mode control or with inductance variation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
According to an embodiment of the present invention, a driving circuit and a driving method are disclosed, the driving circuit of the present invention includes an energy storage capacitor, a first power converter and a bidirectional converter, wherein an output terminal of the first power converter is coupled to a load and the energy storage capacitor which are connected in parallel, and the bidirectional converter is coupled between the load and the energy storage capacitor; during a light load interval, the first power converter provides energy for a load, and at least during a part of the light load interval, the first power converter provides energy for an energy storage capacitor through the bidirectional converter; during a heavy-load interval, the first power converter provides energy to a load, and the energy storage capacitor provides energy to the load through the bidirectional converter. The driving circuit can be used for driving the load with low average power and high peak power, the maximum power requirement of the first power converter is reduced, the capacity of the energy storage capacitor is reduced, and the volume of the energy storage capacitor is further reduced.
Description
Technical Field
The invention relates to the field of power electronics, in particular to a driving circuit and a driving method.
Background
With the increasing popularity of load types, applications and applications, higher requirements are also put on the driving circuit of the load. The driving circuit of the load in the prior art is a power converter, and as shown in fig. 1, the load 2 is directly driven by using a first power converter 1, and the first power converter 1 has the maximum output power. Fig. 2 shows the output characteristic of the first power converter of fig. 1. As shown in fig. 2, when the load is too heavy, the output voltage Vout of the first power converter 1 is made lower than the threshold voltage VUVLOThereby triggering a protection mechanismCausing the first power converter 1 to shut down or restart.
However, in some applications, there may be a section in which the power required by the Load 2 is greater than the maximum output power of the first power converter 1 during the operation of the Load 2, that is, the average power of the Load 2 is lower than the maximum output power of the first power converter 1, and the peak power of the Load 2 is higher than the maximum output power of the first power converter 1, as shown in fig. 3, the average power P _ Load _ avg required by the Load 2 is lower than the maximum output power Po _ max of the first power converter 1, Po _ max is Vo _ max, Io _ max, and in most light Load sections (for example, the section t0-t1 and the section t2-t 3), the power required by the Load 2 is very low, and at this time, the first power converter 1 may provide the power required by the Load, but in a heavy Load section (for example, the section t1-t 2), the power P _ Load 2 required by the Load P _ Load _ max is higher than the maximum output power Po _ max of the first power converter 1, the output voltage Vout of the first power converter 1 is made lower than the threshold voltage VUVLOThereby triggering a protection mechanism when the first power converter 1 is not able to supply the power required by the load 2. The prior art drive circuit is unable to drive a load with low average power and high peak power.
Disclosure of Invention
In view of this, the present invention provides a driving circuit and a driving method to solve the technical problem that the prior art cannot drive a load with low average power and high peak power.
In a first aspect, an embodiment of the present invention provides a driving circuit, including: an energy storage capacitor; the output end of the first power converter is coupled with a load and the energy storage capacitor which are connected in parallel, and the first power converter is used for generating a direct current signal so as to provide energy for the load in a light load interval and a heavy load interval; a bidirectional converter coupled between the load and the energy storage capacitor; and the first power converter supplies energy to the energy storage capacitor through the bidirectional converter at least in a part of the light load interval, and the energy storage capacitor supplies energy to the load through the bidirectional converter in the heavy load interval.
Preferably, when the voltage of the first end of the bidirectional converter is smaller than the first reference voltage, the load enters a heavy load section from a light load section, wherein the first end of the bidirectional converter is an end coupled with the load.
Preferably, during a part of the light load interval, the first power converter supplies energy to the energy storage capacitor through a bidirectional converter; during another part of the light load interval, the bidirectional converter does not work, and the first power converter does not provide energy to the energy storage capacitor any more.
Preferably, in a light load interval, the first power converter supplies energy to the energy storage capacitor through a bidirectional converter.
Preferably, the operating state of the bidirectional converter is controlled so that the bidirectional converter operates in a forward direction at least during a part of the light load interval; and in a heavy-load interval, the bidirectional converter works reversely.
Preferably, the energy storage capacitor is charged and discharged through the bidirectional converter, so that the voltage variation range of the energy storage capacitor is large, and the capacity of the energy storage capacitor is reduced.
Preferably, whether the energy storage capacitor is allowed to be charged or discharged is judged according to the voltage of the first end of the bidirectional converter and the voltage of the energy storage capacitor.
Preferably, when the voltage of the first end of the bidirectional converter is less than the first reference voltage, the bidirectional converter is enabled, and the energy storage capacitor is allowed to be charged and discharged.
Preferably, when the voltage of the energy storage capacitor is greater than the second reference voltage, the bidirectional converter does not operate, and the energy storage capacitor is not allowed to be charged and discharged.
Preferably, the bidirectional converter comprises an inductor, and when the bidirectional converter is enabled, the magnitude and the direction of the current flowing through the inductor are controlled according to an inductor current reference signal, so that the voltage at the first end of the bidirectional converter is a third reference voltage, wherein the inductor current reference signal is adjusted according to the voltage at the first end of the bidirectional converter.
Preferably, when the voltage at the first end of the bidirectional converter is greater than the corresponding third reference voltage, the inductor current reference signal is controlled to increase so that more energy is transferred from the first end of the bidirectional converter to the energy storage voltage; when the voltage at the first terminal of the bidirectional converter is less than a third reference voltage, the inductor current reference signal is controlled to decrease such that less energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage or such that energy is transferred from the energy storage voltage to the first terminal of the bidirectional converter.
Preferably, in a light-load interval, the output power of the first power converter is equal to the sum of the load power and the input power of the first end of the bidirectional converter; in a heavy load interval, the load power is equal to the sum of the output power of the first power converter and the output power of the first end of the bidirectional converter.
Preferably, the bidirectional converter is a bidirectional DC-DC converter.
Preferably, in a light-load interval, the output current of the first power converter is equal to the sum of a load current and the input current of the first end of the bidirectional converter; in a heavy-load interval, the load current is equal to the sum of the output current of the first power converter and the output current of the first end of the bidirectional converter.
Preferably, the driving circuit further comprises a control circuit, the control circuit comprises an enabling circuit, the enabling circuit receives a first sampling signal representing the voltage of the first end of the bidirectional converter, a second sampling signal representing the voltage of the energy storage capacitor, a first reference voltage signal and a second reference voltage signal, and outputs a first enabling signal; when the first sampling signal is smaller than the first reference voltage signal, the first enabling signal is effective, the bidirectional converter is enabled, and when the second sampling signal is larger than the second reference voltage signal, the first enabling signal is ineffective, and the bidirectional converter does not work.
Preferably, the bidirectional converter includes an inductor, and the control circuit further includes:
the reference signal adjusting circuit receives the first sampling signal and the third reference voltage signal, and outputs and adjusts an inductive current reference signal;
the inductive current sampling circuit samples a first current representing the inductive current, increases direct current bias on the first current and outputs a second current, and the second current is a positive value;
the control module is used for receiving the inductive current reference signal, the second current and the first enabling signal and outputting a control signal so as to control the switching state of the bidirectional converter and further control the magnitude and the direction of the inductive current;
wherein when the first sampling signal is greater than the third reference voltage signal, the inductor current reference signal is controlled to increase such that more energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage; when the first sampling signal is less than the third reference voltage signal, controlling the inductor current reference signal to decrease such that less energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage or such that energy is transferred from the energy storage voltage to the first terminal of the bidirectional converter.
Preferably, the bidirectional converter is a bidirectional buck converter, and when the bidirectional converter works in the forward direction, the bidirectional converter works in a buck state; when the bidirectional converter works in a reverse direction, the bidirectional converter works in a boost state.
Preferably, the bidirectional converter is a bidirectional boost converter, and when the bidirectional converter works in a forward direction, the bidirectional converter works in a boost state; and when the bidirectional converter works in the reverse direction, the bidirectional converter works in a buck state.
Preferably, the bidirectional converter is a bidirectional buck-boost converter, and when the bidirectional converter works in the forward direction, the bidirectional converter works in a buck state firstly and then works in a boost state; when the bidirectional converter works reversely, the bidirectional converter works in buck state firstly and then works in boost state.
Preferably, the bidirectional converter comprises a current limiting circuit for limiting a maximum input current or a maximum output current when the bidirectional converter is in forward operation.
Preferably, the bidirectional converter is a bidirectional boost converter, and the current limiting circuit is coupled between a first terminal of the bidirectional converter and the load to limit the maximum input current.
Preferably, the bidirectional converter is a bidirectional boost converter, the bidirectional converter includes a power switch, the power switch is coupled to the energy storage capacitor, and the current limiting circuit is coupled to the power switch to limit the maximum output current.
Preferably, the bidirectional converter is a bidirectional buck-boost converter, the buck-boost circuit includes a power switch coupled to the load, and the power switch is multiplexed as a current limiting circuit when the bidirectional converter operates in a boost state in a forward direction.
Preferably, the current limiting circuit is a switching tube, the switching tube works in a linear state, and the resistance of the switching tube is controlled by controlling the voltage of a control end of the switching tube so as to control the maximum output current or the maximum input current.
Preferably, the bidirectional converter is a bidirectional buck-boost converter, the buck-boost circuit includes an inductor, a first power switch and a second power switch, the first power switch is coupled to the load, the second power switch is coupled to the first power switch, the inductor is coupled to both the first power switch and the second power switch, the first power switch operates in a PWM state, the second power switch functions as a diode, and the inductor, the first power switch and the second power switch form a buck circuit so as to be multiplexed as a current limiting circuit.
Preferably, the first power converter is a DC-DC converter or an AC-DC converter.
In a second aspect, an embodiment of the present invention further provides a driving method applied to a driving circuit, where the driving circuit includes a bidirectional converter, a first power converter, and an energy storage capacitor, an output terminal of the first power converter is coupled to a load and the energy storage capacitor that are connected in parallel, the bidirectional converter is coupled between the load and the energy storage capacitor, and the driving method includes:
the first power converter provides energy to the load in a light load interval and a heavy load interval;
at least during a part of the light load interval, the first power converter provides energy to the energy storage capacitor through the bidirectional converter;
in a heavy-load interval, the energy storage capacitor supplies energy to the load through the bidirectional converter.
Compared with the prior art, the technical scheme of the invention has the following advantages: the driving circuit comprises an energy storage capacitor, a first power converter and a bidirectional converter, wherein the output end of the first power converter is coupled with a load and the energy storage capacitor which are connected in parallel, and the bidirectional converter is coupled between the load and the energy storage capacitor; during a light load interval, the first power converter provides energy for a load, and at least during a part of the light load interval, the first power converter provides energy for an energy storage capacitor through the bidirectional converter; during a heavy-load interval, the first power converter provides energy to a load, and the energy storage capacitor provides energy to the load through the bidirectional converter. The driving circuit can be used for driving a load with low average power and high peak power, and the energy storage capacitor is charged and discharged through the bidirectional converter, so that the voltage change range of the energy storage capacitor is larger, the capacity of the energy storage capacitor is reduced, namely the energy storage capacitor with smaller capacity is used, the volume of the energy storage capacitor is further reduced, the volume and the cost of the driving circuit are further reduced, and the maximum power requirement of the first power converter is reduced.
Drawings
The above and other objects, features and advantages of the present invention will become more apparent from the following description of the embodiments of the present invention with reference to the accompanying drawings, in which:
FIG. 1 is a schematic diagram of a prior art drive circuit;
FIG. 2 is a graph of the output characteristic of a first prior art power converter;
FIG. 3 is a diagram of an exemplary operating waveform of a load of the present invention;
FIG. 4 is a circuit block diagram of the driving circuit of the present invention;
FIG. 5 is a waveform diagram illustrating an exemplary operation of the driving circuit of the present invention;
FIG. 6 is a waveform diagram illustrating another exemplary operation of the driving circuit of the present invention;
FIG. 7 is an exemplary schematic diagram of a control circuit of the drive circuit of the present invention;
FIG. 8 is a circuit diagram of a driving circuit according to a first embodiment of the present invention;
FIG. 9 is a schematic diagram of a control circuit according to a first embodiment of the present invention;
FIG. 10 is a circuit diagram of a second embodiment of a driving circuit according to the present invention;
FIG. 11 is a schematic diagram of a control circuit according to a second embodiment of the present invention;
FIG. 12 is a schematic diagram of a current limiting circuit according to a second embodiment of the present invention;
FIG. 13 is a schematic diagram of another current limiting circuit according to a second embodiment of the present invention;
FIG. 14 is a circuit diagram of a third embodiment of a driving circuit according to the present invention;
fig. 15 is a schematic diagram of a control circuit according to a third embodiment of the invention.
Detailed Description
The present invention will be described below based on examples, but the present invention is not limited to only these examples. In the following detailed description of the present invention, certain specific details are set forth. It will be apparent to one skilled in the art that the present invention may be practiced without these specific details. Well-known methods, procedures, components and circuits have not been described in detail so as not to obscure the present invention.
Further, those of ordinary skill in the art will appreciate that the drawings provided herein are for illustrative purposes and are not necessarily drawn to scale.
Meanwhile, it should be understood that, in the following description, a "circuit" refers to a conductive loop constituted by at least one element or sub-circuit through electrical or electromagnetic connection. When an element or circuit is referred to as being "connected to" another element or element/circuit is referred to as being "connected between" two nodes, it may be directly coupled or connected to the other element or intervening elements may be present, and the connection between the elements may be physical, logical, or a combination thereof. In contrast, when an element is referred to as being "directly coupled" or "directly connected" to another element, it is intended that there are no intervening elements present.
Fig. 4 is a circuit block diagram of a driving circuit of the present invention, the driving circuit is used for driving a load with low average power and high peak power, and includes a first power converter 11, an energy storage capacitor (Cap)13 and a bidirectional converter 14, an output terminal of the first power converter 11 is coupled to a load 12 and the energy storage capacitor 13 which are connected in parallel, and the bidirectional converter 14 is coupled between the load 12 and the energy storage capacitor 13; the first power converter 11 is configured to generate a dc signal to provide energy to the load 12 during a light-load interval and a heavy-load interval, and at least during a part of the light-load interval, the first power converter 11 provides energy to the energy storage capacitor 13 through the bidirectional converter 14, and during the heavy-load interval, the energy storage capacitor 13 provides energy to the load 12 through the bidirectional converter 14.
The application occasions of the load driven by the driving circuit of the invention are as follows: during operation of the load 12, there are one or more intervals in which the power required by the load 12 is greater than the maximum output power of the first power converter 11. During the load operation, an interval in which the power required by the load 12 is greater than the maximum output power of the first power converter 11 is a heavy load interval, and an interval in which the power required by the load 12 is less than or equal to the maximum output power of the first power converter 11 is a light load interval. Optionally, the load is an active load. Preferably, the load is a power amplifier, and when the load is operated in a situation where the sound power required to be output is increased, the operation waveform thereof may have a section where the power required by the load 12 is larger than the maximum output power of the first power converter 11. Further, the load is a class D amplifier. It should be noted that fig. 3 is only an exemplary operating waveform diagram of the load of the present invention, and the operating wave of the load in fig. 3 is periodic and the period is fixed, but in other embodiments, the operating waveform of the load may be aperiodic or the period is not fixed. In fig. 3, the peak powers of the loads (i.e., the load powers in the heavy-duty intervals) are the same in different heavy-duty intervals (t1-t2 and t3-t 4), but in other embodiments, the peak powers of the loads may be different in different heavy-duty intervals, which is not limited in the present invention. For convenience of description, the load operation waveform shown in fig. 3 is described later, but the operation waveform of the load is not limited by the present invention.
The first power converter 11 is used for outputting a direct current signal, and may be a DC-DC power converter or an AC-DC power converter. Optionally, the first power converter is a power converter or a power adapter. The bidirectional converter is any DC-DC bidirectional converter, such as a bidirectional buck converter, a bidirectional boost converter, a bidirectional buck-boost converter, a bidirectional boost-buck converter and the like.
Optionally, during a part of the light load interval, the first power converter 11 supplies energy to the energy storage capacitor 13 through a bidirectional converter 14; during another part of the light load interval, the bidirectional converter 14 does not work, and the first power converter 11 no longer supplies energy to the energy storage capacitor 13. For example, the voltage of the energy storage capacitor 13 is controlled, and when the voltage of the energy storage capacitor 13 is greater than a preset reference value, the first power converter 11 no longer provides energy to the energy storage capacitor 13.
Optionally, the first power converter 11 supplies energy to the energy storage capacitor 13 through a bidirectional converter 14 in the whole light load interval. For example, the charging of the energy storage capacitor 13 is not controlled, or the voltage of the energy storage capacitor 13 is controlled, but the light load period is short, and until the light load interval is cut off, the voltage of the energy storage capacitor 13 is still not greater than the preset reference value.
Further, the working state of the bidirectional converter 14 is controlled, so that at least in a part of the light load interval, the bidirectional converter 14 works in the forward direction, and the energy storage capacitor 13 is charged; in a heavy-load interval, the bidirectional converter 14 works reversely, and the energy storage capacitor 13 discharges.
The driving circuit is used for driving a load with low average power and high peak power, the first power converter supplies energy to the load in a light-load interval, and the first power converter supplies energy to the energy storage capacitor through the bidirectional converter at least in part of the light-load interval; during a heavy-load interval, the first power converter provides energy to a load, and the energy storage capacitor provides energy to the load through the bidirectional converter. The energy storage capacitor is charged and discharged through the bidirectional converter, so that the voltage change range of the energy storage capacitor is large, the capacity of the energy storage capacitor is reduced, the energy storage capacitor with small capacity can be used, the size of the energy storage capacitor is reduced, the size of the driving circuit is further reduced, the cost and the size of a system are reduced to the maximum extent, the maximum power requirement of the first power converter is reduced, and the maximum power of the first power converter is low. Specifically, the formula of Energy _ Ccap stored in the Energy storage capacitor 13 is Energy _ Ccap (1/2 × C) (Vcp)2-Vcv2) Where C is the capacity of the Energy storage capacitor 13, Vcp is the voltage of the Energy storage capacitor 13 when charging is completed, Vcv is the voltage of the Energy storage capacitor when charging is just started, and in a light load interval, the Energy _ Ccap stored in the Energy storage capacitor 13 needs to be higher than the Energy that the load 12 needs in a heavy load interval and exceeds the Energy that the first power converter 11 can provide. If the bidirectional converter 14 is not provided in the driving circuit, the voltage across the energy storage capacitor 13 is equal to the output voltage of the first power converter 11, and since the variation range of the output voltage of the first power converter 11 is not large, the variation range Vcp-Vcv of the voltage across the energy storage capacitor 13 is not large, that is, the difference between Vcp and Vcv is not large, so that Vcp is enabled to be smaller2-Vcv2Since the value of (C) is not large, the capacity C of the storage capacitor 13 needs to be large when storing the same energy. In the driving circuit of the present invention, the bidirectional converter 14 is coupled between the load 12 and the energy storage capacitor 13, the energy storage capacitor 13 is charged and discharged through the bidirectional converter 14, and the voltage on the energy storage capacitor 13 is independent of the output voltage of the first power converter 11, so that the variation range Vcp-Vcv of the voltage of the energy storage capacitor 13 can be relatively large, i.e. Vcp and VcvVcv is greatly different, so that Vcp2-Vcv2The value of (C) is large, so that when the same energy is stored, the capacity C of the energy storage capacitor 13 is small, the capacity C of the energy storage capacitor 13 is reduced, and the energy storage capacitor 13 with the small capacity C can be used. The advantages of the invention over a scheme without a bidirectional converter are: the energy storage capacitor is charged and discharged through the bidirectional converter, the voltage change range of the energy storage capacitor is large, the capacity of the energy storage capacitor is small, and the volume and the number of the energy storage capacitor are reduced. The energy storage capacitor 13 may be a capacitor with a smaller capacity, or a capacitor with a smaller capacity formed by connecting a plurality of capacitors with a smaller capacity in parallel, which is not limited in the present invention.
Optionally, as a control implementation manner, when the voltage of the first end of the bidirectional converter 14 is smaller than a first reference voltage, the load enters a heavy-load interval from a light-load interval, where the first end of the bidirectional converter 14 is an end coupled to the load, and the second end of the bidirectional converter is an end coupled to the energy storage capacitor.
Further, it is determined whether to enable the bidirectional converter 14, that is, whether to allow the energy storage capacitor to be charged or discharged, according to the voltage of the first end of the bidirectional converter 14 and the voltage of the energy storage capacitor 13, where the first end of the bidirectional converter 14 is an end coupled to a load. Specifically, when the voltage at the first end of the bidirectional converter 14 is smaller than the first reference voltage, the bidirectional converter 14 is enabled, and the energy storage capacitor is allowed to be charged and discharged. When the voltage of the energy storage capacitor 13 is greater than the second reference voltage, the bidirectional converter 14 does not operate, and the energy storage capacitor 13 is not allowed to be charged or discharged. Optionally, the first reference voltage is equal to the second reference voltage.
Further, the bidirectional converter 14 includes an inductor, and when the bidirectional converter 14 is enabled, the magnitude and the direction of the inductor current are controlled according to an inductor current reference signal, so that the voltage at the first end of the bidirectional converter 14 is a third reference voltage, where the inductor current reference signal is adjusted according to the voltage at the first end of the bidirectional converter 14.Specifically, when the voltage at the first terminal of the bidirectional converter 14 is greater than the corresponding third reference voltage, the inductor current reference signal is controlled to increase so that more energy is transmitted from the first terminal of the bidirectional converter 14 to the energy storage voltage 13; when the voltage at the first terminal of the bidirectional converter 14 is less than the third reference voltage, the inductor current reference signal is controlled to decrease such that less energy is transferred from the first terminal of the bidirectional converter 14 to the energy storage voltage 13, or such that energy is transferred from the energy storage voltage 13 to the first terminal of the bidirectional converter 14. Preferably, the third reference voltage is greater than VUVLOSaid V isUVLOIs the minimum output voltage of the first power converter 11.
Fig. 5 is a waveform diagram illustrating an exemplary operation of the driving circuit of the present invention, where P _ Load is the power of the Load 12, Po is the output power of the first power converter 11, P _ ex is the power of the first terminal of the bidirectional converter 14, Vcap is the voltage of the energy storage capacitor 13, P _ Load _ max is the maximum power of the Load 12, Po _ max is the maximum output power of the first power converter 11, and P _ Load _ min is the minimum power of the Load 12.
In the interval t0-t1 (or interval t2-t 4), the power P _ Load of the Load 12 is smaller than the maximum output power Po _ max of the first power converter 11;
in the interval t0-t 0', the first power converter 11 not only supplies the power required by the Load 12, but also supplies energy to the energy storage capacitor 13, the first power converter 11 charges the energy storage capacitor 13 through the bidirectional converter 14, so that the voltage Vcap of the energy storage capacitor 13 rises from Vcv to Vcp, and in this interval, the output power Po of the first power converter 11 is equal to the sum of the power P _ Load of the Load 12 and the power P _ ex of the first end of the bidirectional converter 14 (P _ ex is greater than zero, that is, P _ ex is the input power of the first end of the bidirectional converter 14); in the interval t 0' -t1, the bidirectional converter 14 is not operated, the voltage of the energy storage capacitor is kept at Vcp, the first power converter 11 only provides the power required by the Load 12, in this interval, the power P _ ex at the first end of the bidirectional converter 14 is zero, and the output power Po of the first power converter 11 is equal to the power P _ Load of the Load 12.
In the interval t1-t2, the power P _ Load of the Load 12 is greater than the maximum output power Po _ max of the first power converter 11, the power required by the Load 12 is provided by the first power converter 11 and the energy storage capacitor 13, and the energy storage capacitor 13 discharges the Load 12 through the bidirectional converter 14, so that the voltage of the energy storage capacitor 13 decreases from Vcp to Vcv, in this interval, the power P _ Load of the Load 12 is equal to the sum of the output power Po of the first power converter 11 and the absolute value of the power P _ ex at the first end of the bidirectional converter 14 (P _ ex is less than zero, i.e., P _ ex is the output power at the first end of the bidirectional converter 14).
In a part of light load interval, the first power converter 11 stores energy in the energy storage capacitor 13 through the bidirectional converter 14, and in a heavy load interval, the energy storage capacitor 13 supplies power exceeding the maximum output power Po _ max of the first power converter 11 to the load 12 through the bidirectional converter 14, so that the driving circuit shown in fig. 4 drives the load with low average power and high peak power.
In addition, in the light load interval, the energy stored in the energy storage capacitor 13 needs to be higher than that in the heavy load interval, and the power required by the load 12 exceeds the maximum output power Po _ max of the first power converter 11. In fig. 5, the voltage rising range and the voltage falling range of the energy storage capacitor 13 are equal to each other, and are Vcp-Vcv, but the voltage rising range and the voltage falling range of the energy storage capacitor 13 in the present invention do not need to be equal to each other, and the description is given here.
The operating waveforms in fig. 5 are the output power Po of the first power converter, the power P _ ex at the first end of the bidirectional converter 14 and the power P _ Load of the Load 12 varying with time, and the corresponding powers can be adjusted by adjusting the voltage and/or current during the control process. The present invention provides an exemplary control mode for regulating the corresponding power by controlling the voltage at the first terminal of the bidirectional converter 14 to be relatively constant (i.e. making the voltage at the first terminal of the bidirectional converter 14 equal to the third reference voltage), but the present invention is not limited thereto. Further, since the voltage of the load 12, the output voltage of the first power converter 11 and the voltage at the first end of the bidirectional converter are equal, during the control process, the voltage of the load 12, the output voltage of the first power converter 11 and the voltage at the first end of the bidirectional converter are relatively constant, so that the operating waveform in fig. 5 can be converted into an operating waveform diagram of the corresponding current over time as described in fig. 6. As shown in fig. 6, in the light Load interval, the output current Io of the first power converter 11 is equal to the sum of the Load current i _ Load and the current i _ ex of the first terminal of the bidirectional converter 14; in a heavy Load interval, the Load current i _ Load is equal to the sum of the output current Io of the first power converter and the absolute value of the current i _ ex of the first end of the bidirectional converter. Since the waveforms in fig. 6 and the waveforms in fig. 5 are the same except that the corresponding power is changed into the corresponding current, and the working process will be described in detail in the following embodiments with reference to the waveforms in fig. 6, further description is omitted here.
FIG. 7 is an exemplary schematic diagram of a control circuit of the drive circuit of the present invention; the control circuit includes an enable circuit 1411, a reference signal conditioning circuit 1412, an inductor current sampling circuit 1413, and a control module 1414.
The enabling circuit 1411 receives a first sampling signal V1 representing the voltage Vin of the first end of the bidirectional converter 14, a second sampling signal V2 representing the voltage Vcap of the energy storage capacitor 13, a first reference voltage signal Vref1 and a second reference voltage signal Vref2, and outputs a first enabling signal EN; when the first sampling signal V1 is less than the first reference voltage signal Vref1, the first enable signal EN is asserted, enabling the bidirectional converter 14, and when the second sampling signal V2 is greater than the second reference voltage signal Vref2, the first enable signal EN is de-asserted, disabling the bidirectional converter 14. Optionally, the first reference voltage signal Vref1 and the second reference voltage signal Vref2 are equal, but the present invention is not limited thereto, and for convenience of description, the first reference voltage signal Vref1 and the second reference voltage signal Vref1 are considered to be one voltage reference signal, and thus the description is provided herein.
The bidirectional converter 14 comprises an inductor, and a reference signal adjusting circuit 1412 receives the first sampling signal V1 and a third reference voltage signal Vref3, outputs and adjusts an inductor current reference signal Iref to adjust the currentThe current through the inductor. Also, the reference signal adjusting circuit 1412 sets the maximum value of the inductor current reference signal Iref and the minimum value of the inductor current reference signal Iref. The inductor current reference signal Iref is adjusted according to the first sampling signal V1, and specifically, when the first sampling signal V1 is greater than the third reference voltage signal Vref3, the inductor current reference signal Iref is controlled to be increased so that more energy is transmitted from the first terminal of the bidirectional converter 14 to the energy storage voltage 13, and when the first sampling signal V1 is less than the third reference voltage signal Vref3, the inductor current reference signal Iref is controlled to be decreased so that less energy is transmitted from the first terminal of the bidirectional converter 14 to the energy storage voltage 13, or so that energy is transmitted from the energy storage voltage 13 to the first terminal of the bidirectional converter 14. Preferably, the third reference voltage is greater than VUVLOSaid V isUVLOIs the minimum output voltage of the first power converter 11.
The inductive current sampling circuit 1413 samples a first current representing an inductive current, adds a dc bias to the first current, and outputs a second current Isen, where the second current is a positive value, optionally, the first current is positive in a direction from the bidirectional converter 14 to the energy storage capacitor 13, the first current may be an inductive current sampling signal IL, in other embodiments, the first current may be a sampling signal ISX of a current flowing through each power switch in the bidirectional converter 14, where X may be 1 to N, and N is the number of power switches in the bidirectional converter 14;
the control module 1414 is configured to receive the inductor current reference signal Iref, the second current Isen, and the first enable signal EN, and when the first enable signal EN is asserted, output control signals Vc 1-VcN to respectively control on and off of power switches S1-SN in the bidirectional converter 14, and control a switching state of the bidirectional converter 14, so as to control a magnitude and a direction of the inductor current, so that the second current Isen approaches the inductor current reference signal Iref, and further make the first sampling signal V1 equal to the third reference voltage signal Vref 3. It should be noted that the present invention may control the direction and magnitude of the inductor current through any current control mode, which is not limited by the present invention.
In addition, the control circuit further comprises a first sampling circuit 1416 and a second sampling circuit 1415, wherein the first sampling circuit 1416 is used for generating a first sampling signal V1 according to the voltage Vin of the first end of the bidirectional converter 14, and the second sampling circuit 1405 is used for generating a second sampling signal V2 according to the voltage Vcap of the energy storage capacitor 13.
The control circuit shown in the invention has the advantages that: the bidirectional energy storage capacitor is used for any type of bidirectional converter, and the control mode is simple, so that the direction and the size of the inductive current are adaptively adjusted, the adaptive bidirectional transmission of energy from the first end of the bidirectional converter to the energy storage capacitor is realized, and the energy transmission is smooth.
FIG. 8 is a circuit diagram of a driving circuit according to a first embodiment of the present invention; the driving circuit comprises a first power converter 11, an energy storage capacitor 13 and a bidirectional converter 14, wherein the output end of the first power converter 11 is sequentially coupled with a load 12 and the energy storage capacitor 13 which are connected in parallel, and the bidirectional converter 14 is coupled between the load 12 and the energy storage capacitor 13.
The bidirectional converter 14 is a bidirectional buck converter, the bidirectional converter 14 includes a buck circuit and a control circuit 141, the buck circuit includes a first power switch S1, a second power switch S2 and a first inductor L1, the first power switch S1 and the second power switch S2 are sequentially connected in series at a first end of the bidirectional converter 14, one end of the first inductor L1 is connected to a common end of the first power switch S1 and the second power switch S2, and the other end of the first inductor L1 is connected to a high potential end of the energy storage capacitor 13. Optionally, the buck circuit further includes an input capacitor Cin for filtering an input signal (e.g., voltage or current) at the first end of the bidirectional converter 14. The input end of the control circuit 141 is used for sampling a sampling signal representing the inductor current, sampling the voltage Vin of the first end of the bidirectional converter 14 and sampling the voltage Vcap of the energy storage capacitor 13, and the output end is connected with the control ends of the first power switch S1 and the second power switch S2.
Specifically, fig. 9 is a schematic diagram of a control circuit according to a first embodiment of the present invention; the control circuit 141 includes an enable circuit 1411, a reference signal conditioning circuit 1412, an inductor current sampling circuit 1413, and a control module 1414.
The enabling circuit 1411 receives a first sampling signal V1 representing the voltage Vin of the first end of the bidirectional converter 14, a second sampling signal V2 representing the voltage Vcap of the energy storage capacitor 13 and a first reference voltage signal Vref1, and outputs a first enabling signal EN; when the first sampling signal V1 is less than the first reference voltage signal Vref1, the first enable signal EN is asserted, enabling the bidirectional converter 14, and when the second sampling signal V2 is greater than the first reference voltage signal Vref1, the first enable signal EN is de-asserted, disabling the bidirectional converter 14. In this embodiment, the first reference voltage signal Vref1 is greater than or equal to Vcp.
The reference signal adjusting circuit 1412 receives the first sampling signal V1 and the third reference voltage signal Vref3, and outputs and adjusts the inductor current reference signal Iref. Also, the reference signal adjusting circuit 1412 sets the maximum value of the inductor current reference signal Iref and the minimum value of the inductor current reference signal Iref. The inductor current reference signal Iref is adjusted according to the first sampling signal V1, and specifically, when the first sampling signal V1 is greater than the third reference voltage signal Vref3, the inductor current reference signal Iref is controlled to be increased so that more energy is transmitted from the first terminal of the bidirectional converter 14 to the energy storage voltage 13, and when the first sampling signal V1 is less than the third reference voltage signal Vref3, the inductor current reference signal Iref is controlled to be decreased so that less energy is transmitted from the first terminal of the bidirectional converter 14 to the energy storage voltage 13, or so that energy is transmitted from the energy storage voltage 13 to the first terminal of the bidirectional converter 14. In the present embodiment, the first reference voltage signal Vref1 is smaller than the third reference voltage signal Vref 3.
The inductor current sampling circuit 1413 samples a first current representing the inductor current, adds a dc bias to the first current, and outputs a second current Isen, where the second current Isen IS a positive value, and the first current IS an inductor current sampling signal IL, and in other embodiments, the first current may also be a current sampling signal IS1 of the current through the first power switch S1 or a current sampling signal IS2 of the current through the second power switch S2 in the bidirectional converter 14. The direction of the inductor current IS positive in the direction from the common terminal of the first power switch S1 and the second power switch S2 to the energy storage capacitor 13 (as shown in fig. 9), and the direction in which the current sampling signal IS1 of the current passing through the first power switch S1 or the current sampling signal IS2 of the current passing through the second power switch S2 IS positive (as shown in fig. 9) corresponds to the positive direction of the inductor current.
The control module 1414 is configured to receive the inductor current reference signal Iref, the second current Isen, and the first enable signal EN, and when the first enable signal EN is asserted, output control signals Vc1 and Vc2 to control the on and off of the first power switch S1 and the second power switch S2, respectively, so as to control the switching state of the bidirectional converter 14, thereby controlling the magnitude and direction of the inductor current, so that Isen approaches Iref, and further making the first sampling signal V1 equal to the third reference voltage signal Vref 3. It should be noted that the present invention may control the direction and magnitude of the inductor current through any current control mode, which is not limited by the present invention.
Optionally, the control circuit further includes a driving module 1417, which is configured to generate driving signals V11 and V22 capable of driving the first power switch S1 and the second power switch S2 according to the control signals Vc1 and Vc2, respectively.
In addition, the control circuit further comprises a first sampling circuit 1416 and a second sampling circuit 1415, wherein the first sampling circuit 1416 is used for generating a first sampling signal V1 according to the voltage Vin of the first end of the bidirectional converter 14, and the second sampling circuit 1415 is used for generating a second sampling signal V2 according to the voltage Vcap of the energy storage capacitor 13. As shown in fig. 9, the first sampling circuit 1416 and the second sampling circuit 1415 are voltage dividing circuits. Specifically, the first sampling circuit 1416 includes a third resistor R3 and a fourth resistor R4, the third resistor R3 and the fourth resistor R4 are connected in series between the voltage Vin at the first end of the bidirectional converter 14 and the ground, and the first sampling signal V1 is a common-end voltage of the third resistor R3 and the fourth resistor R4. The second sampling circuit 1415 comprises a first resistor R1 and a second resistor R2, the first resistor R1 and the second resistor R2 are connected in series between the voltage Vcap of the energy storage capacitor 12 and the ground, and the second sampling signal V2 is a common voltage of the first resistor R1 and the second resistor R2. The first sampling circuit 1416 and the second sampling circuit 1415 may be in other forms, and the invention is not limited thereto.
The operation of the first embodiment is described with reference to fig. 8 and 6. Since the bidirectional converter 14 operates in forward direction as a buck circuit and in reverse direction as a boost circuit, Vcv < Vcp < Vin.
In the interval t0-t 0', the bidirectional converter 14 operates in the forward direction and operates in the buck state, the current i _ ex at the first end of the bidirectional converter 14 flows from the first end of the bidirectional converter 14 to the energy storage capacitor 13 to charge the energy storage capacitor 13, and the voltage of the energy storage capacitor 13 rises from Vcv to Vcp. The Load current i _ Load and the current i _ ex at the first terminal of the bidirectional converter 14 are both provided by the first power converter 11.
During the time period t 0't 1, the bidirectional converter 14 is not operating. The Load current i _ Load is provided by the first power converter 11.
During the period from t1 to t2, the bidirectional converter 14 operates in reverse and operates in a boost state, the current i _ ex at the first terminal of the bidirectional converter 14 flows from the energy storage capacitor 13 to the first terminal of the bidirectional converter 14, so that the energy storage capacitor 13 discharges to the load 12, and the voltage of the energy storage capacitor 13 decreases from Vcp to Vcv. The Load current i _ Load is supplied by the bidirectional converter 14 and the first power converter 11 simultaneously.
Fig. 10 is a circuit diagram of a second embodiment of the driving circuit of the invention, and fig. 11 is a control circuit diagram of the second embodiment of the invention. The difference between the second embodiment and the first embodiment is that:
1. the bidirectional converter 14 is a bidirectional boost converter, the bidirectional converter comprises a boost circuit and a control circuit 141, the boost circuit comprises a first power switch S1, a second power switch S2 and a first inductor L1, one end of the first inductor L1 is connected to the high potential end of the first end of the bidirectional converter 14, the other end of the first inductor L1 is connected to the first end of the first power switch S1, the second end of the first power switch is connected to the high potential end of the energy storage capacitor 13, the second end of the second power switch S2 is connected to the common end of the first inductor L1 and the first power switch S1, and the first end of the second power switch S2 is grounded.
2. The direction of the inductor current in the control circuit 141 IS positive in the direction from the first terminal of the bidirectional converter 14 to the common terminal of the first power switch S1 and the second power switch S2 (as shown in fig. 11), and the direction in which the current sampling signal IS1 of the current passing through the first power switch S1 or the current sampling signal IS2 of the current passing through the second power switch S2 IS positive (as shown in fig. 11) corresponds to the positive direction of the inductor current.
The operation of the second embodiment is described with reference to fig. 10 and 6. Since the bidirectional converter 14 operates as a boost circuit in the forward direction and as a buck circuit in the reverse direction, Vin < Vcv < Vcp.
In the interval from t0 to t 0', the bidirectional converter 14 operates in the forward direction and operates in the boost state, the current i _ ex at the first end of the bidirectional converter 14 flows from the first end of the bidirectional converter 14 to the energy storage capacitor 13 to charge the energy storage capacitor 13, and the voltage of the energy storage capacitor 13 rises from Vcv to Vcp. The Load current i _ Load and the current i _ ex at the first terminal of the bidirectional converter 14 are both provided by the first power converter 11.
During the time period t 0't 1, the bidirectional converter 14 is not operating. The Load current i _ Load is provided by the first power converter 11.
During the period from t1 to t2, the bidirectional converter 14 operates in reverse and in buck, the current i _ ex at the first terminal of the bidirectional converter 14 flows from the energy storage capacitor 13 to the first terminal of the bidirectional converter 14, so that the energy storage capacitor discharges to the load 12, and the voltage of the energy storage capacitor 13 decreases from Vcp to Vcv. The Load current i _ Load is supplied by the bidirectional converter 14 and the first power converter 11 simultaneously.
Further, the second embodiment further includes a current limiting circuit, and the current limiting circuit is configured to limit an inrush current, i.e., a maximum current, in the bidirectional converter. Preferably, the current limiting circuit is an inrush current limiter. Optionally, the inrush current limiter is a power switch (a switching tube), the power switch operates in a linear state, and the voltage of the control end of the power switch is reduced to increase the resistance of the power switch, so as to limit the maximum current. The current limiting circuit may be used to limit the maximum current of the bidirectional converter when operating in forward or reverse. Second embodiment the current limiting circuit is mainly used to limit the maximum input current or the maximum output current when the bidirectional converter operates in the boost state in the forward direction, and specifically, the current limiting circuit is used to limit the surge current when the bidirectional converter operates in the boost state in the forward direction and the bidirectional converter is just powered on, that is, the voltage of the energy storage capacitor 13 rises from 0 to Vin.
As shown in fig. 12, in the second embodiment, the current limiting circuit is a power switch (switch tube) S33, and the power switch S33 and the first power switch S1 are coupled in series to form a bidirectional switch S11, instead of the first power switch S1 in fig. 10. Specifically, a first terminal of the power switch S33 is connected to a first terminal of the first power switch S1, and a control terminal of the power switch S33 is connected to a control terminal of the first power switch S1. The current limiting circuit of fig. 12 is mainly used to limit the maximum output current of the bidirectional converter when it is operating in the boost state in the forward direction, and also provides short-circuit protection for the energy storage capacitor 13. When the power switch S33 is operating in the linear state, the control module 1414 of the control circuit 141 controls the resistance of the power switch S33 by controlling the voltage at the control terminal of the power switch S33 to control the maximum output current, as shown in fig. 11.
Further, in the second embodiment, the current limiting circuit may also be connected to other parts, as shown in fig. 13, the current limiting circuit is a power switch (switch tube) S33 ', and the power switch S33' is coupled between the first terminal of the bidirectional converter 14 and the load 12. The current limiting circuit in fig. 13 is mainly used to limit the maximum input current when the bidirectional converter is operating in the boost state in the forward direction, and since the bidirectional converter is a bidirectional boost converter, the voltage at the first end of the bidirectional converter is lower than the voltage of the energy storage capacitor, so that the withstand voltage required by the power switch S33' in fig. 13 is lower than that required by the power switch S33 in fig. 12, and thus a current limiting device with a lower withstand voltage can be selected in fig. 13. The power switch S33 ' operates in a linear state, and the control module 1414 of the control circuit 141 controls the resistance of the power switch S33 ' by controlling the voltage at the control terminal of the power switch S33 ' to control the maximum input current.
Fig. 14 is a circuit diagram of a third embodiment of the driving circuit of the invention, and fig. 15 is a control circuit diagram of the third embodiment of the invention. The difference between the third embodiment and the first embodiment is that:
1. the bidirectional converter 14 is a bidirectional buck-boost converter, the bidirectional converter comprises a buck-boost circuit and a control circuit 141, the buck-boost circuit comprises a first power switch S1, a second power switch S2, a third power switch S3, a fourth power switch S4 and a first inductor L1, the first power switch S1 and the second power switch S2 are sequentially connected in series at a first end of the bidirectional converter 14, one end of the first inductor L1 is connected to a common end of the first power switch S1 and the second power switch S2, the other end of the first inductor L1 is connected to a first end of the fourth power switch S4, a second end of the fourth power switch S4 is connected to a high end of the energy storage capacitor 13, a second end of the third power switch S3 is connected to a common end of the first inductor L1 and the fourth power switch S4, a first terminal of the third power switch S3 is connected to ground.
2. The control module 1414 is configured to receive an inductor current reference signal Iref, a second current Isen, and a first enable signal EN, and when the first enable signal EN is asserted, output control signals Vc1, Vc2, Vc3, and Vc4, and respectively control the on and off of the first power switch S1, the second power switch S2, the second power switch S3, and the fourth power switch S4, so as to control the switching state of the bidirectional converter 14.
3. The first current may also be a current sample signal IS1 of the current through the first power switch S1 or a current sample signal IS2 of the current through the second power switch S2 or a current sample signal IS3 of the current through the third power switch S3 or a current sample signal IS4 of the current through the fourth power switch S4 in the bidirectional converter 14. The direction of the inductor current in the control circuit 141 IS positive in a direction (as shown in fig. 15) flowing from the common terminal of the first power switch S1 and the second power switch S2 to the common terminal of the third power switch S3 and the fourth power switch S4, and the direction (as shown in fig. 15) in which the current sampling signal IS1 of the current passing through the first power switch S1, the current sampling signal IS2 of the current passing through the second power switch S2, the current sampling signal IS3 of the current passing through the third power switch S3, and the current sampling signal IS4 of the current passing through the fourth power switch S4 are positive corresponds to the direction in which the inductor current IS positive.
The operation of the first embodiment is described with reference to fig. 14 and 6. Since the bidirectional converter 14 is a bidirectional buck-boost converter, Vcv < Vin < Vcp.
In a range from t0 to t 0', the bidirectional converter 14 works in the forward direction and works in a buck-boost state, specifically, during a period that the voltage Vcap of the energy storage capacitor 13 rises from Vcv to Vin, the first inductor L1, the first power switch S1 and the second power switch S2 form a buck circuit and work in the buck state, the third power switch S3 is turned off all the time, and the fourth power switch S4 is turned on all the time; during the period that the voltage Vcap of the energy storage capacitor 13 rises from Vin to Vcp, the first inductor L1, the third power switch S3 and the fourth power switch S4 form a boost circuit, and operate in a boost state, the first power switch S1 is always turned on, and the second power switch S2 is always turned off. In this interval, the current i _ ex at the first terminal of the bidirectional converter 14 flows from the first terminal of the bidirectional converter 14 to the energy storage capacitor 13 to charge the energy storage capacitor 13, and the voltage of the energy storage capacitor 13 rises from Vcv to Vcp. The Load current i _ Load and the current i _ ex at the first terminal of the bidirectional converter 14 are both provided by the first power converter 11.
During the time period t 0't 1, the bidirectional converter 14 is not operating. The Load current i _ Load is provided by the first power converter 11.
During a period from t1 to t2, the bidirectional converter 14 works in a reverse direction and works in a buck-boost state, specifically, during a period that the voltage Vcap of the energy storage capacitor 13 is reduced from Vcp to Vin, the first inductor L1, the third power switch S3 and the fourth power switch S4 form a buck circuit and work in the buck state, the first power switch S1 is always on, and the second power switch S2 is always off; when the voltage Vcap of the energy storage capacitor 13 drops from Vin by Vcv, the first inductor L1, the first power switch S1 and the second power switch S2 form a boost circuit, and operate in a boost state, the third power switch S3 is turned off, and the fourth power switch S4 is turned on. In this interval, the current i _ ex at the first terminal of the bidirectional converter 14 flows from the energy storage capacitor 13 to the first terminal of the bidirectional converter 14, so that the energy storage capacitor 13 discharges to the load 12, and the voltage of the energy storage capacitor 13 decreases from Vcp to Vcv. The Load current i _ Load is supplied by the bidirectional converter 14 and the first power converter 11 simultaneously.
Further, the third embodiment also has a current limiting circuit for limiting the maximum current of the bidirectional converter in forward operation or reverse operation. The current limiting circuit may preferably be an inrush current limiter. In the third embodiment, the current limiting circuit is configured to limit a maximum input current or a maximum output current of the bidirectional converter during forward operation. Specifically, the current limiting circuit is used to limit the forward operation of the bidirectional converter, and the surge current of the bidirectional converter just after power-on, i.e., the voltage of the energy storage capacitor 13 rises from 0 to Vin.
Specifically, optionally, when the bidirectional converter 14 operates in the forward direction, and the first inductor L1, the third power switch S3, and the fourth power switch S4 form a boost circuit, the first power switch S1 is multiplexed as a current limiting circuit, so as to limit the maximum input current when the bidirectional converter operates in the boost state in the forward direction. When the first power switch S1 is multiplexed as a current-limiting circuit, the first power switch S1 is operated in a linear state, and the control module 1414 of the control circuit 141 controls the resistance of the first power switch S1 by controlling the voltage at the control terminal of the first power switch S1, so as to control the maximum input current.
Further, the third embodiment may also implement the current limiting function in other forms. The bidirectional converter 14 operates in the forward direction, and the control module 1414 of the control circuit 141 controls the first power switch S1 to operate in the PWM state and controls the second power switch S2 to operate in the diode state, so as to achieve the purpose of current limiting. Specifically, at this time, the first inductor L1, the first power switch S1, and the second power switch S2 form a buck circuit, and operate in a buck current-limiting state, so as to be multiplexed as a current-limiting circuit, the third power switch S3 is always turned off, and the fourth power switch S4 is always turned on, so as to control the maximum input current.
Furthermore, in the embodiment of the present invention, the power switch may adopt various existing electrically controllable switching devices, such as a Metal Oxide Semiconductor Field Effect Transistor (MOSFET), a Bipolar Junction Transistor (BJT), or an Insulated Gate Bipolar Transistor (IGBT), which is not limited by the present invention.
An embodiment of the present invention further provides a driving method applied to a driving circuit, where the driving circuit includes a bidirectional converter, a first power converter, and an energy storage capacitor, an output terminal of the first power converter is coupled to a load and the energy storage capacitor which are connected in series, and the bidirectional converter is coupled between the load and the energy storage capacitor, and the driving method includes:
the first power converter provides energy to the load in a light load interval and a heavy load interval;
at least during a part of the light load interval, the first power converter provides energy to the energy storage capacitor through the bidirectional converter;
in a heavy-load interval, the energy storage capacitor supplies energy to the load through the bidirectional converter.
When the voltage of the first end of the bidirectional converter is smaller than a first reference voltage, the load enters a heavy-load interval from a light-load interval, wherein the first end of the bidirectional converter is an end coupled with the load.
Preferably, during a part of the light load interval, the first power converter supplies energy to the energy storage capacitor through a bidirectional converter; during another part of the light load interval, the bidirectional converter does not work, and the first power converter does not provide energy to the energy storage capacitor any more.
Optionally, in a light-load interval, the first power converter supplies energy to the energy storage capacitor through a bidirectional converter.
Optionally, controlling the operating state of the bidirectional converter, so that the bidirectional converter operates in a forward direction at least in a part of the light load interval; and in a heavy-load interval, the bidirectional converter works reversely.
Furthermore, the energy storage capacitor is charged and discharged through the bidirectional converter, so that the voltage variation range of the energy storage capacitor is large, and the capacity of the energy storage capacitor is reduced.
And further, judging whether the energy storage capacitor is allowed to be charged or discharged according to the voltage of the first end of the bidirectional converter and the voltage of the energy storage capacitor. Specifically, when the voltage of the first end of the bidirectional converter is smaller than a first reference voltage, the bidirectional converter is enabled, and the energy storage capacitor is allowed to be charged and discharged; when the voltage of the energy storage capacitor is larger than a second reference voltage, the bidirectional converter does not work, and the energy storage capacitor is not allowed to be charged and discharged.
The bidirectional converter comprises an inductor, and when the bidirectional converter is enabled, the size and the direction of the inductor current are controlled according to an inductor current reference signal, so that the voltage of the first end of the bidirectional converter is a third reference voltage, wherein the inductor current reference signal is adjusted according to the voltage of the first end of the bidirectional converter. Specifically, when the voltage of the first end of the bidirectional converter is greater than the corresponding third reference voltage, the inductor current reference signal is controlled to be increased so that more energy is transmitted from the first end of the bidirectional converter to the energy storage voltage; when the voltage at the first terminal of the bidirectional converter is less than a third reference voltage, the inductor current reference signal is controlled to decrease such that less energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage or such that energy is transferred from the energy storage voltage to the first terminal of the bidirectional converter.
Although the embodiments have been described and illustrated separately, it will be apparent to those skilled in the art that some common techniques may be substituted and integrated between the embodiments, and reference may be made to one of the embodiments not explicitly described, or to another embodiment described.
While embodiments in accordance with the invention have been described above, these embodiments are not intended to be exhaustive or to limit the invention to the precise embodiments described. Obviously, many modifications and variations are possible in light of the above teaching. The embodiments were chosen and described in order to best explain the principles of the invention and the practical application, to thereby enable others skilled in the art to best utilize the invention and various embodiments with various modifications as are suited to the particular use contemplated. The invention is limited only by the claims and their full scope and equivalents.
Claims (27)
1. A driver circuit, comprising:
an energy storage capacitor;
the output end of the first power converter is coupled with a load and the energy storage capacitor which are connected in parallel, and the first power converter is used for generating a direct current signal so as to provide energy for the load in a light load interval and a heavy load interval;
a bidirectional converter coupled between the load and the energy storage capacitor;
and the first power converter supplies energy to the energy storage capacitor through the bidirectional converter at least in a part of the light load interval, and the energy storage capacitor supplies energy to the load through the bidirectional converter in the heavy load interval.
2. The drive circuit according to claim 1, wherein: when the voltage of the first end of the bidirectional converter is smaller than a first reference voltage, the load enters a heavy-load interval from a light-load interval, wherein the first end of the bidirectional converter is an end coupled with the load.
3. The drive circuit according to claim 1, wherein: during a part of the light load interval, the first power converter provides energy to the energy storage capacitor through a bidirectional converter; during another part of the light load interval, the bidirectional converter does not work, and the first power converter does not provide energy to the energy storage capacitor any more.
4. The drive circuit according to claim 1, wherein: in a light load interval, the first power converter provides energy to the energy storage capacitor through a bidirectional converter.
5. The drive circuit according to claim 1, wherein: controlling the working state of the bidirectional converter so that the bidirectional converter works in a forward direction at least in a part of the light load interval; and in a heavy-load interval, the bidirectional converter works reversely.
6. The drive circuit according to claim 1, wherein: the energy storage capacitor is charged and discharged through the bidirectional converter, so that the voltage variation range of the energy storage capacitor is large, and the capacity of the energy storage capacitor is reduced.
7. The drive circuit according to claim 1, wherein: and judging whether the energy storage capacitor is allowed to be charged or discharged according to the voltage of the first end of the bidirectional converter and the voltage of the energy storage capacitor.
8. The drive circuit according to claim 7, wherein: when the voltage of the first end of the bidirectional converter is smaller than the first reference voltage, the bidirectional converter is enabled, and the energy storage capacitor is allowed to be charged and discharged.
9. The drive circuit according to claim 7, wherein: when the voltage of the energy storage capacitor is larger than a second reference voltage, the bidirectional converter does not work, and the energy storage capacitor is not allowed to be charged and discharged.
10. The drive circuit according to claim 1, wherein: the bidirectional converter comprises an inductor, and when the bidirectional converter is enabled, the size and the direction of current flowing through the inductor are controlled according to an inductor current reference signal, so that the voltage of the first end of the bidirectional converter is a third reference voltage, wherein the inductor current reference signal is adjusted according to the voltage of the first end of the bidirectional converter.
11. The drive circuit according to claim 10, wherein:
when the voltage of the first end of the bidirectional converter is greater than the corresponding third reference voltage, controlling the inductor current reference signal to increase so that more energy is transmitted from the first end of the bidirectional converter to the energy storage voltage;
when the voltage at the first terminal of the bidirectional converter is less than a third reference voltage, the inductor current reference signal is controlled to decrease such that less energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage or such that energy is transferred from the energy storage voltage to the first terminal of the bidirectional converter.
12. The drive circuit according to claim 1, wherein: in a light-load interval, the output power of the first power converter is equal to the sum of load power and input power of the first end of the bidirectional converter; in a heavy load interval, the load power is equal to the sum of the output power of the first power converter and the output power of the first end of the bidirectional converter.
13. The drive circuit according to claim 1, wherein: the bidirectional converter is a bidirectional DC-DC converter.
14. The drive circuit according to claim 1, wherein: in a light load interval, the output current of the first power converter is equal to the sum of a load current and the input current of the first end of the bidirectional converter; in a heavy-load interval, the load current is equal to the sum of the output current of the first power converter and the output current of the first end of the bidirectional converter.
15. The drive circuit according to claim 1, wherein:
the drive circuit further comprises a control circuit, wherein the control circuit comprises an enabling circuit, receives a first sampling signal representing the voltage of the first end of the bidirectional converter, a second sampling signal representing the voltage of the energy storage capacitor, a first reference voltage signal and a second reference voltage signal, and outputs a first enabling signal;
when the first sampling signal is smaller than the first reference voltage signal, the first enabling signal is effective, the bidirectional converter is enabled, and when the second sampling signal is larger than the second reference voltage signal, the first enabling signal is ineffective, and the bidirectional converter does not work.
16. The drive circuit according to claim 15, wherein: the bidirectional converter includes an inductor, and the control circuit further includes:
the reference signal adjusting circuit receives the first sampling signal and the third reference voltage signal, and outputs and adjusts an inductive current reference signal;
the inductive current sampling circuit samples a first current representing the inductive current, increases direct current bias on the first current and outputs a second current, and the second current is a positive value;
the control module is used for receiving the inductive current reference signal, the second current and the first enabling signal and outputting a control signal so as to control the switching state of the bidirectional converter and further control the magnitude and the direction of the inductive current;
wherein when the first sampling signal is greater than the third reference voltage signal, the inductor current reference signal is controlled to increase such that more energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage; when the first sampling signal is less than the third reference voltage signal, controlling the inductor current reference signal to decrease such that less energy is transferred from the first terminal of the bidirectional converter to the energy storage voltage or such that energy is transferred from the energy storage voltage to the first terminal of the bidirectional converter.
17. The drive circuit according to claim 1, wherein: the bidirectional converter is a bidirectional buck converter, and when the bidirectional converter works in the forward direction, the bidirectional converter works in a buck state; when the bidirectional converter works in a reverse direction, the bidirectional converter works in a boost state.
18. The drive circuit according to claim 1, wherein: the bidirectional converter is a bidirectional boost converter, and when the bidirectional converter works in the forward direction, the bidirectional converter works in a boost state; and when the bidirectional converter works in the reverse direction, the bidirectional converter works in a buck state.
19. The drive circuit according to claim 1, wherein: the bidirectional converter is a bidirectional buck-boost converter, and when the bidirectional converter works in the forward direction, the bidirectional converter works in a buck state firstly and then works in a boost state; when the bidirectional converter works reversely, the bidirectional converter works in buck state firstly and then works in boost state.
20. The drive circuit according to claim 18 or 19, wherein: the bidirectional converter comprises a current limiting circuit for limiting the maximum input current or the maximum output current when the bidirectional converter works in the forward direction.
21. The drive circuit according to claim 20, wherein: the bidirectional converter is a bidirectional boost converter, and the current limiting circuit is coupled between a first terminal of the bidirectional converter and the load to limit the maximum input current.
22. The drive circuit according to claim 20, wherein: the bidirectional converter is a bidirectional boost converter, and comprises a power switch, wherein the power switch is coupled with the energy storage capacitor, and the current limiting circuit is coupled with the power switch to limit the maximum output current.
23. The drive circuit according to claim 20, wherein: the bidirectional converter is a bidirectional buck-boost converter, the buck-boost circuit comprises a power switch, the power switch is coupled with the load, and when the bidirectional converter works in a boost state in a forward direction, the power switch is multiplexed into a current limiting circuit.
24. The drive circuit according to any one of claims 21 to 23, wherein: the current limiting circuit is a switching tube, the switching tube works in a linear state, and the resistance of the switching tube is controlled by controlling the voltage of a control end of the switching tube so as to control the maximum output current or the maximum input current.
25. The drive circuit according to claim 20, wherein: the bidirectional converter is a bidirectional buck-boost converter, the buck-boost circuit comprises an inductor, a first power switch and a second power switch, the first power switch is coupled with the load, the second power switch is coupled with the first power switch, the inductor is coupled with both the first power switch and the second power switch, the first power switch works in a PWM state, the second power switch serves as a diode, and the inductor, the first power switch and the second power switch form a buck circuit so as to be multiplexed into a current limiting circuit.
26. The drive circuit according to claim 1, wherein: the first power converter is a DC-DC converter or an AC-DC converter.
27. A driving method applied to a driving circuit, the driving circuit including a bidirectional converter, a first power converter and an energy storage capacitor, the first power converter having an output terminal coupled to a load and the energy storage capacitor connected in parallel, the bidirectional converter being coupled between the load and the energy storage capacitor, the driving method comprising:
the first power converter provides energy to the load in a light load interval and a heavy load interval;
at least during a part of the light load interval, the first power converter provides energy to the energy storage capacitor through the bidirectional converter;
in a heavy-load interval, the energy storage capacitor supplies energy to the load through the bidirectional converter.
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| CN202010813834.XA CN112039319A (en) | 2020-08-13 | 2020-08-13 | Drive circuit and drive method |
| US17/400,818 US11682964B2 (en) | 2020-08-13 | 2021-08-12 | Driving circuit and driving method |
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| CN202010813834.XA CN112039319A (en) | 2020-08-13 | 2020-08-13 | Drive circuit and drive method |
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| CN112821757A (en) * | 2020-12-30 | 2021-05-18 | 南京矽力微电子技术有限公司 | Power converter |
| WO2023070308A1 (en) * | 2021-10-26 | 2023-05-04 | Telefonaktiebolaget Lm Ericsson (Publ) | Power supply and a method performed by a power supply |
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| US12143017B2 (en) | 2022-07-29 | 2024-11-12 | Ge Aviation Systems Llc | Energy accumulator apparatus and associated methods |
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| US20220052597A1 (en) | 2022-02-17 |
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