[go: up one dir, main page]

CN111141949A - Alternating voltage sampling circuit for output power control and design method thereof - Google Patents

Alternating voltage sampling circuit for output power control and design method thereof Download PDF

Info

Publication number
CN111141949A
CN111141949A CN202010088867.2A CN202010088867A CN111141949A CN 111141949 A CN111141949 A CN 111141949A CN 202010088867 A CN202010088867 A CN 202010088867A CN 111141949 A CN111141949 A CN 111141949A
Authority
CN
China
Prior art keywords
resistor
voltage
operational amplifier
circuit
chip
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN202010088867.2A
Other languages
Chinese (zh)
Other versions
CN111141949B (en
Inventor
王念春
崔熠凡
彭斌
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Wuxi Juneng New Energy Technology Co ltd
Original Assignee
Southeast University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Southeast University filed Critical Southeast University
Priority to CN202010088867.2A priority Critical patent/CN111141949B/en
Publication of CN111141949A publication Critical patent/CN111141949A/en
Application granted granted Critical
Publication of CN111141949B publication Critical patent/CN111141949B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/25—Arrangements for measuring currents or voltages or for indicating presence or sign thereof using digital measurement techniques
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R15/00—Details of measuring arrangements of the types provided for in groups G01R17/00 - G01R29/00, G01R33/00 - G01R33/26 or G01R35/00
    • G01R15/04—Voltage dividers
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R15/00—Details of measuring arrangements of the types provided for in groups G01R17/00 - G01R29/00, G01R33/00 - G01R33/26 or G01R35/00
    • G01R15/14—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks
    • G01R15/22—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks using light-emitting devices, e.g. LED, optocouplers

Landscapes

  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Rectifiers (AREA)

Abstract

本发明公开了一种用于输出功率控制的交流电压采样电路及其设计方法，包括交流分压电路、二阶带通有源滤波电路、高精度全波整流器电路、比较器电路和隔离采样电路，其中交流输入电压输入交流分压电路，交流分压电路输出端与二阶带通有源滤波电路输入端连接，二阶带通有源滤波电路输出端与高精度全波整流器电路输入端连接，高精度全波整流器输出端与比较器电路输入端连接，比较器电路输出端与隔离采样电路输入端连接。该方法避免原边单片机采样再传输到副边而造成开关电源采样延时和成本的增加，使得车载电源精准的根据输入电压进行降功率。

Figure 202010088867

The invention discloses an AC voltage sampling circuit for output power control and a design method thereof, including an AC voltage divider circuit, a second-order band-pass active filter circuit, a high-precision full-wave rectifier circuit, a comparator circuit and an isolation sampling circuit , wherein the AC input voltage is input to the AC voltage divider circuit, the output end of the AC voltage divider circuit is connected to the input end of the second-order band-pass active filter circuit, and the output end of the second-order band-pass active filter circuit is connected to the input end of the high-precision full-wave rectifier circuit , the output end of the high-precision full-wave rectifier is connected with the input end of the comparator circuit, and the output end of the comparator circuit is connected with the input end of the isolation sampling circuit. The method avoids the sampling delay and cost increase of the switching power supply caused by the sampling of the primary side microcontroller and then transmitted to the secondary side, so that the vehicle power supply can accurately reduce the power according to the input voltage.

Figure 202010088867

Description

Alternating voltage sampling circuit for output power control and design method thereof
Technical Field
The invention belongs to the technical field of electronics, and mainly comprises an alternating current voltage division circuit, a second-order band-pass active filter circuit, a high-precision full-wave rectifier circuit, a comparator circuit and an isolation sampling circuit; to an ac voltage sampling circuit for output power control and a method of designing the same.
Background
The switch power supply is a power supply which utilizes the modern power electronic technology to control the time proportion of the on and off of a switch tube and maintain the stability of output voltage. The switching power supply is generally composed of a Pulse Width Modulation (PWM) control chip (IC), a transformer, and a switching tube (MOSFET). With the development and innovation of power electronic technology, the technology of the switching power supply is continuously innovated. At present, the switching power supply is widely applied to almost all electronic devices due to its characteristics of small size, light weight and high efficiency, and is an indispensable power supply mode for the rapid development of the electronic information industry.
In order to meet the requirements of equipment, the switching power supply requires wide ranges of input voltage and output voltage, and when the difference between the input voltage and the output voltage is large, a transformer can be used, so that the isolation effect is achieved, and the wide output voltage range can be adapted. In the field of new energy, a vehicle-mounted power supply needs to adapt to the voltage fluctuation of a power grid, for example, the European voltage is 110V, the domestic commercial power (alternating current input voltage) is 220V, and the commercial power refers to single-phase alternating current; in order to meet the charging requirement, when the input voltage is reduced to a certain value, the vehicle-mounted power supply cannot be shut down and only can be operated in a power reducing mode.
In the charging device of the electric vehicle, the input voltage sampling circuit of the switching power supply aims to realize power reduction and shutdown according to a certain rule according to the currently sampled alternating input voltage value and prevent the possible overheating damage caused by overlarge current of a power switch tube (MOSFET) under the condition of low input voltage. The sampling of the input voltage of the low-power switch power supply mostly directly adopts the undervoltage protection function of a control chip (IC), the input voltage enters the inverting input end of the internal operational amplifier of the IC through resistance voltage division and is compared with the reference voltage of the non-inverting input end, when the input voltage is smaller than the reference voltage, the PWM driving signal is closed, namely, when the input voltage is lower than a certain value, the switch power supply is directly shut down. The input voltage range under the mode is narrow, and certain requirements are required on the input voltage during operation.
In order to realize power reduction, real-time input voltage needs to be sampled at the primary side of the vehicle-mounted power supply, and because a chip for realizing the power reduction control function is arranged at the secondary side, the chip needs to collect output voltage, output current and the like and control the output voltage and the output current according to the magnitude of the input voltage. At present, the charging machine industry mostly adopts a method of using a single chip microcomputer on a primary side to sample input voltage. As shown in fig. 1, the input voltage is rectified and filtered to obtain a direct current component, and the direct current component enters a sampling circuit after passing through a voltage division circuit; the singlechip converts the input voltage according to the proportional voltage of the ADC port, the communication between the two chips needs to pass through the optical coupler because the two chips are in an isolated state, the singlechip transmits the value of the sampled input voltage into the control chip on the secondary side through serial communication and the optical coupler, and the control chip controls the driving signal of the main circuit according to the obtained voltage and controls the output power. The method has the defects of time delay and inaccuracy in the process of filtering after sampling and transmitting to the control chip through the serial port, and the problem that a single chip microcomputer is added on the primary side, so that the cost is increased, the circuit is complex, the hardware cost is increased, and the workload of research and development personnel is increased in the aspect of software.
Disclosure of Invention
The purpose of the invention is as follows: in order to solve the technical defects of time delay and inaccuracy of input voltage sampling in the prior art, the alternating voltage sampling circuit for output power control and the design method thereof are provided, so that the problems of time delay and cost increase of the switching power supply caused by the fact that a primary-side single chip microcomputer samples and then transmits the samples to a secondary side are avoided, and the vehicle-mounted power supply accurately performs power reduction according to the input voltage.
The technical scheme is as follows: in order to realize the purpose, the invention adopts the following technical scheme:
the utility model provides an alternating voltage sampling circuit for output power control, including exchanging bleeder circuit, second order band-pass active filter circuit, high accuracy full wave rectifier circuit, comparator circuit and isolation sampling circuit, wherein exchange input voltage input exchange bleeder circuit, exchange bleeder circuit output and second order band-pass active filter circuit input and be connected, second order band-pass active filter circuit output and high accuracy full wave rectifier circuit input are connected, high accuracy full wave rectifier output is connected with comparator circuit input, comparator circuit output and isolation sampling circuit input are connected.
Optionally, the ac voltage dividing circuit includes a resistor R4 and a resistor R6, the ac input voltage is connected to the resistor R4 and then connected to the ground GND through a resistor R6, and the center points of the resistor R4 and the resistor R6 are connected to the input end of the second-order band-pass active filter circuit; the voltage of the divided alternating current input voltage can be changed by changing the resistance values of the resistor R and the resistor R6.
Optionally, the second-order band-pass active filter circuit includes a resistor R3, a resistor R5, a resistor R9, a capacitor C1, a capacitor C3, a capacitor C4, and an operational amplifier chip OA 1; the output voltage of the alternating current voltage division circuit is connected to a resistor R5 and then connected to the negative input end of an operational amplifier chip OA1 through a capacitor C3; one end of the resistor R9 is connected to the center point of the resistor R5 and the capacitor C3, and the other end is connected to the ground GND; the output end of the operational amplifier chip OA1 is connected to the central points of the resistor R5 and the capacitor C3 and the negative input end of the operational amplifier chip OA1 through a capacitor C1 and a resistor R3 respectively; the positive power supply VCC is connected to the positive input end of the operational amplifier chip OA1 after being divided by the resistor R12 and the resistor R15, and is connected to the ground GND through the capacitor C4; the positive and negative power supply terminals of the operational amplifier chip OA1 are connected to the positive voltage VCC and the ground GND, respectively.
Optionally, the high-precision full-wave rectifier circuit comprises a resistor R1, a resistor R2, a resistor R7, a diode D1, a diode D2, a capacitor C2, and operational amplifier chips OA2 and OA 3; the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA2, the cathode input end of the second-order band-pass active filter circuit is connected in parallel with a capacitor C2 through a diode D1, a resistor R1 is connected to the output end and the cathode input end of the operational amplifier chip OA3, and the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA3 through a diode D2; the negative input end of the operational amplifier chip OA3 is connected to the output end of the operational amplifier chip OA3 through a resistor R2, and the positive input end of the operational amplifier chip OA3 is connected to a ground wire R7 through a resistor R7; the positive and negative power supply ends of the operational amplifier chips OA2 and OA3 are respectively connected to the positive voltage VCC and the ground GND; the high-precision full-wave rectifier circuit converts sinusoidal alternating current into direct current.
Optionally, the comparator circuit includes a voltage stabilizing chip, an operational amplifier chip OA4, a resistor R11, a resistor R13 and a resistor R16, the voltage stabilizing chip, the resistor R11, the resistor R13 and the resistor R16 are configured to generate a precise and stable dc voltage, and the dc voltage is connected to the negative voltage input terminal of the operational amplifier chip OA 4; the output end of the high-precision full-wave rectifier circuit is connected to the positive voltage input end of the operational amplifier chip OA 4; the positive and negative input voltages of the operational amplifier chip OA4 are compared by the operational amplifier chip, and then a square wave signal with the amplitude VCC is generated at the output end of the operational amplifier chip.
Optionally, the isolation circuit part in the isolation sampling circuit includes an isolation optocoupler, a resistor R10, a resistor R14, a resistor R8, the output end of the comparator circuit is connected with the first port of the isolation optocoupler through a resistor R10, the second port of the isolation optocoupler is connected with GND through a resistor R14, the third port of the isolation optocoupler is connected with the power supply through a resistor R8, and the fourth port of the isolation optocoupler is connected with the SGND.
The invention also provides a design method of the alternating voltage sampling circuit for controlling the output power, which comprises the following design steps:
(1) establishing an alternating current voltage dividing circuit which comprises a resistor R4 and a resistor R6, wherein alternating current input voltage is connected to a resistor R4 and then connected to a ground wire GND through a resistor R6, and the voltage of the alternating current input voltage after voltage division can be changed by changing the resistance values of the resistor R4 and the resistor R6; setting the voltage obtained by the AC voltage divider circuit to V1Voltage V obtained by an AC voltage divider circuit1And an alternating current input voltage VinThe relationship of (1) is:
Figure BDA0002383027230000031
(2) establishing a second-order band-pass active filter circuit which comprises a resistor R3, a resistor R5, a resistor R9, a capacitor C1, a capacitor C3, a capacitor C4 and an operational amplifier chip OA 1; the output voltage of the alternating current voltage division circuit is connected to a resistor R5 and then connected to the negative input end of an operational amplifier chip OA1 through a capacitor C3; one end of the resistor R9 is connected to the center point of the resistor R5 and the capacitor C3, and the other end is connected to the ground GND; the output end of the operational amplifier chip OA1 is connected to the central points of the resistor R5 and the capacitor C3 and the negative input end of the operational amplifier chip OA1 through a capacitor C1 and a resistor R3 respectively; the positive power supply VCC is connected to the positive input end of the operational amplifier chip OA1 after being divided by resistors R12 and R15, and is connected to the ground GND through a capacitor C4; the positive and negative power supply terminals of the operational amplifier chip OA1 are respectivelyTo a positive voltage VCC and ground GND; let C1 ═ C3 ═ C, ReqIs the value of R1 in parallel with R2, BW represents the bandwidth of the filter circuit, fcRepresenting the set center frequency, and setting Q to represent the quality factor, the following equation is obtained:
Figure BDA0002383027230000041
Figure BDA0002383027230000042
Figure BDA0002383027230000043
(3) establishing a high-precision full-wave rectifier circuit which comprises a resistor R1, a resistor R2, a resistor R7, a diode D1, a diode D2, a capacitor C2 and operational amplifier chips OA2 and OA 3; the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA2, the cathode input end of the second-order band-pass active filter circuit is connected in parallel with a capacitor C2 through a diode D1, a resistor R1 is connected to the output end and the cathode input end of the operational amplifier chip OA3, and the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA3 through a diode D2; the negative input end of the operational amplifier chip OA3 is connected to the output end of the operational amplifier chip OA3 through a resistor R2, and the positive input end of the operational amplifier chip OA3 is connected to a ground wire R7 through a resistor R7; the positive and negative power supply ends of the operational amplifier chips OA2 and OA3 are respectively connected to the positive voltage VCC and the ground GND; setting the input voltage of a high-precision full-wave rectifier circuit to V2Output voltage of V3；
1) Selecting the gain of the positive input signal:
Figure BDA0002383027230000044
2) selecting the gain of the negative input signal:
Figure BDA0002383027230000045
3) r1, R2, R7 were chosen to have the same resistance value:
R1＝R2＝R7；
4) c2 is selected based on the desired transient response.
(4) Establishing a comparator circuit which comprises a voltage stabilizing chip, an operational amplifier chip OA4, a resistor R11, a resistor R13 and a resistor R16, wherein the voltage stabilizing chip, the resistor R11, the resistor R13 and the resistor R16 are used for generating accurate and stable direct current voltage which is connected to a negative electrode voltage input end of the operational amplifier chip OA 4; the output end of the high-precision full-wave rectifier circuit is connected to the positive voltage input end of the operational amplifier chip OA 4; setting the positive input voltage of the operational amplifier chip to be VpNegative input voltage is VnThe relation between the output voltage of the voltage stabilizing chip and the negative electrode input voltage of the operational amplifier chip is as follows:
Figure BDA0002383027230000051
the duty ratio of the output waveform of the operational amplifier chip OA4 is set as D, and the relationship between the duty ratio and the positive input voltage and the negative input voltage of the operational amplifier chip is as follows:
Figure BDA0002383027230000052
(5) an isolation sampling circuit is established, wherein the isolation circuit part comprises an isolation optocoupler, a resistor R10, a resistor R14 and a resistor R8, the output end of the comparator circuit is connected with a first port of the isolation optocoupler through a resistor R10, a second port of the isolation optocoupler is connected with GND through a resistor R14, a third port of the isolation optocoupler is connected with a power supply through a resistor R8, and a fourth port of the isolation optocoupler is connected with SGND.
(6) Through the formulas and methods provided in the steps (1) to (4), the relation between the duty ratio D and the alternating current input voltage value is obtained as follows:
Figure BDA0002383027230000053
(7) when the alternating-current input voltage changes, the duty ratio of the voltage square-wave signal output by the operational amplifier chip OA4 also changes, the duty ratio is measured by the eCAP module inside the control chip, and the alternating-current input voltage value is calculated by the formula and method provided in the step (6).
Further, the operational amplifier chip OA1 is a dual-path high-speed low-noise operational amplifier with model number MC 33078; the operational amplifier chips OA2 and OA3 are two-way low-noise high-speed JFET input operational amplifiers with the model number TLE 2072; the operational amplifier chip OA4 is a low power consumption dual operational amplifier with model number LM 258.
Furthermore, the voltage stabilizing chip is a three-end adjustable shunt reference voltage source, and the model number of the voltage stabilizing chip is TL 431; the isolation optocoupler is a low profile coupler, type TLP 185.
Further, the control chip is a DSP, and the model thereof is TMS320F 28035.
Has the advantages that: compared with the prior art, the invention has the following advantages:
(1) the method avoids the situation that a single chip microcomputer is added on the primary side or an isolation sampling device with higher price is used for sampling the alternating current input voltage, reduces the hardware design difficulty and saves the design cost;
(2) compared with the method for carrying out isolation sampling by using a transformer, the method has the advantages that the isolation optocoupler is utilized to realize electrical isolation of the original secondary side, sampling deviation caused by turn-to-turn voltage change of the transformer when the load of the vehicle-mounted power supply is changed is avoided, and more accurate voltage sampling and power reduction control are realized;
(3) the second-order band-pass active filter circuit is used for filtering the alternating voltage, so that the alternating voltage signal only keeps the part of the frequency near the fundamental wave frequency of the alternating input voltage, the sine of the sampled alternating voltage signal is ensured to the greatest extent, and the result obtained when the alternating voltage value is calculated by a formula in the follow-up process is more accurate, so that the power reduction control is more accurate;
(4) the high-precision full-wave rectifier circuit is used for rectifying the alternating current signals without using a traditional diode rectification mode, and the influence of diode voltage drop on a rectification result is avoided.
Drawings
FIG. 1 is a schematic diagram of AC input voltage sampling by level;
FIG. 2 is a schematic diagram of the control system of the present invention;
FIG. 3 is an isolated AC voltage sampling circuit diagram;
fig. 4 is a waveform diagram of the conversion of an ac input voltage to a duty cycle signal.
Detailed Description
The technical solution of the present invention is described in detail below with reference to the accompanying drawings and specific embodiments.
As shown in fig. 2 and 3, an ac voltage sampling circuit for output power control includes an ac voltage dividing circuit, a second-order band-pass active filter circuit, a high-precision full-wave rectifier circuit, a comparator circuit and an isolation sampling circuit, wherein an ac input voltage is input to the ac voltage dividing circuit, an output of the ac voltage dividing circuit is connected to an input of the second-order band-pass active filter circuit, an output of the second-order band-pass active filter circuit is connected to an input of the high-precision full-wave rectifier circuit, an output of the high-precision full-wave rectifier circuit is connected to an input of the comparator circuit, and an output of the comparator circuit is connected to an input of the isolation sampling circuit; the isolation sampling circuit adopts optical coupling isolation.
As shown in fig. 3, the ac voltage dividing circuit includes resistors R4 and R6, the ac input voltage is connected to the resistor R4 and then connected to the ground GND through the resistor R6, and the voltage magnitude of the divided ac input voltage can be changed by changing the resistances of the resistors R4 and R6; the function of the alternating current voltage division circuit is to divide the high-voltage alternating current input into low-voltage alternating current input, so that an operational amplifier in a post-stage circuit works in a reasonable voltage range.
The second-order band-pass active filter circuit comprises resistors R3, R5 and R9, capacitors C1, C3 and C4 and an operational amplifier chip OA 1; the output voltage of the alternating current voltage division circuit is connected to R5 and then connected to the negative electrode input end (pin No. 2) of the operational amplifier chip OA1 through a capacitor C3; one end of the resistor R9 is connected to the center point of the resistor R5 and the capacitor C3, and the other end is connected to the ground GND; the output end (pin 1) of the operational amplifier chip OA1 is connected to the central point of the resistor R5 and the capacitor C3 and the negative input end of the operational amplifier chip OA1 through the capacitor C1 and the resistor R3 respectively; the positive power supply VCC is connected to the positive input end of the operational amplifier chip OA1 after being divided by resistors R12 and R15, and is connected to the ground GND through a capacitor C4; the positive and negative power supply ends of the operational amplifier chip OA1 are respectively connected to a positive voltage VCC and a ground wire GND; the upper limit cut-off frequency and the lower limit cut-off frequency of the second-order band-pass active filter circuit can be very close to each other, and the second-order band-pass active filter circuit has very strong frequency selection characteristics, so that the alternating voltage passing through the filter only keeps the part of the frequency near the fundamental wave frequency of the alternating input voltage, good sine of the subsequently sampled alternating signal is ensured, and the sampled alternating voltage value is more accurate.
The high-precision full-wave rectifier circuit comprises resistors R1, R2 and R7, diodes D1 and D2, a capacitor C2 and operational amplifier chips OA2 and OA 3; the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA2, the cathode input end of the second-order band-pass active filter circuit is connected in parallel with a capacitor C2 through a diode D1, a resistor R1 is connected to the output end and the cathode input end of the operational amplifier chip OA3, and the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA3 through a diode D2; the negative input end of the operational amplifier chip OA3 is connected to the output end of the operational amplifier chip OA3 through a resistor R2, and the positive input end of the operational amplifier chip OA3 is connected to a ground wire R7 through a resistor R7; the positive and negative power supply ends of the operational amplifier chips OA2 and OA3 are respectively connected to the positive voltage VCC and the ground GND; the high-precision full-wave rectifier circuit converts sine alternating current into direct current, the coincidence degree of the rectified output waveform and the input waveform of the high-precision full-wave rectifier circuit is higher compared with that of a general diode rectifying circuit, the output voltage of the rectifier changes linearly along with the input voltage and is distinguished from zero, and the influence of diode voltage drop on the output voltage value is avoided.
The comparator circuit comprises a voltage stabilizing chip, an operational amplifier chip OA4, resistors R11, R13 and R16, wherein the voltage stabilizing chip and the resistors R11, R13 and R16 are used for generating accurate and stable direct-current voltage which is connected to the negative voltage input end of the operational amplifier chip OA 4; the output end of the high-precision full-wave rectifier circuit is connected to the positive voltage input end of the operational amplifier chip OA 4; the positive and negative input voltages of the operational amplifier chip OA4 are compared by the operational amplifier chip, and then a square wave signal with the amplitude VCC is generated at the output end of the operational amplifier chip. The principle of the operational amplifier chip for generating square wave signals is as follows: when the anode input voltage is higher than the cathode input voltage, the operational amplifier chip outputs a high level, and when the anode input voltage is lower than the cathode input voltage, the operational amplifier chip outputs a low level. Therefore, when the alternating-current input voltage changes, the voltage value obtained after the voltage division circuit and the rectifying circuit also changes, so that the duty ratio of the square wave signal obtained by the operational amplifier chip also changes, and the function of converting the voltage signal into the duty ratio signal is realized.
The isolation circuit part in the isolation sampling circuit comprises an isolation optocoupler, resistors R10, R14 and R8, the output end of the comparator circuit is connected with the first port of the isolation optocoupler through a resistor R10, the second port of the isolation optocoupler is connected with GND through a resistor R14, the third port of the isolation optocoupler is connected with a power supply through a resistor R8, and the fourth port of the isolation optocoupler is connected with SGND. Because the primary side and the secondary side of the vehicle-mounted power supply are not grounded together, the isolation optocoupler realizes the electrical isolation of a primary side voltage signal and the secondary side control chip; the sampling part comprises a control chip and a peripheral circuit thereof, and the sampling circuit has the functions of sampling a duty ratio signal by utilizing an enhanced capture module (eCAP) module in the control chip, and calculating to obtain a primary side alternating current input voltage signal by utilizing the sampled duty ratio so as to realize the subsequent power reduction control function.
The process of converting the ac input voltage signal to the duty cycle signal is shown in fig. 4. The alternating-current input voltage signal is a sine wave, the waveform obtained through the alternating-current voltage division circuit, the second-order band-pass active filter circuit and the high-precision full-wave rectifier circuit is a sine half-wave with only a positive half cycle, and the sine half-wave is compared with a fixed voltage value to obtain a duty ratio signal so as to be sampled through the control chip.
A design method of an alternating voltage sampling circuit for output power control comprises the following steps:
step 1: establishing an alternating current voltage division circuit which comprises resistors R4 and R6, wherein alternating current input voltage is connected to a resistor R4 and then connected to a ground wire GND through a resistor R6, and the voltage of the alternating current input voltage after voltage division can be changed by changing the resistance values of resistors R4 and R6; setting the resistances of the resistors R4 and R6 as R4 and R6, respectively, and setting the voltage obtained by the ac voltage divider circuit as V1, the following equations can be obtained:
voltage V obtained by AC voltage-dividing circuit1And an alternating current input voltage VinThe relationship of (1) is:
Figure BDA0002383027230000081
step 2: establishing a second-order band-pass active filter circuit which comprises resistors R3, R5 and R9, capacitors C1, C3 and C4 and an operational amplifier chip OA 1; the output voltage of the alternating current voltage division circuit is connected to R5 and then connected to the negative electrode input end (pin No. 2) of the operational amplifier chip OA1 through a capacitor C3; one end of the resistor R9 is connected to the center point of the resistor R5 and the capacitor C3, and the other end is connected to the ground GND; the output end (pin 1) of the operational amplifier chip OA1 is connected to the central point of the resistor R5 and the capacitor C3 and the negative input end of the operational amplifier chip OA1 through the capacitor C1 and the resistor R3 respectively; the positive power supply VCC is connected to the positive input end of the operational amplifier chip OA1 after being divided by resistors R12 and R15, and is connected to the ground GND through a capacitor C4; the positive and negative power supply ends of the operational amplifier chip OA1 are respectively connected to a positive voltage VCC and a ground wire GND; the resistances of the resistors R3, R5 and R9 are set as R3, R5 and R9, the capacitances of the capacitors C1, C3 and C4 are set as C1, C3 and C4, C1 is set as C3, and R5 is set as C4eqIs the value of R1 in parallel with R2, BW represents the bandwidth of the filter circuit, fcRepresenting the set center frequency, i.e., 50Hz, and setting Q to represent the quality factor, the following equation can be obtained:
Figure BDA0002383027230000091
Figure BDA0002383027230000092
Figure BDA0002383027230000093
the value of R3 can be made much larger than ReqTo obtain a larger Q value. The larger the Q value is, the better the frequency selection characteristic is;
and step 3: establishing a high-precision full-wave rectifier circuit which comprises resistors R1, R2 and R7, diodes D1 and D2, a capacitor C2 and operational amplifier chips OA2 and OA 3; the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA2, the cathode input end of the second-order band-pass active filter circuit is connected in parallel with a capacitor C2 through a diode D1, a resistor R1 is connected to the output end and the cathode input end of the operational amplifier chip OA3, and the output end of the second-order band-pass active filter circuit is connected to the anode input end of the operational amplifier chip OA3 through a diode D2; the negative input end of the operational amplifier chip OA3 is connected to the output end of the operational amplifier chip OA3 through a resistor R2, and the positive input end of the operational amplifier chip OA3 is connected to a ground wire R7 through a resistor R7; the positive and negative power supply ends of the operational amplifier chips OA2 and OA3 are respectively connected to the positive voltage VCC and the ground GND; setting the input voltage of a high-precision full-wave rectifier circuit to V2Output voltage of V3The resistances of the resistors R1, R2 and R7 are set to be R1, R2 and R7, and the capacitance value of the capacitor C2 is set to be C2.
1) Selecting the gain of the positive input signal:
Figure BDA0002383027230000094
2) selecting the gain of the negative input signal:
Figure BDA0002383027230000095
3) r1, R2, R7 were chosen to have the same resistance value:
R1＝R2＝R7(7)；
4) selecting C2 based on the desired transient response;
care needs to be taken in building high precision full wave rectifiers to select operational amplifiers with sufficient bandwidth and high slew rate, and if higher precision needs to be achieved operational amplifiers with low offset voltage, low noise and low Total Harmonic Distortion (THD) are used, resistors with 0.1% tolerance are selected in the design to reduce gain error, and diodes are selected to switch fast.
And 4, step 4: establishing comparator circuits, including voltage regulationThe chip, the operational amplifier chip OA4, resistance R11, R13, R16. The voltage stabilizing chip and the resistors R11, R13 and R16 are used for generating accurate and stable direct-current voltage, and the direct-current voltage is connected to the negative electrode voltage input end of the operational amplifier chip OA 4; the output end of the high-precision full-wave rectifier circuit is connected to the positive voltage input end of the operational amplifier chip OA 4; setting the resistance values of the resistors R11, R13 and R16 as R11, R13 and R16, and setting the input voltage of the anode of the operational amplifier chip as VpNegative input voltage is VnThe relation between the output voltage of the voltage stabilizing chip and the negative electrode input voltage of the operational amplifier chip is as follows:
Figure BDA0002383027230000101
the duty ratio of the output waveform of the operational amplifier chip OA4 is set as D, and the relationship between the duty ratio and the positive input voltage and the negative input voltage of the operational amplifier chip is as follows:
Figure BDA0002383027230000102
and 5: establishing an isolation sampling circuit, wherein the isolation circuit part comprises an isolation optocoupler, resistors R10, R14 and R8, and the isolation optocoupler realizes the electrical isolation of a primary voltage signal and a secondary control chip because the primary side and the secondary side of the vehicle-mounted power supply are not in common; the sampling part comprises a control chip and a peripheral circuit thereof, and the sampling circuit has the functions of sampling a duty ratio signal by utilizing an enhanced capture module (eCAP) module in the control chip, and calculating to obtain a primary side alternating current input voltage signal by utilizing the sampled duty ratio so as to realize the subsequent power reduction control function.
Step 6: through the formulas and methods provided in the steps 1 to 4, the relation between the duty ratio D and the AC input voltage value is obtained as follows:
Figure BDA0002383027230000103
and 7: when the ac input voltage changes, for example, the ac input voltage decreases, the duty ratio of the voltage square wave signal output by the operational amplifier chip OA4 also decreases, the duty ratio is measured by the eCAP module inside the control chip, and the ac input voltage value is calculated by the formula and method provided in step 6.
Preferably, the operational amplifier chip OA1 is a two-way high-speed low-noise operational amplifier with model number MC 33078;
preferably, the operational amplifier chips OA2 and OA3 are two-way low-noise high-speed JFET input operational amplifiers, and the type thereof is TLE 2072;
preferably, the operational amplifier chip OA4 is a low power consumption dual operational amplifier, whose model is LM 258;
preferably, the voltage stabilizing chip is a three-terminal adjustable shunt reference voltage source, and the model number of the voltage stabilizing chip is TL 431;
preferably, the isolation optocoupler is a low-profile coupler, the model of which is TLP 185;
preferably, the control chip is a DSP, and the model thereof is TMS320F 28035.
The invention relates to a method for controlling output power of a vehicle-mounted charger according to the magnitude of input voltage after sampling alternating current input voltage when the input voltage is lower than a certain value. For example, when the input voltage is 200V, the power is reduced until the input voltage is 80V, and the vehicle-mounted power supply is in a linear power reduction state between 200V and 80V. The general high-power vehicle-mounted power supply is provided with a Power Factor Correction (PFC) circuit, and partial power can be output after boosting when the input voltage is 90V. A power reduction method comprises the following steps: the power down is started when the input voltage is less than 200V. When the input voltage is equal to 90V, the output power is 25% of the total power; the output power is reduced by 75%/(200-90) — 0.655% when the input voltage is reduced by 1V; the invention aims to solve the problem that the sampling of the alternating-current input voltage is realized by converting the alternating-current input voltage signal into the duty ratio signal under the condition that a primary side does not have a single chip microcomputer or an expensive isolation sampling device is not used, and the invention has the advantages of low price, good real-time performance and the like.
The invention relates to an alternating current voltage sampling circuit and a design method for output power control, which solve the technical defects of input voltage sampling delay and inaccurate sampling result, and avoid the cost increase caused by adding a singlechip on a primary side for sampling and then transmitting to a secondary side or using a voltage-frequency conversion chip with higher price.

Claims (10)

1.一种用于输出功率控制的交流电压采样电路，其特征在于，包括交流分压电路、二阶带通有源滤波电路、高精度全波整流器电路、比较器电路和隔离采样电路，其中交流输入电压输入交流分压电路，交流分压电路输出端与二阶带通有源滤波电路输入端连接，二阶带通有源滤波电路输出端与高精度全波整流器电路输入端连接，高精度全波整流器输出端与比较器电路输入端连接，比较器电路输出端与隔离采样电路输入端连接。1. an AC voltage sampling circuit for output power control, is characterized in that, comprises AC voltage divider circuit, second-order band-pass active filter circuit, high-precision full-wave rectifier circuit, comparator circuit and isolation sampling circuit, wherein The AC input voltage is input to the AC voltage divider circuit, the output end of the AC voltage divider circuit is connected to the input end of the second-order band-pass active filter circuit, and the output end of the second-order band-pass active filter circuit is connected to the input end of the high-precision full-wave rectifier circuit. The output end of the precision full-wave rectifier is connected with the input end of the comparator circuit, and the output end of the comparator circuit is connected with the input end of the isolation sampling circuit. 2.根据权利要求1所述的一种用于输出功率控制的交流电压采样电路，其特征在于，交流分压电路包括电阻R4和电阻R6，交流输入电压连接到电阻R4再通过电阻R6连接到地线GND，电阻R4和电阻R6的中心点与二阶带通有源滤波电路的输入端连接；通过改变电阻R4和电阻R6的阻值能够改变交流输入电压经分压后的电压大小。2. The AC voltage sampling circuit for output power control according to claim 1, wherein the AC voltage divider circuit comprises a resistor R4 and a resistor R6, and the AC input voltage is connected to the resistor R4 and then connected to the resistor R6 through the resistor R6. The ground line GND, the center point of the resistor R4 and the resistor R6 are connected to the input end of the second-order band-pass active filter circuit; by changing the resistance values of the resistor R4 and the resistor R6, the voltage of the AC input voltage after the voltage division can be changed. 3.根据权利要求1所述的一种用于输出功率控制的交流电压采样电路，其特征在于，二阶带通有源滤波电路包括电阻R3、电阻R5、电阻R9，电容C1、电容C3、电容C4以及运放芯片OA1；交流分压电路的输出电压连接到电阻R5再通过电容C3连接到运放芯片OA1的负极输入端；电阻R9的一端连接到电阻R5与电容C3的中心点，另一端连接到地线GND；运放芯片OA1的输出端通过电容C1和电阻R3分别连接到电阻R5与电容C3的中心点以及运放芯片OA1的负极输入端；正电源VCC通过电阻R12和电阻R15分压后连接到运放芯片OA1的正极输入端，再通过电容C4连接到地线GND；运放芯片OA1的正负供电端分别连接到正电压VCC和地线GND。3. The AC voltage sampling circuit for output power control according to claim 1, wherein the second-order band-pass active filter circuit comprises resistor R3, resistor R5, resistor R9, capacitor C1, capacitor C3, Capacitor C4 and op amp chip OA1; the output voltage of the AC voltage divider circuit is connected to resistor R5 and then connected to the negative input end of op amp chip OA1 through capacitor C3; one end of resistor R9 is connected to the center point of resistor R5 and capacitor C3, and the other One end is connected to the ground wire GND; the output end of the op amp chip OA1 is connected to the center point of the resistor R5 and the capacitor C3 and the negative input end of the op amp chip OA1 through the capacitor C1 and the resistor R3 respectively; the positive power supply VCC passes through the resistor R12 and the resistor R15. After dividing the voltage, it is connected to the positive input terminal of the operational amplifier chip OA1, and then connected to the ground wire GND through the capacitor C4; the positive and negative power supply terminals of the operational amplifier chip OA1 are respectively connected to the positive voltage VCC and the ground wire GND. 4.根据权利要求1所述的一种用于输出功率控制的交流电压采样电路，其特征在于，高精度全波整流器电路包括电阻R1、电阻R2、电阻R7，二极管D1、二极管D2，电容C2以及运放芯片OA2、OA3；二阶带通有源滤波电路的输出端连接到运放芯片OA2的正极输入端，其负极输入端通过二极管D1和电容C2并联以及电阻R1连接到输出端和运放芯片OA3的负极输入端，其输出端再通过二极管D2连接到运放芯片OA3的正极输入端；运放芯片OA3的负极输入端通过电阻R2连接到其输出端，其正极输入端则通过电阻R7连接到地线R7；运放芯片OA2、OA3的正负供电端分别连接到正电压VCC和地线GND；高精度全波整流器电路将正弦交流电转换为直流电。4. The AC voltage sampling circuit for output power control according to claim 1, wherein the high-precision full-wave rectifier circuit comprises a resistor R1, a resistor R2, a resistor R7, a diode D1, a diode D2, and a capacitor C2 And the operational amplifier chips OA2, OA3; the output end of the second-order band-pass active filter circuit is connected to the positive input end of the operational amplifier chip OA2, and its negative input end is connected to the output end and the operational amplifier through the diode D1 and the capacitor C2 in parallel and the resistor R1. The negative input terminal of the amplifier chip OA3, and its output terminal is connected to the positive input terminal of the operational amplifier chip OA3 through the diode D2; the negative input terminal of the operational amplifier chip OA3 is connected to its output terminal through the resistor R2, and its positive input terminal is connected through the resistor. R7 is connected to the ground wire R7; the positive and negative power supply terminals of the operational amplifier chips OA2 and OA3 are respectively connected to the positive voltage VCC and the ground wire GND; the high-precision full-wave rectifier circuit converts the sinusoidal alternating current into direct current. 5.根据权利要求1所述的一种用于输出功率控制的交流电压采样电路，其特征在于，比较器电路包括稳压芯片、运放芯片OA4、电阻R11、电阻R13和电阻R16，稳压芯片与电阻R11、电阻R13、电阻R16用以产生精准稳定的直流电压，该直流电压连接到运放芯片OA4的负极电压输入端；高精度全波整流器电路的输出端连接到运放芯片OA4的正极电压输入端；运放芯片OA4的正、负极输入电压通过运放芯片进行比较，进而在运放芯片输出端产生幅值为VCC的方波信号。5. The AC voltage sampling circuit for output power control according to claim 1, wherein the comparator circuit comprises a voltage regulator chip, an operational amplifier chip OA4, a resistor R11, a resistor R13 and a resistor R16, and the voltage regulator The chip and resistor R11, resistor R13, and resistor R16 are used to generate a precise and stable DC voltage, which is connected to the negative voltage input terminal of the operational amplifier chip OA4; the output terminal of the high-precision full-wave rectifier circuit is connected to the operational amplifier chip OA4. Positive voltage input terminal; the positive and negative input voltages of the operational amplifier chip OA4 are compared through the operational amplifier chip, and then a square wave signal with an amplitude of VCC is generated at the output terminal of the operational amplifier chip. 6.根据权利要求1所述的一种用于输出功率控制的交流电压采样电路，其特征在于，隔离采样电路中隔离电路部分包括隔离光耦，电阻R10、电阻R14、电阻R8，比较器电路的输出端通过电阻R10与隔离光耦的第一端口连接，隔离光耦的第二端口通过电阻R14接GND，隔离光耦的第三端口通过电阻R8连接电源，隔离光耦的第四端口接SGND。6. The AC voltage sampling circuit for output power control according to claim 1, wherein the isolation circuit part in the isolation sampling circuit comprises an isolation optocoupler, a resistor R10, a resistor R14, a resistor R8, and a comparator circuit. The output terminal of the isolated optocoupler is connected to the first port of the isolated optocoupler through the resistor R10, the second port of the isolated optocoupler is connected to GND through the resistor R14, the third port of the isolated optocoupler is connected to the power supply through the resistor R8, and the fourth port of the isolated optocoupler is connected to the GND. SGND. 7.一种用于输出功率控制的交流电压采样电路设计方法，其特征在于：包括如下设计步骤：7. A design method for an AC voltage sampling circuit for output power control, characterized in that: comprising the following design steps: (1)建立交流分压电路，包括电阻R4和电阻R6，交流输入电压连接到电阻R4再通过电阻R6连接到地线GND，通过改变电阻R4和电阻R6的阻值能够改变交流输入电压经分压后的电压大小；设定经交流分压电路得到的电压大小为V1，经交流分压电路得到的电压V1与交流输入电压Vin的关系为：(1) Establish an AC voltage divider circuit, including resistor R4 and resistor R6. The AC input voltage is connected to resistor R4 and then connected to ground GND through resistor R6. By changing the resistance values of resistor R4 and resistor R6, the AC input voltage can be changed after dividing. Set the voltage obtained by the AC voltage divider circuit as V 1 , and the relationship between the voltage V 1 obtained by the AC voltage divider circuit and the AC input voltage V in is:
Figure FDA0002383027220000021
Figure FDA0002383027220000021
 (2)建立二阶带通有源滤波电路，包括电阻R3、电阻R5、电阻R9，电容C1、电容C3、电容C4以及运放芯片OA1；交流分压电路的输出电压连接到电阻R5再通过电容C3连接到运放芯片OA1的负极输入端；电阻R9的一端连接到电阻R5与电容C3的中心点，另一端连接到地线GND；运放芯片OA1的输出端通过电容C1和电阻R3分别连接到电阻R5与电容C3的中心点以及运放芯片OA1的负极输入端；正电源VCC通过电阻R12、R15分压后连接到运放芯片OA1的正极输入端，再通过电容C4连接到地线GND；运放芯片OA1的正负供电端分别连接到正电压VCC和地线GND；令C1＝C3＝C，Req是R1和R2并联的值，BW代表滤波电路的频带宽度，fc代表设定的中心频率，设定Q代表品质因数，那么便得到如下公式：(2) Establish a second-order band-pass active filter circuit, including resistor R3, resistor R5, resistor R9, capacitor C1, capacitor C3, capacitor C4 and operational amplifier chip OA1; the output voltage of the AC voltage divider circuit is connected to resistor R5 and then passes through The capacitor C3 is connected to the negative input terminal of the operational amplifier chip OA1; one end of the resistor R9 is connected to the center point of the resistor R5 and the capacitor C3, and the other end is connected to the ground wire GND; the output terminal of the operational amplifier chip OA1 passes through the capacitor C1 and the resistor R3 respectively. Connect to the center point of resistor R5 and capacitor C3 and the negative input terminal of op amp chip OA1; the positive power supply VCC is divided by resistors R12 and R15 and then connected to the positive input terminal of op amp chip OA1, and then connected to the ground wire through capacitor C4 GND; the positive and negative power supply terminals of the operational amplifier chip OA1 are respectively connected to the positive voltage VCC and the ground wire GND; let C1=C3=C, Req is the value of the parallel connection of R1 and R2, BW represents the frequency bandwidth of the filter circuit, and f c represents Set the center frequency and set Q to represent the quality factor, then the following formula is obtained:
Figure FDA0002383027220000022
Figure FDA0002383027220000022
Figure FDA0002383027220000023
Figure FDA0002383027220000023
Figure FDA0002383027220000031
Figure FDA0002383027220000031
 (3)建立高精度全波整流器电路，包括电阻R1、电阻R2、电阻R7，二极管D1、二极管D2，电容C2以及运放芯片OA2、OA3；二阶带通有源滤波电路的输出端连接到运放芯片OA2的正极输入端，其负极输入端通过二极管D1和电容C2并联以及电阻R1连接到输出端和运放芯片OA3的负极输入端，其输出端再通过二极管D2连接到运放芯片OA3的正极输入端；运放芯片OA3的负极输入端通过电阻R2连接到其输出端，其正极输入端则通过电阻R7连接到地线R7；运放芯片OA2、OA3的正负供电端分别连接到正电压VCC和地线GND；设定高精度全波整流器电路的输入电压为V2，输出电压为V3；(3) Establish a high-precision full-wave rectifier circuit, including resistor R1, resistor R2, resistor R7, diode D1, diode D2, capacitor C2 and operational amplifier chips OA2, OA3; the output end of the second-order band-pass active filter circuit is connected to The positive input terminal of the operational amplifier chip OA2, the negative input terminal is connected to the output terminal and the negative input terminal of the operational amplifier chip OA3 through the diode D1 in parallel with the capacitor C2 and the resistor R1, and the output terminal is connected to the operational amplifier chip OA3 through the diode D2. The positive input terminal of the operational amplifier chip OA3 is connected to its output terminal through the resistor R2, and its positive input terminal is connected to the ground wire R7 through the resistor R7; the positive and negative power supply terminals of the operational amplifier chips OA2 and OA3 are respectively connected to Positive voltage VCC and ground GND; set the input voltage of the high-precision full-wave rectifier circuit as V 2 and the output voltage as V 3 ; 1)选择正输入信号的增益：1) Select the gain of the positive input signal:
Figure FDA0002383027220000032
Figure FDA0002383027220000032
 2)选择负输入信号的增益：2) Select the gain of the negative input signal:
Figure FDA0002383027220000033
Figure FDA0002383027220000033
 3)选择R1、R2、R7具有相同的电阻值：3) Choose R1, R2, R7 to have the same resistance value: R1＝R2＝R7；R 1 =R 2 =R 7 ; 4)基于所需的瞬态响应选择C2；4) Select C2 based on the desired transient response; (4)建立比较器电路，包括稳压芯片、运放芯片OA4、电阻R11、电阻R13、电阻R16，稳压芯片与电阻R11、电阻R13、电阻R16用以产生精准稳定的直流电压，该直流电压连接到运放芯片OA4的负极电压输入端；高精度全波整流器电路的输出端连接到运放芯片OA4的正极电压输入端；设定运放芯片正极输入电压为Vp，负极输入电压为Vn，稳压芯片的输出电压与运放芯片负极输入电压关系为：(4) Establish a comparator circuit, including a voltage regulator chip, an operational amplifier chip OA4, a resistor R11, a resistor R13, and a resistor R16. The voltage regulator chip and resistor R11, resistor R13, and resistor R16 are used to generate a precise and stable DC voltage. The voltage is connected to the negative voltage input terminal of the operational amplifier chip OA4; the output terminal of the high-precision full-wave rectifier circuit is connected to the positive voltage input terminal of the operational amplifier chip OA4; the positive input voltage of the operational amplifier chip is set as Vp , and the negative input voltage is V n , the relationship between the output voltage of the voltage regulator chip and the negative input voltage of the op amp chip is:
Figure FDA0002383027220000034
Figure FDA0002383027220000034
 设定运放芯片OA4的输出波形的占空比为D，该占空比与运放芯片正极输入电压以及负极输入电压的关系为：Set the duty cycle of the output waveform of the operational amplifier chip OA4 as D, and the relationship between the duty cycle and the positive input voltage and negative input voltage of the operational amplifier chip is:
Figure FDA0002383027220000041
Figure FDA0002383027220000041
 (5)建立隔离采样电路，其中隔离电路部分包括隔离光耦，电阻R10、电阻R14、电阻R8，比较器电路的输出端通过电阻R10与隔离光耦的第一端口连接，隔离光耦的第二端口通过电阻R14接GND，隔离光耦的第三端口通过电阻R8连接电源，隔离光耦的第四端口接SGND；(5) Establish an isolation sampling circuit, wherein the isolation circuit part includes an isolation optocoupler, a resistor R10, a resistor R14, and a resistor R8. The output end of the comparator circuit is connected to the first port of the isolation optocoupler through the resistor R10, and the first port of the isolation optocoupler is connected. The second port is connected to GND through the resistor R14, the third port of the isolated optocoupler is connected to the power supply through the resistor R8, and the fourth port of the isolated optocoupler is connected to SGND; (6)通过步骤(1)到步骤(4)提供的公式和方法，得到占空比D与交流输入电压值的关系为：(6) Through the formulas and methods provided in steps (1) to (4), the relationship between the duty cycle D and the AC input voltage value is obtained as:
Figure FDA0002383027220000042
Figure FDA0002383027220000042
 (7)当交流输入电压发生变化时，运放芯片OA4输出的电压方波信号的占空比也随之变化，通过控制芯片内部的eCAP模块对该占空比进行测量，并通过步骤(6)提供的公式和方法计算出交流输入电压值。(7) When the AC input voltage changes, the duty cycle of the voltage square wave signal output by the op amp chip OA4 also changes, and the duty cycle is measured by the eCAP module inside the control chip, and through step (6 ) provides the formula and method to calculate the AC input voltage value. 8.根据权利要求7所述的一种用于输出功率控制的交流电压采样电路的设计方法，其特征在于：运放芯片OA1为双路高速低噪声运算放大器，其型号为MC33078；运放芯片OA2、OA3为二路低噪声高速JFET输入运算放大器，其型号为TLE2072；运放芯片OA4为低功耗双运算放大器，其型号为LM258。8. the design method of a kind of AC voltage sampling circuit for output power control according to claim 7, it is characterized in that: operational amplifier chip OA1 is a dual-channel high-speed low-noise operational amplifier, and its model is MC33078; OA2 and OA3 are two-way low-noise high-speed JFET input operational amplifiers, and their model is TLE2072; the operational amplifier chip OA4 is a low-power dual operational amplifier, and its model is LM258. 9.根据权利要求7所述的一种用于输出功率控制的交流电压采样电路的设计方法，其特征在于：稳压芯片为三端可调分流基准电压源，其型号为TL431；隔离光耦为小外型耦合器，其型号为TLP185。9. The design method of an AC voltage sampling circuit for output power control according to claim 7, wherein the voltage regulator chip is a three-terminal adjustable shunt reference voltage source, and its model is TL431; the isolation optocoupler It is a small form factor coupler, its model is TLP185. 10.根据权利要求7所述的一种用于输出功率控制的交流电压采样电路的设计方法，其特征在于：控制芯片为DSP，其型号为TMS320F28035。10 . The method for designing an AC voltage sampling circuit for output power control according to claim 7 , wherein the control chip is a DSP, and its model is TMS320F28035. 11 .
CN202010088867.2A 2020-02-12 2020-02-12 Alternating voltage sampling circuit for output power control and design method thereof Active CN111141949B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202010088867.2A CN111141949B (en) 2020-02-12 2020-02-12 Alternating voltage sampling circuit for output power control and design method thereof

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202010088867.2A CN111141949B (en) 2020-02-12 2020-02-12 Alternating voltage sampling circuit for output power control and design method thereof

Publications (2)

Publication Number Publication Date
CN111141949A true CN111141949A (en) 2020-05-12
CN111141949B CN111141949B (en) 2022-02-11

Family

ID=70527414

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202010088867.2A Active CN111141949B (en) 2020-02-12 2020-02-12 Alternating voltage sampling circuit for output power control and design method thereof

Country Status (1)

Country Link
CN (1) CN111141949B (en)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111856106A (en) * 2020-07-24 2020-10-30 天地（常州）自动化股份有限公司 Three-phase five-column voltage transformer for coal mine based on resistance division
CN113884744A (en) * 2021-11-24 2022-01-04 四川升华电源科技有限公司 A Variation Differential AC Voltage Sampling Circuit
WO2022242215A1 (en) * 2021-05-17 2022-11-24 青岛海尔生物医疗科技有限公司 Circuit, method and apparatus for temperature control of cell incubator, and incubator
CN117554687A (en) * 2024-01-10 2024-02-13 常州通宝光电股份有限公司 Alternating current mains voltage sampling circuit

Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102075071A (en) * 2011-01-20 2011-05-25 浙江大学 Compensation control circuit beneficial to harmonic reduction of active flyback power factor correction device
CN102158068A (en) * 2011-02-23 2011-08-17 北京运通恒昌驱动技术有限公司 High-efficiency and high-power factor power circuit for permanent magnet synchronous driver
CN202583298U (en) * 2012-04-14 2012-12-05 漳州科华技术有限责任公司 Alternating current voltage isolated sampling circuit
CN103698579A (en) * 2013-12-30 2014-04-02 长沙奥托自动化技术有限公司 Direct-current voltage sampling device of low-voltage frequency converter
CN104253549A (en) * 2014-10-11 2014-12-31 东南大学 LCL filtering-based circuit topology structure of high-power PWM (pulse-width modulation) rectifier
CN204855627U (en) * 2015-07-10 2015-12-09 威海天力电源有限公司 Isolated alternating voltage sampling circuit
CN106992689A (en) * 2017-04-28 2017-07-28 东南大学 A single-phase direct AC-AC frequency conversion circuit and control method based on pulse equivalent method
CN206540973U (en) * 2017-03-08 2017-10-03 杭州明特科技有限公司 Buffer-type power-fail detection circuit
KR20180007567A (en) * 2016-07-13 2018-01-23 현대오트론 주식회사 Method and apparatus for measuring average current of 3 phase motor based on current measurement of pwm on-duty period
CN110763909A (en) * 2019-11-11 2020-02-07 绵阳市维博电子有限责任公司 Digital display DC meter and voltage sampling circuit thereof

Patent Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102075071A (en) * 2011-01-20 2011-05-25 浙江大学 Compensation control circuit beneficial to harmonic reduction of active flyback power factor correction device
CN102158068A (en) * 2011-02-23 2011-08-17 北京运通恒昌驱动技术有限公司 High-efficiency and high-power factor power circuit for permanent magnet synchronous driver
CN202583298U (en) * 2012-04-14 2012-12-05 漳州科华技术有限责任公司 Alternating current voltage isolated sampling circuit
CN103698579A (en) * 2013-12-30 2014-04-02 长沙奥托自动化技术有限公司 Direct-current voltage sampling device of low-voltage frequency converter
CN104253549A (en) * 2014-10-11 2014-12-31 东南大学 LCL filtering-based circuit topology structure of high-power PWM (pulse-width modulation) rectifier
CN204855627U (en) * 2015-07-10 2015-12-09 威海天力电源有限公司 Isolated alternating voltage sampling circuit
KR20180007567A (en) * 2016-07-13 2018-01-23 현대오트론 주식회사 Method and apparatus for measuring average current of 3 phase motor based on current measurement of pwm on-duty period
CN206540973U (en) * 2017-03-08 2017-10-03 杭州明特科技有限公司 Buffer-type power-fail detection circuit
CN106992689A (en) * 2017-04-28 2017-07-28 东南大学 A single-phase direct AC-AC frequency conversion circuit and control method based on pulse equivalent method
CN110763909A (en) * 2019-11-11 2020-02-07 绵阳市维博电子有限责任公司 Digital display DC meter and voltage sampling circuit thereof

Non-Patent Citations (6)

* Cited by examiner, † Cited by third party
Title
NIANCHUN WANG ETC.: "Optimization of Photovoltaic MPPT System Efficiency Based on Combined Algorithm", 《2018 21ST INTERNATIONAL CONFERENCE ON ELECTRICAL MACHINES AND SYSTEMS (ICEMS)》 *
孙玉巍等: "级联式电力电子变压器的主动非均衡功率控制", 《电力系统自动化》 *
曾全堃等: "二阶带通有源滤波电路", 《仪器电路》 *
李成华: "变频器中的故障检测电路详解及实例分析", 《机床电器》 *
王念春等: "基于状态空间的逆变器数字双环控制技术研究", 《中国电机工程学报》 *
石右仁等: "交流稳压电源控制中数据采样技术及算法改进", 《移动电源与车辆》 *

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111856106A (en) * 2020-07-24 2020-10-30 天地（常州）自动化股份有限公司 Three-phase five-column voltage transformer for coal mine based on resistance division
WO2022242215A1 (en) * 2021-05-17 2022-11-24 青岛海尔生物医疗科技有限公司 Circuit, method and apparatus for temperature control of cell incubator, and incubator
CN113884744A (en) * 2021-11-24 2022-01-04 四川升华电源科技有限公司 A Variation Differential AC Voltage Sampling Circuit
CN117554687A (en) * 2024-01-10 2024-02-13 常州通宝光电股份有限公司 Alternating current mains voltage sampling circuit
CN117554687B (en) * 2024-01-10 2024-03-22 常州通宝光电股份有限公司 Alternating current mains voltage sampling circuit

Also Published As

Publication number Publication date
CN111141949B (en) 2022-02-11

Similar Documents

Publication Publication Date Title
CN111141949B (en) Alternating voltage sampling circuit for output power control and design method thereof
CN102628889B (en) Voltage sampling circuit
CN107896069A (en) A kind of New single-phase mixes three-level rectifier
CN107733245B (en) A kind of efficient amplitude modulation perseverance high-frequency electric dust removal power circuit
CN203039590U (en) Numerically-controlled voltage-regulating high-voltage direct current power supply
CN105226916A (en) The current sample method of isolated power converters and sampling apparatus
CN104578820B (en) A kind of high power density AC great current generator
CN208636373U (en) Precise measurement device for primary frequency modulation electrical parameters
CN115616427A (en) A lithium battery detection system and detection device
CN109687735A (en) A kind of isolated DC power supply of high precision wide range
CN101694969B (en) Frequency conversion speed regulation input voltage conversion device and method
CN115473442B (en) LLC single-stage AC-DC converter numerical analysis modeling and boundary power control method
CN112217390A (en) A fast dynamic response CRM boost PFC converter based on controllable current source
CN208112509U (en) A dual-stage input step-up DC constant voltage output converter
CN105226932A (en) High efficiency circuit of power factor correction topological structure and control method thereof
CN211959064U (en) Novel non-isolated Buck PFC converter system
CN219576691U (en) Compact high-voltage energy storage pulse capacitor charging power supply
CN203747682U (en) A device for single-phase AC-DC conversion power supply
CN104702092B (en) Power Factor Correction Circuits for Power Converters
CN103138606A (en) Energy conservation type switch power source
CN208015596U (en) A kind of DC constant pressures output translator
CN215734027U (en) Switch power supply
CN105527518A (en) Aluminum electrolytic capacitor life tester
CN203859678U (en) Switching power supply of photovoltaic grid-connected inverter
CN211959080U (en) Buck three-phase four-wire three-level PFC rectifier system

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant
TR01 Transfer of patent right

Effective date of registration: 20240428

Address after: 214185, 1st to 2nd floors, Building 5, No. 29 Huibei Road, Liangxi District, Wuxi City, Jiangsu Province

Patentee after: WUXI JUNENG NEW ENERGY TECHNOLOGY CO.,LTD.

Country or region after: China

Address before: 211102 No. 2 Southeast University Road, Jiangning District, Nanjing City, Jiangsu Province

Patentee before: SOUTHEAST University

Country or region before: China

TR01 Transfer of patent right