CN109994822B - High-power microwave space beam swept planar array antenna - Google Patents

Abstract

The invention discloses a high-power microwave space beam scannable plane array antenna. The invention consists of N rotary adjustable phase shifters based on rectangular waveguide narrow-side slot bridges, N connection waveguides, N high-power microwave one-dimensional beam sweepable linear arrays, N phase shifter phase control units, M It is composed of the drive control unit of the inner conductor of the helix of the linear array. The number of radiation elements in each linear array is M. In the x-axis direction, the n1th radiation element to the nMth radiation element constitute the nth row of radiation elements; in the y-axis direction, the 1mth radiation element to the Nmth radiation element constitute the mth column. The radiation unit; the m-th helix inner conductor drive control unit controls the m-th column of radiation units; the n-th phase shifter phase control unit adjusts the output phase of the n-th rotary adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge. On the basis of realizing beam scanning, the present invention has higher oral surface efficiency, and the number of required control motors is only M+N.

Description

High-power microwave space beam swept planar array antenna

technical field

The invention relates to an antenna in the field of high-power microwave technology, in particular to a high-power microwave plane array antenna with space beam scanning capability.

Background technique

The high-power microwave antenna is the terminal of the high-power microwave system, and its performance has an important influence on the irradiation ability of the high-power microwave system. With the development of high-power microwave technology, high-power microwave antennas are urgently required to have the ability to scan spatial beams. The existing hyperbolic surface antenna radiated by the horn after mode conversion can realize beam scanning through two rotation axes, but the efficiency of the antenna surface is low, and the conformal design with the platform cannot be realized; the high-power microwave radial line helix The array antenna has a power capacity of GW level. The spatial azimuth angle of the conductor in the helical radiation unit is controlled by the control unit (usually a stepper motor), and a certain range of spatial beam scanning can be achieved. In terms of the system, M×N control units are required to control the rotation of the conductors in the helical radiation unit, which leads to a complicated servo system, and many control units lead to higher costs for manufacturing the antenna. Therefore, the invention of a high-power microwave spatial beam swept planar array antenna with high aperture efficiency and a small number of control units has important application value.

SUMMARY OF THE INVENTION

The technical problem to be solved by the present invention is to provide a high-power microwave spatial beam swept planar array antenna with higher aperture efficiency and fewer control units.

The present invention consists of five parts, which are respectively N (20<N<100) rotary-adjustable phase shifters based on rectangular waveguide narrow-side slot bridges, namely the first rotary-adjustable phase shifters based on rectangular-waveguide narrow-side slot bridges Phase shifter, second rotary adjustable phase shifter based on rectangular waveguide narrow-side slot bridge, third rotary adjustable phase shifter based on rectangular waveguide narrow-side slot bridge, ... nth (1≤n≤N) Rotational Adjustable Phase Shifter Based on Rectangular Waveguide Narrow Side Slot Bridge, ... Nth Rotation Adjustable Phase Shifter Based on Rectangular Waveguide Narrow Side Slot Bridge; N connection waveguides, namely the first connection waveguide and the second connection waveguide , the third connecting waveguide, ...the nth connecting waveguide, ...the Nth connecting waveguide; 1D beam scannable linear array, third high power microwave 1D beam scannable linear array, ...nth high power microwave 1D beam scannable linear array, ...Nth high power microwave 1D beam scannable linear array, ( The number of radiation elements of each high-power microwave one-dimensional beam scannable linear array is M, and the distance between adjacent radiation elements along the x-axis direction is d). The x-axis direction is the n1th radiation unit, the n2th radiation unit, the n3th radiation unit...the nm (1≤m≤M) radiation unit...the nMth radiation unit. In the x-axis direction, the n1th radiation unit to the nMth radiation unit constitute the nth row radiation unit; in the y-axis direction, the 1mth radiation unit to the Nmth radiation unit constitute the mth column radiation unit); N phase shifters phase control Units, namely the first phase shifter phase control unit, the second phase shifter phase control unit, the third phase shifter phase control unit,...the nth phase shifter phase control unit,...the Nth phase shifter phase control unit; M high-power microwave one-dimensional beam scannable linear arrays of drive control units for the inner conductors of the helix, namely the first helix inner conductor drive control unit, the second helix inner conductor drive control unit, and the third helix inner conductor drive control unit control unit, ... mth inner conductor drive control unit, ... mth inner conductor drive control unit. (The inner conductor drive control unit of each spiral controls the radiation units of the corresponding column, that is, the m-th inner conductor drive control unit of the spiral controls the radiation units of the mth column). The nth rotary adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide and the nth high-power microwave one-dimensional beam scannable linear array are connected by the nth connecting waveguide, and the three together form the nth linear array along the x-axis direction . The N-way linear arrays have exactly the same structure, and are arranged in parallel along the y-axis in space to form a plane array, and the distance between the adjacent two-way linear arrays in the y-axis direction is s. The output phase of the nth phase shifter based on the narrow side slot bridge of the rectangular waveguide is adjusted by the phase control unit of the nth phase shifter. The spiral inner conductor of the nth row is the first spiral inner conductor of the nth row 3n31...the nth row of the mth spiral inner conductor 3n3m...the nth row of the Mth spiral inner conductor 3n3M; the mth column of the spiral inner conductor The order is the m-th column first spiral inner conductor 313m, the m-th column second spiral inner conductor 323m... m-th column n-th spiral inner conductor 3n3m... m-th column N-th spiral inner conductor 3N3m.

Microwaves are injected from the first phase shifter port of the nth rotary-adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge, and the second phase shifter of the n-th rotary-adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge The filter port is connected to the input port of the nth connecting waveguide. The phase control unit of the nth phase shifter is connected with the first rotation joint and the second rotation joint of the nth rotation-adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide. The output port of the nth connecting waveguide is connected to the input port of the nth high-power microwave one-dimensional beam scannable linear array, and the second port of the nth high-power microwave one-dimensional beam scannable linear array is connected to an external matching load. The inner conductor of the helix of the mth radiation unit of the nth high-power microwave one-dimensional beam can scan the linear array is connected to the drive control unit of the mth helix inner conductor, and the first high-power microwave one-dimensional beam can scan the mth of the linear array. The helical inner conductors of the radiating elements to the helical inner conductors of the m-th radiating element of the Nth high-power microwave one-dimensional beam-scannable linear array are defined as the m-th column helical inner conductors.

The rotary-adjustable phase shifter based on a rectangular waveguide narrow-side slot bridge is composed of a rectangular waveguide narrow-side slot bridge, a first phase adjustment arm and a second phase adjustment arm. The first phase adjustment arm is connected to the third bridge port of the rectangular waveguide narrow-side slot bridge, and the second phase adjustment arm is connected to the fourth bridge port of the rectangular waveguide narrow-side slot bridge. The first phase adjusting arm is composed of a first wire-rotating circular polarizer and a first rotary joint; the second phase regulating arm is composed of a second wire-rotating circular polarizer and a second rotary joint. The structures of the first line-to-circular polarizer and the second line-to-circular polarizer are identical; the structures of the first rotary joint and the second rotary joint are identical. Microwaves are injected from the first bridge port of the rectangular waveguide narrow-side slot bridge, and output from the second bridge port of the rectangular waveguide narrow-side slot bridge.

The rectangular waveguide narrow-side slot bridge is a cavity made of metal material, and the metal wall thickness is T (T>1.5mm). The first bridge port, the second bridge port, the third bridge port, and the fourth bridge port of the narrow-side slot bridge of the rectangular waveguide are all rectangular waveguides, and the lengths of the broad sides of the inner cavity of the rectangular waveguide of the four ports are all is a, and the length of the narrow side is b.

The rectangular waveguide narrow-side slot bridge is composed of four ports: a first bridge port, a second bridge port, a third bridge port, and a fourth bridge port, a first microwave transmission channel, a second microwave transmission channel, and a third microwave transmission channel. The transmission channel, the fourth microwave transmission channel, four microwave transmission channels, and the central coupling area are formed. The first electric bridge port is communicated with the first microwave transmission channel, the second electric bridge port is communicated with the second microwave transmission channel, the first microwave transmission channel and the second microwave transmission channel are both communicated with the central coupling area, and the central coupling area is communicated with the third microwave transmission channel. The microwave transmission channel is communicated with the fourth microwave transmission channel, the third microwave transmission channel is communicated with the third electric bridge port, the fourth microwave transmission channel is communicated with the fourth electric bridge port, and the two microwave transmission channels of the first microwave transmission channel and the second microwave transmission channel are communicated with each other. The vertical distance between the axes of the bars is h, the length of the central coupling region is L ₁ ', the third microwave transmission channel and the fourth microwave transmission channel are both turned 90 degrees, and the inner radius of the rounded corners at the corners are both R ₁ '', the outer radius of the rounded corner at the corner is R ₂ ', R ₁ ' and R ₂ ' can be optimized by electromagnetic simulation software, and the optimization goal is that the reflection caused by the corner is zero. The horizontal distance between the axes of the third microwave transmission channel P18 and the fourth microwave transmission channel is L, and it is required that 2a<L<3a.

The first linear-to-circular polarizer consists of an injection port, a circular waveguide, a first waveguide ridge, a second waveguide ridge and an end port. The injection port is sealed by metal, and a rectangular gap is left in the center to connect with the third bridge port of the narrow-side slot bridge of the rectangular waveguide. The length of the wide side of the rectangular gap is a, and the length of the narrow side is b. The thickness of the metal wall of the circular waveguide is T, and the diameter of the inner circle is R' (λ ₀ /2.61>R'>λ ₀ /3.41). The structure of the first waveguide ridge is exactly the same as that of the second waveguide ridge, and the two waveguide _ridges are symmetrical about the z-axis. /2.61>w>λ ₀ /3.41, and w<R'), the projection of PP' on the plane of the injection port is OQ' (the origin of the coordinates is at the center of the injection port), and the angle between OQ' and the x-axis is α ( α=45°). The end port is connected to the first rotary joint.

The first waveguide ridge has the same shape as the second waveguide ridge, shaped like a saddle, the length of the back of the waveguide ridge is d ₂ , and the length of the belly of the waveguide ridge is d ₁ . The backs (length d ₁ ) of the first waveguide ridge and the second waveguide ridge are in close contact with the inner wall of the circular waveguide.

The first rotary joint is composed of a cylindrical base plate and a narrow metal plate, and the narrow metal plate is welded in the center of the cylindrical base plate. The cylindrical base plate has a radius R ₀ ' (R ₀ '=L/2) and a thickness w ₁ (w ₁ >2mm). The length of the narrow metal plate is Ls (Ls=λ ₀ /4, where λ ₀ is the waveguide wavelength of the circularly polarized TE ₁₁ mode propagating in the circular waveguide), the width is R', and the thickness is w ₂ (1mm<w ₂ < 4mm). The two sides of the narrow metal plate along the z-axis are rounded with a radius of R'/2. The narrow metal plate is inserted into the circular waveguide of the first linear-to-circular polarizer from the end port of the first linear-to-circular polarizer, and the cylindrical base plate seals the end port of the first linear-to-circular polarizer. The first rotation joint is rotatable about the axis of symmetry (ie, the z-axis).

In the initial state of the first rotary joint and the second rotary joint of the rotary adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide, there is an included angle between the two narrow metal plates, and the size of the included angle is γ.

The ports at both ends of the n-th connecting waveguide are rectangular waveguides, and the outer dimension of the rectangular waveguide connecting the input port of the n-th waveguide is a×b. The port of the phase shifter is connected, and the waveguide size of the two is the same. The outer dimension of the rectangular waveguide connected to the output port of the nth waveguide is a ₂ ×b ₂ , which is the same as the size of the input port of the nth high-power microwave one-dimensional beam-sweepable linear array. same. The center of the nth connecting waveguide is the gradual transition section of the waveguide connecting the two ports. The length of the transition section is L, which can be optimized by electromagnetic simulation software (such as CST Microwave Studio). The optimization goal is zero transmission reflection. The cross-section of the transition section remains rectangular, the width of the broad side transitions from a to a ₂ , and the size of the narrow side transitions from b to b ₂ .

The high-power microwave one-dimensional beam swept linear array is an all-metal structure and consists of two parts, the first part is a rectangular waveguide, and the second part is a one-dimensional linear array composed of radiating elements. The microwave is injected from the injection end of the rectangular waveguide, and the output end of the rectangular waveguide is connected to a matching load. The one-dimensional linear array is composed of M (generally: 20<M<500) radiating elements, the spacing between adjacent radiating elements is d, and they are installed on the narrow side of the rectangular waveguide along the x-axis direction. The one-dimensional linear array formed by the radiation elements is the first radiation unit, the second radiation unit, the third radiation unit...the mth radiation unit...the Mth radiation unit in the direction from the injection end to the output end of the rectangular waveguide, where 1≤m≤ M.

The inner dimension of the rectangular cross-section of the rectangular waveguide is a ₂ , the length of the narrow side is b ₂ , and the metal wall thickness of the four sides of the rectangular waveguide (that is, the other four sides except the injection end and the output end) are T. M circular through holes are dug in the center of the first side of the rectangular waveguide. The circular through holes are the first circular through holes on the first side of the rectangular waveguide in the direction from the injection end to the output end of the rectangular waveguide. The second circular through hole of the rectangular waveguide, the third circular through hole on the first side of the rectangular waveguide...the mth circular through hole on the first side of the rectangular waveguide...the Mth circular through hole on the first side of the rectangular waveguide. The radii from the first circular through hole on the first side of the rectangular waveguide to the M-th circular through hole are all R ₁ (R ₁ <b ₂ /2), and the center of the first circular through hole on the first side of the rectangular waveguide is The distance from the injection end is s ₀ (s ₀ >d/2), the distance between the center of the m-th circular through hole on the first side of the rectangular waveguide and the injection end is s ₀ +(m-1)d, and the adjacent first circle The distance between the centers of the through holes is d. 2M circular through holes are dug in the center of the second side of the rectangular waveguide opposite to the first side of the rectangular waveguide. Through hole, second circular through hole on the second side of the rectangular waveguide, third circular through hole on the second side of the rectangular waveguide, fourth circular through hole on the second side of the rectangular waveguide...2m on the second side of the rectangular waveguide -1 circular via, 2mth circular via on the second side of the rectangular waveguide, ... 2M-1 circular via on the second side of the rectangular waveguide, 2M circular via on the second side of the rectangular waveguide. The radii of the first, 3...2m-1...2M-1 circular through holes on the second side of the rectangular waveguide are all R ₂ , and the distance between the center of the first circular through hole on the second side of the rectangular waveguide and the injection end is s ₀ , the distance between the center of the 2m-1 circular through hole on the second side of the rectangular waveguide and the injection end is s ₀ +(m-1)d; the radius of the 2m-th circular through hole on the second side of the rectangular waveguide is r _m , The distance between the center of the second circular through hole on the second side of the rectangular waveguide and the injection end is s ₁ , and the distance between the center of the second circular through hole on the second side of the rectangular waveguide and the injection end is s _m , satisfying s _m -s ₀ -(m-1)d≈λ ₀ /4, where λ ₀ is the waveguide wavelength of the microwave propagating in the rectangular waveguide.

The composition of the first radiation unit, the second radiation unit, the third radiation unit...the mth radiation unit...the Mth radiation unit of the present invention is the same (all including the reflection elimination rod, the inner conductor of the helix and the coupling cavity). Taking the mth radiation unit as an example, the mth radiation unit is composed of the mth reflection cancellation rod, the mth helix inner conductor and the mth coupling cavity. The m-th reflection cancellation rod is completely inserted into the rectangular waveguide through the 2m-th circular through hole on the second side of the rectangular waveguide, and the tip is in contact with the inner wall of the first side of the rectangular waveguide; The through hole is inserted into the rectangular waveguide to be fixed on the rectangular waveguide; the inner conductor of the m-th helix is inserted into the rectangular waveguide through the m-th coupling cavity, and the 2m-1 circular through hole on the second side of the rectangular waveguide passes through the rectangular waveguide, and the external step Into the motor, the length of the rectangular waveguide is h'.

The m-th reflection cancelling rod has the shape of a cylinder with a radius equal to r _m . The mth reflection cancellation rod is inserted into the rectangular waveguide through the 2mth circular through hole on the second side of the rectangular waveguide. , the lengths from the first reflection cancellation rod to the M reflection cancellation rod are a ₂ +T.

The structures of the inner conductor of the first helix to the inner conductor of the Mth helix are completely the same. The inner conductor of the m-th helix consists of a straight cylinder, a semi-circle perpendicular to the straight cylinder and a helix. The straight cylinder is a metal rod with a diameter of 2R ₂ and the length of the straight cylinder is L ₁ (The length of L ₁ is about twice the length of the broad side a ₂ of the rectangular waveguide, and one end of the right cylinder passes through the 2m-1 circular through hole on the second side of the rectangular waveguide, and is connected to a stepping motor. The semicircular ring and The total height of the helix is L ₂ ; the diameter of the semicircular ring is L ₃ /2, the helix 2m23 is a helix with equal helix radius and equal pitch, and the outer diameter of the helix is L ₃ . The angle between the initial segment tangent and the x-axis is defined as the spatial azimuth angle of the conductor in the helix, denoted by α _m , where α _m represents the spatial azimuth of the conductor in the mth helix. The spatial azimuth angle difference of the conductors is a constant P, that is, α _m -α _m-1 =P, where 1<m≤M.

外孔的对称轴与x轴的夹角定义为耦合腔的旋转角，用θ_m表示。第二孔2m34的高度为H₂-H₁，第二孔的轮廓由两段弧线构成，尺寸较大的圆弧线的半径为R₄，对应的圆心角为

尺寸较小弧线的半径为R₅，对应的圆心角为

第二孔的对称轴与x轴的夹角也为θ_m，第一耦合腔到第M耦合腔结构的尺寸除了耦合腔的旋转角θ_m不同外，其它结构尺寸均相同。第三孔的高度H₃-H₂，截面形状为圆形，圆形半径为R₅。第四孔的高度H₄-H₃，截面形状为圆形，圆形半径为R₆。One end of the shape of the mth coupling cavity is a cylindrical boss and the other end is a cuboid, the outer radius of the cylindrical boss is R ₁ , and the height of the boss is H ₁ . There are four holes of different shapes dug inside the mth coupling cavity, the first hole, the second hole, the third hole, and the fourth hole are in sequence from the cylindrical boss to the cuboid, and the four holes are connected together to form a microwave transmission channel. The first hole is composed of an inner hole and an outer hole. The heights of the two holes are H ₁ . The cross-sectional shape of the inner hole is a circle with a radius of R _2. The inner conductor of the m-th helix is inserted into the waveguide through this hole. Approximate semi-circular shape, the inner radius is R ₃ , the outer radius is R ₄ , and the central angle of the outer hole is

The angle between the symmetry axis of the outer hole and the x-axis is defined as the rotation angle of the coupling cavity, represented by θ _m . The height of the second hole 2m34 is H ₂ -H ₁ , the contour of the second hole is composed of two arcs, the radius of the larger arc is R ₄ , and the corresponding central angle is

The radius of the arc with the smaller size is R ₅ , and the corresponding central angle is

The angle between the symmetry axis of the second hole and the x-axis is also θ _m , and the dimensions of the structures from the first coupling cavity to the M-th coupling cavity are the same except for the rotation angle θ _m of the coupling cavity. The height of the third hole is H ₃ -H ₂ , the cross-sectional shape is a circle, and the radius of the circle is R ₅ . The height of the fourth hole is H ₄ -H ₃ , the cross-sectional shape is a circle, and the radius of the circle is R ₆ .

为一个常量，即

因此相邻两路直线阵列的馈入相位差也应为常量，即馈入相位差等于相邻两路直线阵列的移相器的旋转角度差。The phase control unit of the nth phase shifter is a rotatable bearing, and the bearing is connected to a stepping motor, which is driven by the stepping motor to rotate around its own axis (ie, the z-axis). The rotatable bearing has the same outer diameter R' ₀ (R' ₀ >R') as the first rotary joint and the second rotary joint of the n-th rectangular waveguide narrow-side slot bridge-based rotary adjustable phase shifter, and the n-th The phase shifter phase control unit is connected with the first rotary joint and the second rotary joint of the nth rotary adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide (the three are meshed by the peripheral gears, and the specific structure is not introduced here. Only the principle is introduced). The phase control unit of the nth phase shifter is connected to a stepping motor, and rotates around the z-axis, that is, drives the first rotary joint and the second rotary joint to rotate synchronously. It can be seen from the rotary-adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide that every time the phase control unit of the n-th phase shifter rotates by θ _n , it synchronously drives the n-th rotational-adjustable phase-shifter based on the narrow-side slot bridge of the rectangular waveguide. The first and second rotary joints of the phase shifter rotate around the same direction by θ _n , so the output phase of the phase shifter changes by 2θ _n . The working state of the high-power microwave space beam swept planar array antenna requires the rotation angle difference of the phase shifters of the two adjacent linear arrays

is a constant, that is

Therefore, the feeding phase difference of the two adjacent linear arrays should also be constant, that is, the feeding phase difference is equal to the rotation angle difference of the phase shifters of the adjacent two linear arrays.

有

The m-th helical inner conductor drive control unit is composed of the m-th geared sliding plate (the principle is introduced here, all gear structures are not described) and N geared bearings, and the N geared bearings are in turn along the y-axis direction. For the m1th bearing, the m2th bearing, the m3th bearing...the mnth bearing...the mNth bearing, the above bearings are sequentially connected with the inner conductors of the spirals of the N radiation units in the mth row along the y-axis direction (that is, the inner conductors of the helix in the mth row). The conductors) are closely connected, and the rotation of the bearing will drive the inner conductor of the helix to rotate along with it. The outer diameter of each bearing is r (d/2>r>R ₂ ), the sliding plate and the gear of the bearing are meshed together, and the gear of the bearing is the same size as the gear of the sliding plate. One end of the m-th helix inner conductor drive control unit is driven by a stepping motor to move h _m along the y-axis direction, thereby driving the m1th bearing to the Nmth bearing to rotate by 2h _m /r radians, and at the same time driving the mth row of helix inner conductors The spatial azimuth is rotated by 2h _m /r radians, and the size of this rotation angle is determined by the desired beam pointing. In the x-axis direction, the length difference between the adjacent helix inner conductor drive control units driven by the external stepping motor is a constant Δh=h _m -h _m-1 , so the space of the conductors in the adjacent column helix in the x-axis direction The azimuth difference is also a constant, set to

Have

The conditions and design steps satisfied by the structural parameters are as follows:

1. Determining the structural parameters of the rotary adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide

1) Determine the basic parameters of the rectangular waveguide narrow-side slot bridge. The dimensions a and b of the rectangular waveguide corresponding to the four microwave transmission channels are designed according to practical application requirements. In order to satisfy the transmission of the TE ₁₀ mode in it, it generally satisfies λ/2<a<λ, b<λ/2, where λ is the wavelength of the microwave in free space; the two axes of the first microwave transmission channel and the second microwave transmission channel The vertical distance between them, i.e. the height h of the central coupling region, satisfies the requirement of transmitting only the TE ₁₀ and TE ₂₀ modes of the rectangular waveguide, that is, λ<h+a<1.5λ, and the length L ₁ ' of the central coupling region satisfies the phase of the two modes The difference is π/2, i.e.

where k is the free-space wavenumber of the microwave. The chamfers R ₁ ' and R ₂ ' can be optimized by electromagnetic simulation software (such as CSTMicrowave Studio), and the purpose of optimization is to make the reflection of the microwave transmission channel zero.

2) Determine the parameters of the line-to-circular polarizer. The dimensions d ₁ and d ₂ of the waveguide ridges and the distance w between the 2 waveguide ridges can be optimized by electromagnetic simulation software (such as CST Microwave Studio), and the purpose of optimization is to inject the linearly polarized TE ₁₁ mode into the circular polarizer After that, the output is the circularly polarized TE ₁₁ mode, and the axial ratio of the circularly polarized TE ₁₁ mode is 1.

3) The angle difference γ of the initial state of the two rotary joints is determined by the following formula

2. Determine the structural parameters of the high-power microwave one-dimensional beam scannable linear array

1) Determine the basic parameters of the waveguide. The dimensions a ₂ and b ₂ of the rectangular slot waveguide are designed according to practical application requirements. In order to meet the transmission of TE ₁₀ mode in it, generally λ/2<a ₂ <λ, b ₂ <λ/2, λ is the wavelength of microwave in free space; the wall thickness T is generally based on the strength and the need to ensure power capacity. Take T≥1.5mm.

的确定方法是：在保证功率容量的前提下，其取值由电磁仿真软件(如CST Microwave Studio)仿真得到，优化的目标是尺寸参数能使耦合腔的第一孔工作在谐振状态，等效电导随频率变化的曲线在中心频点获得极大值。2) The size of the outer hole of the first hole of the coupling cavity is within the range allowed by the space. In order to ensure a certain power capacity requirement, the general requirement is: R ₄ -R ₃ >1.50mm, and at the same time, R ₃ >3.00mm, height H ₁ , _H2 and the central angle

The determination method is: on the premise of ensuring the power capacity, its value is simulated by electromagnetic simulation software (such as CST Microwave Studio), and the optimization goal is that the size parameters can make the first hole of the coupling cavity work in the resonant state, equivalent to The curve of conductance versus frequency obtains a maximum value at the center frequency.

3) Determine the rotation angle θ _m of the mth coupling cavity. The coupling electric field strength of the present invention is determined by θ _m , and the equivalent conductance g _m of the outer hole increases with the increase of θ _m (0<θ _m <90°). The theoretical normalized equivalent conductance of the mth radiating element in the linear array is related to the aperture distribution, and the theoretical calculation formula of g _m is:

α_e为波导衰减常数，d为相邻辐射单元之间的间距，E_i为第i(1≤i≤m)个辐射单元的电场强度，由口径电场分布确定。η为天线辐射效率，一般取1>η>0.95。通过电磁仿真软件计算提取得到耦合腔的等效电导随耦合腔的旋转角度的关系后(即任意一个角度对应一个等效电导数值)，根据公式(3)，利用插值法即可得直线阵列中各个辐射单元(1—M)的耦合腔的旋转角度θ_m。in,

α _e is the attenuation constant of the waveguide, d is the spacing between adjacent radiation elements, and E _i is the electric field intensity of the i-th (1≤i≤m) radiation element, which is determined by the aperture electric field distribution. η is the radiation efficiency of the antenna, generally 1>η>0.95. After calculating and extracting the relationship between the equivalent conductance of the coupled cavity and the rotation angle of the coupled cavity through electromagnetic simulation software (that is, any angle corresponds to an equivalent conductance value), according to formula (3), the linear array can be obtained by interpolation method. The rotation angle θ _m of the coupling cavity of each radiation element (1-M).

4) Determine the structural parameters of the coupling cavity and the conductor in the helix. The radiation unit spacing d determines the beam scanning range. If space allows, reducing d as much as possible can increase the beam scanning range. d satisfies

where ρ ₀ is the maximum angle that the beam deviates from the normal direction of the antenna radiation port. The radius of the inner conductor of the helix is equal to the radius of the 1st, 3...2m-1...2M-1 circular through holes on the second side of the rectangular waveguide, both are R ₂ , and 0<R ₂ <R ₃ -1 is required. _The circular boss height H1 is equal to the waveguide wall thickness T. Other structural parameters of the coupled cavity and the inner conductor of the helix, including H ₃ , H ₄ , L ₁ , L ₂ , L ₃ , R ₆ and R ₅ , can be optimized by electromagnetic simulation software (such as CST Microwave Studio). The optimization goal is that the reflection of the radiation element is close to 0 at the operating frequency, and the axial ratio (the ratio of the electric field of the radiation electric field in two orthogonal directions on a plane perpendicular to the microwave transmission direction) is close to 1 in the axial direction of the helix. This ensures that the radiation element formed by the inner conductor of the helix and the coupling cavity works in the axial mode state. In addition, H ₄ -H ₁ ≈ 0.75λ is required.

5) The size of the reflection eliminating rod is determined. The radius of the m-th reflection cancellation rod is equal to r _m , which satisfies that the reflection caused by the reflection cancellation rod in the rectangular waveguide is equal to the reflection amplitude caused by the m-th coupling cavity and the m-th helix inner conductor. The specific value can be determined by the electromagnetic simulation software ( Such as CST Microwave Studio) simulation calculation and comparison. The position s _m of the m-th reflection cancellation rod satisfies the phase difference of the reflected wave caused by the m-th reflection cancellation rod and the reflection phase caused by the m-th coupling cavity and the m-th helix inner conductor, which makes the reflection cancellation rod, The reflections caused by the coupling cavity and the inner conductor of the helix cancel each other out, and the specific value of the size can be calculated and compared by the electromagnetic simulation software for the same reason.

6) The inner conductor of the helix is connected to an external stepping motor. The linear array composed of M radiation units requires M stepping motors in total. the axis of the helix) rotates. Define the angle between the direction of the radiated main beam of the linear array antenna and the normal direction of the mouth (that is, the z-axis in Figure 1) as ρ, and the spatial azimuth angle α of the linear array antenna after the rotation of the conductor in the adjacent helix along the x-axis direction The _m difference P is determined by the beam direction ρ, and the relationship between P and ρ is as follows

where k is the free-space wave number, and β is the propagation constant of the rectangular waveguide, which is calculated as

The working principle of the rotary-adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide is as follows: the high-power microwave is injected into the narrow-side slot bridge of the rectangular waveguide from the injection port, and after passing through the central coupling area, it is divided into two paths with the same amplitude. The third and fourth channels of the narrow-side slot bridge of the rectangular waveguide are injected into the first and second phase adjustment arms; the linearly polarized microwave of the TE ₁₀ mode transmitted in each channel of the rectangular waveguide transmission channel is injected into the linear-to-circular polarizer. After the circular waveguide, it is converted into a circularly polarized wave and transmitted forward. The function of the rotating joint is to change the left and right rotation characteristics of the circularly polarized wave (that is, to convert the left-handed circularly polarized wave into a right-handed circularly polarized wave, or to convert the right-handed circularly polarized wave into a right-handed circularly polarized wave. The polarized wave is converted into a left-handed circularly polarized wave). After the microwaves divided into two transmissions by the narrow-side slot bridge of the rectangular waveguide are reflected by the cylindrical base plate of the rotary joint, the reflection phase is related to the spatial orientation of the rotary joint. In the initial state, the angle difference γ of the two rotating joints is used to compensate for the different phase differences between the two microwave transmission paths. Therefore, under the above initial conditions, when the two reflected microwaves pass through the third and fourth transmission channels of the rectangular waveguide narrow-side slot bridge again, the phase of the reflected wave is related to the spatial orientation of the rotating joint. After the above conditions are met, the reflected wave All will be output from the second bridge port of the rectangular waveguide narrow-side slot bridge. The angle at which the two rotary joints rotate in the same direction around their respective axes of symmetry is defined as Δθ. After the above rotation is performed, the phase of the reflected microwave will change by 2Δθ.

The working process of the high-power microwave one-dimensional beam swept linear array is as follows: the high-power microwave is fed into the rectangular waveguide from the injection end of the rectangular waveguide and transmitted along the x-axis direction. The current on one side causes the energy to be coupled from the rectangular waveguide to the coupling cavity, thereby radiating to the free space through the radiating element formed by the conductor in the helix and the coupling cavity. Transmission reflections within the rectangular waveguide can be canceled by reflection cancellation rods. After the microwave is radiated by the one-dimensional linear array formed by the radiation unit, a small part of the remaining energy is absorbed by the external matching load, and the whole antenna works in the traveling wave state. The inner conductor of the helix works in the axial mode state and radiates circularly polarized waves. The radiation phase of the circularly polarized wave is related to the spatial azimuth angle α _m of the inner conductor of the helix. An external stepping motor controls the rotation of the inner conductor of the helix to adjust the spatial azimuth angle α _m of the inner conductor of the helix of the linear array antenna, that is, to adjust the phase distribution of each radiating element of the linear array antenna along the x-axis, so as to realize the function of beam scanning.

辐射单元的螺旋线内导体经过M个螺旋线内导体驱动控制单元调节后，沿x轴方向形成梯度相位差分布，相邻列的相位差为

微波中剩余的少部分能量被匹配负载吸收，整个天线工作在行波状态。每个控制单元对应由一个步进电机驱动，因此该高功率微波空间波束可扫平面阵列天线所需的步进电机数目为M+N。最大波束指向与

和

有关：Therefore, the high-power microwaves are injected with equal amplitude and equal phase from the first to the Nth first to Nth first phase shifters based on the rectangular waveguide narrow-side slot bridge to the N ports of the first phase shifter. The phase control unit of the rotary adjustable phase shifter of the side-slot bridge is adjusted so that the microwave injected into the high-power microwave one-dimensional beam-sweepable linear array forms an equidistant phase distribution along the y-axis direction. The injection phase difference of the dimensional beam scannable linear array is

After the inner conductor of the helix of the radiation unit is adjusted by the M driving control units of the inner conductor of the helix, a gradient phase difference distribution is formed along the x-axis direction, and the phase difference of the adjacent columns is

A small part of the energy remaining in the microwave is absorbed by the matching load, and the entire antenna works in a traveling wave state. Each control unit is correspondingly driven by a stepping motor, so the number of stepping motors required by the high-power microwave space beam swept planar array antenna is M+N. Maximum beam pointing and

and

related:

为主波束在x-o-y平面投影与x轴夹角，β为高功率微波一维波束可扫直线阵列矩形波导中的波导传播常数，k为自由空间波数。通过步进电机调整

和

即可实现空间波束扫描。where ρ is the angle between the main radiating beam and the normal direction (ie, the z-axis) of the swept planar array antenna of the high-power microwave space beam,

is the angle between the projection of the main beam on the xoy plane and the x-axis, β is the waveguide propagation constant of the high-power microwave one-dimensional beam sweepable linear array rectangular waveguide, and k is the free-space wave number. Adjusted by stepper motor

and

Spatial beam scanning can be achieved.

Compared with the prior art, the following technical effects can be achieved by adopting the present invention:

1) In the form of an array antenna, the antenna surface is flat, which is convenient for conformal design. From the design of a high-power microwave one-dimensional beam swept linear array antenna, it can be seen that the electric field amplitude of the antenna surface is easy to control and has a higher surface. efficiency;

2) Using the method of controlling the phase of the array in the whole way and in the whole column, the number of required control motors is reduced from M×N of the traditional phased array antenna to M+N, which greatly reduces the manufacturing cost of the antenna.

Description of drawings

Fig. 1 is the overall system schematic diagram of the present invention;

2 is a schematic structural diagram of a single-channel linear array of the present invention;

3 is a schematic diagram of the overall structure of a rotary adjustable phase shifter based on a rectangular waveguide narrow-side slot bridge according to the present invention;

4 is a schematic structural diagram of a rectangular waveguide narrow-side slot bridge based on a rotary-adjustable phase shifter based on a rectangular waveguide narrow-side slot bridge of the present invention;

5 is a front view of the cross-sectional structure of the rectangular waveguide narrow-side slot bridge of the rotary-adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge of the present invention;

6 is a schematic structural diagram of a linear-to-circular polarizer of a rotary-adjustable phase shifter based on a rectangular waveguide narrow-side slot bridge according to the present invention;

7 is a schematic diagram of the shape of the waveguide ridge of the rotary adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge of the present invention;

FIG. 8 is a schematic structural diagram of a rotary joint of a rotary adjustable phase shifter based on a rectangular waveguide narrow-side slot bridge according to the present invention;

Fig. 9 is the initial state schematic diagram of the working condition of the rotary joint of the rotary adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge of the present invention;

FIG. 10 is a schematic diagram of the connecting waveguide structure of the present invention;

FIG. 11 is a schematic diagram of the overall structure of the high-power microwave one-dimensional beam scannable linear array of the present invention;

FIG. 12 is a schematic structural diagram of the rectangular waveguide of the high-power microwave one-dimensional beam sweepable linear array of the present invention. Fig. 2(a) is a left side view of the rectangular waveguide, Fig. 2(b) is a top view of the rectangular waveguide, and Fig. 2(c) is a bottom view of the rectangular waveguide;

13 is a schematic structural diagram of the mth radiation unit of the high-power microwave one-dimensional beam scannable linear array of the present invention;

14 is a schematic diagram of the structure of the inner conductor of the m-th helix of the high-power microwave one-dimensional beam scannable linear array of the present invention, FIG. 4(a) is a front view of the inner conductor of the m-th helix, and FIG. 4(b) is the m-th helix. Top view of the inner conductor of the helix;

FIG. 15 is a schematic diagram of the structure of the m-th coupling cavity of the high-power microwave one-dimensional beam scannable linear array of the present invention, FIG. 15(a) is a perspective view of the m-th coupling cavity, and FIG. a) is a cross-sectional view of the NN' axis, Fig. 15(c) is a cross-sectional view of the m-th coupling cavity along BB' in Fig. 15(b), and Fig. 15(d) is a cross-sectional view of the m-th coupling cavity along Fig. 51(b) AA' section view;

FIG. 16 is a schematic diagram of the output phase adjustment principle of the phase shifter of the present invention;

FIG. 17 is a schematic diagram of the principle of phase adjustment of the inner conductor of the helix of the present invention.

Detailed ways

The schematic diagram of the structure of the high-power microwave space beam swept planar array antenna system of the present invention is shown in Figure 1. The present invention consists of five parts, which are N (20<N<100) rotations based on rectangular waveguide narrow-side slot bridges. Adjustable phase shifter 1, namely the first rotary adjustable phase shifter 11 based on rectangular waveguide narrow-side slot bridges, the second rotary adjustable phase shifter 12 based on rectangular waveguide narrow-side slot bridges, and the third based on rectangular Rotational Adjustable Phase Shifter for Waveguide Narrow Side Slot Bridge 13,...nth (1≤n≤N) Rotation Adjustable Phase Shifter 1n Based on Rectangular Waveguide Narrow Side Slot Bridge 1n,...Nth Rectangular Waveguide Narrow Side Based Rotational Adjustable Phase Shifter 1N of the Slot Bridge; N connecting waveguides 2, namely the first connecting waveguide 21, the second connecting waveguide 22, the third connecting waveguide 23,...the nth connecting waveguide 2n,...the Nth connecting waveguide 2N ; N high-power microwave one-dimensional beams can scan the linear array 3, that is, the first high-power microwave one-dimensional beam can scan the linear array 31, the second high-power microwave one-dimensional beam can scan the linear array 32, and the third high-power microwave one-dimensional beam can scan the linear array 32. One-dimensional beam scannable linear array 33, ... nth high-power microwave one-dimensional beam scannable linear array 3n, ... Nth high-power microwave one-dimensional beam scannable linear array 3N, (each high-power microwave one-dimensional beam scans a straight line The number of radiation elements of the array is M—represented by small circles in Figure 1, where 50<M<500, the spacing between adjacent radiation elements along the x-axis direction is d, and the nth high-power microwave one-dimensional beam can scan the linear array. The radiation units along the x-axis direction are the n1th radiation unit n1, the n2th radiation unit n2, the n3th radiation unit n3...the nm (1≤m≤M) radiation unit nm...the nMth radiation unit nM. In the x-axis direction, The n1th radiation unit n1 to the nMth radiation unit nM constitute the nth row radiation unit; in the y-axis direction, the 1mth radiation unit 1m to the Nmth radiation unit Nm constitute the mth column radiation unit); N phase shifter phase control units 4, that is, the first phase shifter phase control unit 41, the second phase shifter phase control unit 42, the third phase shifter phase control unit 43,...the nth phase shifter phase control unit 4n,...the Nth phase shifter Phase control unit 4N; drive control unit 5 for M high-power microwave one-dimensional beam sweepable linear arrays of helix inner conductors, namely first helix inner conductor drive control unit 51, second helix inner conductor drive control unit 52 , the third helix inner conductor drive control unit 53, ... the mth helix inner conductor drive control unit 5m, ... the Mth helix inner conductor drive control unit 5M. (The inner conductor drive control unit in the helix is represented by a dotted line in FIG. 1, each inner conductor drive control unit in the helix controls the radiation units in the corresponding column, that is, the mth inner conductor drive control unit 5m controls the mth column of radiation units) . The nth rotary-adjustable phase shifter 1n based on the narrow-side slot bridge of the rectangular waveguide and the nth high-power microwave one-dimensional beam scannable linear array 3n are connected by the nth connecting waveguide 2n, and the three together form the nth Road line array. The N-way linear arrays have exactly the same structure, and are arranged in parallel along the y-axis in space to form a plane array, and the distance between the adjacent two-way linear arrays in the y-axis direction is s. The output phase of the n-th rotary-adjustable phase shifter 1 n based on the rectangular waveguide narrow-side slot bridge is adjusted by the n-th phase shifter phase control unit 4 n.

FIG. 2 is a front view of the nth linear array of the high-power microwave space beam swept planar array antenna along the y-axis direction of the present invention. The microwave is injected from the first phase shifter port 1n1 of the nth rotary adjustable phase shifter 1n based on the rectangular waveguide narrow-side slot bridge, and the nth of the rotary adjustable phase shifter 1n based on the rectangular waveguide narrow-side slot bridge is injected. The second phase shifter port 1n2 is connected to the input port of the nth connecting waveguide 2n. The nth phase shifter phase control unit 4n is connected to the first rotation joint P22 and the second rotation joint P32 of the nth rotation-adjustable phase shifter 1n based on the rectangular waveguide narrow-side slot bridge. The output port of the nth connecting waveguide 2n is connected to the input port 3n1 of the nth high-power microwave one-dimensional beam scannable linear array 3n, and the second port 3n2 of the nth high-power microwave one-dimensional beam scannable linear array 3n is connected to an external matching load. The spiral inner conductor 3n3m of the m-th radiating element of the n-th high-power microwave one-dimensional beam can scan the linear array 3n is connected to the m-th spiral inner conductor drive control unit 5m, and the first high-power microwave one-dimensional beam can scan the linear array The spiral inner conductor of the m-th radiation element 1m of 31 313m to the N-th high-power microwave one-dimensional beam-scannable linear array 3N The spiral inner conductor of the m-th radiation element Nm of 3N is defined as the m-th column spiral inner conductor 3N3m .

As shown in FIG. 3 , the nth rotary-adjustable phase shifter 1 n based on a rectangular waveguide narrow-side slot bridge is composed of a rectangular waveguide narrow-side slot bridge P1 , a first phase adjustment arm P2 and a second phase adjustment arm P3 . The first phase adjusting arm P2 is connected to the third bridge port P13 of the rectangular waveguide narrow-side slot bridge, and the second phase adjusting arm P3 is connected to the fourth bridge port P14 of the rectangular waveguide narrow-side slot bridge P1. The first phase adjustment arm P2 is composed of a first linear circular polarizer P21 and a first rotary joint P22; the second phase adjustment arm P3 is composed of a second linear circular polarizer P31 and a second rotary joint P32. The structures of the first line-to-circular polarizer P21 and the second line-to-circular polarizer P31 are identical; the structures of the first rotary joint P22 and the second rotary joint P32 are identical. Microwaves are injected from the first bridge port P11 of the rectangular waveguide narrow-side slot bridge, and output from the second bridge port P12 of the rectangular waveguide narrow-side slot bridge.

Cut along the x-o-z plane (NN' axis) in Fig. 3, the structure of the rectangular waveguide narrow-side slot bridge P1 is shown in Fig. 4. The rectangular waveguide narrow-side slot bridge P1 is a cavity made of metal material, and the metal wall thickness is T (T>1.5mm). The first bridge port P11, the second bridge port P12, the third bridge port P13, and the fourth bridge port P14 of the narrow-side slot bridge P1 of the rectangular waveguide are all rectangular waveguides, and the inner cavity of the four-port rectangular waveguide The length of the broad side is a, and the length of the narrow side is b.

The rectangular waveguide narrow-side slot bridge is cut along the xoz plane in FIG. 3 (ie, the MM' axis), as shown in FIG. 5 . The rectangular waveguide narrow-side slot bridge P1 consists of four ports: the first bridge port P11, the second bridge port P12, the third bridge port P13, the fourth bridge port P14, the first microwave transmission channel P15, the second microwave The transmission channel P16, the third microwave transmission channel P18, the fourth microwave transmission channel P19 are four microwave transmission channels, and the central coupling area P17 is formed. The first bridge port P11 communicates with the first microwave transmission channel P15, the second bridge port P12 communicates with the second microwave transmission channel P16, and both the first microwave transmission channel P15 and the second microwave transmission channel P16 communicate with the central coupling area P17 , the central coupling area P17 communicates with the third microwave transmission channel P18 and the fourth microwave transmission channel P19, the third microwave transmission channel P18 communicates with the third electric bridge port P13, and the fourth microwave transmission channel P19 communicates with the fourth electric bridge port P14 , the vertical distance between the two axes of the first microwave transmission channel P15 and the second microwave transmission channel P16 is h, the length of the central coupling region P17 is L ₁ ′, the third microwave transmission channel P18 and the fourth microwave transmission channel P19 All turned 90 degrees, the inner radius of the rounded corners at the corners is R ₁ ', and the outer radius of the rounded corners at the corners is R ₂ ', R ₁ ' and R ₂ ' can be optimized by electromagnetic simulation software. The goal is to have zero reflections due to cornering. The horizontal distance between the axes of the third microwave transmission channel P18 and the fourth microwave transmission channel P19 is L, and it is required that 2a<L<3a.

As shown in FIG. 6 , the first linear-to-circular polarizer P21 is composed of an injection port P211 , a circular waveguide P212 , a first waveguide ridge P213 , a second waveguide ridge P214 and an end port P215 . The injection port P211 is sealed by metal, and a rectangular gap is left in the center to connect with the third bridge port P13 of the rectangular waveguide narrow-side slot bridge. The length of the wide side of the rectangular gap is a, and the length of the narrow side is b. The thickness of the metal wall of the circular waveguide P212 is T, and the diameter of the inner circle is R' (λ ₀ /2.61>R'>λ ₀ /3.41). The structures of the first waveguide ridge P213 and the second waveguide ridge P214 are exactly the same. The two waveguide ridges are symmetrical about the z-axis. λ ₀ /2.61>w>λ ₀ /3.41, and w<R), the projection of PP' on the xoy plane is OQ' (the coordinate origin is located at the center of the injection port 211 ), and the angle between OQ' and the x-axis is α (α=45°). The end port P215 is connected to the first rotary joint P22.

As shown in FIG. 7 , the first waveguide ridge P213 and the second waveguide ridge P214 have the same shape as a saddle, the length of the back of the waveguide ridge is d ₂ , and the length of the belly of the waveguide ridge is d ₁ . The backs (length d ₁ ) of the first waveguide ridge P213 and the second waveguide ridge P214 are in close contact with the inner wall of the circular waveguide P212.

As shown in FIG. 8 , the first rotary joint P22 is composed of a cylindrical bottom plate P221 and a narrow metal plate P222, and the narrow metal plate P222 is welded to the center of the cylindrical bottom plate P221. The cylindrical base plate has a radius R ₀ ' (R ₀ '=L/2) and a thickness w ₁ (w ₁ >2mm). The length of the narrow metal plate P222 is Ls (Ls=λ ₀ /4, where λ ₀ is the waveguide wavelength of the circularly polarized TE ₁₁ mode propagating in the circular waveguide), the width is R', and the thickness is w ₂ (1mm<w ₂ <4mm). The two side surfaces of the narrow metal plate P222 along the z-axis direction are rounded with a corner radius of R'/2. The narrow metal plate P222 is inserted into the circular waveguide 212 of the first linear-to-circular polarizer from the end port P215 of the first linear-to-circular polarizer, and the cylindrical base plate P221 seals the end port P215 of the first linear-to-circular polarizer . The first rotation joint P22 is rotatable around the axis of symmetry (ie, the z-axis).

Figure 9 is a schematic diagram of the initial state of the working conditions of the rotary joint of the rotary adjustment type phase shifter based on the rectangular waveguide narrow-side slot bridge; Figure 9(a) is a right side view of the first rotary joint P22 in Figure 8, Figure 9(b ) is a right side view of the second rotary joint P32. In the initial state of the first rotary joint P22 and the second rotary joint P32 of the present invention, there is an included angle between the two narrow metal plates, and the size of the included angle is γ.

10 is an enlarged schematic view of the nth connecting waveguide 2n of the present invention, the ports at both ends of the nth connecting waveguide 2n are rectangular waveguides, the outer dimension of the input port 2n1 of the nth connecting waveguide is a×b, and the nth connecting waveguide is narrow based on the rectangular waveguide. The _second phase shifter port _1n2 of the rotary adjustable phase shifter of the side-slot bridge is connected, and the waveguide size of the two is the same. The input ports 3n1 of the microwave one-dimensional beam scannable linear array have the same size. The center of the nth connecting waveguide is the gradual transition section of the waveguide connecting the two ports. The length of the transition section is L _x , which can be optimized by electromagnetic simulation software (such as CST Microwave Studio). The optimization goal is zero transmission reflection. The cross-section of the transition section remains rectangular, the width of the broad side transitions from a to a ₂ , and the size of the narrow side transitions from b to b ₂ .

As shown in FIG. 11 , the high-power microwave one-dimensional beam scannable linear array 3n is an all-metal structure and consists of two parts, the first part is a rectangular waveguide L1, and the second part is a one-dimensional linear array L2 composed of radiating elements. The microwave is injected by the injection end L11 of the rectangular waveguide, and the output end L12 of the rectangular waveguide is connected to a matching load. A one-dimensional linear array consists of M (generally: 20<M<500) radiation elements, and the spacing between adjacent radiation elements is d (0.5λ<d<λ, where λ is the wavelength of microwave in free space), along x The axial direction is installed on the narrow side of the rectangular waveguide. According to the direction from the injection end L11 of the rectangular waveguide to the output end L12, the radiation units are the first radiation unit L21, the second radiation unit L22, the third radiation unit L23, the fourth radiation unit L24, the fifth radiation unit L25...the mth radiation unit Units L2m...M-6th radiation unit L2M-6...M-4th radiation unit L2M-4...M-2th radiation unit L2M-2, Mth radiation unit L2M, where 1≤m≤M.

As shown in FIG. 12 , the inner dimension of the rectangular cross-section of the rectangular waveguide L1 has a wide side length a ₂ and a narrow side length b ₂ . Four sides) the metal wall thickness is T. M circular through holes are dug in the center of the first side L13 of the rectangular waveguide, and the circular through holes are the first circular through holes L131 on the first side of the rectangular waveguide in the direction from the injection end L11 of the rectangular waveguide to the output end L12. The second circular through hole L132 on the first side of the rectangular waveguide, the third circular through hole L133 on the first side of the rectangular waveguide...the mth circular through hole L13m on the first side of the rectangular waveguide...the Mth circular through hole L13m on the first side of the rectangular waveguide -2 The circular through hole L13M-2, the M-1th circular through hole L13M-1 on the first side of the rectangular waveguide, and the M-th circular through hole L13M on the first side of the rectangular waveguide. The radii of the first circular through hole L131 on the first side of the rectangular waveguide to the M-th circular through hole L13M are all R ₁ (R ₁ <b ₂ /2), and the first circular through hole L131 on the first side of the rectangular waveguide is The distance between the center of the circle and the injection end L11 is s ₀ (s ₀ >d/2), and the distance between the center of the m-th circular through hole L13m on the first side of the rectangular waveguide and the injection end L11 is s ₀ +(m-1) d, the distance between the centers of adjacent first circular through holes is d. 2M circular through holes are dug in the center of the second side L14 of the rectangular waveguide opposite to the first side L13 of the rectangular waveguide. The first circular through hole L1411 of the rectangular waveguide, the second circular through hole L1421 of the second side of the rectangular waveguide, the third circular through hole L1412 of the second side of the rectangular waveguide, and the fourth circular through hole L1422 of the second side of the rectangular waveguide ...the 2m-1th circular through hole L141m on the second side of the rectangular waveguide, the 2mth circular through hole L142m on the second side of the rectangular waveguide, ...the 2M-5th circular through hole L141M-2 on the second side of the rectangular waveguide, The 2M-4 circular through hole L142M-2 on the second side of the rectangular waveguide, the 2M-3 circular through hole L141M-1 on the second side of the rectangular waveguide, and the 2M-2 circular through hole on the second side of the rectangular waveguide L142M-1, the 2M-1 circular through hole L141M on the second side of the rectangular waveguide, and the 2M circular through hole L142M on the second side of the rectangular waveguide. The radii of the first, 3...2m-1...2M-1 circular through holes on the second side of the rectangular waveguide are all R ₂ , and the distance between the center of the first circular through hole on the second side of the rectangular waveguide and the injection end L11 is s ₀ , the distance between the center of the 2m-1th circular through hole on the second side of the rectangular waveguide and the injection end L11 is s ₀ +(m-1)d; the radius of the 2mth circular through hole on the second side of the rectangular waveguide is s 0 +(m-1)d; is r _m , the distance between the center of the second circular through hole on the second side of the rectangular waveguide and the injection end L11 is s ₁ , and the distance between the center of the 2mth circular through hole on the second side of the rectangular waveguide and the injection end L11 is s _m , which satisfies s _m -s ₀ -(m-1)d≈λ ₀ /4, where λ ₀ is the waveguide wavelength for microwave transmission in the rectangular waveguide L1.

The first radiating unit L21, the second radiating unit L22, the third radiating unit L23...the mth radiating unit 2m...the Mth radiating unit 2M of the present invention have the same structures (all include a reflection cancellation rod, a helix inner conductor and a coupling cavity three part). As shown in Fig. 13, taking the mth radiation unit L2m as an example, the mth radiation unit L2m consists of the mth reflection cancellation rod L2m1, the mth helix inner conductor L2m2 and the mth coupling cavity L2m3. The m-th reflection cancellation rod L2m1 is completely inserted into the rectangular waveguide L1 through the 2m-th circular through hole L142m on the second side of the rectangular waveguide, and the tip is in contact with the inner wall of the first side L13 of the rectangular waveguide; one end of the m-th coupling cavity L2m3 is connected by the first side of the rectangular waveguide. The mth circular through hole L13m is inserted into the rectangular waveguide L1 to be fixed on the rectangular waveguide L1; the mth helix inner conductor L2m2 is inserted into the rectangular waveguide L1 through the mth coupling cavity, and the 2m-1th circle on the second side of the rectangular waveguide is inserted into the rectangular waveguide L1 The shaped through hole L141m passes through the rectangular waveguide L1 and is connected to a stepping motor, and the length passing through the rectangular waveguide L1 is h'.

The m-th reflection cancelling rod L2m1 is in the shape of a cylinder with a radius equal to r _m . The m-th reflection cancellation rod L2m1 is inserted into the rectangular waveguide L1 through the 2m-th circular through hole L142m on the second side of the rectangular waveguide. In the through hole L142m, the lengths of the first reflection cancellation rod L211, the second reflection cancellation rod L221, ..., the mth reflection cancellation rod L2m1, ..., and the Mth reflection cancellation rod L2M1 are all a ₂ +T.

As shown in Figure 14, the inner conductor L2m2 of the mth helix is composed of a straight cylinder L2m21, a semicircle L2m22 perpendicular to the straight cylinder L2m21, and a helix L2m23. The straight cylinder L2m21 is a metal rod with a diameter of is 2R ₂ , the length of the straight cylinder L2m21 is L ₁ (the length of L ₁ is about twice the length of the broad side a ₂ of the rectangular waveguide, and one end of the straight cylinder L2m21 extends from the 2m-1 circular through hole on the second side of the rectangular waveguide. L141m passes through the rectangular waveguide L1 and is connected to a stepping motor. The total height of the semicircular ring _L2m22 and the helix L2m23 is L2 _; The outer diameter of the helix L2m23 is L ₃ . The angle between the initial segment tangent of the semicircular ring L2m22 and the x-axis is α _m , where α _m represents the spatial orientation of the conductor L2m2 in the mth helix. In the array, the spatial azimuth angle difference of the inner conductors of two adjacent spirals is a constant P, namely α _m -α _m-1 =P, where 1<m≤M. The above-mentioned structural parameters L ₁ , L ₂ , and L ₃ are optimized by electromagnetic simulation software (such as CST Microwave Studio). The optimization goal is that the axial ratio of the radiation of the helix in the axial direction is zero, and the reflection is close to zero.

外孔L2m332的对称轴CC'与x轴的夹角定义为耦合腔的旋转角，用θ_m表示。沿图15(b)BB'轴截断，得到第二孔L2m34的截面俯视图如图15(d)所示，第二孔L2m34的高度为H₂-H₁，第二孔L2m34的轮廓由两段弧线构成，尺寸较大的圆弧线的半径为R₄，对应的圆心角为

尺寸较小弧线的半径为R₅，对应的圆心角为

第二孔L2m34的对称轴DD'与x轴的夹角也为θ_m，第一耦合腔L213到第M耦合腔L2M3结构的尺寸除了耦合腔的旋转角θ_m不同外，其它结构尺寸均相同。第三孔L2m35的高度H₃-H₂，截面形状为圆形，圆形半径为R₅。第四孔L2m36的高度H₄-H₃，截面形状为圆形，圆形半径为R₆。As shown in Figure 15(a), the m-th coupling cavity L2m3 has a cylindrical boss L2m31 at one end and a rectangular parallelepiped L2m32 at the other end, the outer radius of the cylindrical boss is R ₁ , and the height of the boss is H ₁ . Cut along NN' in Fig. 15(a), the front view of the m-th coupling cavity L2m3 is shown in Fig. 15(b). Four holes of different shapes are dug inside the m-th coupling cavity L2m3. The direction from the cylindrical boss L2m31 to the cuboid 2m32 is the first hole L2m33, the second hole L2m34, the third hole L2m35, the fourth hole L2m36, and four holes. The holes are connected together to form a channel for microwave transmission. 15(b) AA', the cross-sectional top view of the first hole L2m33 is obtained as shown in Fig. 15(d). _1. The cross-sectional shape of the inner hole 2m331 is a circle with a radius of _{R 2.} The inner conductor _L2m2 of the m-th helix is inserted into the waveguide through the inner hole. The central angle of the outer hole L2m332 is

The angle between the symmetry axis CC' of the outer hole L2m332 and the x-axis is defined as the rotation angle of the coupling cavity, which is represented by θ _m . 15(b) along the BB' axis, the cross-sectional top view _of the _second hole L2m34 is obtained as shown in FIG. 15(d). The arc is formed, the radius of the larger arc is R ₄ , and the corresponding central angle is

The radius of the arc with the smaller size is R ₅ , and the corresponding central angle is

The angle between the symmetry axis DD' of the second hole L2m34 and the x-axis is also θ _m . The dimensions of the structures from the first coupling cavity L213 to the M-th coupling cavity L2M3 are the same except for the rotation angle θ _m of the coupling cavity. . The height of the third hole L2m35 is H ₃ -H ₂ , the cross-sectional shape is a circle, and the circle radius is R ₅ . The height of the fourth hole L2m36 is H ₄ -H ₃ , the cross-sectional shape is a circle, and the radius of the circle is R ₆ .

因此相邻两路直线阵列的馈入相位差也应为常量，即馈入相位差等于相邻两路直线阵列的移相器的旋转角度差：

FIG. 16 is a schematic diagram of the phase adjustment principle of the phase shifter of the present invention. The phase control unit 4n of the nth phase shifter is a rotatable bearing, the bearing is connected to a stepping motor, and is driven by the stepping motor to rotate around its own axis (ie, the z-axis). The rotatable bearing has the same outer diameter R' ₀ as the first rotary joint P22 and the second rotary joint P32 of the nth rotary adjustable phase shifter 1n based on the narrow side slot bridge of the rectangular waveguide, and the nth phase shifter phase control The unit 4n is connected with the first rotation joint P22 and the second rotation joint P32 of the nth rotation-adjustable phase shifter 1n based on the narrow-side slot bridge of the rectangular waveguide (the three are meshed by peripheral gears). The nth phase shifter phase control unit 4n is externally connected to a stepping motor, and rotates around the z-axis, that is, drives the first rotating joint P22 and the second rotating joint P32 to rotate synchronously. It can be known from the rotationally adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge that the nth phase shifter phase control unit 4n rotates θ _n synchronously to drive the nth rotationally adjustable phase shifter based on the rectangular waveguide narrow-side slot bridge. The first rotary joint P22 and the second rotary joint P32 of the phaser 1n rotate in the same direction by θ _n , so that the output phase of the phase shifter changes by 2θ _n . The working state of the high-power microwave space beam swept planar array antenna requires that the rotation angle difference of the phase shifters of the two adjacent linear arrays be a constant, namely

Therefore, the feeding phase difference of the two adjacent linear arrays should also be constant, that is, the feeding phase difference is equal to the rotation angle difference of the phase shifters of the adjacent two linear arrays:

有

FIG. 17 is a schematic diagram of the phase adjustment principle of the linear array of the present invention. The m-th helical inner conductor drive control unit 5m is composed of the m-th geared sliding plate 5m2 and N geared bearings. The N geared bearings are the m1th bearing 5m11 and the m2th bearing 5m12 in sequence along the y-axis direction. The m3th bearing 5m13...the mnth bearing 5m1n...the mNth bearing 5m1N, the above bearings are sequentially connected to the helical inner conductors of the mth row of N radiation units along the y-axis direction (that is, the helical inner conductor 313m to the helical inner conductor 3N3m) Closely connected, the rotation of the bearing will drive the inner conductor of the helix to rotate along with it. The outer diameter of each bearing is r (d/2>r>R ₂ ), the sliding plate and the gear of the bearing are meshed together, and the gear of the bearing is the same size as the gear of the sliding plate. One end 5m3 of the inner conductor drive control unit 5m of the mth helix is driven by the stepping motor to move h _m along the y-axis direction, thereby driving the m1th bearing 5m11 to the Nmth bearing 5m1N to rotate by 2h _m /r radians, and at the same time driving the mth row The spatial azimuth of the conductors in the helix is rotated by 2h _m /r radians. In the x-axis direction, the length difference between the adjacent helix inner conductor drive control units driven by the external stepping motor is a constant Δh=h _m -h _m-1 , so the space of the conductors in the adjacent column helix in the x-axis direction The azimuth difference is also a constant, set to

Have

辐射单元的螺旋线内导体经过M个螺旋线内导体驱动控制单元调节后，沿x轴方向形成梯度相位差分布，相邻列的相位差为

微波中剩余的少部分能量被匹配负载吸收，整个天线工作在行波状态。每个控制单元对应由一个步进电机驱动，因此该高功率微波空间波束可扫平面阵列天线所需的步进电机数目为M+N。增益最大波束指向

与

和

有关。(参考公式(7))Therefore, high-power microwaves are injected with equal amplitude and equal phase from the first to Nth first to Nth first phase shifter ports of the rotary adjustable phase shifters 11 to 1N based on rectangular waveguide narrow-side slot bridges. The phase control units 41 to 4N of the rotary adjustable phase shifters 11 to 1N of the side-slot bridge are adjusted so that the microwaves injected into the high-power microwave one-dimensional beam-sweepable linear array form an equidistant phase distribution along the y-axis direction. The injection phase difference of the high-power microwave one-dimensional beam scannable linear array in the adjacent row is

After the inner conductor of the helix of the radiation unit is adjusted by the M driving control units of the inner conductor of the helix, a gradient phase difference distribution is formed along the x-axis direction, and the phase difference of the adjacent columns is

A small part of the energy remaining in the microwave is absorbed by the matching load, and the entire antenna works in a traveling wave state. Each control unit is correspondingly driven by a stepping motor, so the number of stepping motors required by the high-power microwave space beam swept planar array antenna is M+N. Gain maximum beam pointing

and

and

related. (Refer to formula (7))

为主波束在x-o-y平面投影与x轴夹角，β为高功率微波一维波束可扫直线阵列矩形波导中的波导传播常数，k为自由空间波数。因此在波束扫描的过程中需要波束指向某一空间方位

时，通过(7)式即可算出

和

进而根据

和

计算得到移相器和螺旋线内导体的工作状态，通过步进电机调整实现上述状态后，即可引导波束指向所需要的角度，此即为波束扫描的原理。where ρ is the angle between the main radiating beam and the normal direction (ie, the z-axis) of the swept planar array antenna of the high-power microwave space beam,

is the angle between the projection of the main beam on the xoy plane and the x-axis, β is the waveguide propagation constant of the high-power microwave one-dimensional beam sweepable linear array rectangular waveguide, and k is the free-space wave number. Therefore, in the process of beam scanning, the beam needs to be pointed to a certain spatial orientation

, it can be calculated by formula (7)

and

and then according to

and

The working state of the phase shifter and the inner conductor of the helix is obtained by calculation. After the above state is achieved by adjusting the stepper motor, the beam can be directed to the required angle, which is the principle of beam scanning.

和

可由步进电机驱动在0到360度变化，根据(4)式可计算得到波束扫描范围，在x-o-z和y-o-z平面上最大波束指向均达到±35°。Taking the system operating at the center frequency of X-band at 8.4GHz as an example, the output rectangular waveguide of the rotary adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide is a=24mm, b=12mm, and the high-power microwave one-dimensional The dimensions of the rectangular waveguide of the beam-scannable linear array antenna are a ₂ =30mm, b ₂ =15mm. When the spacing between adjacent radiating elements in the x-axis direction is d=0.63λ=22.5mm, and the spacing between two adjacent linear arrays in the y-axis direction is also s=0.63λ=22.5mm,

and

It can be driven by a stepping motor to change from 0 to 360 degrees. According to the formula (4), the beam scanning range can be calculated, and the maximum beam pointing on the xoz and yoz planes can reach ±35°.

Claims (15)

1. A high-power microwave space beam swept planar array antenna is characterized in that the high-power microwave space beam swept planar array antenna is made up of five parts, and they are respectively N based on the rotary adjustment type of the rectangular waveguide narrow-side slot bridge. Phase shifters, namely, a first rotary-adjustable phase shifter (11) based on a rectangular waveguide narrow-side slot bridge, a second rotary-adjustable phase shifter (12) based on a rectangular waveguide narrow-side slot bridge, and a third based on Rotational Adjustable Phase Shifter for Rectangular Waveguide Narrow Side Slot Bridge Rotationally adjustable phase shifter of the bridge (1N); N connection waveguides, namely the first connection waveguide (21), the second connection waveguide (22), the third connection waveguide (23), ... the nth connection waveguide (2n) , ... Nth connecting waveguide (2N); N high-power microwave one-dimensional beams can scan a linear array, that is, the first high-power microwave one-dimensional beam can scan a linear array (31), and the second high-power microwave one-dimensional beam can scan Linear array (32), third high-power microwave one-dimensional beam scannable linear array (33), ... nth high-power microwave one-dimensional beam scannable linear array (3n), ... Nth high-power microwave one-dimensional beam scannable linear array (3n) Linear array (3N), the number of radiation elements of the linear array that can be scanned by each high-power microwave one-dimensional beam is M, the distance between adjacent radiation elements along the x-axis direction is d, and the nth high-power microwave one-dimensional beam can scan a straight line The radiation units of the array are sequentially the n1th radiation unit, the n2th radiation unit, the n3th radiation unit...the nmth radiation unit...the nMth radiation unit along the x-axis direction; in the x-axis direction, the n1th radiation unit to the nMth radiation unit) constitute the nth row of radiation units; in the y-axis direction, the mth radiation unit to the Nmth radiation unit constitute the mth column of radiation units; N phase shifter phase control units, namely the first phase shifter phase control unit (41), The second phase shifter phase control unit (42), the third phase shifter phase control unit (43),...the nth phase shifter phase control unit (4n),...the Nth phase shifter phase control unit (4N); The drive control units for the inner conductors of the spirals of the M high-power microwave one-dimensional beam scannable linear arrays, namely the first spiral inner conductor drive control unit (51), the second spiral inner conductor drive control unit (52), the first spiral inner conductor drive control unit (52), Triple helix inner conductor drive control unit (53), ... mth helix inner conductor drive control unit (5m), ... Mth helix inner conductor drive control unit (5M), mth helix inner conductor drive control unit ( 5m) Control the m-th row of radiation units; the n-th rotary-adjustable phase shifter based on the narrow-side slot bridge of the rectangular waveguide (1n) and the n-th high-power microwave one-dimensional beam-scannable linear array (3n) are connected by the n-th waveguide (2n) connected, the three together form the nth linear array along the x-axis direction; the N-channel linear arrays have exactly the same structure, and are arranged in parallel along the y-axis in space to form a plane array, and the two adjacent linear arrays are in the y-axis direction. The spacing is s; the nth is based on the rotational adjustment of the narrow-side slot bridge of the rectangular waveguide. The segmental phase shifter (1n) is adjusted by the nth phase shifter phase control unit (4n) to adjust the output phase; wherein 1≤n≤N, 1≤m≤M, N and M are both positive integers; The inner conductor of the spiral is the first spiral inner conductor of the nth row (3n31)…the nth row of the mth spiral inner conductor (3n3m)…the nth row of the Mth spiral inner conductor (3n3M); the mth column of the spiral The inner conductors are the first spiral inner conductor (313m) in the mth column, the second spiral inner conductor in the mth column (323m)...the mth column and the nth spiral inner conductor (3n3m)...the mth column Nth spiral Inner conductor (3N3m); Microwaves are injected from the first phase shifter port (1n1) of the nth rotary-adjustable phase shifter (1n) based on the rectangular waveguide narrow-side slot bridge, and the n-th rotary-adjustable phase shifter based on the rectangular-waveguide narrow-side slot bridge The second phase shifter port (1n2) of the device (1n) is connected to the input port (2n1) of the nth connecting waveguide (2n); The first rotary joint (P22) of the rotary adjustable phase shifter (1n) of the electric bridge is connected with the second rotary joint (P32); the output port (2n2) of the nth connection waveguide (2n) is connected with the nth high-power microwave one. The input port (3n1) of the 2D beam scannable linear array (3n) is connected, and the second port (3n2) of the nth high-power microwave one-dimensional beam scannable linear array (3n) is connected to an external matching load; the nth high-power microwave one-dimensional The helix inner conductor (3n3m) of the mth radiating element of the beam scannable linear array (3n) is connected to the mth helix inner conductor drive control unit (5m), and the first high-power microwave one-dimensional beam scannable linear array ( 31) The inner conductor of the helix (313m) of the mth radiation element (1m) to the inner conductor of the helix of the mth radiation element (Nm) of the Nth high-power microwave one-dimensional beam scannable linear array (3N) ( 3N3m) is defined as the inner conductor of the m-th column spiral; The nth rotary-adjustable phase shifter (1n) based on a rectangular waveguide narrow-side slot bridge is composed of a rectangular waveguide narrow-side slot bridge (P1), a first phase adjustment arm (P2) and a second phase adjustment arm (P3) ; The first phase adjustment arm (P2) is connected to the third bridge port (P13) of the rectangular waveguide narrow-side slot bridge, and the second phase adjustment arm (P3) is connected to the fourth of the rectangular waveguide narrow-side slot bridge (P1). The bridge port (P14) is connected; the first phase adjustment arm (P2) is composed of the first wire-rotating circular polarizer (P21) and the first rotary joint (P22); the second phase-adjusting arm (P3) is formed by the second wire-rotating The circular polarizer (P31) and the second rotary joint (P32) are composed; the first wire-to-circular polarizer (P21) and the second wire-to-circular polarizer (P31) have the same structure, and the first rotary joint (P22) The structure is exactly the same as that of the second rotary joint (P32); microwaves are injected from the first bridge port (P11) of the rectangular waveguide narrow-side slot bridge, and output from the second bridge port (P12) of the rectangular waveguide narrow-side slot bridge; The rectangular waveguide narrow-side slot bridge (P1) is a cavity made of metal material. Three bridge ports (P13), fourth bridge ports (P14) four ports, the first microwave transmission channel (P15), the second microwave transmission channel (P16), the third microwave transmission channel (P18), the fourth microwave transmission channel The transmission channel (P19) consists of four microwave transmission channels and the central coupling area (P17); the rectangular waveguide narrow-side slot bridge is composed of the first bridge port (P11) (P11), the second bridge port (P12), and the third bridge port (P12). The bridge port (P13) and the fourth bridge port (P14) are both rectangular waveguides, and the length of the broad side of the inner cavity of the rectangular waveguide of the four ports is a, and the length of the narrow side is both b; the first microwave transmission channel (P15 ) and the vertical distance between the two axes of the second microwave transmission channel (P16) is h, the length of the central coupling region (P17) is L ₁ ', the third microwave transmission channel (P18) and the fourth microwave transmission channel ( The horizontal distance of the axis of P19) is L; The first line-to-circular polarizer (P21) consists of an injection port (P211), a circular waveguide (P212), a first waveguide ridge (P213), a second waveguide ridge (P214) and an end port (P215); the injection port ( P211) is sealed by metal, and there is a rectangular gap in the center, which is connected to the third bridge port (P13) of the narrow-side slot bridge of the rectangular waveguide. The length of the wide side of the rectangular gap is a, and the length of the narrow side is b; The inner circle diameter is R'; the first waveguide ridge (P213) has the same shape and structure as the second waveguide ridge (P214), and the two waveguide ridges are symmetrical about the z-axis; the end port (P215) is connected to the first rotary joint (P22) ; The first waveguide ridge (P213) and the second waveguide ridge (P214) are shaped like a saddle, the length of the back of the waveguide ridge is d ₂ , and the length of the belly of the waveguide ridge is d ₁ ; the first waveguide ridge (P213) and the second The back of the waveguide ridge (P214) is in contact with the inner wall of the circular waveguide (P212); the angle between the projection OQ' of the line segment PP' connecting the centers of the ventral surfaces of the two waveguide ridge ridges on the xoy plane and the x-axis is α=45°, the origin of the coordinates O is located in the center of the injection port (P211); The first rotary joint (P22) consists of a cylindrical base plate (P221) and a narrow metal plate (P222). The narrow metal plate (P222) is welded in the center of the cylindrical base plate (P221); The end port (P215) of the circular polarizer is inserted into the circular waveguide (P212) of the first linear-to-circular polarizer, and the cylindrical base plate (P221) seals the end port (P215) of the first linear-to-circular polarizer; The first rotary joint (P22) can rotate around the axis of symmetry, that is, the z-axis; In the initial state of the first rotary joint (P22) and the second rotary joint (P32), there is an included angle between the narrow metal plate (P222) and the narrow metal plate of the second rotary joint (P32), which is named as The angle difference between the initial states of the first rotary joint (P22) and the second rotary joint (P32), and the magnitude is γ; The ports at both ends of the nth connecting waveguide (2n) are rectangular waveguides, the outer dimension of the input port 2n1 of the nth connecting waveguide is a _× b, and the The two phase shifter ports (1n2) are connected, and the waveguide dimensions of the two are the same. The outer dimension of the output port (2n2) of the n-th connection waveguide (2n) is a ₂ ×b ₂ , which is compatible with the n-th high-power microwave one-dimensional beam. The input port (3n1) of the sweep line array has the same size; The high-power microwave one-dimensional beam-scannable linear array (3n) is an all-metal structure and consists of two parts, the first part is a rectangular waveguide (L1), and the second part is a one-dimensional linear array (L2) composed of radiating elements; one-dimensional The linear array is composed of M radiating elements, M is a positive integer, and the distance between adjacent radiating elements is d, and is installed on the narrow side of the rectangular waveguide (L1) along the x-axis direction; The direction to the output end (L12) is the first radiation unit (L21), the second radiation unit (L22), the third radiation unit (L23)...the mth radiation unit (L2m)...the Mth radiation unit (L2M), where 1≤m≤M; The inner dimension of the rectangular cross-section of the rectangular waveguide (L1) is a ₂ , and the length of the narrow side is b ₂ . The wall thickness of each surface is T; M circular through holes are dug in the center of the first side (L13) of the rectangular waveguide, and the circular through holes are rectangular in the direction from the injection end (L11) to the output end (L12) of the rectangular waveguide. The first circular through hole (L131) on the first side of the waveguide, the second circular through hole (L132) on the first side of the rectangular waveguide, the third circular through hole (L133) on the first side of the rectangular waveguide... The mth circular through hole on one side (L13m)...the M-2 circular through hole (L13M-2) on the first side of the rectangular waveguide, the M-1 circular through hole on the first side of the rectangular waveguide (L13M- 1), the Mth circular through hole (L13M) on the first side of the rectangular waveguide; the radii from the first circular through hole (L131) to the Mth circular through hole (L13M) on the first side of the rectangular waveguide are all R ₁ , the distance between the center of the first circular through hole (L131) on the first side of the rectangular waveguide and the injection end (L11) is s ₀ , and the distance between the centers of the first circular through holes on the first side of the adjacent rectangular waveguide is d; 2M circular through holes are dug in the center of the second side (L14) of the rectangular waveguide opposite to the first side (L13) of the rectangular waveguide. The directions are the first circular via (L1411) on the second side of the rectangular waveguide, the second circular via (L1421) on the second side of the rectangular waveguide, and the third circular via (L1412) on the second side of the rectangular waveguide , the fourth circular via (L1422) on the second side of the rectangular waveguide...the 2m-1 circular via (L141m) on the second side of the rectangular waveguide, the 2m-th circular via (L142m) on the second side of the rectangular waveguide …the 2M-5 circular via (L141M-2) on the second side of the rectangular waveguide, the 2M-4 circular via (L142M-2) on the second side of the rectangular waveguide, the 2M- 3 circular through holes (L141M-1), 2M-2 circular through holes on the second side of the rectangular waveguide (L142M-1), 2M-1 circular through holes on the second side of the rectangular waveguide (L141M), rectangular waveguides The 2M circular through hole (L142M) on the second side; the radii of the 1st, 3...2m-1...2M-1 circular through holes on the second side of the rectangular waveguide are all R ₂ . The distance between the center of the circular through hole (L1411) and the injection end (L11) is s ₀ , and the distance between the center of the circular through hole (L141m) on the second side of the rectangular waveguide and the injection end (L11) is s ₀ +(m-1)d; the radius of the 2mth circular through hole (L142m) on the second side of the rectangular waveguide is r _m , the center and injection end of the second circular through hole (L1421) on the second side of the rectangular waveguide (L11) with distance s ₁ , rectangle The distance between the center of the 2mth circular through hole (L142m) on the second side of the waveguide and the injection end (L11) is s _m ; The first radiation unit (L21), the second radiation unit (L22), the third radiation unit (L23), the fourth radiation unit (L24), the fifth radiation unit (L25),...the mth radiation unit (L2m)...the M-6 radiation unit (L2M-6)...M-4th radiation unit (L2M-4)...M-2th radiation unit (L2M-2)...Mth radiation unit (L2M) has the same structure; mth radiation unit (L2m) consists of the mth reflection cancellation rod (L2m1), the mth helix inner conductor (L2m2) and the mth coupling cavity (L2m3); the mth reflection cancellation rod (L2m1) passes through the second side of the rectangular waveguide. The 2m circular through hole (L142m) is completely inserted into the rectangular waveguide (L1), and the top is in contact with the inner wall of the first side (L13) of the rectangular waveguide; one end of the m-th coupling cavity (L2m3) is connected by the m-th circular hole on the first side of the rectangular waveguide. The hole (L13m) is inserted into the rectangular waveguide (L1) to be fixed on the rectangular waveguide (L1); the m-th helix inner conductor (L2m2) is inserted into the rectangular waveguide (L1) through the m-th coupling cavity, and the m A 2m-1 circular through hole (L141m) passes through the rectangular waveguide (L1), an external stepping motor is connected, and the length passing through the rectangular waveguide (L1) is h'; The mth reflection cancellation rod (L2m1) is in the shape of a cylinder with a radius equal to r _m ; the mth reflection cancellation rod (L2m1) is inserted into the rectangular waveguide (L1) through the 2mth circular through hole (L142m) on the second side of the rectangular waveguide , one end is on the inner wall of the first side (L13) of the rectangular waveguide, and the other end is embedded in the 2mth circular through hole (L142m) on the second side of the rectangular waveguide; The inner conductors of the M spirals have exactly the same structure; the inner conductor of the mth spiral (L2m2) consists of a straight cylinder (L2m21), a semicircle (L2m22) perpendicular to the straight cylinder (L2m21), and a helix (L2m22). L2m23), the straight cylinder (L2m21) is a metal rod, the length of the straight cylinder (L2m21) is L ₁ , and one end of the straight cylinder (L2m21) passes through the 2m-1 circle on the second side of the rectangular waveguide. The hole (L141m) passes through the rectangular waveguide (L1), and the stepper motor is externally connected; the total height of the semi-circular ring (L2m22) and the helix (L2m23) is L ₂ ; the diameter of the semi-circular ring (L2m22) is L ₃ / 2. The helix (L2m23) is a helix with equal helix radius and equal pitch, L3 is the helix outer diameter _of the helix (L2m23); the angle between the initial segment tangent of the semicircle (L2m22) and the x-axis is α _m , α _m represents the spatial orientation of the m-th helix inner conductor (L2m2); the spatial azimuth angle difference of the inner conductors of the two adjacent spirals is a constant P, that is, α _m -α _m-1 =P; The m-th coupling cavity (L2m3) has a cylindrical boss (L2m31) at one end and a cuboid (L2m32) at the other end, the outer radius of the cylindrical boss is R ₁ , and the height of the boss is H ₁ ; Four holes of different shapes are dug inside the mth coupling cavity (L2m3), from the cylindrical boss (L2m31) to the cuboid (L2m32) are the first hole (L2m33), the second hole (L2m34), the third hole The hole (L2m35), the fourth hole (L2m36), the four holes are connected together to form a microwave transmission channel; cut along the AA' direction to obtain the section of the first hole (L2m33), the first hole (L2m33) is composed of an inner hole ( L2m331) and an outer hole (L2m332), the heights of the inner hole (L2m331) and the outer hole (L2m332) are both H ₁ , the cross-sectional shape of the inner hole (L2m331) is a circle with a radius of R ₂ , and the m-th spiral inner conductor (L2m2) is inserted into the waveguide through the inner hole, the outer hole (L2m332) is approximately semi-circular, the inner radius is R ₃ , the outer radius is R ₄ , and the central angle of the outer hole (L2m332) is

The angle between the symmetry axis CC' of the outer hole (L2m332) and the x-axis is defined as the rotation angle of the coupling cavity, represented by θ _m , 0<θ _m <90°; the height of the second hole (L2m34) is H ₂ -H _1. The contour of the second hole (L2m34) consists of two arcs, the radius of the arc with a larger size is R ₄ , and the corresponding central angle is

The radius of the arc with the smaller size is R ₅ , and the corresponding central angle is

The angle between the symmetry axis DD' of the second hole ( _L2m34 ) and the x-axis is the same as the rotation angle θm of the coupling cavity. Except for the different rotation angle θ _m , other structural dimensions are the same; the height H ₃ -H ₂ of the third hole (L2m35), the cross-sectional shape is a circle, and the radius of the circle is R ₅ ; the height H ₄ of the fourth hole (L2m36) -H ₃ , the cross-sectional shape is a circle, and the radius of the circle is R ₆ ; The nth phase shifter phase control unit (4n) is a rotatable bearing, the bearing is externally connected to a stepping motor, and is driven by the stepping motor to rotate around its own axis, and the nth phase shifter phase control unit (4n) is externally connected to the stepping motor, Rotating around the z-axis, that is, driving the first rotary joint (P22) and the second rotary joint (P32) to rotate synchronously; every time the nth phase shifter phase control unit (4n) rotates by θ _n , synchronously drives the nth th The first rotary joint (P22) and the second rotary joint (P32) of the rotary-adjustable phase shifter (1n) of the side-slit bridge rotate around the same direction by θ _n , and the output phase of the phase shifter changes by 2θ _n ; The m-th helical inner conductor drive control unit (5m) is composed of the m-th geared sliding plate (5m2) and N geared bearings. The N geared bearings are the m1th bearing (5m11) in the y-axis direction. , the m2th bearing (5m12), the m3th bearing (5m13)...the mnth bearing (5m1n)...the mNth bearing (5m1N), the above bearings are sequentially connected to the helical inner conductor of the mth row of N radiation units along the y-axis direction Closely connected, the rotation of the bearing will drive the inner conductor of the helix to rotate along with it; the sliding plate and the gear of the bearing are meshed together, and the gear of the bearing is the same size as the gear of the sliding plate; High-power microwaves are injected from the first bridge ports (P11) of the rectangular waveguide narrow-side slot bridges (11) to (1N) based on the rotary-adjustable phase shifters (11) to (1N) of the rectangular-waveguide narrow-side slot bridges, and pass through After adjustment by the first phase shifter phase control unit (41) to the Nth phase shifter phase control unit (4N), the microwaves injected into the high-power microwave one-dimensional beam scannable linear array form an equidistant phase distribution along the y-axis direction , the injection phase difference of the high-power microwave one-dimensional beam scannable linear array of adjacent rows is

After the inner conductor of the helix of the radiation unit is adjusted by the M driving control units of the inner conductor of the helix, a gradient phase difference distribution is formed along the x-axis direction, and the phase difference of the adjacent columns is

A small part of the energy remaining in the microwave is absorbed by the matching load, and the entire antenna works in a traveling wave state. 2. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that said N satisfies 20<N<100, and the number M of radiation units satisfies 20<M<500; the distance between adjacent radiation units 0.5λ<d<λ is satisfied for d, where λ is the wavelength of microwave in free space. 3. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that the nth rectangular waveguide narrow-side slot circuit based on the rotation-adjustable phase shifter 1n of the rectangular-waveguide narrow-side slot bridge The metal wall thickness of the bridge (P1) and circular waveguide (P212) is T, and the metal wall thickness of the four sides of the rectangular waveguide (L1) of the high-power microwave one-dimensional beam sweepable linear array (3n) is also T, T>1.5 mm. 4. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that the first bridge port (P11) and the second bridge port of the rectangular waveguide narrow-side slot bridge (P1) (P12), the third bridge port (P13), the fourth bridge port (P14), the broad side length a of the inner cavity satisfies λ/2<a<λ, the narrow side length b satisfies b<λ/2, λ is the wavelength of microwave in free space; the vertical distance h between the two axes of the first microwave transmission channel (P15) and the second microwave transmission channel (P16) satisfies λ<h+a<1.5λ, the central coupling region ( The length L ₁ ' of P17) satisfies the following formula

where k is the free-space wave number of the microwave; the third microwave transmission channel (P18) and the fourth microwave transmission channel (P19) of the rectangular waveguide narrow-side slot bridge (P1) both turn 90 degrees, and the corners are rounded The inner radii are R ₁ ', and the outer radius of the rounded corners is R ₂ '; R ₁ ' and R ₂ ' are optimized by electromagnetic simulation software, and the purpose of optimization is to make the reflection of the microwave transmission channel zero. 5. high-power microwave space beam swept planar array antenna as claimed in claim 1, it is characterized in that the inner circle diameter R ' of the circular waveguide (P212) of described first line rotating circular polarizer (P21) satisfies: λ ₀ /2.61>R'>λ ₀ /3.41, λ ₀ is the waveguide wavelength of the circularly polarized TE ₁₁ mode propagating in the circular waveguide; the dimensions of the first waveguide ridge (P213) and the second waveguide ridge (P214) d ₁ and d ₂ and the distance w between the first waveguide ridge (P213) and the second waveguide ridge (P214), that is, the length of the line segment PP' connecting the centers of the top surfaces of the two waveguide ridges, are optimized by electromagnetic simulation software. The optimized The purpose is to inject the circular polarizer into the linearly polarized TE ₁₁ mode, and the output is the circularly polarized TE ₁₁ mode, and the axial ratio of the circularly polarized TE ₁₁ mode is 1; the first waveguide ridge (P213) and the second waveguide The distance w between the ridges (P214) satisfies λ ₀ /2.61>w>λ ₀ /3.41 and w<R', where λ ₀ is the waveguide wavelength of the circularly polarized TE ₁₁ mode propagating in the circular waveguide. 6. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that the diameter R' ₀ of the cylindrical base plate (P221) of the first rotary joint (P22) requires R' ₀ = L/2, thickness w ₁ >2mm; the length of the narrow metal plate (P222) s=λ ₀ /4, where λ ₀ is the waveguide wavelength of the circularly polarized TE ₁₁ mode propagating in the circular waveguide, and the width is equal to R' , the thickness w ₂ satisfies 1mm<w ₂ <4mm; the two sides of the narrow metal plate (P222) of the first rotary joint (P22) along the z-axis are rounded, and the fillet radius is R'/2; the first rotation The angle difference γ of the initial state of the joint (P22) and the second rotary joint (P32) is determined by the following formula

where k is the free space wave number, 3a>L>2a, h is the vertical distance between the two axes of the first microwave transmission channel (P15) and the second microwave transmission channel (P16), and a is the inner cavity of the rectangular waveguide of the broadside length. 7. The high-power microwave space beam swept planar array antenna as claimed in claim 1, wherein the length of the transition section of the nth connecting waveguide (2n) is that L is optimized by electromagnetic simulation software, and the optimized target is The transmission reflection is zero, the cross-section of the transition segment remains rectangular, the broad side dimension transitions from a to a ₂ , and the narrow side dimension transitions from b to b ₂ . 8. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that the high-power microwave one-dimensional beam swept linear array (3n) on the rectangular waveguide (L1) on the first side surface The radius of the first circular through hole (L131) is R ₁ to satisfy R ₁ <b ₂ /2; The distance s ₀ satisfies s ₀ >d/2, and the distance between the center of the m-th circular through hole (L13m) on the first side of the rectangular waveguide and the injection end (L11) is s ₀ +(m-1)d; The distance s _m between the center of the 2mth circular through hole (L142m) on the two sides and the injection end (L11) satisfies s _m -s ₀ -(m-1)d≈λ ₀ /4, where λ ₀ is the microwave in the rectangular The waveguide wavelength transmitted in the waveguide (L1); the dimensions a ₂ and b ₂ of the rectangular waveguide (L1) satisfy λ/2<a ₂ <λ, b ₂ <λ/2, where λ is the wavelength of the microwave in free space. 9. The high-power microwave space beam swept planar array antenna according to claim 1, wherein the structural parameters L ₁ , L ₂ and L ₃ of the m-th helix inner conductor (L2m2) are all determined by electromagnetic simulation software The optimization is obtained, and the optimization goal is that the axial ratio of the radiation of the helix in the axial direction is zero, and the reflection is close to zero; the diameter of the right cylinder (L2m21) is the same as the second side of the rectangular waveguide. ... 2M-1 circular through holes have the same diameter as 2R ₂ , and the size of R ₂ requires 0<R ₂ <R ₃ -1. 10. The high-power microwave space beam swept planar array antenna as claimed in claim 1, wherein the parameter of the mth coupling cavity (L2m3) satisfies: R ₄ -R ₃ >1.50mm, while requiring R ₃ > 3.00mm, height H ₁ , H ₂ and central angle

The determination method is: on the premise of ensuring the power capacity, its value is obtained by the electromagnetic simulation software, and the optimization goal is to make the first hole (L2m33) of the mth coupling cavity (L2m3) work in the resonance state, The curve of equivalent conductance versus frequency obtains a maximum value at the center frequency point; the equivalent conductance g _m of the outer hole of the first hole (L2m33) of the mth coupling cavity (L2m3) increases with the increase of θ _m , and g The theoretical formula for _m is

in,

α _e is the attenuation constant of the waveguide, d is the spacing between adjacent radiating elements, E _i is the electric field strength of the ith radiating element, 1≤i≤m, η is the antenna radiation efficiency, take 1>η>0.95, pass After the parameters of the coupling conductance g _m of the coupled cavity structure with the θ _m are obtained by the electromagnetic simulation software, θ _m can be obtained by the interpolation method. 11. The high-power microwave space beam swept planar array antenna according to claim 1, wherein the relationship between the radiating element spacing d and the maximum beam pointing angle is shown in the following formula

where ρ ₀ is the maximum angle that the beam deviates from the normal direction of the antenna radiation port; the height H ₁ of the circular boss is equal to the wall thickness T of the waveguide; other structural parameters of the coupling cavity and the conductor in the helix, including H ₃ , H ₄ , L ₁ , L ₂ , L ₃ , R ₆ and R ₅ are optimized by electromagnetic simulation software. The optimization goal is that the reflection of the radiating element is close to 0 at the operating frequency, and the axial ratio is that the radiation electric field is on a plane perpendicular to the microwave transmission direction. The electric field ratio in the orthogonal direction is close to 1 in the axial direction of the helix, and requires H ₄ -H ₁ ≈ 0.75λ. 12. The high-power microwave space beam swept planar array antenna according to claim 1, wherein the mth reflection cancellation rod (L2m1) has a length of a ₂ +T, and the mth reflection cancellation rod (L2m1) The radius of r m is equal to r _m , which satisfies that the reflection caused by the reflection eliminating rod in the rectangular waveguide is equal to the reflection amplitude caused by the m-th coupling cavity and the m-th helix inner conductor. The specific value of r _m is obtained by the electromagnetic simulation software simulation calculation and comparison; The position s _m of the m-th reflection cancellation rod satisfies the phase difference of the reflected wave caused by the m-th reflection cancellation rod and the reflection phase caused by the m-th coupling cavity and the m-th helix inner conductor. The specific value of the size is determined by the electromagnetic simulation software. The simulation calculation is compared. 13. The high-power microwave space beam swept planar array antenna according to claim 1, wherein the linear array formed by the M radiating elements is connected to M stepping motors, and the inner conductor of the mth helix passes through a rectangular waveguide. The size of the length h' of (L1) is determined by the size of the stepper motor, and it is required to achieve effective connection and cooperation between the piercing part and the stepper motor; the mth stepper motor controls the axis of the mth helix inner conductor around the helix Rotation; define the angle between the direction of the radiated main beam of the linear array antenna and the normal direction of the mouth as ρ, and the spatial azimuth angle α _m difference P of the linear array antenna after the rotation of the conductor in the adjacent helix along the x-axis direction is determined by the beam direction ρ It is decided that the relationship between P and ρ is as follows

where k is the free-space wave number, and β is the propagation constant of the rectangular waveguide, which is calculated as

14. The high-power microwave space beam swept planar array antenna according to claim 1, characterized in that the nth phase shifter phase control unit (4n) and the nth are based on the rotation adjustment of the rectangular waveguide narrow-side slot bridge The first rotary joint (P22) and the second rotary joint (P32) of the phase shifter (1n) have the same outer diameter, both of which are R' ₀ , and the rotation angles of the phase shifters of the two adjacent linear arrays are different.

is a constant, that is

θ _n is the angle at which the n-th phase shifter phase control unit 4n rotates, and θ _n-1 is the angle at which the n-1th phase shifter phase control unit ( 4n-1 ) rotates. 15. The high-power microwave space beam swept planar array antenna according to claim 1, wherein the outer diameter of each bearing of the m-th helix inner conductor drive control unit (5m) is that r satisfies d/2 >r>R ₂ ; one end (5m3) of the mth helix inner conductor drive control unit (5m) is driven by the stepping motor to move h _m along the y-axis direction, thereby driving the m1th bearing (5m11) to the Nmth bearing (5m1N ) are rotated by 2h _m /r radians, and at the same time drive the spatial azimuth angle of the inner conductors of the m-th column to rotate 2h _m /r radians; in the x-axis direction, the adjacent helix inner conductor drive control unit is driven by an external stepping motor. The length difference is a constant Δh=h _m -h _m-1 , and the spatial azimuth difference of the conductors in the adjacent columns of the helix in the x-axis direction is also a constant, set as

Have

Gain maximum beam pointing

and

and

related:

where ρ is the angle between the main radiating beam and the high-power microwave space beam swept planar array antenna, that is, the normal direction of the mouth, that is, the z-axis,

is the angle between the projection of the main beam on the xoy plane and the x-axis, β is the waveguide propagation constant of the high-power microwave one-dimensional beam sweepable linear array rectangular waveguide, and k is the free-space wave number.

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