[go: up one dir, main page]

CN109302070A - Circuit topology structure of power converter and its control method - Google Patents

Circuit topology structure of power converter and its control method Download PDF

Info

Publication number
CN109302070A
CN109302070A CN201811173717.0A CN201811173717A CN109302070A CN 109302070 A CN109302070 A CN 109302070A CN 201811173717 A CN201811173717 A CN 201811173717A CN 109302070 A CN109302070 A CN 109302070A
Authority
CN
China
Prior art keywords
capacitor
dynamic compensation
compensation network
output
bridge
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
CN201811173717.0A
Other languages
Chinese (zh)
Inventor
李建科
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
PLA University of Science and Technology
Original Assignee
Individual
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Individual filed Critical Individual
Priority to CN201811173717.0A priority Critical patent/CN109302070A/en
Publication of CN109302070A publication Critical patent/CN109302070A/en
Pending legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The invention discloses a kind of power converter circuit topological structure and its control method, the circuit topology includes full-bridge inverting, primary side resonant dynamic compensation network, primary coil, secondary coil, secondary side resonant dynamic compensation network, full-bridge synchronous rectification and load.Primary side resonant dynamic compensation network of the present invention is using compensation inductance and the concatenated structure of turnable resonator capacitor, secondary side resonant dynamic compensation network is using coil and the concatenated structure of turnable resonator capacitor, in the different coil coefficients of coup, different loads size and due to temperature, under the conditions of system parameter variations caused by the factors such as device production foozle etc., the PWM duty cycle that switch can be switched by adjusting capacitor generates the adjustable equivalent tank capacitor of consecutive variations and carries out dynamic compensation to resonant network, to realize the Sofe Switch of full-bridge inverting, minimize the reactive power in system capacity transmission, and then maximize system power efficiency of transmission, in systems constant working frequency, effectively enhance the adjustment capability of system output characteristics.

Description

Power converter circuit topological structure and its control method
Technical field
The present invention relates to power electronics topological circuit more particularly to a kind of power converter circuit topological structure and its controls Method.
Background technique
Electric energy transmission near field is produced in secondary coil by converting alternating electromagnetic field by primary coil for high-frequency circuit The rectified circuit of raw high frequency induction current is converted into direct current output.In recent years, which has been widely used in smart phone Wireless charging product in, in addition this technology also has wide answer in domestic robot, industrial robot, electric car field Use prospect.
In order to improve energy transmission distance and efficiency, resonance compensation net can be increased in primary coil and secondary coil respectively Network, i.e. composition magnetic resonance.The resonance frequency of current existing resonance compensation network by inductance in compensation network or capacitor, coil from Sense or mutual inductance determine that when relative position changes between coil, mutual inductance and the coefficient of coup can be sent out between self-induction of loop and coil Raw corresponding change, in addition under different operating temperature environment, ferritic magnetic conductivity can also change in loop construction, in turn Coil electric parameter is caused to change.Further, since inductance error caused by batch production and capacitance error not can avoid yet. Therefore, in actual operation, a degree of variation can occur for resonance frequency, if switching frequency off-resonance frequency is excessive, meeting Cause the hard switching and excessive reactive power loss of high-frequency inverter, the serious problems such as power output capacity reduction；If switch frequency Rate follows resonance frequency to change, then system will occupy biggish frequency bandwidth resource under different operating conditions, and it is on the one hand domestic and International relevant criterion is defined operating frequency range, and on the other hand, wider operating frequency range will make system electric Magnetic compatible design is more complicated, and increases system cost.
Summary of the invention
The object of the present invention is to provide a kind of power converter circuit topological structure and its control methods.
Realize the technical solution of the object of the invention are as follows: a kind of power converter circuit topological structure, including input dc power Source U1, full bridge inverter, primary side resonant dynamic compensation network, primary coil 3Li1, secondary coil 3Lo1, secondary side resonant dynamic mends Repay network, full-bridge synchronous rectification circuit and load battery U2；
The input DC power U1, full bridge inverter, primary side resonant dynamic compensation network be sequentially connected, the primary side Resonant dynamic compensation network output end respectively with primary coil 3Li1Both ends connection, the secondary coil 3Lo1Both ends difference It is connect with the input terminal of secondary side resonant dynamic compensation network, the primary coil 3Li1, secondary coil 3Lo1Same Name of Ends is opposite, institute The output end for stating secondary side resonant dynamic compensation network is connect with the input terminal of full-bridge synchronous rectification circuit, full-bridge synchronous rectification circuit Output end and load battery U2Both ends connection.
Preferably, the full bridge inverter includes the first bus capacitor CBUS1, four switching tube Qi1-Qi4, described first Bus capacitor CBUS1Anode with input DC power U1Anode connection, the first bus capacitor CBUS1Cathode and input DC power supply U1Cathode connection, four switching tube Qi1-Qi4Connect into inversion H bridge, anode and the first bus of inversion H bridge Capacitor CBUS1Anode connection, the cathode of inversion H bridge and the first bus capacitor CBUS1Cathode connection.
Preferably, the primary side resonant dynamic compensation network includes the first compensation inductance Lif, the first equivalent impedance module, One series capacitance Ci1, the first shunt capacitance Cif, wherein the first compensation inductance LifOne end and full bridge inverter one A output end connection, the first compensation inductance LifThe other end connect with one end of the first equivalent impedance module, described first The other end of equivalent impedance module and the first series capacitance Ci1One end connection, the first shunt capacitance CifOne end and institute State the other end connection of the first equivalent impedance module, the first shunt capacitance CifThe other end and full bridge inverter it is another A output end connection, the first shunt capacitance CifThe other end and the first series capacitance Ci1The other end it is humorous as primary side Two output ends of vibrational state compensation network；
The first equivalent impedance module specifically: the first compensating electric capacity being connected in parallel and the first compensating switch, or First compensating electric capacity is connected in parallel with the first compensating switch, then connects with another compensating electric capacity, or to be cascaded One compensating electric capacity and the first compensating switch or the first compensating electric capacity are connected with the first compensating switch, then whole and another compensation Capacitor is in parallel.
Preferably, the implementation of first compensating switch is two or more MOSFET or IGBT pair in series To switch.
Preferably, the secondary side resonant dynamic compensation network is at least one compensating switch S, at least two capacitors form Tunable capacitor network with non-zero offset capacitance, i.e., all compensating switches disconnect or have when closing the group of certain capacitance Close network.
Preferably, the secondary side resonant dynamic compensation network includes the second series capacitance Co1, the second compensating electric capacity Cov1, Two compensating switch So1, wherein the second series capacitance Co1One end and the second compensating switch So1One end, secondary coil 3Lo1's Same Name of Ends connection, the second compensating switch So1The other end and the second compensating electric capacity Cov1One end connection, it is described second compensation Capacitor Cov1The other end and the second series capacitance Co1The other end be connected to one of secondary side resonant dynamic compensation network output End, the secondary coil 3Lo1Another output of the non-same polarity as secondary side resonant dynamic compensation network.
Preferably, the second compensating switch So1Implementation be single MOSFET or IGBT single-way switch, or For two or more MOSFET or IGBT two-way switch in series.
Preferably, full-bridge synchronous rectification circuit includes the second bus capacitor CBUS2And four switching tube Qo1-Qo4, four are opened Close pipe Qo1-Qo4Inversion H bridge is connected into, two input terminals of inversion H bridge are defeated with two of secondary side resonant dynamic compensation network respectively Outlet connection, anode and the second bus capacitor C of the inversion H bridgeBUS2Anode connection, the cathode of the inversion H bridge and the Two bus capacitor CBUS2Cathode connection, the second bus capacitor CBUS2Anode, cathode simultaneously with load battery U2It is positive and negative Pole connection.
Since full-bridge synchronous rectification realizes that structure is identical with full-bridge inverting, primary side resonant dynamic compensation network and secondary side resonance Dynamic compensation can actively dynamic adjust, therefore the reverse biography of energy may be implemented in circuit topological structure of the present invention It is defeated.In forward energy flowing, primary coil is alternating electromagnetic field transmitting coil, and secondary coil is receiving coil.In reverse energy When amount flowing, primary coil is converted to receiving coil, and secondary coil is alternating electromagnetic field transmitting coil, inverse in full bridge inverter Become the operating mode that H bridge is converted to rectification H bridge, similarly, in full-bridge synchronous rectification circuit rectifies the work that H bridge is converted to inversion H bridge Operation mode.
The present invention also provides a kind of control method of power converter circuit topological structure, specific steps are as follows:
Detect power converter circuit topological structure, that is, nearly electric field Transmission system input voltage U1, full bridge inverter it is defeated Voltage U outAB, secondary side resonant dynamic compensation network output voltage UCDAnd system output voltage U2；Detection system input current I1, full bridge inverter output electric current IAB, primary coil electric current Ii1, the output electric current I of secondary side resonant dynamic compensation networkCD、 And system output current I2；
Four control loop controls are carried out according to acquisition data, four control loops are inverter current control loop, primary side Resonant dynamic compensation network control loop, secondary side resonant dynamic compensation network control loop and output control circuit；
The inverter current control loop specifically: the output electric current I for the full bridge inverter that will testABWith current reference Value compares, and obtains the phase shifting control angle θ of full bridge inverter by pid algorithm according to the two differenceAB, inversion modulator will shifting Phase control angular transition is four switch Q that corresponding four pwm signals control full bridge inverter respectivelyi1-4；
The primary side resonant dynamic compensation network control loop specifically: compare the output electricity of the full bridge inverter of measurement The phase of stream and output voltage, obtains phase difference ψZ, the phase difference ψZWith the phase difference reference value ψ of settingrefCompare, is obtained Difference obtain the resonance frequency omega of primary side resonant dynamic compensation network by pid algorithmr0, primary side resonance frequency is converted to pair The pwm signal answered controls the first compensating switch S of the primary side resonant dynamic compensation networki1；
Pair side resonant dynamic compensation network control loop specifically: compare the primary coil electric current I of measurementi1With secondary side The output electric current I of resonant dynamic compensation networkCDPhase, obtain phase difference Фdiff, the phase difference ФdiffWith the phase of setting Potential difference reference value ФrefCompare, the difference obtained obtains the resonance frequency of secondary side resonant dynamic compensation network by pid algorithm ωr2, primary side resonance frequency be converted into corresponding pwm signal control the second compensation of the secondary side resonant dynamic compensation network and open Close So1；
The output control circuit specifically: compare output voltage or output electric current or output power and the setting of measurement Output voltage reference value or output current reference value or output power reference value, the difference obtained calculate institute by pid algorithm State the output current reference value I of full bridge inverterABref。
Central Plains pair of the present invention side associated signal parameter (such as system output current, system output voltage, system output work Rate, the output electric current of secondary side resonant dynamic compensation network, pwm control signal of the second compensating switch etc.) pass through no line number It is realized according to transmission mode, such as bluetooth, WIFI.
Compared with prior art, the present invention its remarkable result are as follows: 1) PWM that the present invention passes through the former secondary side compensating switch of change Duty ratio realizes that continuous dynamic adjusts the equivalent impedance of former secondary side resonance compensation network, simultaneously with reactive power loss in reduction system Realize Sofe Switch, therefore the present invention can realize that efficient energy is transmitted under different operating conditions；2) the former secondary side harmonic motion of the present invention State compensation network can effectively offset the influence of device error bring, so that near field electric energy transmission system be made to have under complex working condition High-performance and high reliability reduce Primary Component and manufacture and design difficulty and cost, and then have practical application value；3) of the invention Can be realized can work under different complex working conditions in a certain constant frequency；4) circuit topology full-bridge synchronous rectification of the present invention with Full-bridge inverting realizes that structure is identical, and primary side resonant dynamic compensation network and secondary side resonant dynamic compensation network can actively dynamic be adjusted It is whole, be not required to increase additional circuit structure, the transmitted in both directions of energy can be realized, can scale access smart grid, more adduction Reason effectively utilizes power grid and carries out charge and discharge；5) the secondary side resonant dynamic compensation network of original of the invention is unsymmetric structure, secondary side In a mobile system as receiving end installation, it since secondary side resonant dynamic compensation network power device is few, is compensated without large volume Inductance, therefore receiving end volume can substantially reduce, and reduce weight, it is portable and facilitate installation.
The present invention will be further described for explanation with reference to the accompanying drawing.
Detailed description of the invention
Fig. 1 is circuit topological structure of the present invention.
Fig. 2 is primary side resonant dynamic compensation network equivalent impedance module diagram of the present invention.
Fig. 3 is secondary side resonant dynamic compensation network schematic diagram of the present invention.
Fig. 4 is the first compensating switch of the present invention and the second compensating switch schematic diagram.
Fig. 5 is system voltage gain of the present invention and full-bridge inverting phase difference output with normalization resonance frequency variation Characteristic curve schematic diagram.
Fig. 6 is that system of the present invention voltage gain when normalizing resonance frequency and being 1 changes with the coil coefficient of coup Characteristic curve schematic diagram.
Fig. 7 is that system of the present invention normalizes resonance frequency when inverter output voltage current and phase difference is constant with coil The characteristic curve schematic diagram of coefficient of coup variation.
Fig. 8 is the control method block diagram of circuit topological structure of the present invention.
Fig. 9 is the circuit diagram that compensating switch is two-way switch in circuit topological structure of the present invention.
Figure 10 is the former secondary coil current waveform schematic diagram under secondary side resonant dynamic compensation network effect.
Figure 11 is the constant voltage output waveform realized in the different coefficients of coup by primary side resonant dynamic compensation network Figure.
Specific embodiment
In order to clearly describe thought of the invention, technical solution and advantage, specific embodiment passes through embodiment Show with attached drawing.It is apparent that described embodiment is a part of the embodiments of the present invention, instead of all the embodiments. Based on the embodiments of the present invention, those of ordinary skill in the art under the premise of not making the creative labor it is obtained it is all its His embodiment, shall fall within the protection scope of the present invention.
A kind of power converter circuit topological structure, including input DC power U1, full bridge inverter 1, primary side resonance Dynamic compensation 2, primary coil 3Li1, secondary coil 3Lo1, secondary side resonant dynamic compensation network 4, full-bridge synchronous rectification circuit 5 and load battery U2；
The input DC power U1, full bridge inverter 1, primary side resonant dynamic compensation network 2 be sequentially connected, the original 2 output end of side resonant dynamic compensation network respectively with primary coil 3Li1Both ends connection, the secondary coil 3Lo1Both ends point It is not connect with the input terminal of secondary side resonant dynamic compensation network 4, the primary coil 3Li1, secondary coil 3Lo1Same Name of Ends is opposite, The output end of pair side resonant dynamic compensation network 4 is connect with the input terminal of full-bridge synchronous rectification circuit 5, full-bridge synchronous rectification The output end and load battery U of circuit 52Both ends connection.
In further embodiment, the full bridge inverter includes the first bus capacitor CBUS1, four switching tube Qi1- Qi4, the first bus capacitor CBUS1Anode with input DC power U1Anode connection, the first bus capacitor CBUS1's Cathode and input DC power U1Cathode connection, four switching tube Qi1-Qi4Connect into inversion H bridge, the anode of inversion H bridge With the first bus capacitor CBUS1Anode connection, the cathode of inversion H bridge and the first bus capacitor CBUS1Cathode connection.
In further embodiment, the primary side resonant dynamic compensation network 2 includes the first compensation inductance Lif, it is first equivalent Impedance module, the first series capacitance Ci1, the first shunt capacitance Cif, wherein the first compensation inductance LifOne end and full-bridge it is inverse One output end on power transformation road 1 connects, the first compensation inductance LifThe other end and the first equivalent impedance module one end connect It connects, the other end of the first equivalent impedance module and the first series capacitance Ci1One end connection, the first shunt capacitance Cif One end connect with the other end of the first equivalent impedance module, the first shunt capacitance CifThe other end and full-bridge inverting The another output of circuit 1 connects, the first shunt capacitance CifThe other end and the first series capacitance Ci1The other end Two output ends as primary side resonant dynamic compensation network 2；
The first equivalent impedance module specifically: the first compensating electric capacity being connected in parallel and the first compensating switch, or First compensating electric capacity is connected in parallel with the first compensating switch, then connects with another compensating electric capacity, or to be cascaded One compensating electric capacity and the first compensating switch or the first compensating electric capacity are connected with the first compensating switch, then whole and another compensation Capacitor is in parallel.Its specific implementation example is as shown in Figure 2.
Preferably, the first compensating switch Si1Implementation be two or more MOSFET or IGBT it is in series Two-way switch, as shown in Figure 4.
In further embodiment, the pair side resonant dynamic compensation network is at least one compensating switch S, at least two The tunable capacitor network with non-zero offset capacitance of capacitor composition, i.e., all compensating switches disconnect or have when closing certain The combinational network of capacitance.In certain embodiments, the specific structure is shown in FIG. 3 for secondary side resonant dynamic compensation network.Secondary side Resonant dynamic compensation network has to comprising Fig. 3 a and Fig. 3 b one of both, and Fig. 3 a and Fig. 3 b are two indispensable units, optionally its One.Concrete implementation mode is Fig. 3 (a-f) six kinds of situations, wherein Fig. 3 c, contain Fig. 3 a unit in 3d, 3e, wherein in Fig. 3 f It include Fig. 3 b unit.
By taking Fig. 3 a as an example, the pair side resonant dynamic compensation network includes the second series capacitance Co1, the second compensating electric capacity Cov1, the second compensating switch So1, wherein the second series capacitance Co1One end and the second compensating switch So1One end, secondary sideline Enclose 3Lo1Same Name of Ends connection, the second compensating switch So1The other end and the second compensating electric capacity Cov1One end connection, it is described Second compensating electric capacity Cov1The other end and the second series capacitance Co1The other end be connected to secondary side resonant dynamic compensation network One output end, the secondary coil 3Lo1Another output of the non-same polarity as secondary side resonant dynamic compensation network.
Preferably, the second compensating switch So1Implementation be single MOSFET or IGBT single-way switch, or For two or more MOSFET or IGBT two-way switch in series.
In further embodiment, full-bridge synchronous rectification circuit includes the second bus capacitor CBUS2And four switching tubes Qo1-Qo4, four switching tube Qo1-Qo4Inversion H bridge is connected into, two input terminals of inversion H bridge are compensated with secondary side resonant dynamic respectively Two output ends of network connect, anode and the second bus capacitor C of the inversion H bridgeBUS2Anode connection, the inversion H The cathode of bridge and the second bus capacitor CBUS2Cathode connection, the second bus capacitor CBUS2Anode, cathode simultaneously with load Battery U2Positive and negative anodes connection.
As shown in Figure 1, in the primary side resonant dynamic compensation network the first equivalent impedance module the first compensating switch Si1 Under a certain the duty when control of switching frequency PWM, the first compensating electric capacity CisIt is changed into equivalent capacity Ciseq, described first mends Repay the impedance X of inductance and the first equivalent impedance moduleiAre as follows:
Wherein LifeqFor the equivalent compensation inductance value of the first compensation inductance and the first equivalent impedance module, primary side compensation Resonance frequency omegar0Are as follows:
The primary coil Li1The first series capacitance of capacitor C connected in paralleli1, the first shunt capacitance CifResonance frequency omegar1 Are as follows:
The equivalent impedance X of pair side resonant dynamic compensation networkoAre as follows:
Wherein CoveqFor the equivalent capacitance that second compensating electric capacity obtains under the second compensating switch PWM control, secondary side Resonance frequency are as follows:
As primary coil electric current Ii1With secondary coil electric current ICDPhase difference ФdiffWhen being 90 degree, secondary side resonant dynamic is mended The reactive power repaid in network is minimum, and former secondary coil energy transmission efficiency is maximum, at this time secondary side resonance frequency omegar2With system work Working frequency ωsIt is identical.To reduce the reactive power in primary coil, the primary coil resonance frequency omegar1It works frequently with system Rate ωsIt designs identical, it may be assumed that
ωs=ωr1=ωr2
Define normalized frequency ωNResonance frequency omega is compensated for primary sider0With system switching working frequency ωsRatio, by It works in system in constant switching frequency ωs, normalized frequency ωNVariation show corresponding resonance frequency omegar0Variation:
System voltage gain GVExpression formula is as follows:
Wherein θ is full-bridge inverting phase shifting control angle, and M is the mutual inductance of former secondary coil, RACFor output equivalent load, RL is Output load impedance,
The full-bridge inverting output impedance ZinvExpression formula are as follows:
Full bridge inverter fundamental voltage output of voltage and output current and phase difference are as follows:
Full bridge inverter output voltage and output current and phase difference are as follows:
The ω in different loads RL (shown in such as Fig. 5 (a)) and coefficient of coup k (shown in such as Fig. 5 (b))r0It is adjustable System voltage gain GV；The ω in different loads RL (shown in such as Fig. 5 (c)) and coefficient of coup k (shown in such as Fig. 5 (d))r0It can To adjust full bridge inverter fundamental voltage output of voltage and output current and phase difference ψi, i.e., under constant operation frequency, by adjusting Primary side compensates resonance frequency omegar0Realize control full-bridge inverting output voltage current and phase difference ψiWith system voltage gain GVMesh 's.
When primary side compensates resonance frequency omegar0With system operating frequency ωsWhen identical, system voltage gain GV0Are as follows:
I.e. system voltage gain is not influenced by payload size variation, linear with former secondary coil coefficient of coup k, such as Shown in Fig. 6.
When setting full bridge inverter output voltage and output current and phase difference ψZWhen for fixed value, normalized frequency ωN? Characteristic curve in the case of different loads and the different coefficients of coup is as shown in fig. 7, i.e. in different loads size and different coupled systemes Under number operating condition, resonance frequency omega is compensated by adjusting primary sider0Can according to reference value control full bridge inverter output voltage with Export current and phase difference ψZ。
Since full-bridge synchronous rectification realizes that structure is identical with full-bridge inverting, primary side resonant dynamic compensation network and secondary side resonance Dynamic compensation can actively dynamic adjust, therefore the reverse biography of energy may be implemented in circuit topological structure of the present invention It is defeated.In forward energy flowing, primary coil is alternating electromagnetic field transmitting coil, and secondary coil is receiving coil.In reverse energy When amount flowing, primary coil is converted to receiving coil, and secondary coil is alternating electromagnetic field transmitting coil, inverse in full bridge inverter Become the operating mode that H bridge is converted to rectification H bridge, similarly, in full-bridge synchronous rectification circuit rectifies the work that H bridge is converted to inversion H bridge Operation mode.
The control strategy of near field electric energy transmission system of the present invention are as follows: as shown in figure 8, detecting electric power by voltage sampling circuit Converter circuit topological structure input voltage U1, full bridge inverter output voltage UAB, secondary side resonant dynamic compensation network Output voltage UCDAnd system output voltage U2；Pass through current sampling circuit detection system input current I1, full bridge inverter Export electric current IAB, primary coil electric current Ii1, the output electric current I of secondary side resonant dynamic compensation networkCDAnd system output current I2。 The control method includes four control loops, inverter current control loop, primary side resonant dynamic compensation network control loop, pair Side resonant dynamic compensation network control loop and output control circuit.The inverter current control loop is inverse by the full-bridge of measurement Become output electric current compared with current reference value, difference obtains the phase shifting control angle θ of full bridge inverter by pid algorithmAB, Phase shifting control angle is converted to four switches that corresponding four pwm signals control full bridge inverter respectively by inversion modulator (Qi1-4).The primary side resonant dynamic compensation network control loop by comparing measurement full bridge inverter output electric current and The phase of output voltage obtains phase difference ψZ, the phase difference ψZWith the phase difference reference value ψ of settingrefCompare, the difference obtained Value obtains the resonance frequency omega of primary side resonant dynamic compensation network by pid algorithmr0, 1 module of resonant modulation device is by primary side resonance Frequency conversion is the first compensating switch S that corresponding pwm signal controls the primary side resonant dynamic compensation networki1.The pair side Resonant dynamic compensation network control loop compares the primary coil electric current I of measurement by 2 module of phase-detectioni1With secondary side harmonic motion The output electric current I of state compensation networkCDPhase, obtain phase difference Фdiff, the phase difference ФdiffJoin with the phase difference of setting Examine value ФrefCompare, the difference obtained obtains the resonance frequency omega of secondary side resonant dynamic compensation network by pid algorithmr2, humorous Primary side resonance frequency is converted to corresponding pwm signal and controls the secondary side resonant dynamic compensation network by vibration 2 module of modulator Second compensating switch So1, the phase difference reference value ФrefIt is 90 degree, works as ФdiffWhen being 90 degree, secondary side resonant dynamic compensates net Reactive power in network is minimum, and former secondary coil energy transmission efficiency is maximum.The output control circuit compares the output of measurement Voltage or the output voltage reference value or output current reference value or output power reference of output electric current or output power and setting Value, the difference obtained calculate the output current reference value I of the full bridge inverter by pid algorithmABref, this reference value biography Pass the input terminal of inverter current control loop.
Control strategy Central Plains pair side associated signal parameter (such as system output current, system output voltage, system are defeated Power, the output electric current of secondary side resonant dynamic compensation network, pwm control signal of the second compensating switch etc. out) pass through nothing Line data transfer mode is realized, such as bluetooth, WIFI.
Embodiment 1
A kind of power converter circuit topological structure, which is characterized in that including input DC power U1, full bridge inverter 1, primary side resonant dynamic compensation network 2, primary coil 3Li1, secondary coil 3Lo1, secondary side resonant dynamic compensation network 4, full-bridge it is same Walk rectification circuit 5 and load battery U2；
The input DC power U1, full bridge inverter 1, primary side resonant dynamic compensation network 2 be sequentially connected, the original 2 output end of side resonant dynamic compensation network respectively with primary coil 3Li1Both ends connection, the secondary coil 3Lo1Both ends point It is not connect with the input terminal of secondary side resonant dynamic compensation network 4, the primary coil 3Li1, secondary coil 3Lo1Same Name of Ends is opposite, The output end of pair side resonant dynamic compensation network 4 is connect with the input terminal of full-bridge synchronous rectification circuit 5, full-bridge synchronous rectification The output end and load battery U of circuit 52Both ends connection.
The primary side resonant dynamic compensation network 2 includes the first compensation inductance Lif, the first equivalent impedance module, first series connection Capacitor Ci1, the first shunt capacitance Cif, wherein the first compensation inductance LifOne end and one of full bridge inverter 1 output End connection, the first compensation inductance LifThe other end connect with one end of the first equivalent impedance module, the first equivalent resistance The other end of anti-module and the first series capacitance Ci1One end connection, the first shunt capacitance CifOne end and described first The other end of equivalent impedance module connects, the first shunt capacitance CifThe other end and full bridge inverter 1 another is defeated Outlet connection, the first shunt capacitance CifThe other end and the first series capacitance Ci1The other end as primary side harmonic motion Two output ends of state compensation network 2；
The first compensating switch of the first equivalent impedance module and secondary side resonant dynamic are mended in primary side resonant dynamic compensation network The two-way switch implementation that the second compensating switch of network is made of two MOSFET is repaid, as shown in Figure 9.
The secondary coil design inductance is Lo1 0, in practical situations, due between coil relative position change, Inductance error caused by different operating temperature environment, batch production etc. causes secondary coil inductance offset design value, when secondary sideline It encloses actual inductance and increases Lo1 2When, as shown in Figure 10, primary coil electric current Ii1With the output electric current of secondary side resonant dynamic compensation network ICDPhase difference Ф2Greater than 90 degree；When secondary coil actual inductance reduces Lo1 1When, as shown in Figure 10, primary coil electric current Ii1With The output electric current I of secondary side resonant dynamic compensation networkCDPhase difference Ф1Less than 90 degree.Both the above situation can pass through control The duty ratio of shown second compensating switch is identical as system operating frequency to adjust secondary side resonance frequency, compensates primary coil electric current Ii1With the output electric current I of secondary side resonant dynamic compensation networkCDPhase difference to 90 degree, realize the secondary side resonant network of minimum Reactive power.
It, can be by adjusting normalization frequency by Fig. 5 (b) it is found that system voltage gain changes as the coefficient of coup is different Rate ωNI.e. primary side compensates resonance frequency omegar0Control system voltage gain, as shown in figure 11, when the coefficient of coup is 0.15, system Output voltage is 50V；When relative position changes between former secondary coil, when the coefficient of coup becomes 0.2, system output voltage is mentioned A height of 67V compensates resonance by adjusting the duty ratio of the first compensating switch to control the primary side of primary side resonant dynamic compensation network Frequencies omegar0, system output voltage is stablized in 50V, therefore system voltage gain can be controlled by primary side resonant dynamic compensation network.

Claims (9)

1.一种电力变换器电路拓扑结构，其特征在于，包括输入直流电源U1、全桥逆变电路(1)、原边谐振动态补偿网络(2)、原边线圈3Li1、副边线圈3Lo1、副边谐振动态补偿网络(4)、全桥同步整流电路(5)及负载电池U2；1. A circuit topology structure of a power converter, characterized in that it comprises an input DC power supply U 1 , a full-bridge inverter circuit (1), a primary resonance dynamic compensation network (2), a primary coil 3L i1 , a secondary coil 3L o1 , secondary resonance dynamic compensation network (4), full-bridge synchronous rectification circuit (5) and load battery U 2 ; 所述输入直流电源U1、全桥逆变电路(1)、原边谐振动态补偿网络(2)依次连接，所述原边谐振动态补偿网络(2)输出端分别与原边线圈3Li1的两端连接，所述副边线圈3Lo1的两端分别与副边谐振动态补偿网络(4)的输入端连接，所述原边线圈3Li1、副边线圈3Lo1同名端相对，所述副边谐振动态补偿网络(4)的输出端与全桥同步整流电路(5)的输入端连接，全桥同步整流电路(5)的输出端与负载电池U2的两端连接。The input DC power supply U 1 , the full-bridge inverter circuit ( 1 ), and the primary resonance dynamic compensation network ( 2 ) are connected in sequence, and the output ends of the primary resonance dynamic compensation network ( 2 ) are respectively connected to the primary side coil 3L i1 . The two ends are connected, the two ends of the secondary coil 3L o1 are respectively connected with the input end of the secondary resonance dynamic compensation network (4), the primary coil 3L i1 and the secondary coil 3L o1 are opposite to the same names, and the secondary The output end of the side resonance dynamic compensation network (4) is connected with the input end of the full-bridge synchronous rectification circuit (5), and the output end of the full-bridge synchronous rectification circuit (5) is connected with both ends of the load battery U2. 2.根据权利要求1所述的电力变换器电路拓扑结构，其特征在于，所述全桥逆变电路包括第一母线电容CBUS1、四个开关管Qi1-Qi4，所述第一母线电容CBUS1的正极与输入直流电源U1的正极连接，所述第一母线电容CBUS1的负极与输入直流电源U1的负极连接，所述四个开关管Qi1-Qi4连接成逆变H桥，逆变H桥的正极与第一母线电容CBUS1的正极连接，逆变H桥的负极与第一母线电容CBUS1的负极连接。2 . The circuit topology of the power converter according to claim 1 , wherein the full-bridge inverter circuit comprises a first bus capacitor C BUS1 , four switch tubes Q i1 -Q i4 , and the first bus The positive pole of the capacitor C BUS1 is connected to the positive pole of the input DC power supply U1, the negative pole of the first bus capacitor C BUS1 is connected to the negative pole of the input DC power supply U1, and the four switch tubes Q i1 -Q i4 are connected to form an inverter In the H bridge, the positive electrode of the inverter H bridge is connected to the positive electrode of the first bus capacitor C BUS1 , and the negative electrode of the inverter H bridge is connected to the negative electrode of the first bus capacitor C BUS1 . 3.根据权利要求1所述的电力变换器电路拓扑结构，其特征在于，所述原边谐振动态补偿网络(2)包括第一补偿电感Lif、第一等效阻抗模块、第一串联电容Ci1、第一并联电容Cif，其中，所述第一补偿电感Lif的一端与全桥逆变电路(1)的一个输出端连接，所述第一补偿电感Lif的另一端与第一等效阻抗模块的一端连接，所述第一等效阻抗模块的另一端与第一串联电容Ci1的一端连接，所述第一并联电容Cif的一端与所述第一等效阻抗模块的另一端连接，所述第一并联电容Cif的另一端与全桥逆变电路(1)的另一个输出端连接，所述第一并联电容Cif的另一端以及第一串联电容Ci1的另一端作为原边谐振动态补偿网络(2)的两个输出端；3. The circuit topology of the power converter according to claim 1, wherein the primary resonance dynamic compensation network (2) comprises a first compensation inductance L if , a first equivalent impedance module, a first series capacitor C i1 , a first parallel capacitor C if , wherein one end of the first compensation inductance L if is connected to one output end of the full-bridge inverter circuit (1), and the other end of the first compensation inductance L if is connected to the One end of an equivalent impedance module is connected, the other end of the first equivalent impedance module is connected to one end of the first series capacitor C i1 , and one end of the first parallel capacitor C if is connected to the first equivalent impedance module The other end of the first parallel capacitor C if is connected to the other output end of the full-bridge inverter circuit (1), the other end of the first parallel capacitor C if and the first series capacitor C i1 The other end is used as the two output ends of the primary resonance dynamic compensation network (2); 所述第一等效阻抗模块具体为：并联在一起的第一补偿电容与第一补偿开关，或第一补偿电容与第一补偿开关并联在一起，再与另一个补偿电容串联，或串联在一起的第一补偿电容与第一补偿开关，或第一补偿电容与第一补偿开关串联，再整体与另一个补偿电容并联。The first equivalent impedance module is specifically: the first compensation capacitor and the first compensation switch connected in parallel, or the first compensation capacitor and the first compensation switch are connected in parallel, and then connected in series with another compensation capacitor, or connected in series. The first compensation capacitor and the first compensation switch together, or the first compensation capacitor and the first compensation switch are connected in series, and then the whole is connected in parallel with another compensation capacitor. 4.根据权利要求3所述的电力变换器电路拓扑结构，其特征在于，所述第一补偿开关的实现方式为两个或多个MOSFET或IGBT串联构成的双向开关。4 . The circuit topology of the power converter according to claim 3 , wherein the first compensation switch is implemented as a bidirectional switch composed of two or more MOSFETs or IGBTs in series. 5 . 5.根据权利要求1所述的电力变换器电路拓扑结构，其特征在于，所述副边谐振动态补偿网络为至少一个补偿开关S、至少两个电容组成的具有非零偏置电容值的可调电容网络，即所有补偿开关断开或关闭时均有一定电容值的组合网络。5 . The circuit topology of the power converter according to claim 1 , wherein the secondary resonance dynamic compensation network is composed of at least one compensation switch S and at least two capacitors with a non-zero bias capacitance value. 6 . Adjustable capacitance network, that is, a combined network with a certain capacitance value when all compensation switches are disconnected or closed. 6.根据权利要求1或5任一所述的电力变换器电路拓扑结构，其特征在于，所述副边谐振动态补偿网络包括第二串联电容Co1、第二补偿电容Cov1、第二补偿开关So1，其中，所述第二串联电容Co1一端与第二补偿开关So1的一端、副边线圈3Lo1的同名端连接，所述第二补偿开关So1的另一端与第二补偿电容Cov1的一端连接，所述第二补偿电容Cov1的另一端与第二串联电容Co1的另一端连接作为副边谐振动态补偿网络的一个输出端，所述副边线圈3Lo1的非同名端作为副边谐振动态补偿网络的另一个输出端。6 . The power converter circuit topology according to claim 1 , wherein the secondary resonance dynamic compensation network comprises a second series capacitor C o1 , a second compensation capacitor C ov1 , a second compensation capacitor C o1 , and a second compensation capacitor C o1 . switch S o1 , wherein one end of the second series capacitor C o1 is connected to one end of the second compensation switch S o1 and the same name end of the secondary coil 3L o1 , and the other end of the second compensation switch S o1 is connected to the second compensation switch S o1 One end of the capacitor C ov1 is connected, the other end of the second compensation capacitor C ov1 is connected to the other end of the second series capacitor C o1 as an output end of the secondary resonance dynamic compensation network, and the non-current of the secondary coil 3L o1 is connected. The same name terminal is used as another output terminal of the secondary resonance dynamic compensation network. 7.根据权利要求6所述的电力变换器电路拓扑结构，其特征在于，所述第二补偿开关So1的实现方式为单个MOSFET或IGBT的单向开关，或者为两个或多个MOSFET或IGBT串联构成的双向开关。7 . The circuit topology of the power converter according to claim 6 , wherein the implementation of the second compensation switch S o1 is a unidirectional switch of a single MOSFET or IGBT, or two or more MOSFETs or A bidirectional switch composed of IGBTs connected in series. 8.根据权利要求1所述的电力变换器电路拓扑结构，其特征在于，全桥同步整流电路(5)包括第二母线电容CBUS2以及四个开关管Qo1-Qo4，四个开关管Qo1-Qo4连接成逆变H桥，逆变H桥的两个输入端分别与副边谐振动态补偿网络的两个输出端连接，所述逆变H桥的正极与第二母线电容CBUS2的正极连接，所述逆变H桥的负极与第二母线电容CBUS2的负极连接，所述第二母线电容CBUS2的正极、负极同时与负载电池U2的正负极连接。8 . The circuit topology of the power converter according to claim 1 , wherein the full-bridge synchronous rectifier circuit ( 5 ) comprises a second bus capacitor C BUS2 and four switch tubes Q o1 -Q o4 , the four switch tubes Q o1 -Q o4 are connected to form an inverter H bridge, the two input terminals of the inverter H bridge are respectively connected to the two output terminals of the secondary resonance dynamic compensation network, and the positive pole of the inverter H bridge is connected to the second bus capacitor C The positive pole of BUS2 is connected, the negative pole of the inverter H-bridge is connected to the negative pole of the second bus capacitor C BUS2 , and the positive pole and the negative pole of the second bus capacitor C BUS2 are connected to the positive and negative poles of the load battery U 2 at the same time. 9.一种如权利要求1所述的电力变换器电路拓扑结构的控制方法，其特征在于，检测电力变换器电路拓扑结构输入电压U1、全桥逆变电路的输出电压UAB、副边谐振动态补偿网络的输出电压UCD、及系统输出电压U2；检测电力变换器电路拓扑结构输入电流I1、全桥逆变电路的输出电流IAB、原边线圈电流Ii1，副边谐振动态补偿网络的输出电流ICD、及系统输出电流I2；9 . A method for controlling the topology of a power converter circuit according to claim 1 , wherein the input voltage U 1 of the topology structure of the power converter circuit, the output voltage U AB of the full-bridge inverter circuit, and the secondary side are detected. 10 . The output voltage U CD of the resonance dynamic compensation network and the system output voltage U 2 ; the input current I 1 of the power converter circuit topology, the output current I AB of the full-bridge inverter circuit, the primary coil current I i1 , and the secondary side resonance are detected. the output current I CD of the dynamic compensation network, and the system output current I 2 ; 根据采集数据进行四个控制回路控制，四个控制回路为逆变电流控制回路、原边谐振动态补偿网络控制回路、副边谐振动态补偿网络控制回路及输出控制回路；According to the collected data, four control loops are controlled, and the four control loops are the inverter current control loop, the primary resonance dynamic compensation network control loop, the secondary resonance dynamic compensation network control loop and the output control loop; 所述逆变电流控制回路具体为：将检测的全桥逆变电路的输出电流IAB与电流参考值比较，根据二者差值经过PID算法得出全桥逆变电路的移相控制角度θAB，逆变调制器将移相控制角度转换为相应的四个PWM信号分别控制全桥逆变电路的四个开关Qi1-4；The inverter current control loop is specifically as follows: comparing the detected output current I AB of the full-bridge inverter circuit with the current reference value, and obtaining the phase-shift control angle θ of the full-bridge inverter circuit through a PID algorithm according to the difference between the two. AB , the inverter modulator converts the phase-shift control angle into corresponding four PWM signals to respectively control the four switches Q i1-4 of the full-bridge inverter circuit; 所述原边谐振动态补偿网络控制回路具体为：比较测量的全桥逆变电路的输出电流和输出电压的相位，得出相位差ψZ，所述相位差ψZ与设定的相位差参考值ψref比较，所得出的差值经过PID算法得出原边谐振动态补偿网络的谐振频率ωr0，将原边谐振频率转换为对应的PWM信号控制所述原边谐振动态补偿网络的第一补偿开关Si1；The primary side resonance dynamic compensation network control loop is specifically: comparing the measured phase of the output current and the output voltage of the full-bridge inverter circuit to obtain the phase difference ψ Z , the phase difference ψ Z and the set phase difference reference The value of ψ ref is compared, and the difference obtained is obtained through the PID algorithm to obtain the resonant frequency ω r0 of the primary side resonance dynamic compensation network, and the primary side resonance frequency is converted into a corresponding PWM signal to control the first side of the primary side resonance dynamic compensation network. Compensation switch S i1 ; 所述副边谐振动态补偿网络控制回路具体为：比较测量的原边线圈电流Ii1和副边谐振动态补偿网络的输出电流ICD的相位，得出相位差Фdiff，所述相位差Фdiff与设定的相位差参考值Фref比较，所得出的差值经过PID算法得出副边谐振动态补偿网络的谐振频率ωr2，将原边谐振频率转换为对应的PWM信号控制所述副边谐振动态补偿网络的第二补偿开关So1；The control loop of the secondary resonance dynamic compensation network is specifically: comparing the phase of the measured primary coil current I i1 and the output current I CD of the secondary resonance dynamic compensation network to obtain a phase difference Ф diff , the phase difference Ф diff Compared with the set phase difference reference value Ф ref , the difference obtained is obtained through the PID algorithm to obtain the resonance frequency ω r2 of the secondary side resonance dynamic compensation network, and the primary side resonance frequency is converted into a corresponding PWM signal to control the secondary side. a second compensation switch S o1 of the resonance dynamic compensation network; 所述输出控制回路具体为：比较测量的输出电压或输出电流或输出功率和设定的输出电压参考值或输出电流参考值或输出功率参考值，得出的差值经过PID算法计算出所述全桥逆变电路的输出电流参考值IABref。The output control loop is specifically: comparing the measured output voltage or output current or output power with the set output voltage reference value or output current reference value or output power reference value, and the difference obtained is calculated by PID algorithm. The output current reference value I ABref of the full-bridge inverter circuit.
CN201811173717.0A 2018-10-09 2018-10-09 Circuit topology structure of power converter and its control method Pending CN109302070A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201811173717.0A CN109302070A (en) 2018-10-09 2018-10-09 Circuit topology structure of power converter and its control method

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201811173717.0A CN109302070A (en) 2018-10-09 2018-10-09 Circuit topology structure of power converter and its control method

Publications (1)

Publication Number Publication Date
CN109302070A true CN109302070A (en) 2019-02-01

Family

ID=65161882

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201811173717.0A Pending CN109302070A (en) 2018-10-09 2018-10-09 Circuit topology structure of power converter and its control method

Country Status (1)

Country Link
CN (1) CN109302070A (en)

Cited By (28)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109962625A (en) * 2019-05-10 2019-07-02 安徽水利水电职业技术学院 A resonant high-gain DC-DC device based on a loosely coupled transformer
CN110297120A (en) * 2019-07-16 2019-10-01 浙江万安亿创电子科技有限公司 The primary coil current measurement circuit of magnetic inductive radio energy transmission system
CN110554236A (en) * 2019-09-30 2019-12-10 福州大学 Frequency online detection method for constant-voltage or constant-current output of wireless power transmission
CN110649821A (en) * 2019-10-24 2020-01-03 湖南大学 Bidirectional SCC type LLC resonant converter, circuit and control method thereof
CN110949152A (en) * 2019-12-20 2020-04-03 中兴新能源汽车有限责任公司 Wireless charging system and method and automobile wireless charging device
CN110994811A (en) * 2019-12-20 2020-04-10 中兴新能源汽车有限责任公司 Wireless charging system, control method and automobile wireless charging device
WO2020183076A1 (en) * 2019-03-14 2020-09-17 Safran Isolated and reconfigurable power converter
CN111682658A (en) * 2020-05-28 2020-09-18 哈尔滨工业大学 A resonant cavity constant current control system and its control method for wireless power transmission LPE position detection
CN111697799A (en) * 2020-07-29 2020-09-22 中惠创智无线供电技术有限公司 Wireless charging system and zero-voltage switch control method of inverter of wireless charging system
CN111799897A (en) * 2020-09-08 2020-10-20 飞频科技(上海)有限公司 Method for controlling power converter circuit
CN112825441A (en) * 2019-11-20 2021-05-21 李建廷 Wireless transmission device, wireless transmission method, wireless reception device, wireless reception method, and medium
CN112994183A (en) * 2021-04-23 2021-06-18 湖北工业大学 Maximum efficiency point tracking phase control capacitor resonance adaptive wireless charging system
CN113039700A (en) * 2019-08-07 2021-06-25 华为技术有限公司 Wireless charging device, position detection method and system
CN113285531A (en) * 2021-05-21 2021-08-20 华南理工大学 Anti-deviation SS type wireless power transmission system based on variable compensation element parameters
CN113346760A (en) * 2021-06-29 2021-09-03 同济大学 Dynamic construction method for resonance characteristics of high-efficiency power converter
CN113517763A (en) * 2021-06-30 2021-10-19 西安交通大学 Periodic energy control method of wireless power transmission system
CN113726028A (en) * 2020-06-05 2021-11-30 华为技术有限公司 Electronic equipment and control method thereof
CN113726029A (en) * 2021-07-29 2021-11-30 西南交通大学 Variable inductance-based efficient constant current/constant voltage charging method for WPT system
CN114172249A (en) * 2022-01-10 2022-03-11 深圳威迈斯新能源股份有限公司 Automobile wireless charging system and control method thereof
CN114243945A (en) * 2021-11-12 2022-03-25 深圳供电局有限公司 Wireless charging system and resonant network matching method thereof
CN114598236A (en) * 2022-03-28 2022-06-07 苏州大学 Wireless motor system based on variable capacitor
CN115056660A (en) * 2022-06-22 2022-09-16 深圳威迈斯新能源股份有限公司 Wireless charging system and control method thereof
CN115296444A (en) * 2022-10-10 2022-11-04 国网江西省电力有限公司电力科学研究院 Wireless energy transfer device
CN115473351A (en) * 2022-11-15 2022-12-13 江苏展芯半导体技术有限公司 Constant-efficiency control method suitable for S/S compensation IPT system
CN116231883A (en) * 2023-03-21 2023-06-06 广东工业大学 Multi-degree-of-freedom symmetrical dynamic circuit compensation topological structure
CN116247831A (en) * 2023-03-03 2023-06-09 中国矿业大学 A concrete-air cross-medium wireless power transmission system and its control method
CN116527087A (en) * 2023-05-09 2023-08-01 东南大学 A serial injection system and method for improving the performance of wireless signal energy simultaneous interpretation
EP4312344A3 (en) * 2022-07-29 2024-06-12 Huawei Digital Power Technologies Co., Ltd. Wireless charging module, control circuit, and electronic device

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102754305A (en) * 2010-02-10 2012-10-24 富士通株式会社 Resonance frequency control method, power transmission device, and power reception device for magnetic-resonant-coupling type power transmission system
CN105826997A (en) * 2016-05-20 2016-08-03 西安交通大学 Closed-loop control method for battery full-range charging
CN105958667A (en) * 2016-06-03 2016-09-21 东南大学 Maximum efficiency point tracking method for bidirectional wireless electric energy transmission system
CN208955902U (en) * 2018-08-24 2019-06-07 李建科 A kind of circuit topological structure suitable for the transmission of two-way near field electric energy

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102754305A (en) * 2010-02-10 2012-10-24 富士通株式会社 Resonance frequency control method, power transmission device, and power reception device for magnetic-resonant-coupling type power transmission system
CN105826997A (en) * 2016-05-20 2016-08-03 西安交通大学 Closed-loop control method for battery full-range charging
CN105958667A (en) * 2016-06-03 2016-09-21 东南大学 Maximum efficiency point tracking method for bidirectional wireless electric energy transmission system
CN208955902U (en) * 2018-08-24 2019-06-07 李建科 A kind of circuit topological structure suitable for the transmission of two-way near field electric energy

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
孙伟华: ""可控开关电容SCC的拓扑及其应用研究"", 《中国优秀硕士学位论文全文数据库工程科技Ⅱ辑》, pages 6 - 37 *

Cited By (44)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113597734A (en) * 2019-03-14 2021-11-02 赛峰公司 Isolated and reconfigurable power converter
WO2020183076A1 (en) * 2019-03-14 2020-09-17 Safran Isolated and reconfigurable power converter
FR3093875A1 (en) * 2019-03-14 2020-09-18 Safran INSULATED AND RECONFIGURABLE POWER CONVERTER
US11736027B2 (en) 2019-03-14 2023-08-22 Safran Isolated and reconfigurable power converter
CN109962625A (en) * 2019-05-10 2019-07-02 安徽水利水电职业技术学院 A resonant high-gain DC-DC device based on a loosely coupled transformer
CN110297120A (en) * 2019-07-16 2019-10-01 浙江万安亿创电子科技有限公司 The primary coil current measurement circuit of magnetic inductive radio energy transmission system
CN110297120B (en) * 2019-07-16 2024-04-02 亿创智联(浙江)电子科技有限公司 Primary coil current measuring circuit of magnetic induction type wireless electric energy transmission system
CN113039700A (en) * 2019-08-07 2021-06-25 华为技术有限公司 Wireless charging device, position detection method and system
CN113039700B (en) * 2019-08-07 2024-06-11 华为数字能源技术有限公司 A wireless charging device, a method and a system for position detection
CN110554236A (en) * 2019-09-30 2019-12-10 福州大学 Frequency online detection method for constant-voltage or constant-current output of wireless power transmission
CN110554236B (en) * 2019-09-30 2023-12-19 福州大学 Frequency online detection method for constant voltage or constant current output of wireless power transmission
CN110649821B (en) * 2019-10-24 2021-11-26 湖南大学 Bidirectional SCC type LLC resonant converter, circuit therein and control method
CN110649821A (en) * 2019-10-24 2020-01-03 湖南大学 Bidirectional SCC type LLC resonant converter, circuit and control method thereof
CN112825441A (en) * 2019-11-20 2021-05-21 李建廷 Wireless transmission device, wireless transmission method, wireless reception device, wireless reception method, and medium
CN110949152A (en) * 2019-12-20 2020-04-03 中兴新能源汽车有限责任公司 Wireless charging system and method and automobile wireless charging device
CN110949152B (en) * 2019-12-20 2023-06-20 中兴新能源汽车有限责任公司 Wireless charging system and method and automobile wireless charging device
CN110994811A (en) * 2019-12-20 2020-04-10 中兴新能源汽车有限责任公司 Wireless charging system, control method and automobile wireless charging device
CN111682658A (en) * 2020-05-28 2020-09-18 哈尔滨工业大学 A resonant cavity constant current control system and its control method for wireless power transmission LPE position detection
CN113726028A (en) * 2020-06-05 2021-11-30 华为技术有限公司 Electronic equipment and control method thereof
CN111697799B (en) * 2020-07-29 2021-08-24 中惠创智（深圳）无线供电技术有限公司 Wireless charging system and zero-voltage switch control method of inverter of wireless charging system
CN111697799A (en) * 2020-07-29 2020-09-22 中惠创智无线供电技术有限公司 Wireless charging system and zero-voltage switch control method of inverter of wireless charging system
CN111799897A (en) * 2020-09-08 2020-10-20 飞频科技(上海)有限公司 Method for controlling power converter circuit
CN112994183A (en) * 2021-04-23 2021-06-18 湖北工业大学 Maximum efficiency point tracking phase control capacitor resonance adaptive wireless charging system
CN112994183B (en) * 2021-04-23 2023-02-03 湖北工业大学 A Maximum Efficiency Point Tracking Phase-controlled Capacitive Resonant Adaptive Wireless Charging System
CN113285531A (en) * 2021-05-21 2021-08-20 华南理工大学 Anti-deviation SS type wireless power transmission system based on variable compensation element parameters
CN113346760A (en) * 2021-06-29 2021-09-03 同济大学 Dynamic construction method for resonance characteristics of high-efficiency power converter
CN113517763A (en) * 2021-06-30 2021-10-19 西安交通大学 Periodic energy control method of wireless power transmission system
CN113517763B (en) * 2021-06-30 2023-03-31 西安交通大学 Periodic energy control method of wireless power transmission system
CN113726029A (en) * 2021-07-29 2021-11-30 西南交通大学 Variable inductance-based efficient constant current/constant voltage charging method for WPT system
CN113726029B (en) * 2021-07-29 2023-05-12 西南交通大学 Efficient constant-current/constant-voltage charging method of WPT system based on variable inductor
CN114243945B (en) * 2021-11-12 2024-06-14 深圳供电局有限公司 Wireless charging system and resonant network matching method thereof
CN114243945A (en) * 2021-11-12 2022-03-25 深圳供电局有限公司 Wireless charging system and resonant network matching method thereof
CN114172249A (en) * 2022-01-10 2022-03-11 深圳威迈斯新能源股份有限公司 Automobile wireless charging system and control method thereof
CN114172249B (en) * 2022-01-10 2023-11-07 深圳威迈斯新能源股份有限公司 Automobile wireless charging system and control method thereof
CN114598236A (en) * 2022-03-28 2022-06-07 苏州大学 Wireless motor system based on variable capacitor
CN115056660A (en) * 2022-06-22 2022-09-16 深圳威迈斯新能源股份有限公司 Wireless charging system and control method thereof
EP4312344A3 (en) * 2022-07-29 2024-06-12 Huawei Digital Power Technologies Co., Ltd. Wireless charging module, control circuit, and electronic device
CN115296444A (en) * 2022-10-10 2022-11-04 国网江西省电力有限公司电力科学研究院 Wireless energy transfer device
CN115473351B (en) * 2022-11-15 2023-02-14 江苏展芯半导体技术有限公司 Constant-efficiency control method suitable for S/S compensation IPT system
CN115473351A (en) * 2022-11-15 2022-12-13 江苏展芯半导体技术有限公司 Constant-efficiency control method suitable for S/S compensation IPT system
CN116247831A (en) * 2023-03-03 2023-06-09 中国矿业大学 A concrete-air cross-medium wireless power transmission system and its control method
CN116231883A (en) * 2023-03-21 2023-06-06 广东工业大学 Multi-degree-of-freedom symmetrical dynamic circuit compensation topological structure
CN116231883B (en) * 2023-03-21 2023-09-15 广东工业大学 A multi-degree-of-freedom symmetrical dynamic circuit compensation topology
CN116527087A (en) * 2023-05-09 2023-08-01 东南大学 A serial injection system and method for improving the performance of wireless signal energy simultaneous interpretation

Similar Documents

Publication Publication Date Title
CN109302070A (en) Circuit topology structure of power converter and its control method
CN109245542A (en) A kind of symmetrical power converter circuit topological structure and its control method
CN109245536A (en) A kind of circuit topological structure suitable for the transmission of two-way near field electric energy
WO2018126617A1 (en) Wireless charging circuit with constant-current constant-voltage compound topology
CN109823206B (en) A soft-switching high-efficiency wireless charging method based on bilateral phase shifting and frequency modulation
TWI611647B (en) Resonant type non-contact power supply device, electric energy transmitting end and control method
CN210608706U (en) Induction type wireless power transmission system for realizing constant-current and constant-voltage output switching
CN208955902U (en) A kind of circuit topological structure suitable for the transmission of two-way near field electric energy
CN108173353B (en) Constant voltage-constant current ECPT system and parameter design method based on F-F/T variable topology network
CN110554236B (en) Frequency online detection method for constant voltage or constant current output of wireless power transmission
CN110429718B (en) A constant current/constant voltage control method for wireless power transfer system based on primary side parameter identification
CN111799897A (en) Method for controlling power converter circuit
CN106740238A (en) A kind of electric automobile wireless charging circuit and its control method
CN109638978A (en) A kind of efficient constant pressure and flow switching wireless charging topological structure
CN109343647A (en) A dynamic wireless charging maximum efficiency tracking system and method
CN111555612A (en) Magnetic coupling resonant wireless energy transfer maximum efficiency tracking method based on constant output voltage
CN108521177A (en) Adjusting device and control method for resonant converter based on additional coupled inductance
CN115133666A (en) Bilateral capacitor array WPT system and adaptive critical coupling coefficient adjusting method
CN117254603A (en) Wireless power transmission system with constant-current and constant-voltage output characteristics
CN106712319B (en) Magnetic resonance type wireless charging circuit of electric automobile and control method thereof
CN114243951B (en) Magnetic coupling type wireless power transmission system without parameter identification
CN114614582A (en) double-U-shaped coupling mechanism, underwater constant-voltage wireless charging system and parameter design method
CN112467891B (en) IPT system efficiency optimization method based on full-bridge half-bridge switching
CN107776429A (en) A kind of semi-bridge type MERS electric automobiles wireless charging circuit and its control method
JP2022086784A (en) High frequency inverter, rectifier circuit and wireless power transfer system

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
TA01 Transfer of patent application right

Effective date of registration: 20210412

Address after: 210 007 No. 88 Houbaoying Road, Qinhuai District, Nanjing City, Jiangsu Province

Applicant after: ARMY ENGINEERING University OF PLA

Address before: 210007 electric power of No.1 Fangyuan, Haifu lane, Qinhuai District, Nanjing City, Jiangsu Province

Applicant before: Li Jianke

TA01 Transfer of patent application right
RJ01 Rejection of invention patent application after publication

Application publication date: 20190201

RJ01 Rejection of invention patent application after publication