CN107769523B - Inductor current alternating current component reconstruction circuit, control circuit and switch circuit - Google Patents
Inductor current alternating current component reconstruction circuit, control circuit and switch circuit Download PDFInfo
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- CN107769523B CN107769523B CN201711067015.XA CN201711067015A CN107769523B CN 107769523 B CN107769523 B CN 107769523B CN 201711067015 A CN201711067015 A CN 201711067015A CN 107769523 B CN107769523 B CN 107769523B
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- 230000001939 inductive effect Effects 0.000 claims abstract description 6
- 239000003990 capacitor Substances 0.000 claims description 37
- 230000010354 integration Effects 0.000 claims description 17
- 230000001360 synchronised effect Effects 0.000 claims description 10
- 230000003321 amplification Effects 0.000 claims description 9
- 238000003199 nucleic acid amplification method Methods 0.000 claims description 9
- 238000000034 method Methods 0.000 abstract description 4
- 230000004044 response Effects 0.000 abstract description 3
- 230000001052 transient effect Effects 0.000 abstract description 3
- 230000008569 process Effects 0.000 abstract description 2
- 230000001105 regulatory effect Effects 0.000 abstract 1
- 238000010586 diagram Methods 0.000 description 21
- 238000005070 sampling Methods 0.000 description 8
- 238000004458 analytical method Methods 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000007423 decrease Effects 0.000 description 1
- 238000011084 recovery Methods 0.000 description 1
- 238000006467 substitution reaction Methods 0.000 description 1
Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1588—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses an inductive current alternating current component reconstruction circuit for a switching circuit, a control circuit and the switching circuit. The inductor current alternating current component reconstruction circuit comprises: the output voltage of the integrating circuit contains information representing the alternating current component of the inductive current, and the bias regulating circuit regulates the direct current bias of the output voltage of the integrating circuit to the first voltage. By reconstructing the alternating current component of the inductance circuit, the output is controlled, the transient response of the circuit is good, the inductance current does not need to be sampled, the influence of the switching process on the control circuit is avoided, and the control circuit is simpler.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to an inductance current alternating current component reconstruction circuit, a control circuit and a switch circuit.
Background
In a switching power supply, a current mode is used for control in order to improve the transient response of the switching power supply. Comparing the inductance current sampling value with a current threshold value, and turning off the main switching tube when the inductance current sampling value is larger than the current threshold value in a peak current mode; in the valley current mode, when the inductance current sampling value is smaller than the current threshold value, the main switch tube is conducted. In current mode, therefore, the inductor current needs to be sampled. Because the switching tube in the switching power supply is conducted, reverse recovery exists when the freewheeling diode is turned off, and overshoot exists on the inductance current sampling signal at the switching moment. To prevent this overshoot from causing a false switching of the switching tube, a blanking circuit needs to be added. After the overshoot of the inductance current sampling value is finished, the inductance current sampling signal is compared with the current threshold value, and the overshoot signal is prevented from being compared with the current threshold value, so that false triggering is generated, and the switching tube is enabled to generate false switching. In the prior art, the inductor current needs to be sampled, the requirement on a sampling circuit is high, a blanking circuit needs to be added, and the control is complex.
Disclosure of Invention
In view of the above, the present invention aims to provide an inductor current ac component reconstruction circuit, a control circuit and a switch circuit, which are used for solving the problems of high requirement on a sampling circuit, addition of a blanking circuit and complex control in the prior art that the inductor current needs to be sampled.
The technical solution of the present invention is to provide an inductor current alternating current component reconstruction circuit, the switch circuit includes a switch tube, a freewheeling diode or a synchronous rectifying tube and an inductor, a common node of the switch tube, the freewheeling diode or the synchronous rectifying tube and the inductor is a switch node, the inductor current alternating current component reconstruction circuit includes:
an integrating circuit and a bias adjusting circuit,
the first input end of the integrating circuit receives a signal representing the voltage of the switch node, the integrating circuit integrates the difference value between the voltage of the first input end and the bias voltage, the output voltage of the integrating circuit contains information representing the alternating current component of the inductive current, and the bias adjusting circuit adjusts the direct current bias of the output voltage of the integrating circuit to the first voltage.
Optionally, the bias adjustment circuit receives an output voltage of the integration circuit and adjusts a bias voltage of the integration circuit.
Alternatively, the bias adjustment circuit sets the output of the integrating circuit to zero when the inductor current is zero when the switching circuit is operating in the discontinuous conduction mode.
Optionally, the voltage regulator further comprises a capacitive voltage divider circuit, and the switch node is connected to the first input end of the integrating circuit through the capacitive voltage divider circuit.
Alternatively, the bias adjustment circuit receives the output voltage of the integration circuit and has an output connected to the first input of the integration circuit and adjusts the voltage of the first input of the integration circuit.
Optionally, the integrating circuit comprises a first op-amp and a third capacitor,
the positive input end of the first operational amplifier is a first input end of the integrating circuit, the negative input end of the first operational amplifier receives the bias voltage, the first operational amplifier is a transconductance operational amplifier, and the output end of the first operational amplifier is connected to the reference ground through the third capacitor; the output of the first operational amplifier is the output of the integrating circuit.
Optionally, the bias adjusting circuit comprises a second operational amplifier, a first resistor, a second resistor, a third resistor and a fourth capacitor,
the output of the integrating circuit is connected to the negative input terminal of the second operational amplifier through the first resistor, the first voltage is connected to the positive input terminal of the second operational amplifier,
when the second operational amplifier is a transconductance operational amplifier, the output end of the second operational amplifier is connected to the reference ground through a capacitor; when the second operational amplifier is a voltage type operational amplifier, the output end of the second operational amplifier is connected to the negative input end of the second operational amplifier through the fourth capacitor;
the output of the second operational amplifier is connected to the positive input end of the second operational amplifier through the second resistor; the positive input end of the first operational amplifier is connected to the negative input end of the first operational amplifier through the third resistor.
Optionally, the switching circuit is a four-switch Buckboost circuit, and comprises a first switching tube, a second switching tube, a third switching tube, a fourth switching tube and an inductor, wherein the first switching tube and the second switching tube are connected in series, the common end of the first switching tube and the second switching tube is a first switching node, the first switching tube is connected to an input end, the second switching tube is connected to the ground, the third switching tube and the fourth switching tube are connected in series, the common end of the third switching tube and the fourth switching tube is a second switching node, the third switching tube is connected to an output end, the fourth switching tube is connected to the ground, the inductor is connected between the first switching node and the second switching node,
a second input of the integrating circuit receives a signal representative of the voltage of the second switching node.
Another technical solution of the present invention is to provide a control circuit of a switching circuit, including for example an inductor current alternating current component reconstruction circuit, a comparison circuit and a logic circuit,
the switching node is connected to the input end of the inductance current alternating current component reconstruction circuit, the comparison circuit receives the output signal of the inductance current alternating current component reconstruction circuit and a first threshold value and compares the output signal of the comparison circuit, and the logic circuit receives the output signal of the comparison circuit and outputs a switching signal to control the on and off of a switching tube in the switching circuit.
Optionally, the comparison circuit is a first comparator and a second comparator, the first comparator receives and compares an output signal of the inductor current alternating current component reconstruction circuit with the first threshold value to generate a switching tube turn-off signal, the first threshold value is a sum of a compensation signal and a third voltage, the compensation signal is a signal obtained by performing operational amplification on an output voltage or an output current of the switching circuit and a reference voltage, and the second comparator receives and compares an output signal of the inductor current alternating current component reconstruction circuit with the second threshold value to generate a switching tube turn-on signal, and the second threshold value is a difference between the compensation signal and the third voltage.
Optionally, the circuit further comprises a clock circuit, the comparison circuit compares the output signal of the inductance current alternating current component reconstruction circuit with the first threshold value to generate a switching tube turn-off signal, the clock circuit receives the switching signal and counts time to generate a switching tube turn-on signal, the first threshold value is a compensation signal, and the compensation signal is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal.
Optionally, the circuit further comprises a clock circuit, the comparison circuit compares the output signal of the inductance current alternating current component reconstruction circuit with the first threshold value to generate a switching tube on signal, the clock circuit receives the switching signal and counts time to generate a switching tube off signal, the first threshold value is a compensation signal, and the compensation signal is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal.
A further technical solution of the present invention is to provide a switching circuit.
Compared with the prior art, the circuit structure and the method have the following advantages: the output is controlled by reconstructing the ac component of the inductive circuit. The transient response of the circuit is good, the inductance current does not need to be sampled, the influence of the switching process on the control circuit is avoided, and the control circuit is simpler.
Drawings
FIG. 1 is a schematic diagram of an inductor current AC component reconstruction circuit 100 according to the present invention;
fig. 2 is a block diagram of a switching circuit 300;
fig. 3 is a schematic circuit diagram of the power circuit 320 as a Buck circuit;
FIG. 4 is a schematic diagram of an exemplary embodiment of an inductor current AC component reconstruction circuit 100 according to the present invention;
FIG. 5 is a circuit diagram of one embodiment of integrating circuit 110 and bias adjustment circuit 120 of the present invention when the bias adjustment circuit adjusts the bias voltage;
FIG. 6 is a circuit diagram of another embodiment of the integrating circuit 110 and the bias voltage adjusting circuit 120 when the bias voltage adjusting circuit of the present invention adjusts the bias voltage;
FIG. 7 is a circuit diagram of an embodiment of the capacitive voltage divider 130 of the present invention;
FIG. 8 is a circuit diagram of another embodiment of the capacitive voltage divider 130 according to the present invention;
fig. 9 is a schematic diagram of the bias adjustment circuit 120 adjusting the voltage of the first node V1;
FIG. 10 is a circuit diagram of one embodiment of the integrating circuit 110 and the bias adjusting circuit 120 when the bias adjusting circuit of the present invention adjusts the voltage of the first node V1;
FIG. 11 is a circuit diagram of one embodiment of the integration circuit 110 of the present invention;
FIG. 12 is a circuit diagram of yet another embodiment of the integrating circuit 110 and the bias adjustment circuit 120 of the present invention;
FIG. 13 is a schematic diagram of a power circuit 320 with four switches Buckboost and buck circuits;
FIG. 14 is a schematic diagram of the inductor current AC component reconstruction circuit 100 when the power circuit 320 is a four-switch Buckboost circuit;
FIG. 15 is a schematic diagram of an inductor current AC component reconstruction circuit 100 when the power circuit 320 is a four-switch Buckboost circuit;
FIG. 16 is a circuit diagram of one embodiment of the integrating circuit 110 and the bias adjusting circuit 120 when the power circuit 320 is a four-switch Buckboost circuit according to the present invention;
FIG. 17 is a circuit diagram of one embodiment of the integrating circuit 110 when the power circuit 320 is a four-switch Buckboost circuit according to the present invention;
FIG. 18 is a circuit diagram of another embodiment of the integrating circuit 110 and the bias adjusting circuit 120 when the power circuit 320 is a four-switch Buckboost circuit;
FIG. 19 is a schematic diagram of one embodiment of a control circuit 200 of the present invention;
fig. 20 is a schematic diagram of a control circuit 200 according to another embodiment of the invention.
Detailed Description
The preferred embodiments of the present invention will be described in detail below with reference to the accompanying drawings, but the present invention is not limited to these embodiments only. The invention is intended to cover any alternatives, modifications, equivalents, and variations that fall within the spirit and scope of the invention.
In the following description of preferred embodiments of the invention, specific details are set forth in order to provide a thorough understanding of the invention, and the invention will be fully understood to those skilled in the art without such details.
The invention is more particularly described by way of example in the following paragraphs with reference to the drawings. It should be noted that the drawings are in a simplified form and are not to scale precisely, but rather are merely intended to facilitate and clearly illustrate the embodiments of the present invention.
Referring to fig. 1, an inductor current ac component reconstruction circuit 100 for a switching circuit 300, where the switching circuit 300 includes a switching tube, a freewheeling diode or a synchronous rectifier tube, and an inductor, and a common node of the switching tube, the freewheeling diode or the synchronous rectifier tube, and the inductor is a switching node, and the inductor current ac component reconstruction circuit 100 includes: an integrating circuit 110 and a bias adjustment circuit 120, a first input terminal of the integrating circuit 110 receives a signal representing the voltage of the switch node, the integrating circuit 110 integrates the difference between the voltage at its first input terminal and the bias voltage, the output voltage of the integrating circuit 110 contains information representing the alternating current component of the inductor current, and the bias adjustment circuit 120 adjusts the direct current bias of the output voltage of the integrating circuit 110 to the first voltage.
The invention can reconstruct the alternating current component of the inductive current only by switching the voltage of the node, and has simple circuit, convenient realization and low cost.
Referring to fig. 2, the switching circuit 300 includes a control circuit 200, a driving circuit 310, and a power circuit 320. The power circuit 320 of the switching circuit includes various circuits such as Buck-Boost circuit, boost-Boost circuit, buck-Boost circuit, and four-switch Buck-Boost circuit. Referring to fig. 3, a schematic circuit diagram of a power circuit 320 is a Buck circuit, M321 is a switching transistor, M322 is a synchronous rectifier, L321 is an inductor, and a common node of M321, M322, and L321 is a switching node.
As an embodiment, referring to fig. 4, the bias adjustment circuit 120 receives the output voltage of the integration circuit 110 and adjusts the bias voltage of the integration circuit.
As an embodiment, referring to fig. 5, the integrating circuit 110 includes a first operational amplifier 111 and a third capacitor C111, where a positive input end of the first operational amplifier 111 is a first input end of the integrating circuit 110, a negative input end of the first operational amplifier 111 receives a bias voltage, the first operational amplifier 111 is a transconductance operational amplifier, and an output end of the first operational amplifier is connected to a reference ground through the capacitor C111; the output of the first op-amp 111 is the output Vac of the integrating circuit 110. The bias adjusting circuit 120 comprises operational amplifiers 123 and 124, resistors R124 and R125, R127 and a capacitor C123, the output Vac of the integrating circuit 110 is connected to the negative input end of the operational amplifier 123 through the resistor R124, the output end of the operational amplifier 123 is connected to the negative input end of the operational amplifier 123 through the capacitor 123, the output end of the operational amplifier 123 is connected to the negative input end of the operational amplifier 124 through the resistor R125, the output end of the operational amplifier 124 is connected to the negative input end of the operational amplifier 124 through the resistor R127, the operational amplifier 123, the resistor R125 and the resistor R127 form an inverter, the output of the operational amplifier 124 is the output end of the bias adjusting circuit 120, and is connected to the negative input end of the integrating circuit 110 to adjust the bias voltage. The positive inputs of the operational amplifier 124 and the operational amplifier 123 are connected to the first voltage VCOM.
As an embodiment, referring to fig. 6, unlike fig. 5, the operational amplifier 125 is a transconductance operational amplifier, where a positive input terminal of the operational amplifier 125 receives the output voltage of the integrating circuit 110, and an output terminal is connected to the reference ground through the capacitor C124, and a negative input terminal of the operational amplifier 125 receives the first voltage VCOM. The output of the op-amp 125 is the output of the bias adjustment circuit 120.
As one embodiment, when the switching circuit is operating in discontinuous conduction mode, the bias adjustment circuit sets the output of the integrating circuit to zero when the inductor current is zero.
As an embodiment, referring to fig. 7, the capacitive voltage divider 130 is further included, and the switch node is connected to the first input terminal of the integrating circuit through the capacitive voltage divider.
Referring to fig. 7, a switching node is connected to a ground through a circuit formed by connecting the capacitor C131 and the capacitor C132 in series, and a common node of the capacitor C131 and the capacitor C132 is an output of a capacitive voltage divider circuit, which is a first node V1, and is connected to a first input terminal of the integrating circuit 110.
Referring to fig. 8, in another embodiment of the capacitive voltage divider 130, a switch node is connected to a reference ground through a circuit formed by connecting a resistor R131 and a resistor R132 in series, a common node of the resistor R131 and the resistor R132 is connected to the first input terminal of the integrating circuit 110 through a capacitor C135, and the common node of the capacitor C135 and the first input terminal of the integrating circuit 110 is the output of the capacitive voltage divider 130 and is the first node V1.
Other embodiments of the capacitive voltage divider 130 are possible, and are not limited to the two embodiments described above.
As an embodiment, referring to fig. 9, the switching node is connected to the first input terminal of the integrating circuit 110 through the capacitive voltage dividing circuit 130, and the bias adjusting circuit 120 receives the output voltage of the integrating circuit 110, and its output terminal is connected to the first input terminal of the integrating circuit 110 and adjusts the voltage of the first input terminal of the integrating circuit 110.
As an embodiment, referring to fig. 10, the integrating circuit 110 includes a first operational amplifier 111 and a third capacitor C111, where a positive input end of the first operational amplifier 111 is a first input end of the integrating circuit 110, a negative input end of the first operational amplifier 111 receives a bias voltage, the first operational amplifier 111 is a transconductance operational amplifier, and an output end of the first operational amplifier is connected to a reference ground through the third capacitor C111; the output of the first op-amp 111 is the output Vac of the integrating circuit 110.
As an embodiment, with continued reference to fig. 10, the bias adjustment circuit 120 includes a second operational amplifier 121, a first resistor R123, a second resistor R121, a third resistor R122, and a fourth capacitor C121, where the output Vac of the integrating circuit 110 is connected to the negative input terminal of the second operational amplifier 121 through the first resistor R123, and the first voltage is connected to the positive input terminal of the second operational amplifier 121.
When the second operational amplifier 121 is a transconductance operational amplifier, the output end of the second operational amplifier 121 is connected to the reference ground through the fourth capacitor C121; when the second operational amplifier 121 is a voltage-type operational amplifier, the output end of the second operational amplifier is connected to the negative input end of the second operational amplifier through the fourth capacitor C121; fig. 10 shows a voltage-type operational amplifier as the second operational amplifier 121. The output of the second operational amplifier 121 is connected to the positive input end of the first operational amplifier 111 through the second resistor R121; the positive input terminal of the first operational amplifier 111 is connected to the negative input terminal of the first operational amplifier 111 through the third resistor R122. In fig. 10, the bias voltage is equal to the first voltage VCOM, which may not be equal.
As an embodiment, referring to fig. 11, the integrating circuit 110 includes voltage-type operational amplifiers 112 and 113, resistors R115, R116, R117, and a capacitor C117. The first node V1 is connected to the negative input end of the operational amplifier 112 through a resistor R115, the output end of the operational amplifier 112 is connected to the negative input end of the operational amplifier 112 through a resistor R116, the output end of the operational amplifier 112 is connected to the negative input end of the operational amplifier 113 through a resistor R117, the output end of the operational amplifier 113 is connected to the negative input end of the operational amplifier 113 through a capacitor C117, and the positive input ends of the operational amplifiers 112 and 113 are both connected with the bias voltage. The output voltage of the operational amplifier 112 is the output of the integrating circuit 110.
Referring to fig. 12, as an embodiment, the op-amp is composed of a current source I111, PMOS M111 and M112, NMOS M113 and M114, the output terminal of the current source I111 is connected to the sources of the PMOS M111 and M112, the drain of the M111 is connected to the drain of the NMOS M113, the drain of the M112 is connected to the drain of the NMOS M114, the sources of the M113 and M114 are connected to the ground, the gates of the M113 and M114 are connected to the drain of the M113, the gates of the M111 and M112 are two input terminals of the op-amp, respectively, the output terminal of the op-amp is the drain of the M114, that is, the output terminal Vac of the integrating circuit 110, and is connected to the ground through a capacitor C112. The first node V1 is connected to the gate of M111, the bias voltage is connected to the gate of PMOS M111 through resistor R113, the bias voltage is simultaneously connected to the gate of PMOS M112, and in fig. 12, the bias voltage is equal to the first voltage VCOM. The bias adjustment circuit 120 is constituted by a resistor R123, and Vac is connected to the gates of M113 and M114 through the resistor R123.
As an embodiment, referring to fig. 13, the switching circuit is a four-switch buck circuit, and includes a first switching tube M323, a second switching tube M324, a third switching tube M325, a fourth switching tube M326, and an inductor L321, where the first switching tube M323 and the second switching tube M324 are connected in series, a common terminal of the first switching tube M323 and the second switching tube M324 is a first switching node, the first switching tube is connected to an input terminal VIN, the second switching tube is connected to a ground, a common terminal of the third switching tube M325 and the fourth switching tube M326 is a second switching node, the third switching tube M325 is connected to an output terminal VOUT, the fourth switching tube M326 is connected to a ground, and the inductor L321 is connected between the first switching node and the second switching node.
Referring to fig. 14, a second input of the integrating circuit 110 receives a signal representative of the voltage of the second switching node.
As an embodiment, referring to fig. 15, a first switching node is connected to a first input terminal of the integrating circuit 110 through a capacitive voltage dividing circuit 130, a second switching node is connected to a second input terminal of the integrating circuit 110 through the capacitive voltage dividing circuit 130, and a capacitive voltage dividing circuit formed by two capacitors connected in series is illustrated as an example, the first switching node is connected to a reference ground through a circuit formed by connecting the capacitor C131 and the capacitor C132 in series, a common node of the capacitor C131 and the capacitor C132 is a first node V1, connected to the first input terminal of the integrating circuit 110, the second switching node is connected to the reference ground through a circuit formed by connecting the capacitor C133 and the capacitor C134 in series, and a common node of the capacitor C133 and the capacitor C134 is a second node V2, connected to the second input terminal of the integrating circuit 110.
As an embodiment, referring to fig. 16, the four-switch buck-boost circuit has two switching nodes, a first switching node and a second switching node, and the difference between fig. 16 and fig. 10 is that the bias voltage is connected to the negative input terminal of the first op-amp 111 through the resistor R111, and the second node V2 is connected to the negative input terminal of the first op-amp 111. The integrating circuit 110 integrates the difference between the first node and the second node, i.e., V1-V2. The bias adjustment circuit 120 in fig. 16 is the same as that in fig. 10.
As an embodiment, the integrating circuit 110 is shown with reference to fig. 17, and is different from fig. 11 in that the second node V2 is connected to the positive input terminal of the operational amplifier 112 through a resistor R118, and the bias voltage is connected to the positive input terminal of the operational amplifier 112 through a resistor R119. The circuit also enables integration of the difference between the first node and the second node.
As an embodiment, the integrating circuit 110 and the bias adjusting circuit 120 are shown with reference to fig. 18, and are different from fig. 12 in that the second node V2 is connected to the gate of M112, and the bias voltage is connected to the gate of M112 through a resistor R114.
The control circuit 200 of the switching circuit comprises an inductor current alternating current component reconstruction circuit 100, a comparison circuit 210 and a logic circuit 220, wherein the switching node is connected to the input end of the inductor current alternating current component reconstruction circuit 100, the comparison circuit 210 receives an output signal of the inductor current alternating current component reconstruction circuit 100 and a first threshold value and compares the output signal, and the logic circuit 220 receives an output signal of the comparison circuit 210 and outputs a switching signal PWM to control the on and off of a switching tube in the switching circuit.
Referring to fig. 19, as an embodiment, the comparing circuit 210 is a first comparator and a second comparator, where the first comparator receives and compares the output signal Vac of the inductor current ac component reconstructing circuit with the first threshold value to generate a switching-tube turn-off signal, the first threshold value is a sum of a compensation signal Vc and a third voltage V1, the compensation signal Vc is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal, and the second comparator receives and compares the output signal of the inductor current ac component reconstructing circuit with the second threshold value to generate a switching-tube turn-on signal, and the second threshold value is a difference between the compensation signal Vc and the third voltage V1.
Taking Vac connected to the negative input end of the first comparator, vc+v1 connected to the positive input end of the first comparator, vac connected to the positive input end of the second comparator, vc-V1 connected to the negative input end of the second comparator as an example, when Vac is greater than or equal to vc+v1, the output A1 of the first comparator changes from logic high to logic low, the output A2 of the second comparator is logic high, the logic circuit 220 receives the signal, the output PWM signal thereof controls the switching tube to turn off, taking the Buck circuit of fig. 3 as an example, the PWM signal controls the switching tube to turn off, the driving circuit 310 receives the PWM signal to generate driving signals DRV1 and DRV2, DRV1 is low, DRV2 is high, the main switching tube M321 is turned off, and the synchronous rectifying tube M322 is turned on; after the switching tube is turned off, the inductance current is reduced, vac is smaller than Vc+V1, the output A1 of the first comparator is changed from logic low to logic high, and the PWM signal state is kept unchanged. When Vac is smaller than Vc-V1, the output A2 of the second comparator changes from logic high to logic low, the output A1 of the first comparator is logic high, the logic circuit 220 receives the signal, and outputs a PWM signal to control the switching tube to be turned on, and continuously taking the Buck circuit of fig. 3 as an example, the PWM signal controls the switching tube to be turned on, the driving circuit 310 receives the PWM signal, and generates driving signals DRV1 and DRV2, DRV1 is high, DRV2 is low, the main switching tube M321 is turned on, and the synchronous rectifying tube M322 is turned off; after the switching tube is turned on, the inductor current rises, and Vac rises.
Referring to fig. 13, in the four-switch buck-boost circuit, when the input voltage is higher than the output voltage, the PWM signal controls the switching tube to be turned on, the driving signals DRV3 and DRV5 generated by the driving circuit 310 are at high level, DRV4 and DRV6 are at low level, M323 and M325 are turned on, M324 and M426 are turned off, and the inductor current rises; the PWM signal controls the switching tube to be turned off, driving signals DRV4 and DRV5 generated by the driving circuit 310 are in high level, DRV3 and DRV6 are in low level, M324 and M325 are turned on, M323 and M426 are turned off, and the inductance current is reduced; when the input voltage is lower than the output voltage, the PWM signal controls the switching tube to be conducted, driving signals DRV3 and DRV6 generated by the driving circuit 310 are in high level, DRV4 and DRV5 are in low level, M323 and M326 are conducted, M324 and M425 are turned off, and the inductance current rises; the PWM signal controls the switching tube to turn off, the driving signals DRV3 and DRV5 generated by the driving circuit 310 are at high level, DRV4 and DRV6 are at low level, M323 and M325 are on, M324 and M426 are off, and the inductor current decreases.
The application range of the invention is not limited to the Buck step-down circuit and the four-switch Buckboost circuit as the power circuits analyzed in the embodiment, but can be applied to various switch power supply circuits such as Boost circuits and the like.
Referring to fig. 20, the control circuit 200 further includes a clock circuit 230, the comparing circuit 210 compares the output signal Vac of the inductor current ac component reconstruction circuit 100 with the first threshold value to generate a switching-tube turn-off signal, the clock circuit 230 receives the switching signal PWM and counts time to generate a switching-tube turn-on signal, the first threshold value is a compensation signal Vc, and the compensation signal Vc is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal.
The control mode is a peak current control mode. The clock circuit 230 starts to time from the off to the on of the switching tube, and the time reaches the period T, and generates the on signal of the switching tube, so that the switching period is T. The analysis of the switching-on signal and the switching-off signal in the embodiment of fig. 19 is also applicable to this embodiment, and will not be described here again.
Referring to fig. 20, the control circuit 200 further includes a clock circuit 230, the comparing circuit 210 compares the output signal Vac of the inductor current ac component reconstruction circuit 100 with the first threshold value to generate a switching-on signal, the clock circuit 230 receives the switching signal and counts time to generate a switching-off signal, the first threshold value is a compensation signal Vc, and the compensation signal Vc is a signal obtained by performing operational amplification on an output voltage or an output current of the switching circuit and a reference voltage.
The control mode is a valley current control mode. The clock circuit 230 starts to time from the on-state to the off-state of the switching tube, and the time reaches the period T, and generates the switching tube off signal, so that the switching period is T. The analysis of the switching-on signal and the switching-off signal in the embodiment of fig. 19 is also applicable to this embodiment, and will not be described here again.
In the above control modes, since the output is controlled by the ac component of the inductor current, the range of the compensation voltage Vc is very small because the dc value of the inductor current is not seen, and thus the operational amplifier generating the compensation voltage Vc is easier to design than the corresponding operational amplifier in the current control mode in the prior art.
The invention also discloses a switching circuit which comprises the control circuit. Referring to fig. 1, the control circuit 200 generates a switching signal PWM, and the driving circuit 310 generates a driving signal DRV according to the switching signal PWM to drive on and off of switching transistors and synchronous rectifiers in the power circuit 320.
In addition, although the embodiments are described and illustrated separately above, it will be apparent to those skilled in the art that some common techniques may be substituted and integrated between the embodiments, and that reference may be made to another embodiment without explicitly recited in one of the embodiments.
The above-described embodiments do not limit the scope of the present invention. Any modifications, equivalent substitutions and improvements made within the spirit and principles of the above embodiments should be included in the scope of the present invention.
Claims (13)
1. An inductor current alternating current component reconstruction circuit for a switching circuit, the switching circuit comprising a switching tube, a freewheeling diode or a synchronous rectifying tube and an inductor, wherein a common node of the switching tube, the freewheeling diode or the synchronous rectifying tube and the inductor is a switching node, the inductor current alternating current component reconstruction circuit is characterized by comprising:
an integrating circuit and a bias adjusting circuit,
the first input end of the integrating circuit receives a signal representing the voltage of the switch node, the integrating circuit integrates the difference value between the voltage of the first input end and the bias voltage, the output voltage of the integrating circuit contains information representing the alternating current component of the inductive current, and the bias adjusting circuit adjusts the direct current bias of the output voltage of the integrating circuit to the first voltage;
the bias adjustment circuit receives an output voltage of the integration circuit and adjusts a bias voltage of the integration circuit.
2. The inductor current ac component reconstruction circuit of claim 1, wherein: when the switching circuit works in the intermittent conduction mode, the bias adjusting circuit sets the output of the integrating circuit to zero when the inductance current is zero.
3. The inductor current ac component reconstruction circuit of claim 1, wherein: the capacitive voltage divider circuit is further included, and the switch node is connected to the first input end of the integrating circuit through the capacitive voltage divider circuit.
4. An inductor current ac component reconstruction circuit as claimed in claim 3, wherein: the bias adjustment circuit receives the output voltage of the integration circuit and has an output connected to the first input of the integration circuit and adjusts the voltage of the first input of the integration circuit.
5. An inductor current ac component reconstruction circuit as claimed in claim 3, wherein: the bias adjustment circuit receives the output voltage of the integration circuit and has an output connected to the second input of the integration circuit and adjusts the voltage of the second input of the integration circuit.
6. An inductor current ac component reconstruction circuit as claimed in claim 3, wherein: the integrating circuit comprises a first operational amplifier and a third capacitor,
the positive input end of the first operational amplifier is a first input end of the integrating circuit, the negative input end of the first operational amplifier receives the bias voltage, the first operational amplifier is a transconductance operational amplifier, and the output end of the first operational amplifier is connected to the reference ground through the third capacitor; the output of the first operational amplifier is the output of the integrating circuit.
7. The inductor current ac component reconstruction circuit of claim 6 wherein: the bias adjusting circuit comprises a second operational amplifier, a first resistor, a second resistor, a third resistor and a fourth capacitor, the output of the integrating circuit is connected to the negative input end of the second operational amplifier through the first resistor, the first voltage is connected to the positive input end of the second operational amplifier,
when the second operational amplifier is a voltage type operational amplifier, the output end of the second operational amplifier is connected to the negative input end of the second operational amplifier through the fourth capacitor;
the output of the second operational amplifier is connected to the positive input end of the first operational amplifier through the second resistor; the positive input end of the first operational amplifier is connected to the negative input end of the first operational amplifier through the third resistor.
8. The inductor current ac component reconstruction circuit of claim 1, wherein: the switching circuit is a four-switch Buckboost circuit and comprises a first switching tube, a second switching tube, a third switching tube, a fourth switching tube and an inductor, wherein the first switching tube and the second switching tube are connected in series, the common end of the first switching tube and the second switching tube is a first switching node, the first switching tube is connected to an input end, the second switching tube is connected to the ground, the third switching tube and the fourth switching tube are connected in series, the common end of the third switching tube and the fourth switching tube is a second switching node, the third switching tube is connected to an output end, the fourth switching tube is connected to the ground, the inductor is connected between the first switching node and the second switching node,
a second input of the integrating circuit receives a signal representative of the voltage of the second switching node.
9. A control circuit of a switching circuit, characterized by comprising an inductor current alternating current component reconstruction circuit, a comparison circuit and a logic circuit according to claim 1-8,
the switching node is connected to the input end of the inductance current alternating current component reconstruction circuit, the comparison circuit receives the output signal of the inductance current alternating current component reconstruction circuit and a first threshold value and compares the output signal of the comparison circuit, and the logic circuit receives the output signal of the comparison circuit and outputs a switching signal to control the on and off of a switching tube in the switching circuit.
10. The control circuit of a switching circuit according to claim 9, wherein: the comparison circuit is a first comparator and a second comparator, the first comparator receives and compares an output signal of the inductor current alternating current component reconstruction circuit with a first threshold value to generate a switching tube turn-off signal, the first threshold value is the sum of a compensation signal and a third voltage, the compensation signal is a signal obtained by carrying out operational amplification on the output voltage or the output current of the switching circuit and a reference voltage, the second comparator receives and compares the output signal of the inductor current alternating current component reconstruction circuit with a second threshold value to generate a switching tube turn-on signal, and the second threshold value is the difference between the compensation signal and the third voltage.
11. The control circuit of a switching circuit according to claim 9, wherein: also included is a clock circuit that is configured to provide a clock signal,
the comparison circuit compares the output signal of the inductance current alternating current component reconstruction circuit with the first threshold value to generate a switching tube turn-off signal, the clock circuit receives the switching signal and counts time to generate a switching tube turn-on signal, the first threshold value is a compensation signal, and the compensation signal is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal.
12. The control circuit of a switching circuit according to claim 9, wherein: also included is a clock circuit that is configured to provide a clock signal,
the comparison circuit compares the output signal of the inductance current alternating current component reconstruction circuit with the first threshold value to generate a switching tube conduction signal, the clock circuit receives the switching signal and counts time to generate a switching tube turn-off signal, the first threshold value is a compensation signal, and the compensation signal is a signal obtained by performing operational amplification on the output voltage or the output current of the switching circuit and a reference signal.
13. A switching circuit, characterized in that: comprising a control circuit according to any of claims 9-12.
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| CN110677039A (en) * | 2019-10-10 | 2020-01-10 | 杰华特微电子（杭州）有限公司 | Control method and control circuit of switch circuit and switch circuit |
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| JP2013038782A (en) * | 2011-08-03 | 2013-02-21 | Yue Mei Qiu | Pulse width modulation control circuit and method of controlling the same |
| CN207459969U (en) * | 2017-11-02 | 2018-06-05 | 杰华特微电子（杭州）有限公司 | Inductive current AC compounent reconstruction circuit, control circuit and on-off circuit |
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| JP4810775B2 (en) * | 2001-08-03 | 2011-11-09 | 日本テキサス・インスツルメンツ株式会社 | DC-DC converter |
| EP1920524A2 (en) * | 2005-08-24 | 2008-05-14 | Nxp B.V. | Linear transconductor for a one-cycle controller, notably for a dc-dc switching converter |
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| JP2013038782A (en) * | 2011-08-03 | 2013-02-21 | Yue Mei Qiu | Pulse width modulation control circuit and method of controlling the same |
| CN207459969U (en) * | 2017-11-02 | 2018-06-05 | 杰华特微电子（杭州）有限公司 | Inductive current AC compounent reconstruction circuit, control circuit and on-off circuit |
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