CN104539157A - Slope compensation control method and circuit for inverted welding power source with peak current control mode - Google Patents
Slope compensation control method and circuit for inverted welding power source with peak current control mode Download PDFInfo
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Abstract
The invention relates to a slope compensation control method and a circuit for an inverted welding power source with a peak current control mode. The purpose of the slope compensation control method and the circuit is to effectively solve the sub-harmonic oscillation by providing a control method and a control circuit, to truly reflect the electric current of a power device, and to improve the anti-magnetic biasing capability of a system and the real-time protecting capability of the electric current of the power device. According to the technical scheme, the slope compensation control method and the circuit for the inverted welding power source with peak current control mode is characterized in that addition and subtraction are conducted between a saw-tooth oscillation waveform outputted by an input saw-tooth waveform signal source and a voltage signal outputted by an error amplifier, so that a voltage signal of a negative slope saw-tooth waveform is obtained. The voltage signal of the negative slope saw-tooth waveform is compared in real-time with a sampling feedback signal of a voltage input side current. Accordingly, the PWM pulse width output can be adjusted.
Description
Technical Field
The invention relates to the technical field of inverter welding power supplies, in particular to a slope compensation control method of an inverter welding power supply with a peak current control mode and a slope compensation control circuit of the inverter welding power supply with the peak current control mode.
Background
In an inverter type welding power supply, the control mode of a DC-DC power converter can be divided into two categories, namely a voltage mode and a current mode, wherein the current mode control is divided into peak current control and average current control. Compared with the voltage mode, the peak current control technology has the advantages of fast dynamic response, good adjustment performance, easy realization of current limiting and overcurrent protection, automatic magnetic biasing resistance, easy current sharing and the like, and is widely used. However, in the peak current mode, when the duty ratio is greater than 50%, there are problems of instability of the open loop of the system, subharmonic oscillation, poor interference rejection, etc., which is more serious especially when the ripple current component in the inductor is small. Slope compensation circuits are commonly used to solve the above problems.
The current slope compensation implementation method of the existing inverter welding power supply mainly comprises two methods: firstly, the compensation slope is superposed on the induced voltage of the sampling resistor, so that the voltage change rate of a feedback signal is increased, and then the feedback signal is compared with a smooth error voltage to regulate the pulse width output, but the current of a power device cannot be truly reflected due to the superposition of an additional current slope signal; secondly, an inductive load device is added on the secondary side or the primary side of the power transformer so as to improve the current slope, but an additional physical device is added in the method, the space radiation and the conduction of an inductive magnetic field are not beneficial to meeting the energy-saving and environment-friendly requirements of an inverter welding power supply, and meanwhile, the current passing through a switching device is increased, and the pressure of the switching device is increased.
Disclosure of Invention
The technical problem to be solved by the present invention is to overcome the defects of the background art, and provide a slope compensation control method for a peak current control mode inverter welding power supply and a slope compensation control circuit for a peak current control mode inverter welding power supply, wherein the control method and the control circuit can effectively solve subharmonic oscillation, can truly reflect the current of a power device, and can improve the magnetic bias resistance of a system and the current real-time protection capability of the power device.
In order to realize the purpose, the invention adopts the technical scheme that:
a slope compensation control method of a peak current control mode inverter welding power supply is characterized by comprising the following steps: the voltage signal of the sawtooth oscillation waveform output by the sawtooth waveform signal source is input and is added or subtracted with the voltage signal output by the error amplifier to obtain the voltage signal of the negative slope sawtooth waveform, and the voltage signal of the negative slope sawtooth waveform is compared with the primary side current sampling feedback signal in real time to adjust the output PWM pulse width.
When the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with positive slope, the voltage signal of the sawtooth oscillation waveform with positive slope and the voltage signal output by the error amplifier are subjected to subtraction operation to obtain the voltage signal of the sawtooth waveform with negative slope.
When the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with positive slope, the voltage signal of the sawtooth oscillation waveform with positive slope is firstly subjected to reverse operation to obtain a voltage signal of a sawtooth oscillation waveform with negative slope, and then is subjected to addition operation with the voltage signal output by the error amplifier to obtain the voltage signal of the sawtooth waveform with negative slope.
When the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with a negative slope, the voltage signal of the sawtooth oscillation waveform with the negative slope is directly added with a voltage signal output by the error amplifier to obtain the voltage signal of the sawtooth waveform with the negative slope.
The subtraction is performed according to the following formula: vg ═ Ve- (K1 × Vr + K2); in the formula, Vg is a voltage signal of the negative slope sawtooth waveform, Ve is a voltage signal output by the error amplifier, and Vr is a voltage signal of the positive slope sawtooth waveform; the K1 value represents the slope of the negative slope sawtooth waveform, different compensation slopes can be obtained by changing the K1 value, the K2 value represents the amplitude of the negative slope sawtooth waveform, and the magnitudes of the slope base value and the peak value can be changed by changing the K2 value.
The addition operation is performed according to the following formula: vg (-K1 × Vr + K2) + Ve; in the formula, Vg is a voltage signal of the negative slope sawtooth waveform, Ve is a voltage signal output by the error amplifier, and Vr is a voltage signal of the positive slope sawtooth waveform; the K1 value represents the slope of the negative slope sawtooth waveform, different compensation slopes can be obtained by changing the K1 value, the K2 value represents the amplitude of the negative slope sawtooth waveform, and the magnitudes of the slope base value and the peak value can be changed by changing the K2 value.
The control circuit comprises a full-bridge control chip, an error amplifier, a sampling resistor, a switching tube, an arithmetic unit, a transformer, a rectifying and filtering circuit and an isolation feedback circuit;
the reverse input end of the full-bridge control chip is connected with the output end of the arithmetic unit, so that a voltage signal Vg of a negative slope sawtooth waveform is introduced; the positive input end of the full-bridge control chip is connected with a sampling resistor, and a primary side current sampling feedback voltage signal Vs of the transformer is introduced; the input end of the arithmetic unit is connected with the output end of the error amplifier, and a voltage signal Ve output by the error amplifier is introduced, and the input end of the arithmetic unit is also connected with the oscillator, and a voltage signal Vr of a sawtooth oscillation waveform is introduced; the input end of the error amplifier is connected with the secondary side of the transformer through an isolation feedback circuit and a rectification filter circuit, and an output current feedback signal Vf of the secondary side is introduced; the primary side of the transformer is connected with the output end of the full-bridge control chip and the sampling resistor through the switching tube.
The invention has the beneficial effects that: the invention does not superpose any current slope on the waveform of the primary current sampling feedback signal of the sampling resistor, but directly applies the voltage signal Vs fed back by the primary current sampling and the voltage signal Vg of the negative slope sawtooth waveform to the inside of the full-bridge control chip for comparison, thereby regulating and outputting the PWM waveform.
Drawings
FIG. 1 is a schematic diagram of a slope compensation control circuit according to the present invention.
Fig. 2 is a schematic diagram of PWM waveform modulation of the slope compensation control method according to the present invention.
Fig. 3-5 are schematic diagrams of embodiments of an input sawtooth waveform signal source in the present invention.
Detailed Description
The present invention will be further described with reference to the drawings attached to the specification, but the present invention is not limited to the following examples.
As shown in fig. 1, the present invention provides a slope compensation control circuit for a peak current control mode inverter welding power supply, which includes a full bridge control chip, an error amplifier, a sampling resistor Rs, a switching tube, an operator (which may use an operational amplifier with a gain-bandwidth product greater than 3MHz such as LF353 and LF 347), a transformer, a rectification filter circuit, and an isolation feedback circuit.
The full-bridge control chip is internally integrated with at least an oscillator, a PWM (pulse-width modulation) comparator and a constant-frequency clock pulse set R-S latch. The reverse input end (namely the negative pin of the PWM comparator) of the full-bridge control chip is connected with the output end of the arithmetic unit, so that a voltage signal Vg of a negative slope sawtooth waveform is introduced, the forward input end (namely the positive pin of the PWM comparator) of the full-bridge control chip is connected with the sampling resistor, so that a primary side current sampling feedback voltage signal Vs is obtained, and the PWM output pin (namely the output end of the constant frequency clock pulse setting R-S latch) of the full-bridge control chip outputs a PWM waveform for adjusting the duty ratio of a switching tube in real time, so that the constant current characteristic of the system is realized.
The input end of the error amplifier is connected with the secondary side of the transformer through an isolation feedback circuit and a rectification filter circuit, an output current feedback signal Vf (which is a voltage signal) of the secondary side is introduced, and Vref is the set voltage of the error amplifier; the primary side of the transformer is connected with a PWM output pin of the full-bridge control chip and a sampling resistor through a switching tube. One pin (a positive pin in the graph 1) at the input end of the arithmetic unit is connected with the output end of the error amplifier so as to obtain a voltage signal Ve output by the error amplifier, the other pin (a negative pin in the graph 1) at the input end of the arithmetic unit is connected with the oscillator of the full-bridge control chip so as to obtain a voltage signal Vr of a sawtooth oscillation waveform, the voltage signal Ve and the voltage signal Vr are added or subtracted in the arithmetic unit so as to obtain a voltage signal Vg of the negative slope sawtooth waveform, and the voltage signal of the negative slope sawtooth waveform is introduced from the output end of the arithmetic unit to the reverse input end of the full-bridge control chip and is compared with a primary side current sampling feedback voltage signal Vs of the sampling resistor in real time so as to adjust the PWM pulse width output by the full-bridge control.
The primary side current sampling feedback voltage signal Vs can acquire a primary side current waveform through a mutual inductor and then obtain a voltage value through a sampling resistor; the output current feedback signal Vf of the secondary side can be directly collected from the output loop through a hall sensor or a shunt, and an approximate Vf value can also be obtained through the operation processing of the primary side current sampling feedback signal Vs, which is a conventional technology and is not described in detail herein.
The invention also provides a method for slope compensation control by applying the slope compensation control circuit, which has the following specific technical scheme:
a slope compensation control method of a peak current control mode inverter welding power supply comprises the following steps:
when the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with positive slope, the voltage signal of the sawtooth oscillation waveform with positive slope and the voltage signal output by the error amplifier are subjected to subtraction operation in an arithmetic unit to obtain a voltage signal of the sawtooth waveform with negative slope; or,
when the input sawtooth waveform signal source outputs a voltage signal of a positive slope sawtooth oscillation waveform, the voltage signal of the positive slope sawtooth oscillation waveform is firstly subjected to reverse operation in an arithmetic unit (the reverse operation formula is-K1 x Vr + K2) to obtain a voltage signal of a negative slope sawtooth oscillation waveform, and then the voltage signal and the voltage signal output by the error amplifier are subjected to addition operation in the arithmetic unit to obtain a voltage signal of the negative slope sawtooth waveform; or,
when the input sawtooth waveform signal source outputs a voltage signal of a negative slope sawtooth oscillation waveform, the voltage signal of the negative slope sawtooth oscillation waveform is directly added with a voltage signal output by the error amplifier in the arithmetic unit to obtain a voltage signal of the negative slope sawtooth waveform;
and the voltage signal of the negative slope sawtooth waveform and the primary side current sampling feedback signal of the sampling resistor are compared in real time in the full-bridge control chip, and the PWM pulse width output by the full-bridge control chip is adjusted. And inputting a sawtooth waveform signal source, namely an oscillator of a full-bridge control chip.
The subtraction is performed according to the following formula: vg ═ Ve- (K1 × Vr + K2); the addition operation is performed according to the following formula: vg (-K1 × Vr + K2) + Ve; in the formula, Vg is a voltage signal of the negative slope sawtooth waveform, Ve is a voltage signal output by the error amplifier, and Vr is a voltage signal of the positive slope sawtooth waveform; the K1 value represents the slope of the negative slope sawtooth waveform, different compensation slopes can be obtained by changing the K1 value, the K2 value represents the amplitude of the negative slope sawtooth waveform, and the magnitudes of the slope base value and the peak value can be changed by changing the K2 value. The sawtooth waveform with different slopes and amplitudes can be obtained by selecting proper values of K1 and K2. V in FIG. 10Is a transformer pairThe output voltage after rectification and filtration is carried out,
the slope compensation control method and the full-bridge control chip related to the slope compensation control circuit can adopt the following steps: any one of UC1846/UC1847, UC2846/UC2847, UC3846/UC3847 of Texas TI brand; other brands of chips with substantially consistent internal control principles, such as FAIRCHILD brand KA3846, may also be used, as desired.
The constant frequency clock pulse setting R-S latch outputs high level, the switch tube is connected, the primary side current of the transformer is increased, when the voltage drop Vs of the sampling resistor Rs reaches or is larger than Vg, the PWM comparator is turned over to output high level, the constant frequency clock pulse setting R-S latch is reset to output low level, the driving signal becomes low, the switch tube is turned off until the next pulse enables the switch tube to be set, and therefore pulse width detection and current control adjustment one by one can be achieved.
The voltage signal of the sawtooth oscillation waveform can be realized by the following modes:
directly obtaining from an 8-pin of a full-bridge control chip UC 3846;
as shown in fig. 3, a capacitor C1 connected between the CT pin and the GND pin of the full bridge control chip UC3846, and a resistor R1 connected between the RT pin and the GND pin determine the oscillation frequency of the oscillator; the resistor R1 is 1-500K omega, and the capacitor C1 is preferably over 100 pF; according to the resistance value of R1 and the capacitance value of C1, the frequency of the positive slope sawtooth waveform voltage signal output by the pin 8 of the full bridge control chip can be calculated, and different output frequencies can be obtained by changing the resistance value of R1 and the capacitance value of C1.
The singlechip directly provides an output sawtooth oscillation waveform voltage signal;
as shown in fig. 4, a pin PINA of the single chip microcomputer provides a rectangular pulse width voltage signal, a pin PINB provides a sawtooth waveform voltage signal, and the PINA and the PINB pin output waveform have the same frequency; the high level duration Td of the PINA pin waveform is consistent with the falling edge time in the PINB pin voltage waveform; the pin of the singlechip PINA is connected with the pin 10 (SYNC) of the full-bridge control chip for synchronization, and the dead time of the full-bridge control chip outputting two paths of complementary PWM waveforms is Td; the rising slope and the amplitude of the sawtooth waveform voltage signal output by the pin PINB can be modified arbitrarily through software programming.
(III) directly providing an output sawtooth oscillation waveform voltage signal by a waveform generating circuit;
as shown in fig. 5, the waveform generating circuit provides at least two output waveform voltage signals, the first waveform is a rectangular pulse width voltage signal, the second waveform is a sawtooth waveform voltage signal, the frequencies of the two output waveforms are consistent, the high level duration Td of the first waveform is consistent with the falling edge time of the second waveform, the voltage signal of the first waveform is input to 10 pins (SYNC) of the full-bridge control chip for synchronization, and the dead time of the two complementary PWM waveforms output by the full-bridge control chip is Td.
Finally, it should be noted that the above-mentioned list is only a specific embodiment of the present invention. It is obvious that the present invention is not limited to the above embodiments, but many variations are possible. All modifications which can be derived or suggested by a person skilled in the art from the disclosure of the present invention are to be considered within the scope of the invention.
Claims (7)
1. A slope compensation control method of a peak current control mode inverter welding power supply is characterized by comprising the following steps: the voltage signal of the sawtooth oscillation waveform output by the sawtooth waveform signal source is input and is added or subtracted with the voltage signal output by the error amplifier to obtain the voltage signal of the negative slope sawtooth waveform, and the voltage signal of the negative slope sawtooth waveform is compared with the primary side current sampling feedback signal in real time to adjust the output PWM pulse width.
2. The slope compensation control method of the peak current control mode inverter welding power supply according to claim 1, wherein: when the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with positive slope, the voltage signal of the sawtooth oscillation waveform with positive slope and the voltage signal output by the error amplifier are subjected to subtraction operation to obtain the voltage signal of the sawtooth waveform with negative slope.
3. The slope compensation control method of the peak current control mode inverter welding power supply according to claim 1, wherein: when the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with positive slope, the voltage signal of the sawtooth oscillation waveform with positive slope is firstly subjected to reverse operation to obtain a voltage signal of a sawtooth oscillation waveform with negative slope, and then is subjected to addition operation with the voltage signal output by the error amplifier to obtain the voltage signal of the sawtooth waveform with negative slope.
4. The slope compensation control method of the peak current control mode inverter welding power supply according to claim 1, wherein: when the input sawtooth waveform signal source outputs a voltage signal of a sawtooth oscillation waveform with a negative slope, the voltage signal of the sawtooth oscillation waveform with the negative slope is directly added with a voltage signal output by the error amplifier to obtain the voltage signal of the sawtooth waveform with the negative slope.
5. The slope compensation control method of the peak current control mode inverter welding power supply according to claim 1 or 2, wherein: the subtraction is performed according to the following formula: vg ═ Ve- (K1 × Vr + K2); in the formula, Vg is a voltage signal of the negative slope sawtooth waveform, Ve is a voltage signal output by the error amplifier, and Vr is a voltage signal of the positive slope sawtooth waveform; the K1 value represents the slope of the negative slope sawtooth waveform, different compensation slopes can be obtained by changing the K1 value, the K2 value represents the amplitude of the negative slope sawtooth waveform, and the magnitudes of the slope base value and the peak value can be changed by changing the K2 value.
6. The slope compensation control method of the peak current control mode inverter welding power supply according to claim 1, 3 or 4, wherein: the addition operation is performed according to the following formula: vg (-K1 × Vr + K2) + Ve; in the formula, Vg is a voltage signal of the negative slope sawtooth waveform, Ve is a voltage signal output by the error amplifier, and Vr is a voltage signal of the positive slope sawtooth waveform; the K1 value represents the slope of the negative slope sawtooth waveform, different compensation slopes can be obtained by changing the K1 value, the K2 value represents the amplitude of the negative slope sawtooth waveform, and the magnitudes of the slope base value and the peak value can be changed by changing the K2 value.
7. A slope compensation control circuit applying the slope compensation control method of claim 1, wherein: the control circuit comprises a full-bridge control chip, an error amplifier, a sampling resistor, a switching tube, an arithmetic unit, a transformer, a rectifying and filtering circuit and an isolation feedback circuit;
the reverse input end of the full-bridge control chip is connected with the output end of the arithmetic unit, so that a voltage signal Vg of a negative slope sawtooth waveform is introduced; the positive input end of the full-bridge control chip is connected with a sampling resistor, and a primary side current sampling feedback voltage signal Vs of the transformer is introduced; the input end of the arithmetic unit is connected with the output end of the error amplifier, and a voltage signal Ve output by the error amplifier is introduced, and the input end of the arithmetic unit is also connected with the oscillator, and a voltage signal Vr of a sawtooth oscillation waveform is introduced; the input end of the error amplifier is connected with the secondary side of the transformer through an isolation feedback circuit and a rectification filter circuit, and an output current feedback signal Vf of the secondary side is introduced; the primary side of the transformer is connected with the output end of the full-bridge control chip and the sampling resistor through the switching tube.
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105680708A (en) * | 2015-11-20 | 2016-06-15 | 芜湖锐芯电子科技有限公司 | Current mode synchronous rectification PWM control circuit |
| CN106921296A (en) * | 2017-04-20 | 2017-07-04 | 中国电子科技集团公司第四十三研究所 | A kind of transmitted in both directions magnetic isolation feedback circuit and its implementation |
| CN107453738A (en) * | 2017-09-17 | 2017-12-08 | 北京工业大学 | A kind of feedback signal slope compensation circuit based on digital current type PWM |
| CN109149931A (en) * | 2018-08-29 | 2019-01-04 | 北京机械设备研究所 | Slope-error compensation circuit for peak value comparison method BUCK converter |
| CN110932575A (en) * | 2019-12-25 | 2020-03-27 | 成都启臣微电子股份有限公司 | Control system and method for preventing large and small waves in flyback switching power supply |
| CN111917100A (en) * | 2020-07-08 | 2020-11-10 | 北京卫星制造厂有限公司 | Low-power-consumption output short-circuit protection circuit based on primary current sampling |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101093958A (en) * | 2006-06-23 | 2007-12-26 | 联发科技股份有限公司 | Switching Voltage Regulator and Its Slope Compensation Method |
| CN102025274A (en) * | 2009-09-18 | 2011-04-20 | Det国际控股有限公司 | Digital slope compensation for current mode control |
| CN102324843A (en) * | 2011-05-17 | 2012-01-18 | 浙江大学 | A High Precision Segmented Linear Slope Compensation Circuit |
| US20120176824A1 (en) * | 2011-01-06 | 2012-07-12 | Chris Michael Franklin | Methods and apparatus for digital peak current mode control for switch-mode power converters |
-
2014
- 2014-12-12 CN CN201410765951.8A patent/CN104539157A/en active Pending
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101093958A (en) * | 2006-06-23 | 2007-12-26 | 联发科技股份有限公司 | Switching Voltage Regulator and Its Slope Compensation Method |
| CN102025274A (en) * | 2009-09-18 | 2011-04-20 | Det国际控股有限公司 | Digital slope compensation for current mode control |
| US20120176824A1 (en) * | 2011-01-06 | 2012-07-12 | Chris Michael Franklin | Methods and apparatus for digital peak current mode control for switch-mode power converters |
| CN102324843A (en) * | 2011-05-17 | 2012-01-18 | 浙江大学 | A High Precision Segmented Linear Slope Compensation Circuit |
Non-Patent Citations (2)
| Title |
|---|
| 史永胜等: "斜坡补偿电路在峰值电流控制模式中的应用", 《液晶与显示》 * |
| 杨汝: "峰值电流控制模式中斜坡补偿电路的涉及", 《电力电子技术》 * |
Cited By (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105680708A (en) * | 2015-11-20 | 2016-06-15 | 芜湖锐芯电子科技有限公司 | Current mode synchronous rectification PWM control circuit |
| CN106921296A (en) * | 2017-04-20 | 2017-07-04 | 中国电子科技集团公司第四十三研究所 | A kind of transmitted in both directions magnetic isolation feedback circuit and its implementation |
| CN106921296B (en) * | 2017-04-20 | 2023-11-07 | 中国电子科技集团公司第四十三研究所 | Bidirectional transmission magnetic isolation feedback circuit and implementation method thereof |
| CN107453738A (en) * | 2017-09-17 | 2017-12-08 | 北京工业大学 | A kind of feedback signal slope compensation circuit based on digital current type PWM |
| CN109149931A (en) * | 2018-08-29 | 2019-01-04 | 北京机械设备研究所 | Slope-error compensation circuit for peak value comparison method BUCK converter |
| CN109149931B (en) * | 2018-08-29 | 2019-10-11 | 北京机械设备研究所 | Slope-error compensation circuit for peak value comparison method BUCK converter |
| CN110932575A (en) * | 2019-12-25 | 2020-03-27 | 成都启臣微电子股份有限公司 | Control system and method for preventing large and small waves in flyback switching power supply |
| CN110932575B (en) * | 2019-12-25 | 2022-04-08 | 成都启臣微电子股份有限公司 | Control system and method for preventing large and small waves in flyback switching power supply |
| CN111917100A (en) * | 2020-07-08 | 2020-11-10 | 北京卫星制造厂有限公司 | Low-power-consumption output short-circuit protection circuit based on primary current sampling |
| CN111917100B (en) * | 2020-07-08 | 2022-04-12 | 北京卫星制造厂有限公司 | Low-power-consumption output short-circuit protection circuit based on primary current sampling |
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Application publication date: 20150422 |