CN101910804A - Coriolis flowmeter - Google Patents

Abstract

A drive device for operating an electromagnetic oscillator is formed by: an OP amplifier which amplifies an analog input signal from an electromagnetic pickoff; an A/D converter which converts the analog signal outputted from the OP amplifier into a digital signal; a D/A converter which performs a digital process on the digital signal outputted from the A/D converter in accordance with a phase detection in a DSP and converts the digital signal of the data amount into an analog signal; and a D/A converter which performs a digital process on the digital signal outputted from the D/A converter in accordance with a phase detection in the DSP and converts the digital signal of the data amount into an analog signal.

Description

Coriolis flowmeter

Technical field

The present invention relates to by to act on stream proportional phase differential of Ke Shi (Coriolis) power of pipe and/or vibration frequency and detect the mass rate that obtains measured fluid and/or the Coriolis flowmeter of density.

Background technology

Coriolis flowmeter is the mass flowmeter that utilizes following character: the one or both ends of supporting the stream pipe that measured fluid circulates, when on the direction vertical, applying vibration with the flow direction of stream pipe around this strong point, the coriolis force and the mass rate that act on stream pipe (below, the stream pipe that is applied in vibration is called flowtube) are proportional.Coriolis flowmeter is known flowmeter, and the shape of the flowtube of Coriolis flowmeter roughly is divided into straight pipe type and crooked tubular type.

And, Coriolis flowmeter is a kind of mass flowmeter, at the mobile mensuration pipe of the measured fluid of two end supports, when alternation drives the central portion of supported mensuration pipe on the rectangular direction with respect to Support Level, pair detect with the proportional phase signal of mass rate in the two end supports portion that measures pipe and the symmetric position between the central portion.Though phase signal is and the proportional amount of mass rate that when making driving frequency fixedly, phase signal can be detected as the mistiming signal of the observation position of measuring pipe.

When the frequency that makes the alternation driving of measuring pipe equates with the intrinsic vibration frequency of measuring pipe, can access and the fixing accordingly driving frequency of the density of measured fluid, can drive with less driving energy, therefore, generally drive with natural vibration frequency recently and measure pipe, phase signal is detected as the mistiming signal.

The Coriolis flowmeter of straight pipe type constitutes, when the central portion straight tube to the supported straight tube in two ends applies the vibration of vertical direction, can between the support portion of straight tube and central portion, obtain the straight tube that causes by coriolis force displacement difference, be phase signal, detect mass rate according to this phase signal.The Coriolis flowmeter of such straight pipe type has simple, small-sized and firm structure.But, also have the problem that can not obtain high detection sensitivity.

Relative therewith, the Coriolis flowmeter of crooked tubular type can select to be used for taking out effectively the shape of coriolis force, and is more superior than the Coriolis flowmeter of straight pipe type in this respect, in fact can detect highly sensitive mass rate.And, with regard to the Coriolis flowmeter of crooked tubular type, known have the mode (for example with reference to patent documentation 1) that possesses a flowtube, the mode (for example with reference to patent documentation 2) that possesses two flowtube and make mode (for example with reference to patent documentation 3) that possesses under the flowtube state circlewise etc.

Patent documentation 1: the special fair 4-55250 communique of Jap.P.

Patent documentation 2: No. 2939242 communique of Jap.P.

Patent documentation 3: No. 2951651 communique of Jap.P.

The problem that invention will solve

But,, generally be used in combination coil and magnet as the driver element that is used to drive flowtube.With regard to the installation of this coil and magnet, be installed in the position of not setovering with respect to the direction of vibration of flowtube, this is beneficial to the minimum that departs from of the position relation that makes coil and magnet, and therefore disclosed such two flowtube side by side are installed to be the state that clips coil and magnet in above-mentioned patent documentation 2.Therefore, the distance of two relative flowtube is designed to leave at least the amount that clips coil and magnet.

Under the situation of the Coriolis flowmeter that exists in parallel respectively face two flowtube, bore is higher than the rigidity of big Coriolis flowmeter or flowtube, be necessary to improve the power of driver element, therefore big driver element must be clipped between two flowtube.Therefore, in the anchor portion as the root of flowtube, the mode that must broaden with this flowtube distance each other designs.

As shown in Figure 6, general Coriolis flowmeter 1 has the detecting device 4 and the converter 5 of the pipe 2,3 of two U word tubuloses.

Be equipped with at the mensuration pipe 2,3 of detecting device 4 and execute the device 6 that shakes, speed pickup 7 and temperature sensor 8, be connected with converter 5 respectively.

Coriolis flowmeter converter 5 constitutes and comprises: phase measurement portion 11, temperature survey portion 12 and drive control part 13.

Phase measurement portion 11 constitutes by following mode.

When carrying out the digitizing of signal Processing, the phase measurement 11 of Coriolis flowmeter is asked for the phase differential of the signal that is converted to after the signal to a pair of speed pickup carries out the A/D conversion and carries out digital conversion process.

Then, the measuring method to temperature survey portion 12 describes.

In Coriolis flowmeter, be provided with the temperature sensor that is used to manage Temperature Compensation.The general resistor-type temperature sensor that uses calculates temperature by measured resistance value.

Drive control part 13 is measured executing of the pipe device 6 that shakes and is sent the signal of the pattern of regulation to being installed in, and makes pipe 2,3 can carry out resonant vibration.

In existing driving circuit, therefore the analog driving circuits that constitute positive feedback loop that adopt, circuit component parts are difficult to form the structure of shared converter according to the shape of pipe etc. and different more.

Further, because form 12 independent structures with above-mentioned phase measurement portion, so can not the management of performance function, on the contrary be employed as a component parts of the measuring unit of the principle (phase measurement) of utilizing coriolis force, actual conditions are not expand its good function effectively.

Existing driving circuit is made of mimic channel.The structure of this existing driving circuit has structure shown in Figure 7.

Principle of work to illustrated driving circuit among Fig. 7 describes.

At first, input signal to sensitive element (pickoff) in the full-wave rectifying circuit 21 that constitutes amplitude measurement portion 20 carries out full-wave rectification, and the input signal input of the sensitive element after will carrying out full-wave rectification in this full-wave rectifying circuit 21 constitutes the low-pass filter 22 of amplitude measurement portion 20.

Like this, in amplitude measurement portion 20, ask for the amplitude of input waveform of the input signal of the sensitive element that is input to low-pass filter 22.

Reference voltage value Vref from input summer 23 in totalizer 23 deducts the amplitude of trying to achieve this amplitude measurement portion 20, the input signal with the sensitive element of input amplitude measurement section 20 in multiplier 24 multiplies each other.Then, the input signal carry out multiplying in this multiplier 24 after is transfused to and drives output with amplifier 25.Then, be output as drive signal with amplifier 25 in this driving output.

At this, do not reach under the situation of certain certain level at the amplitude of input signal, the output of beginning circuit 26 changes, and switches the gain of output amplifier 25, and it is big that the level of drive signal becomes, and input signal quickly converges on certain level.

In the existing driving circuit that drives by this way, because constitute driving circuit with mimic channel, thus have the extraordinary advantage of variation response for input signal, but also there is following shortcoming.

In existing driving circuit, because the constant of circuit fixes, so have following problem: be difficult to be designed for change drive usefulness parameter and with various types of sensors coupled, shared driving circuit.

In addition, in existing driving circuit, also has the high problem of cost because the component count of forming circuit is many.

Further, in existing driving circuit, also have following problem: for the function of the autodiagnosis of appending driving circuit etc., require to carry out the adjustment of the individual difference of circuit self, and more multipart installation etc.

Summary of the invention

The object of the present invention is to provide a kind of Coriolis flowmeter, it is by carrying out digitizing to driving circuit, and individual difference, the driving parameters of change driving circuit self, thereby can realize the design of shared driving circuit, and then the arithmetical unit inside of driving circuit can being packed into, can easily realize the function of appending of the reduction of cost and autodiagnosis etc.

The Coriolis flowmeter of a first aspect of the present invention of finishing in order to address the above problem; Make a pair of flowtube of the stream pipe that consists of mensuration usefulness in opposite directions; Make electromagnetic vibrator work by drive unit; Alternation drives above-mentioned flowtube and makes this a pair of flowtube vibration on direction of rotation; Pair detect with the proportional phase difference of the coriolis force that acts on above-mentioned a pair of flowtube and/or vibration frequency by electromagnetic sensor; Obtain thus mass flow and/or the density of measured fluid; This Coriolis flowmeter is characterised in that

Above-mentioned drive unit constitutes and comprises:

OP amplifier (operational amplifier) amplifies the analog input signal from above-mentioned electromagnetic sensor;

A/D converter will be a digital signal from the analog signal conversion of above-mentioned OP amplifier output; And

D/A converter, in DSP (digital signal processor) according to phase-shift detection to carrying out digital processing from the digital signal of above-mentioned A/D converter output, convert the digital signal of its data volume to simulating signal.

The Coriolis flowmeter of a second aspect of the present invention of finishing in order to address the above problem is characterised in that,

DSP (digital signal processor) constitutes and comprises:

Amplitude measurement portion uses FFT, and the spectrum intensity of resonance frequency is calculated amplitude as amplitude;

Zero passage (zero cross) calculating part changes how many times to the sign bit (sign bit) from the numerical data of above-mentioned A/D converter input at time per unit and measures, and its value is exported as the zero passage data;

The drive waveforms generating unit according to from the output of PLL with from the amplitude of the amplitude data decision output waveform of above-mentioned amplitude measurement portion, generates output waveform;

Frequency calculation portion is according to the phase data calculated rate from PLL output; And

PLL (phase locking circuit) carries out phase-shift detection according to the output data of above-mentioned zero passage data and above-mentioned A/D converter.

The Coriolis flowmeter of a third aspect of the present invention of finishing in order to address the above problem is characterised in that,

Constitute PLL (phase locking circuit) in the following manner: according to carry out the digital signal after the A/D conversion from the input simulating signal of above-mentioned electromagnetic sensor, the transmission frequency that utilization obtains by phase-shift detection, the synchronous transmission frequency of follow-up and input signal generates the drive signal that coil is driven.

The Coriolis flowmeter of a fourth aspect of the present invention of finishing in order to address the above problem is characterised in that,

PLL (phase locking circuit) is made of multiplier, low-pass filter and phase control type sender unit,

Above-mentioned multiplier constitutes, to comparing from the digital signal of above-mentioned A/D converter output with from the phase place of the digital output signal of above-mentioned phase control type sender unit output, export its difference signal with and signal,

Above-mentioned low-pass filter constitutes, and only takes out low frequency signal from the output signal from above-mentioned multiplier,

Above-mentioned phase control type sender unit constitutes, generate the phase data of basic output waveform according to zero passage data from above-mentioned zero passage portion, further carry out computing, generate and output waveform according to the phase place of carrying out after this computing so that become 0 mode from the output data of above-mentioned low-pass filter.

The Coriolis flowmeter of a fifth aspect of the present invention of finishing in order to address the above problem is characterised in that,

Forming circuit in the following manner: utilize the OP amplifier that is connected with the lead-out terminal of analog switch that the output signal of exporting from above-mentioned analog switch is amplified, export as drive output signal, and utilize above-mentioned analog switch to switch above-mentioned OP Amplifier Gain.

The effect of invention

According to the present invention, individual difference, driving parameters by change driving circuit self can design shared driving circuit, and the function of appending of the reduction of cost and autodiagnosis etc. can easily be realized in the arithmetical unit inside of driving circuit can also being packed into.

Description of drawings

Fig. 1 is expression PLL (Phase-Locked Loop: the figure of structural drawing phase locking circuit).

Fig. 2 is the block diagram of driving circuit of Coriolis flowmeter that utilizes the principle of PLL shown in Figure 1.

Fig. 3 utilizes DSP (Digital Signal Processor: the block diagram of the driving circuit of the Coriolis flowmeter of principle digital signal processor).

Fig. 4 is the figure of the flow process of expression synchronous feedback and frequency calculation.

Fig. 5 is the figure of the flow process of expression drive controlling.

Fig. 6 is a structural drawing of using general Coriolis flowmeter of the present invention.

Fig. 7 is the figure of principle of work that is used for the driving circuit of key diagram 6 illustrated Coriolis flowmeters.

The explanation of Reference numeral

1 Coriolis flowmeter

2,3 pipes

30PLL

31 phase comparators

32 loop filters

33VCO (Control of Voltage transmitting circuit)

34 frequency dividers

40 driving circuits

The 41OP amplifier

The 42A/D converter

The 43D/A converter

44 analog switches

50DSP (digital signal processor)

51 amplitude measurement portions

52 zero passage calculating parts

53 drive waveforms generating units

54 frequency calculation portions

55PLL

56 multipliers

57 low-pass filters

58 phase control type sender units

Embodiment

When the datumization of driving circuit, key is by driving circuit is carried out digitizing, thereby can reproduce the response of the high speed in the mimic channel on which kind of degree.If though use the arithmetical unit to drive at a high speed just can solve, the arithmetical unit cost of high-speed driving is very high, thereby produce the not high new problem of realizability.

Therefore, inventor of the present invention (PLL:Phase-Locked Loop: the driving method of consideration mode phase locking circuit) has solved the problems referred to above based on PLL by using.This PLL (PLL:Phase-Locked Loop: be phase locking circuit) by FEEDBACK CONTROL, will equate with the AC signal frequency of being imported and phase locked signal from the electronic circuit of other oscillator output.

Like this, PLL is used to make phase locked circuit, can with respect to input signal generate phase-locking signal.

Therefore this PLL can be made of arithmetical unit fairly simplely, and can carry out computing at high speed, can expect to suppress owing to the increase that driving circuit is appended to the computing load that arithmetical unit causes.

Below, be used to implement preferred implementation of the present invention with reference to description of drawings.

Fig. 1 represents PLL (Phase-Locked Loop: 30 circuit structure diagram phase locking circuit).

So-called PLL (Phase-Locked Loop: phase locking circuit), be being fixing mode, apply FEEDBACK CONTROL and make the oscillatory circuit of its vibration to the ring internal oscillator from the reference signal of outside input and phase difference variable from the output of the oscillator in the ring.

PLL30 among Fig. 1 is made of phase comparator 31, loop filter 32, VCO (Control of Voltage transmitting circuit) 33 and frequency divider 34.

Illustrated PLL30 is by FEEDBACK CONTROL among Fig. 1, will equate with the AC signal frequency of being imported and phase locked signal from the circuit of other oscillator output.

Output signal and the phase differential of input (reference frequency) of this PLL30 by VCO (voltage control oscillating circuit) 33 that frequency is changed corresponding to voltage feeds back to VCO33 and carries out synchronously.At this moment, by using, can generate the frequency multiplied signals that makes input signal with the signal behind the output signal frequency division of VCO (voltage control oscillating circuit) 33.

Fig. 2 represents to utilize the block diagram of driving circuit of Coriolis flowmeter of the principle of PLL30.

In Fig. 2, driving circuit 40 is made of OP amplifier 41, A/D converter 42, D/A converter 43 and analog switch 44.

Drive output signal can be in analog switch 44 be switched respectively and is exported the amplifier 45 that drives output usefulness to a kind of output signal and these two kinds of signals of a kind of input signal, wherein, this drive output signal be used to make constitute the stream pipe of measuring usefulness a pair of flowtube in opposite directions, make electromagnetic vibrator work by drive unit, alternation drives flowtube on sense of rotation, thereby make the signal of this a pair of flowtube vibration, this output signal is the signal from D/A converter 43, this input signal is that the proportional phase differential of coriolis force and/or the vibration frequency that produce in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detect, and from the signal of OP amplifier output.

This analog switch 44 adopts following circuit structure: it can switch the gain of the amplifier 45 that drives output usefulness simultaneously by the switching of analog switch 44.

In addition, the output signal from A/D converter 42 is input to DSP (the Digital Signal Processor: digital signal processor) 50 that is connected with A/D converter 42.

Fig. 3 represents to utilize DSP (Digital Signal Processor: the block diagram of the driving circuit of the Coriolis flowmeter of principle digital signal processor).

DSP (Digital Signal Processor: the digital signal processor) the 50th, be used in particular for the microprocessor of digital signal processing.

The inner structure of DSP50 then, is described.This DSP50 is made of amplitude measurement portion 51, zero passage calculating part 52, drive waveforms generating unit 53, frequency calculation portion 54 and PLL55 (multiplier 56, low-pass filter 57, phase control type sender unit 58).

Next illustrate that these constitute each inscape of DSP50.

(1) amplitude measurement portion 51

Amplitude measurement portion 51 is used to calculate amplitude, in the calculating of this amplitude, uses FFT, and the spectrum intensity of resonance frequency as amplitude, is used in the internal arithmetic of amplitude measurement portion 51.

(2) the zero passage calculating part 52

Zero passage calculating part 52 is used for measuring the sign bit of importing data (sin α) and changes how many times at time per unit, wherein, the electromagnetic sensor proportional phase differential of coriolis force detected, that produce when driving flowtube with alternation on sense of rotation and/or the input data of vibration frequency are exported, utilized to these input data (sin α) from A/D converter 42 a pair of flowtube.And, in this zero passage calculating part 52, the value that measures is sent to phase control type sender unit 58 as the zero passage data.

(3) the drive waveforms generating unit 53

The phase data δ that drive waveforms generating unit 53 bases are exported from phase control type sender unit 58 determines the phase place of output waveform, and according to the amplitude data X from 51 outputs of amplitude measurement portion _MAGThe amplitude of decision output waveform generates from the output waveform of drive waveforms generating unit 53 outputs in drive waveforms generating unit 53.

(4) frequency calculation portion 54

Frequency calculation portion 54 calculates according to the phase data δ from 58 outputs of phase control type sender unit and utilizes the detected and proportional vibration frequency of coriolis force of electromagnetic sensor.

(5) multiplier 56

Multiplier 56 pairs of inputs data (sin α) compare with the phase place of output signal cos δ, export low-pass filter 57 to as its difference signal and with signal, wherein, these input data (sin α) are that the proportional phase differential of coriolis force and/or the vibration frequency that produce in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detect, utilize OP amplifier 41 to amplify, the input data that are converted to digital value and obtain in A/D converter 42, this output signal cos δ is the output signal from 58 outputs of phase control type sender unit.

(6) low-pass filter 57

Low-pass filter 57 is to make from the output signal of multiplier 56 outputs to pass through frequency filter, only takes out the circuit of low-frequency signal.

Therefore, here at the composition that from the output signal of multiplier 56 outputs, only takes out difference.

(7) phase control type sender unit 58

Phase control type sender unit 58 generates the phase data δ of output waveform according to the zero passage data (α o) from zero passage portion (zero passage calculating part 52) output.

And, in this phase control type sender unit 58, output signal cos δ is outputed to multiplier 56, in this multiplier 56, to the phase place of the input data (sin α) that in A/D converter 42, are converted to digital value, compare with the phase place of output signal cos δ, export from low-pass filter 57 as its difference signal and with signal, with by this low-pass filter 57 filtering output only be that the output data Vn of the composition of difference is that 0 mode is calculated, and export the phase data δ that calculates to drive waveforms generating unit 53.

In this drive waveforms generating unit 53, generate waveform according to phase data δ from 58 outputs of phase control type sender unit, and as output data (X _AMPSin γ) exports D/A converter 43 to.

Then, DSP (Digital Signal Processor: the method that begins of 50 driving digital signal processor) is described.

Under the original state of driving circuit 40, a pair of flowtube that constitutes the stream pipe of mensuration usefulness is not in opposite directions driven by the electromagnetic vibrator alternation, and this a pair of flowtube is not vibrated.Therefore, no input signal input in the OP amplifier 41 of driving circuit 40 does not have output signal output from the OP amplifier 41 of driving circuit 40 yet, therefore, exports from amplifier 45 no drive output signal.

Herein, at the input signal of exporting and be input to A/D converter 42 from OP amplifier 41 is under the situation of 0 (amplitude is 0), utilize the gain of 44 pairs of output amplifiers 45 of analog switch shown in Figure 2 to switch, further, with from OP amplifier 41 output and the input signal that is input to A/D converter 42 directly the mode of input amplifier 45 connect, as exporting, apply initial vibration to drive coil thus from the output signal of amplifier 45 outputs.

This become to a certain degree from OP amplifier 41 output and the amplitude that is transfused to the input signal of A/D converter 42 big after, with the connection status of analog switch 44, promptly returned to the driving condition of common connection by the direct connection status of input amplifier 45 from 41 outputs of OP amplifier and the input signal that is transfused to A/D converter 42.

The computing method of each inscape of the inside of DSP50 then, are described.

(1) amplitude measurement portion

In amplitude measurement portion 51, utilize the calculating of FFT (high speed Fourier transform) to ask for real number composition and the imaginary number composition of importing data (sin α), utilize formula (1) and utilize the power spectrum of input signal to ask for amplitude X _MAGWherein these input data (sin α) are that proportional phase differential of coriolis force and/or the vibration frequency that produces in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detects, utilize the OP amplifier to amplify, in A/D converter 42, be converted to digital value and the input data that obtain.

(formula 1)

$X_{\mathrm{MAG}}=\sqrt{{\mathrm{<figure-callout\; id="2"\; label="Re"\; filenames="HPA00001087140300051.png"\; state="\{\{state\}\}">Re</figure-callout>}}^2+{\mathrm{Im}}^2}---\left(1\right)$

In the calculating of the amplitude that this amplitude measurement portion 51 carries out, use FFT (high speed Fourier transform) to calculate the spectrum intensity of resonance frequency, regard this spectrum intensity as amplitude X _MAGIn the internal arithmetic of amplitude measurement portion 51, use.

(2) zero passage

In zero passage measurement section 52, the sign bit of counting input data (sin α) signal changes how many times between 0.5sec, wherein, these input data (sin α) are that the proportional phase differential of coriolis force and/or the vibration frequency that produce in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detect, utilize the OP amplifier to amplify, in A/D converter 42, be converted to digital value and the input data signal that obtains.Then, ask for from the value roughly of the incoming frequency of the signal of A/D converter 42 output.The value of trying to achieve in this zero passage calculating part 52 is sent to phase control type sender unit 58 as phase place α o, and wherein, this phase place α o is the phase place that becomes the basis of utilizing the zero passage data computation to obtain.

In addition, the Measuring Time of zero passage is not defined as 0.5sec, for example, can be 1sec yet.

(3) multiplier 56

In the multiplier 56 of PLL55 to input data (sin α) signal with carry out multiplication from the output waveform of the output signal of phase control type sender unit 58 output and calculate, wherein, these input data (sin α) are that the proportional phase differential of coriolis force and/or the vibration frequency that produce in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detect, utilize the OP amplifier to amplify, in A/D converter 42, be converted to digital value and the input data signal that obtains.

Herein, under output the situation as cos δ of hypothesis with phase control type sender unit, the computing in the multiplier 56 (sin α cos δ) can be expressed as:

(formula 2)

$\sin \mathrm{\&alpha;}\&CenterDot;\cos \mathrm{\&delta;}=\frac{1}{2}\left(\sin (\mathrm{\&alpha;}+\mathrm{\&delta;})+\sin (\mathrm{\&alpha;}-\mathrm{\&delta;})\right)---\left(2\right)$

(4) low-pass filter 57

Then, in low-pass filter 57, low-pass filter 57, pass through wave filter, only take out the low frequency composition by low-frequency band by making from the output data of multiplier 56 outputs.By passing through in by wave filter, removed fully at the radio-frequency component of suppositive mood (2), and the coefficient 1/2 of omission formula (2) is when considering that the output Vn by wave filter is from the low-frequency band of low-pass filter 57 in this low-frequency band:

(formula 3)

Vn＝sin(α-δ)…………………………………(3)

Herein, further, when make formula (3) (α-δ) is during for very little value, and the output Vn by wave filter can be approximately from the low-frequency band of low-pass filter 57:

(formula 4)

Vn＝α-δ…………………………………(4)

Thus, control by computing repeatedly, becomes Vn ≈ 0 from the output waveform cos δ of the output signal of phase control type sender unit 58 output, and is final, becomes as the phase data δ of the basic output waveform of the operation result in the phase control type sender unit 58:

(formula 5)

δ＝α…………………………………(5)

By such computing, can calculate phase place δ with the output signal of input signal phase place α homophase.

(5) phase control type sender unit 58

In this phase control type sender unit 58, when if the output signal Vn that utilization is exported from low-pass filter 57 changes transmission frequency, then utilize the condition of the approximate expression of formula (4) according to formula (3), the output frequency of incoming frequency and phase control type sender unit becomes homophase as described above.But, under the condition that phase control is not established, for example, under can not the control original state of homophaseization or during anti-lock (anti-lock), be necessary to improve locking time (locking time).

Under these circumstances, order is V from the value of the output signal Vn of low-pass filter 57 outputs _N-1=0, according to the measurement result of zero passage calculating part 52, the output of posting a letter of the phase control of calculating substrate according to the phase place α o that becomes the basis further uses the output result of low-pass filter 57 to decide transmission frequency suc as formula (6) such phase control type sender unit.

At first, in drive waveforms generating unit 53, when the phase data δ that generates from 58 outputs of phase control type sender unit, phase data δ can ask for by through type (6).

(formula 6)

δ＝αo+Vn ………………………(6)

Based on the phase data δ that obtains from this formula (6), use the sin function, generate the waveform of posting a letter, the phase shift pi/2 can access from phase control type sender unit 58 and is output as:

(formula 7)

sin(δ+π/2)＝cosδ……………………(7)

The output cos δ that is obtained by this formula (7) is input to above-mentioned multiplier.

(6) the drive waveforms generating unit 53

From the phase information δ of phase control type sender unit 58 output with from the amplitude X of the output signal of drive waveforms generating unit 53 outputs _AMP, as output data X from amplitude measurement portion 51 _MAGFunction, can be generated as:

(formula 8)

X _AMP＝Fx(X _MAG)………………………(8)

In addition, same, the function of the δ that can ask for as through type (9) from the phase place γ of the output signal of drive waveforms generating unit 53 outputs and showing.

(formula 9)

γ＝Fa(δ)………………………………(9)

Like this, the drive signal γ by 53 outputs of drive waveforms generating unit can be expressed as:

(formula 10)

X _AMP·sinγ…………………………………(10)

Wherein, Fx, Fa represent to be used to generate the amplitude of output waveform, the function of phase place respectively.

The Fx of formula (8), and the Fa of formula (9) respectively do for oneself according to the bore of Ke Shi detecting device, pattern and different functions.

For example, the target amplitude value at the input waveform is Z, the function under the situation of the drive waveforms after generating phase deviation π (rad), be that the Fx of formula (8), the Fa of formula (9) become:

(formula 11)

Fx＝Z-X _MAG、Fa＝δ+π…………………(11)

(7) frequency calculation portion 54

Can utilize formula (12) to be expressed as from the phase data δ of the output signal of phase control type sender unit 58 output:

(formula 12)

δ＝2·π·f·t ………………………(12)

Wherein, π: circular constant

F: driving frequency

T: sampling rate.

Thus, as the formula (13), will can ask for frequency f thus from the phase data δ of the output signal of phase control type sender unit shown in Figure 3 58 output divided by 2 π t.

(formula 13)

$f=\frac{\mathrm{\&delta;}}{2\&CenterDot;\mathrm{\&pi;}\&CenterDot;t}---\left(13\right)$

If the value of the frequency f that will try to achieve by this formula (13), then can provide the resonant vibration driving of response height, the highly stable and sensor tube that Q value is high as driving frequency.

Then, according to process flow diagram shown in Figure 4, the synchronous feedback among the DSP50 and the processing of frequency calculation are described.

In Fig. 4, in step 100, to from the phase data δ of phase control type sender unit 58 output of PLL55 and from the output signal Vn of low-pass filter 57 outputs of PLL55 carry out initial setting (δ o=0, Vo=0).

Further, in step 101, call in from the data of A/D converter 42 output, in zero passage measurement section 52, the value from the data of A/D converter 42 of using that this calls in becomes the computing of the initial phase α o on basis.

Carry out initial setting (δ o=0 carrying out this step 100, Vo=0) after, in step 101, to amplifying by OP amplifier 41 and in A/D converter 42, be converted to digital value and the input data (sin α) that obtain are called in to the multiplier 56 of PLL55, and call in carrying out data to the phase control type sender unit 58 of PLL 55 from the phase data α o of zero passage measurement section 52 outputs.

Call in if in this step 101, import the data of data (sin α) and phase data α o, then in step 2, use the initial set value δ of initial phase α o, phase data δ _N-1, with from the initial set value V of the output signal V of low-pass filter 57 output of PLL55 _N-1, by following mathematical expression computing and ask for from the phase data δ n of phase control type sender unit 58 output:

δn＝δ _n-1+αo+V _n-1

If in this step 102, carry out, then in semiconductor device 103, use the initial set value δ of initial phase α o, phase data δ from the computing of the phase data δ n of phase control type sender unit 58 outputs _N-1, with from the initial set value V of the output signal V of low-pass filter 57 output of PLL55 _N-1, carry out from the output signal cos δ of phase control type sender unit 58 to multiplier 56 outputs _nThe computing of phase place.Then, the output signal cos δ that this computing is obtained _nWith the input data sin α that in A/D converter 42, is converted to digital value _nMultiply each other, utilize following mathematical expression to ask for output signal Vn in the low-pass filter 57:

V _n＝sinαn×cosδ _n

If in this step 103, ask for the output signal Vn of low-pass filter 57, then in step 104, ask for by low-frequency band by the output signal Vn of wave filter from low-pass filter 57 actual outputs.

That is, in low-pass filter 57, pass through wave filter by low-frequency band, only take out the low frequency composition, as output signal Vn from A/D converter 42 outputs by making from the output data of multiplier 56 outputs.

If in this step 104, ask for by the output signal Vn from the actual output of low-pass filter 57 of low-frequency band by wave filter, then in step 105, the value δ when using the phase place comparison operation _n, carry out the computing of frequency.

That is, in step 105, utilize frequency calculation portion 54, with from the phase data δ of phase control type sender unit 58 output divided by 2 π t, ask for frequency F by following formula:

F＝(δ _n-δ _n-1)/2π·t

Value δ during by such use phase place comparison operation _nComputing frequency F can carry out computing very at high speed.

If the value δ when in this step 105, using the phase place comparison operation _n, carry out the computing of frequency, then in step 106, to the amplitude X when the calculating of frequency F to the input signal of frequency calculation portion 54 _MAGCarry out computing.

That is, because the amplitude X of the input signal in frequency calculation portion 54 during to the calculating of frequency F _MAGCarry out computing, so can be by the amplitude X of this input signal _MAGJudge whether the cycle is correct.

The amplitude X of the input signal when the calculating of this frequency F _MAGComputing in, use FFT (high speed Fourier transform) to carry out.But the moving average of importing waveform also can access same result.

If the amplitude X in step 106 during to the input signal of frequency calculation portion 54 to the calculating of frequency F _MAGCarry out computing, then return step 101,, can more correctly carry out frequency calculation at a high speed by carrying out computing repeatedly from this step 101 to step 106.

In addition, in the synchronous feedback and frequency calculation in DSP50, as shown in Figure 4, calculate, make frequency (phase place) converge on incoming frequency by the ring of keeping usefulness repeatedly.

Lock onto the frequency different or not under the convergent situation, the result of calculation of amplitude becomes very little, therefore can utilize the result of calculation of amplitude to judge whether phase place locks in driving frequency with input signal.

Then, according to the processing of flowchart text drive controlling shown in Figure 5.

In Fig. 5, in step 200, starting DSP (Digital Signal Processor: digital signal processor) 50, carry out the initialization of DSP50, promptly, to from the phase data δ of phase control type sender unit 58 output of PLL55 and from the output signal Vn of low-pass filter 57 outputs of PLL55 carry out initial setting (δ o=0, Vo=0).

After in this step 200, carrying out initialization, in step 201, in A/D converter 42, be converted to the input data (sin α) of digital value to amplitude measurement portion 51 input of DSP50, and be percent how much to carry out computing with respect to the scope (span) of A/D converter 42 amplitude.

Promptly, in amplitude measurement portion 51, utilize the calculating of FFT (high speed Fourier transform) to ask for real number composition and the imaginary number composition of importing data (sin α), ask for the power spectrum that in A/D converter 42, is converted to the input signal of digital value, wherein, these input data (sin α) are that the proportional phase differential of coriolis force and/or the vibration frequency that produce in a pair of flowtube when utilizing electromagnetic sensor pair to drive flowtube with alternation on sense of rotation detect, utilize the OP amplifier to amplify, in A/D converter 42, be converted to data value and the input data that obtain.

In this step 201, the input data (sin α) that will be converted to digital value in A/D converter 42 are input to the amplitude measurement portion 51 of DSP50, to the amplitude X of these input data (sin α) _MAGWith respect to the scope of A/D converter 42 is percent how much to carry out computing.

If in step 201 to the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGWith respect to the scope of A/D converter 42 is percent how much to carry out computing, then in step 202, to the amplitude X of input data (sin α) _MAGWhether the scope with respect to A/D converter 42 is to judge more than 90%.

If in this step 202, judge the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 90%, then in step 203, makes from the amplitude X of drive waveforms generating unit 53 outputs _AMPBe 0.

That is, in drive waveforms generating unit 53, according to amplitude X from 51 inputs of amplitude measurement portion _MAGDecision output signal (X _AMPSin γ) amplitude generates from the output signal (X of drive waveforms generating unit 53 outputs _AMPSin γ).

If in this step 202, judge the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 90%, and in step 203, makes from the amplitude X of drive waveforms generating unit 53 outputs _AMPBe 0, then move to step 201.

If in this step 204, judge the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 10%, then in step 205, according to the amplitude X of the input waveform that is converted to digital value in A/D converter 42 (sin α) _MAG, computing and decision are from the amplitude X of drive waveforms generating unit 53 outputs _AMP

That is, in drive waveforms generating unit 53, according to the amplitude X of the input waveform of importing from amplitude measurement portion 51 that A/D converter 42, is converted to digital value (sin α) _MAG, decision output signal (X _AMPSin γ) amplitude generates from the output signal (X of drive waveforms generating unit 53 outputs _AMPSin γ).

If in this step 204, be judged to be the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 10%, and in step 205 according in A/D converter 42, being converted to the amplitude X of the input waveform (sin α) of digital value _MAGComputing is from the amplitude X of drive waveforms generating unit 53 outputs _AMP, then move to step 201.

Further, if in step 206, be judged to be the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 5%, then in step 207, makes from the amplitude X of drive waveforms generating unit 53 outputs _AMPBe maximal value.

That is, in drive waveforms generating unit 53, according to amplitude X from 51 inputs of amplitude measurement portion _MAGDecision output signal (X _AMPSin γ) amplitude generates from the output signal (X of drive waveforms generating unit 53 outputs _AMPSin γ).

If in this step 206, be judged to be the amplitude X of the input data (sin α) of the amplitude measurement portion 51 that is input to DSP50 _MAGScope with respect to A/D converter 42 is more than 5%, and in step 207, makes from the amplitude X of drive waveforms generating unit 53 outputs _AMPBe maximal value, then move to step 201.

In step 208, in A/D converter 42, be converted to the amplitude X of the input waveform (sin α) of digital value _MAGUnder the little situation, judgement can not obtain synchronously, and the analog switch 44 of switch driving circuit 40 carries out start up process.

Like this, the amplitude that is converted to the input waveform (sin α) that digital value is transfused in A/D converter 42 is under the situation more than 90% with respect to the scope of A/D converter, owing to there is the saturated possibility of input, therefore reduce to drive the amplitude of output, the size of this external input amplitude is to increase more than 5% and less than 10% o'clock to drive the amplitude of exporting, under the littler situation of value (size of input amplitude was less than 5% o'clock), being judged as does not have input signal, carries out start up process.

In addition, in Fig. 5, in the judgement of the amplitude of amplitude, judge, but this only is a concrete example with 90%, 10%, 5%.Preferably, carry out optimal selection according to native system structure and desired condition.

In addition, from the calculating of the amplitude of the drive output signal of drive waveforms generating unit 53 output, ask for amplitude poor of desired value (setting value) and input waveform, calculate drive waveforms according to this difference, so that the amplitude of input waveform becomes the mode controlling and driving output of desired value.

As mentioned above, can not obtain under the synchronous situation of feedback system, it is indefinite that frequency measurement becomes, and amplitude measurement is roughly 0, enters start up process.

Then, the characteristics based on the measuring method of the driving method of control method of the present invention and frequency thereof are described.

The characteristics of driving method

The characteristics of the maximum of this driving method are: phase-locking ability height and noise tolerance are strong.

In addition, has following advantage: because can insert DSP inside, so very miniaturization ground constitutes, further in the whole fields that relate to structurally and functionally related control system, by changing the parameter (Fx, Fa) of DSP inside, can tackle various sensors.

The characteristics of frequency measurement

As the characteristics of frequency measurement method, because for example Hilbert (Hilbert) conversion (90 ° of phase shift computings), the TAN that can get rid of trouble and cause program step quantity to increase ^-1Calculating, therefore, can make and calculate very high speed, in addition, as also narrating in the characteristics of driving method, because use low-pass filter, so have the strong characteristics of noise resistance.

As mentioned above, because can make the computing velocity high speed significantly, feedback loop is always synchronous, carries out computing, so the measurement of frequency is the stable measurement of limit convergent in native system.

For example, and in common measurement, need to compare about 100msec, reduced time extremely, be guided out the ability of 1msec.

Further, can show control function in digitizing ground, consequently, can provide the outlet of a kind of diagnosis (diagnostic) or autodiagnosis, can tackle the needs of client's expectation in the present situation to driver drives.This is very large viewpoint, has great advantage.

Claims (5)

1. Coriolis flowmeter, its a pair of flowtube that makes stream pipe that constitute to measure usefulness in opposite directions, make electromagnetic vibrator work by drive unit, alternation drives described flowtube and makes this a pair of flowtube vibration on sense of rotation, pair detect by electromagnetic sensor, obtain the mass rate and/or the density of measured fluid thus, wherein with proportional phase differential of the coriolis force that acts on described a pair of flowtube and/or vibration frequency, this Coriolis flowmeter is characterised in that

Described drive unit constitutes and comprises:

The OP amplifier amplifies the analog input signal from described electromagnetic sensor;

A/D converter will be a digital signal from the analog signal conversion of described OP amplifier output; And

D/A converter, in DSP (digital signal processor) according to phase-shift detection to carrying out digital processing from the digital signal of described A/D converter output, convert the digital signal of its data volume to simulating signal.

2. Coriolis flowmeter according to claim 1 is characterized in that,

Described DSP (digital signal processor) constitutes and comprises:

Amplitude measurement portion uses FFT, and the spectrum intensity of resonance frequency is calculated amplitude as amplitude;

The zero passage calculating part changes how many times to the sign bit from the numerical data of described A/D converter input at time per unit and measures, and its value is exported as the zero passage data;

The drive waveforms generating unit according to from the output of PLL with from the amplitude of the amplitude data decision output waveform of described amplitude measurement portion, generates output waveform;

Frequency calculation portion is according to the phase data calculated rate from PLL output; And

PLL (phase locking circuit) carries out phase-shift detection according to the output data of described zero passage data and described A/D converter.

3. Coriolis flowmeter according to claim 2 is characterized in that,

Described PLL (phase locking circuit) basis is to carrying out the digital signal after A/D changes from the input simulating signal of described electromagnetic sensor, the transmission frequency that utilization obtains by phase-shift detection is according to generating the drive signal that coil is driven with the synchronous transmission frequency of input signal.

4. according to claim 2 or 3 described Coriolis flowmeters, it is characterized in that,

Described PLL (phase locking circuit) is made of multiplier, low-pass filter and phase control type sender unit,

Described multiplier is to comparing from the digital signal of described A/D converter output with from the phase place of the digital output signal of described phase control type sender unit output, as its difference signal with and signal export,

Described low-pass filter only takes out low frequency signal from the output signal from described multiplier,

Described phase control type sender unit generates the phase data of basic output waveform according to the zero passage data from described zero passage portion, further become 0 mode and carry out computing, generate and output waveform according to carrying out the phase place that this computing obtains with output data from described low-pass filter.

5. as claim 1,2,3 or 4 described Coriolis flowmeters, it is characterized in that,

Adopt following circuit structure:

Utilize the OP amplifier that is connected with the lead-out terminal of described analog switch to amplifying, export as drive output signal from the output signal of described analog switch output,

Utilize described analog switch to switch described OP Amplifier Gain.

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