CN101461090B - Bandpass filter, high-frequency module using the same, and radio communication device using them - Google Patents

Abstract

The present invention relates to a bandpass filter having a superpassband and a passband width suitable for UWB, a high frequency module using the same, and a wireless communication device using the same. In this bandpass filter, a resonant electrode (30a, 30b, 30c) are arranged interdigitated with each other, and the input coupling electrode (40a) opposite to the resonant electrode 30a of the input stage interdigitated and interdigitated with the resonant electrode 30a of the output stage are arranged between different layers of the laminated body. Opposite output coupling electrode (40b). A flat and low-loss high-performance band-pass filter spanning the entire wide-band pass band, which cannot be realized by a band-pass filter of a 1/4 wavelength resonator in the prior art, is realized.

Description

Band-pass filter, high-frequency module using the same, and wireless communication equipment using the same

technical field

The present invention relates to a bandpass filter, a high-frequency module using it and a wireless communication machine using them, especially a bandpass filter with a very wide passband suitable for use in UWB (Ultra Wide Band), using it high-frequency modules and wireless communication devices using them.

Background technique

In recent years, UWB has attracted attention as a new communication unit. UWB is a technology that realizes large-capacity data transmission using a wide frequency band in a short distance of about 10 m. For example, according to the regulations of the FCC (Federal Communication Commission) of the United States, it is planning to use the frequency band of 3.1 to 10.6 GHz. Thus, UWB is characterized by using a very wide frequency band. In Japan and ITU-R, in order to avoid the 5.3GHz used in IEEE802.11.a, it is divided into LowBand (low band) using a band of about 3.1-4.7GHz and a band using about 6GHz-10.6GHz The HighBand (high band) standard of the field has come out. Therefore, a LowBand (low band) filter is required to have sharp attenuation characteristics in 2.5GHz and 5.3GHz.

合構造を用いた超広带域バンドパスフイルタ(使用微波传输带-CPW垂射(broadside)耦合结构的超宽带域带通滤波器)》2005年3月电子信息通信学会综合大会讲演论文集C—2—114p.147)。In recent years, research on such an ultra-wideband filter that can be used in UWB has been actively conducted. For example, it has been reported that using a band-pass filter applying the principle of a directional combiner, the passband width can be obtained in a wide-band region exceeding 100% of the band width (band width/center frequency) (for example, refer to non-patent literature "Microstop-CPW Bro-Doside"

Combination structure を を い た ultra-wideband band pass filter (Ultra-wideband band-pass filter using microstrip-CPW broadside coupling structure) "C —2—114 p. 147).

On the other hand, as a filter widely used in the prior art, a band-pass filter formed by simultaneously arranging a plurality of 1/4 wavelength stripline resonators and coupling them to each other is widely known (for example, refer to JP-A-2004-180032 Bulletin).

In addition, a plurality of resonator inner conductors (1/4 wavelength strip line type resonators) arranged in an interdigitated manner with short-connected ends and open ends shifted from each other are provided on a layer different from the layer where each resonator inner conductor is provided. In another layer, a laminated dielectric filter having a structure in which a short-terminal connection pattern between resonator outer conductors near the short-terminal ends of adjacent resonator inner conductors is embedded is widely known (for example, refer to JP-A-11-88009A ).

However, each of the above-mentioned band-pass filters has disadvantages, and is not suitable for a band-pass filter for UWB.

For example, the band-pass filter disclosed in the non-patent literature has a problem of too wide a pass bandwidth. That is to say, UWB will finally use the frequency band of 3.1-10.6 GHz, but it is planned to use the frequency band of 3.1-4.9 GHz at the beginning, and the ratio will become 45%. Therefore, the filter used by it is required to have a passband width of about 30% of the band width. In addition, the influence with W-LAN (IEEE802.11.a) needs to be considered, and attenuation in 5.15 GHz is required. Therefore, the passband width disclosed in the non-patent literature is a bandpass filter having characteristics exceeding 100% of the band width, and the passband width is too wide to be used.

In addition, the passband of the bandpass filter using the 1/4 wavelength resonator in the prior art is too narrow. The ratio band domain is also less than 10%. Therefore, it cannot be used as a bandpass filter for UWB that requires a ratio band equivalent to 30% or more.

Furthermore, in the bandpass filter disclosed with reference to JP-A-11-88009, an attenuation pole can only be generated on either the low-band side or the high-band side compared with the passband, so it cannot be used as necessary. It is used as a bandpass filter for UWB with sharp attenuation on both sides of the passband.

Contents of the invention

The present invention is developed at those problems of the prior art, and its purpose is to provide an ultra-wideband domain and use a band-pass filter with an appropriate pass-band width as a band-pass filter for UWB, use it high-frequency modules and wireless communication devices using them.

The bandpass filter of the present invention is characterized in that it comprises a laminated body (the laminated body stacks a plurality of dielectric layers),

a first ground electrode (the first ground electrode is disposed on the lower surface of the laminate and connected to a ground potential),

a second ground electrode (the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential),

A plurality of strip-shaped resonant electrodes (these strip-shaped plurality of resonant electrodes are arranged laterally in a manner of electromagnetic field coupling between one layer of the laminated body, one end thereof is respectively connected to the ground potential, and functions as a 1/4 wavelength resonator. ),

strip-shaped input-coupling electrodes (these strip-shaped input-coupling electrodes are arranged between layers different from the one layer of the laminated body, and are electromagnetically coupled to the resonant electrode of the input stage among the plurality of resonant electrodes),

strip-shaped output coupling electrodes (these strip-shaped output coupling electrodes are arranged between layers different from the one layer of the laminated body, and are electromagnetically coupled to the resonant electrode of the output stage among the plurality of resonant electrodes) bandpass filter,

The one end and the other end of each of the plurality of resonant electrodes are arranged alternately;

The input-coupling electrode is disposed opposite to a region spanning more than half of the resonant electrode in the longitudinal direction of the input stage, and a position for supplying an electric signal input from an external circuit is closer to the center than the center in the longitudinal direction. a side of said other end of the resonant electrode of the input stage;

The output-coupling electrode is disposed opposite to a region spanning more than half of the resonant electrode in the longitudinal direction of the output stage, and the position where the electric signal output to the external circuit is obtained is closer to the center than the center in the longitudinal direction. one side of the other end of the resonant electrode of the output stage.

In addition, in the present invention, it is characterized in that a ring-shaped ground electrode is arranged between the one layer, and the ring-shaped ground electrode is formed in a ring shape surrounding the circumference of the plurality of resonant electrodes, and resonates with the plurality of resonant electrodes. The one end of the electrode is connected to the ground potential connection.

Furthermore, in the present invention, it is characterized in that an auxiliary resonant electrode is arranged corresponding to each of the plurality of resonant electrodes, and the auxiliary resonant electrode has an interlayer different from the one interlayer and has a The region facing the ground electrode and the region facing the resonant electrode are arranged in such a way that the region facing the resonant electrode is connected to the other end side of the resonant electrode by a first penetrating conductor, and the first penetrating conductor penetrating through the dielectric layer between the area where the resonant electrode faces and the resonant electrode.

Furthermore, in the present invention, it is characterized in that it includes an auxiliary input-coupling electrode having an interlayer different from that of the one layer, and a layer different from the above-mentioned plurality of auxiliary resonant electrodes. Among the electrodes, the region facing the auxiliary resonant electrode connected to the resonant electrode of the input stage and the region facing the input coupling electrode are arranged, and the region facing the input coupling electrode is connected to the input coupling electrode by a second through conductor. The center of the length direction of the electrode is connected to the side closer to the other end of the resonant electrode of the input stage, and the second through conductor penetrates between the area opposite the input coupling electrode and the input coupling electrode. The dielectric layer between;

an auxiliary output coupling electrode having an auxiliary resonator connected to a resonant electrode of the output stage among the plurality of auxiliary resonant electrodes in a layer different from the one layer and further a different layer A region facing the output coupling electrode and a region facing the output coupling electrode are arranged so that the region facing the output coupling electrode is closer to the output stage than the center of the output coupling electrode in the longitudinal direction by the third through-conductor. The resonant electrode is connected to one side of the other end of the resonant electrode, and the third through-conductor penetrates through the dielectric layer between a region facing the output-coupling electrode and the output-coupling electrode.

The bandpass filter of the present invention is characterized in that it comprises a laminated body (the laminated body stacks a plurality of dielectric layers),

a first ground electrode (the first ground electrode is disposed on the lower surface of the laminate and connected to a ground potential),

a second ground electrode (the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential),

Four or more strip-shaped resonant electrodes (these strip-shaped four or more resonant electrodes are arranged laterally in a manner of electromagnetic field coupling between one layer of the laminated body, and one end is connected to the ground potential respectively, as a 1/4 wavelength resonator function),

Strip-shaped input-coupling electrodes (these strip-shaped input-coupling electrodes are disposed between layers on the upper side of the above-mentioned one layer of the laminated body, and are connected to the input stages of the four or more resonant electrodes. resonant electrode electromagnetic field coupling),

strip-shaped output-coupling electrodes (these strip-shaped output-coupling electrodes are arranged between the layers on the upper side of the above-mentioned one layer of the laminated body, and are connected to the output stages of the four or more resonant electrodes). resonant electrode electromagnetic field coupling),

A resonant electrode coupling conductor (the resonant electrode coupling conductor is arranged between the layers below the one layer of the laminated body, one end of which is interposed between the resonant electrodes of the input stage through the first through-conductor). The vicinity of the one end is connected to the ground potential, and the other end is connected to the ground potential in the vicinity of the one end of the resonant electrode of the output stage via the first through-conductor, and has a region facing each resonant electrode. , so that the resonant electrode of the input stage and the resonant electrode of the output stage are substantially equally electromagnetic field coupled), a bandpass filter,

The one end and the other end of each of the four or more resonant electrodes are arranged alternately;

The input-coupling electrode is disposed opposite to a region spanning more than half of the longitudinal direction of the resonant electrode of the input stage, and a position where an electric signal input from an external circuit is supplied is closer to the center than the longitudinal center. connected to one side of the other end of the resonant electrode of the input stage;

The output-coupling electrode is disposed opposite to an area spanning more than half of the longitudinal direction of the resonant electrode of the output stage, and the position where the electric signal output to the external circuit is obtained is closer to the center than the longitudinal direction center. connected to one side of the other end of the resonant electrode of the output stage.

In addition, in the present invention, it is characterized in that the resonant electrode coupling conductor includes an input stage coupling region opposite to the resonant electrode of the input stage, an output stage coupling region opposite to the resonant electrode of the output stage, and The input-stage coupling region and the output-stage coupling region are respectively constituted by connection regions connecting these regions orthogonally.

Furthermore, in the present invention, it is characterized in that a ring-shaped ground electrode is arranged between the one layer, and the ring-shaped ground electrode is formed in a ring shape surrounding the periphery of the four or more resonant electrodes, and is resonant with the resonant electrodes. The one end of the electrode is connected to the ground potential connection.

Furthermore, in the present invention, it is characterized in that an auxiliary resonant electrode is arranged corresponding to each of the four or more resonant electrodes, and the auxiliary resonant electrode has a layer different from the one layer and has a The region facing the ring-shaped ground electrode and the region facing the resonant electrode are arranged, and the region facing the resonant electrode is connected to the other end side of the resonant electrode by a second penetrating conductor. 2. The through-conductor penetrates through the dielectric layer between the region where the resonant electrode faces and the resonant electrode.

Furthermore, the present invention is characterized in that it includes an auxiliary input-coupling electrode having an interlayer different from the one interlayer and the interlayer on which the auxiliary resonant electrode is disposed, and having a Among the four or more auxiliary resonant electrodes, the region opposite to the auxiliary resonant electrode connected to the resonant electrode of the input stage and the region opposite to the input coupling electrode are arranged, and the region opposite to the input coupling electrode is arranged using the third The through-conductor is connected to a side closer to the other end of the resonant electrode of the input stage than the center of the input-coupling electrode in the longitudinal direction, and the third through-conductor penetrates through a region facing the input-coupling electrode. said dielectric layer between said input coupling electrode;

Auxiliary output coupling electrode, the auxiliary output coupling electrode is in a layer different from the one layer and the layer where the auxiliary resonant electrode is arranged, and has the same connection with the output stage among the four or more auxiliary resonant electrodes. The region facing the auxiliary resonant electrode connected to the resonant electrode and the region facing the output coupling electrode are arranged so that the region facing the output coupling electrode is aligned with the center of the output coupling electrode in the longitudinal direction by a fourth through conductor. For example, a side close to the other end of the resonant electrode of the output stage is connected, and the fourth through-conductor penetrates through the dielectric layer between a region facing the output-coupling electrode and the output-coupling electrode.

The bandpass filter of the present invention is characterized in that it comprises a laminated body (the laminated body stacks a plurality of dielectric layers),

a first ground electrode (the first ground electrode is disposed on the lower surface of the laminate and connected to a ground potential),

a second ground electrode (the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential),

Four or more strip-shaped first resonant electrodes (these four or more strip-shaped first resonant electrodes are arranged laterally in a mutual electromagnetic field coupling between one layer of the laminated body, and one end is connected to the ground potential respectively, as 1/4 wavelength resonator function),

Strip-shaped input-coupling electrodes (these strip-shaped input-coupling electrodes are disposed between layers on the upper side of the above-mentioned one layer of the laminated body, and are connected to the input stages of the four or more resonant electrodes. resonant electrode electromagnetic field coupling),

strip-shaped output-coupling electrodes (these strip-shaped output-coupling electrodes are arranged between the layers on the upper side of the above-mentioned one layer of the laminated body, and are connected to the output stages of the four or more resonant electrodes). resonant electrode electromagnetic field coupling),

A resonant electrode coupling conductor (the resonant electrode coupling conductor is arranged between the layers below the one layer of the laminated body, one end of which is interposed between the resonant electrodes of the input stage through the first through-conductor). The vicinity of the one end is connected to the ground potential, and the other end is connected to the ground potential in the vicinity of the one end of the resonant electrode of the output stage via the first through-conductor, and has a region facing each resonant electrode. , so that the resonant electrode of the input stage and the resonant electrode of the output stage are substantially equally electromagnetically coupled),

One or more second resonant electrodes (these one or more second resonant electrodes are located on the lower side than one interlayer of the laminated body, and between layers different from the interlayer where the resonant electrode coupling conductor is arranged, and The first resonant electrodes are arranged in parallel, one end is connected to the ground potential through a second through-conductor, and is formed in a band shape with a length different from that of the first resonant electrodes, outside the passband, at the cutoff frequency a band-pass filter with a resonant frequency nearby),

The one end and the other end of each of the four or more resonant electrodes are arranged alternately;

The input-coupling electrode is disposed opposite to a region spanning more than half of the resonant electrode in the longitudinal direction of the input stage, and a position for supplying an electric signal input from an external circuit is closer to the center than the center in the longitudinal direction. a side of said other end of the resonant electrode of the input stage;

The output-coupling electrode is disposed opposite to a region spanning more than half of the resonant electrode in the longitudinal direction of the output stage, and the position where the electric signal output to the external circuit is obtained is closer to the center than the center in the longitudinal direction. one side of the other end of the resonant electrode of the output stage.

In addition, in the present invention, it is characterized in that the resonant electrode coupling conductor includes an input stage coupling region opposite to the resonant electrode of the input stage, an output stage coupling region opposite to the resonant electrode of the output stage, and The input-stage coupling region and the output-stage coupling region are respectively constituted by connection regions connecting these regions orthogonally.

Furthermore, in the present invention, it is characterized in that: while having an even number of the first resonance electrodes, an even number of the second resonance electrodes are also provided; These second resonant electrodes are arranged point-symmetrically around the intersection of the line segment at one end of the resonant electrode of the output stage and the line segment connecting the other end of the resonant electrode of the input stage and the other end of the resonant electrode of the output stage as the center. electrode.

Furthermore, in the present invention, it is characterized in that a ring-shaped ground electrode is arranged between the one layer, and the ring-shaped ground electrode is formed in a ring shape surrounding the periphery of the four or more first resonant electrodes, and is connected with The one end of the first resonant electrode is connected to a ground potential.

Furthermore, in the present invention, it is characterized in that an auxiliary resonant electrode is arranged corresponding to each of the four or more first resonant electrodes, and the auxiliary resonant electrode is between layers different from the one layer. The region facing the annular ground electrode and the region facing the first resonant electrode are arranged, and the region facing the first resonant electrode utilizes the connection between the third via conductor and the first resonant electrode. The other end side is connected, and the third penetrating conductor penetrates through the dielectric layer between a region facing the first resonant electrode and the first resonant electrode.

Furthermore, the present invention is characterized in that it includes an auxiliary input-coupling electrode having an interlayer different from the one interlayer and the interlayer on which the auxiliary resonant electrode is disposed, and having a Among the four or more auxiliary resonant electrodes, the region opposite to the auxiliary resonant electrode connected to the resonant electrode of the input stage and the region opposite to the input-coupling electrode are arranged, and the region opposite to the input-coupling electrode utilizes the fourth The through-conductor is connected to a side closer to the other end of the resonant electrode of the input stage than the center of the input-coupling electrode in the longitudinal direction, and the fourth through-conductor penetrates through a region facing the input-coupling electrode. said dielectric layer between said input coupling electrode;

Auxiliary output coupling electrode, the auxiliary output coupling electrode is in a layer different from the one layer and the layer where the auxiliary resonant electrode is arranged, and has the same connection with the output stage among the four or more auxiliary resonant electrodes. The region facing the auxiliary resonant electrode connected to the resonant electrode and the region facing the output coupling electrode are arranged so that the region facing the output coupling electrode is aligned with the center of the output coupling electrode in the longitudinal direction by the fifth through-conductor. For example, the side close to the other end of the resonant electrode of the output stage is connected, and the fifth through-conductor penetrates through the dielectric layer between a region facing the output-coupling electrode and the output-coupling electrode.

A high-frequency module according to the present invention is characterized in that it is a band-pass filter including any one of the above configurations.

The wireless communication device of the present invention is characterized by using the bandpass filter of any one of the above structures or the high frequency module of the present invention having the above structure.

The bandpass filter of the present invention is characterized in that a plurality of band-shaped resonant electrodes functioning as quarter-wavelength resonators that are connected to the ground potential at one end are arranged laterally so as to be electromagnetically coupled to each other between one layer of the laminated body. , and the respective one ends and the other ends of the plurality of resonant electrodes are alternately arranged. Since the respective one end and the other end of the plurality of resonant electrodes are interlaced, and since the plurality of resonant electrodes are interdigitatedly coupled, the coupling under the action of the magnetic field and the coupling under the action of the electric field are added, so it is equivalent to the comb-shaped linear coupling. than, resulting in a stronger coupling. In this way, the frequency interval between the resonant frequencies in the respective resonant modes is used as the frequency interval for UWB for the purpose of obtaining a region far beyond that which can be realized by a filter using a 1/4 wavelength resonator of the prior art. For the bandpass filter, it is appropriate to have a moderate frequency interval with a wider passband than about 40% of the band.

According to the present invention, the input coupling electrode is arranged opposite to more than half of the region in the longitudinal direction of the resonant electrode across the input stage, and the position for supplying the electrical signal input from the external circuit is closer to the input than the center in the longitudinal direction. The side of the other end of the resonant electrode of the output stage; the output coupling electrode is arranged opposite to the region spanning more than half of the resonant electrode of the output stage in the longitudinal direction, and the position of obtaining the electric signal output to the external circuit is consistent with the length direction The central side is closer to the other end of the resonant electrode of the output stage compared to the other. After adopting this structure, since the input coupling electrode and the resonant electrode of the input stage are interdigitally coupled, and the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so it is the same as the case of the resonant electrodes described above. The coupling under the action of the magnetic field and the coupling under the action of the electric field add to produce a strong coupling. In this way, even if it is a wide passband that is far beyond the region that can be realized by a filter using a conventional 1/4 wavelength resonator, it is possible not to increase the frequency between the resonance frequencies of the respective resonance modes. It is possible to obtain a band-pass filter that is flat across a wide pass band and has low-loss pass characteristics due to the low insertion loss.

According to the present invention, when disposing a ring-shaped ground electrode (the ring-shaped ground electrode is formed in a ring shape surrounding a plurality of resonant electrodes between one layer, connected to one end of a plurality of resonant electrodes and connected to the ground potential) , since there are electrodes connected to the ground potential on both sides of the resonant electrode in the longitudinal direction, one end of each resonant electrode arranged alternately can be easily connected to the ground potential.

According to the present invention, an auxiliary resonant electrode is arranged corresponding to each of the plurality of resonant electrodes (the auxiliary resonant electrode is arranged so as to have a region facing the ring-shaped ground electrode, and the other end side of the resonant electrode is connected to the first through conductor. When connected), since capacitance is generated between each resonant electrode and the ring-shaped ground electrode at the opposing portion, the length of the resonant electrode can be shortened, and a small bandpass filter can be obtained.

According to the present invention, an auxiliary input coupling electrode (the auxiliary input coupling electrode has an area opposite to the auxiliary resonant electrode connected to the input stage resonant electrode is arranged and connected to the input coupling electrode) and an auxiliary output coupling electrode (the auxiliary output When the coupling electrode has a regional configuration opposite to the auxiliary resonant electrode connected to the resonant electrode of the output stage, connected to the output coupling electrode), electromagnetic field coupling is generated between the auxiliary resonant electrode connected to the resonant electrode of the input stage and the auxiliary input coupling electrode , and the electromagnetic field coupling is added between the resonant electrode of the input stage and the input coupling electrode, and the electromagnetic field coupling is also generated between the auxiliary resonant electrode connected to the resonant electrode of the output stage and the auxiliary output coupling electrode, and the resonant electrode of the output stage and The electromagnetic field coupling summation is generated between the output coupling electrodes. In this way, due to the stronger electromagnetic field coupling between the input coupling electrode and the resonant electrode of the input stage and the stronger electromagnetic field coupling between the output coupling electrode and the resonant electrode of the output stage, even a very wide passband width can be further reduced. The increase in the insertion loss at frequencies between the resonance frequencies of the respective resonance modes makes it possible to obtain a bandpass filter that is flat over a wide bandwidth and has low-loss pass characteristics.

In addition, the auxiliary input-coupling electrode is connected to the side closer to the other end of the resonant electrode of the input stage than the center of the input-coupling electrode in the longitudinal direction by using the second through-conductor; similarly, the auxiliary output-coupling electrode is connected by the third through-conductor , and the side closer to the other end of the resonant electrode of the output stage than the center in the length direction of the output coupling electrode is connected. In this way, even if the electrical signal input from the outside is supplied to the input coupling electrode through the auxiliary input coupling electrode as the medium, and the electrical signal obtained from the output coupling electrode is output to the external circuit through the auxiliary output coupling electrode as the medium, the resonance between the input coupling electrode and the input stage The electrodes are also interdigitally coupled, and the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so that strong coupling can be generated by adding coupling under the action of a magnetic field and coupling under the action of an electric field.

In the bandpass filter of the present invention, four or more strip-shaped resonant electrodes that are connected to the ground potential at one end and function as 1/4 wavelength resonators are arranged laterally between one layer of the laminate so as to be electromagnetically coupled to each other, and One end and the other end of each of the four or more resonant electrodes are alternately arranged. Since the one end and the other end of each of the four or more resonant electrodes are alternately arranged, they are coupled in an interdigitated manner, and the coupling under the action of a magnetic field and the coupling under the action of an electric field are added, so compared with comb-like linear coupling, produce stronger coupling. In this way, the frequency interval between the resonant frequencies in the respective resonant modes is used as the frequency interval for UWB for the purpose of obtaining a region far beyond that which can be realized by a filter using a 1/4 wavelength resonator of the prior art. For the bandpass filter, it is appropriate to have a moderate frequency interval with a wider passband than about 30% of the band.

Moreover, after coupling the resonant electrode of the input stage and the resonant electrode of the output stage with the resonant electrode coupling conductor whose both ends are connected to the ground potential, the resonant electrode of the input stage and the resonant electrode of the output stage become an L-shaped coupling. Since the adjacent resonant electrodes of the plurality of resonant electrodes are C-coupled, a so-called pseudo elliptic function filter can be configured. In this way, attenuation poles can be formed on both sides of the filter.

According to the present invention, the input-coupling electrode is disposed opposite to more than half of the region in the longitudinal direction of the resonant electrode across the input stage, and the position for supplying the electrical signal input from the external circuit is closer to the input stage than the center in the longitudinal direction. One side of the other end of the resonant electrode of the output stage; the output coupling electrode is disposed opposite to an area spanning more than half of the longitudinal direction of the resonant electrode of the output stage, and obtains the position of the electric signal output to the external circuit, and Compared with the center in the length direction, the side closer to the other end of the resonant electrode of the output stage. After adopting this structure, since the input coupling electrode and the resonant electrode of the input stage are interdigitally coupled, the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so it is the same as the case of the above resonant electrodes. The coupling under the action of the electric field and the coupling under the action of the magnetic field add to produce a strong coupling. Therefore, even if it is a wide and large bandwidth that is far beyond the region that can be realized by a filter using a conventional 1/4 wavelength resonator, it is possible to obtain a frequency that does not lie between the resonance frequencies of the respective resonance modes. It is a band-pass filter with an increased insertion loss, a flat entire area across a wide bandwidth, and low-loss pass characteristics.

According to the present invention, when disposing the ring-shaped ground electrode (the ring-shaped ground electrode is formed in a ring shape surrounding four or more resonant electrodes between one layer, and is connected to the ground potential connected to one end of the resonant electrode), because Since there are electrodes connected to the ground potential on both sides of the resonance electrode in the longitudinal direction, one end of each resonance electrode arranged differently from each other can be easily connected to the ground potential.

According to the present invention, an auxiliary resonant electrode is arranged corresponding to each of four or more resonant electrodes (the auxiliary resonant electrode is arranged so as to have a region facing the ring-shaped ground electrode, and is connected to the resonant electrode by the second penetrating conductor) Since capacitance is generated between each auxiliary resonant electrode and the ring-shaped ground electrode at the opposing portion, the length of each resonant electrode can be shortened, and a small bandpass filter can be obtained.

According to the present invention, an auxiliary input coupling electrode (the auxiliary input coupling electrode has an area opposite to the auxiliary resonant electrode connected to the input stage resonant electrode is arranged and connected to the input coupling electrode) and an auxiliary output coupling electrode (the auxiliary output When the coupling electrode has a regional configuration opposite to the auxiliary resonant electrode connected to the resonant electrode of the output stage, connected to the output coupling electrode), electromagnetic field coupling is generated between the auxiliary resonant electrode connected to the resonant electrode of the input stage and the auxiliary input coupling electrode , and the electromagnetic field coupling is added between the resonant electrode of the input stage and the input coupling electrode, and the electromagnetic field coupling is also generated between the auxiliary resonant electrode connected to the resonant electrode of the output stage and the auxiliary output coupling electrode, and the resonant electrode of the output stage and The electromagnetic field coupling summation is generated between the output coupling electrodes. In this way, due to the stronger electromagnetic field coupling between the input coupling electrode and the resonant electrode of the input stage and the stronger electromagnetic field coupling between the output coupling electrode and the resonant electrode of the output stage, even a very wide passband width can be further reduced. The increase in the insertion loss at frequencies between the resonance frequencies of the respective resonance modes makes it possible to obtain a bandpass filter that is flat over a wide bandwidth and has low-loss pass characteristics.

In addition, the auxiliary input-coupling electrode is connected to the side closer to the other end of the resonant electrode of the input stage than the center of the input-coupling electrode in the longitudinal direction by using the third through-conductor; similarly, the auxiliary output-coupling electrode is connected by the fourth through-conductor , and the side closer to the other end of the resonant electrode of the output stage than the center in the length direction of the output coupling electrode is connected. In this way, even if the electrical signal input from the outside is supplied to the input coupling electrode through the auxiliary input coupling electrode as the medium, and the electrical signal obtained from the output coupling electrode is output to the external circuit through the auxiliary output coupling electrode as the medium, the resonance between the input coupling electrode and the input stage The electrodes are also interdigitally coupled, and the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so that strong coupling can be generated by adding coupling under the action of a magnetic field and coupling under the action of an electric field.

In the bandpass filter of the present invention, four or more strip-shaped first resonant electrodes that are connected to the ground potential at one end and function as 1/4 wavelength resonators are arranged laterally between one layer of the laminate so as to be electromagnetically coupled to each other , and one end and the other end of each of the four or more first resonant electrodes are alternately arranged. Since one end and the other end of each of the four or more first resonant electrodes are alternately arranged, they are coupled in an interdigitated manner, and the coupling under the action of a magnetic field and the coupling under the action of an electric field are added, so it is equivalent to the comb-shaped linear coupling. than, resulting in a stronger coupling. In this way, the frequency interval between the resonant frequencies in the respective resonant modes is used as the frequency interval for UWB for the purpose of obtaining a region far beyond that which can be realized by a filter using a 1/4 wavelength resonator of the prior art. For the bandpass filter, it is appropriate to have a moderate frequency interval with a wider passband than about 30% of the band.

Furthermore, when the resonant electrode of the input stage and the resonant electrode of the output stage are coupled by a resonant electrode coupling conductor whose both ends are connected to the ground potential, the resonant electrode of the input stage and the resonant electrode of the output stage become L (inductive) coupling. In addition, since the adjacent resonance electrodes of the four or more first resonance electrodes are C (capacitively) coupled, a so-called pseudo elliptic function filter or elliptic function filter can be configured. In this way, attenuation poles can be formed on both sides of the filter (lower and higher bands than the pass band).

In addition, to function as a reaction resonator (notch filter), one or more second resonant poles (the second resonant poles have a resonant frequency near the cutoff frequency) are provided outside the passband, so that the resonant electrode coupling conductor Between the formed attenuation pole and the cut-off frequency, further forming the attenuation pole, can obtain a sharper attenuation characteristic.

According to the present invention, the input-coupling electrode is disposed opposite to more than half of the region in the longitudinal direction of the resonant electrode across the input stage, and the position for supplying the electrical signal input from the external circuit is closer to the input stage than the center in the longitudinal direction. One side of the other end of the resonant electrode of the output stage; the output coupling electrode is disposed opposite to an area spanning more than half of the longitudinal direction of the resonant electrode of the output stage, and obtains the position of the electric signal output to the external circuit, and Compared with the center in the length direction, the side closer to the other end of the resonant electrode of the output stage. After adopting this structure, since the input coupling electrode and the resonant electrode of the input stage are interdigitally coupled, the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so it is the same as the case of the above resonant electrodes. The coupling under the action of the electric field and the coupling under the action of the magnetic field add to produce a strong coupling. Therefore, even if it is far beyond the wide bandwidth of the region that can be realized by the filter using the 1/4 wavelength resonator of the prior art, it is possible to obtain the frequency that does not lie between the resonance frequencies of the respective resonance modes This is a bandpass filter that has an increased insertion loss, is flat across a wide bandwidth, and has low-loss pass characteristics.

After adopting the present invention, when arranging the ring-shaped ground electrode (the ring-shaped ground electrode is formed in a ring shape surrounding four or more resonant electrodes between one layer, and is connected to one end of the resonant electrode and connected to the ground potential), because Since there are electrodes connected to the ground potential on both sides of the resonant electrode in the longitudinal direction, one end of each resonant electrode arranged alternately can be easily connected to the ground potential.

According to the present invention, an auxiliary resonant electrode is arranged corresponding to each of four or more resonant electrodes (the auxiliary resonant electrode is arranged so as to have a region facing the ring-shaped ground electrode, and is connected to the resonant electrode by a third through-conductor) Since capacitance is generated between each auxiliary resonant electrode and the ring-shaped ground electrode at the opposing portion, the length of each resonant electrode can be shortened, and a small bandpass filter can be obtained.

According to the present invention, an auxiliary input coupling electrode (the auxiliary input coupling electrode has an area opposite to the auxiliary resonant electrode connected to the input stage resonant electrode is arranged and connected to the input coupling electrode) and an auxiliary output coupling electrode (the auxiliary output When the coupling electrode has a regional configuration opposite to the auxiliary resonant electrode connected to the resonant electrode of the output stage, connected to the output coupling electrode), electromagnetic field coupling is generated between the auxiliary resonant electrode connected to the resonant electrode of the input stage and the auxiliary input coupling electrode , and the electromagnetic field coupling is added between the resonant electrode of the input stage and the input coupling electrode, and the electromagnetic field coupling is also generated between the auxiliary resonant electrode connected to the resonant electrode of the output stage and the auxiliary output coupling electrode, and the resonant electrode of the output stage and The electromagnetic field coupling summation is generated between the output coupling electrodes. In this way, due to the stronger electromagnetic field coupling between the input coupling electrode and the resonant electrode of the input stage and the stronger electromagnetic field coupling between the output coupling electrode and the resonant electrode of the output stage, even a very wide passband width can be further reduced. The increase in the insertion loss at frequencies between the resonance frequencies of the respective resonance modes makes it possible to obtain a bandpass filter that is flat over a wide bandwidth and has low-loss pass characteristics.

In addition, the auxiliary input-coupling electrode is connected to the side closer to the other end of the resonant electrode of the input stage than the center of the input-coupling electrode in the longitudinal direction by using the fourth through-conductor; similarly, the auxiliary output-coupling electrode is connected by the fifth through-conductor , and the side closer to the other end of the resonant electrode of the output stage than the center in the length direction of the output coupling electrode is connected. In this way, even if the electrical signal input from the outside is supplied to the input coupling electrode through the auxiliary input coupling electrode as the medium, and the electrical signal obtained from the output coupling electrode is output to the external circuit through the auxiliary output coupling electrode as the medium, the resonance between the input coupling electrode and the input stage The electrodes are also interdigitally coupled, and the output coupling electrode and the resonant electrode of the output stage are also interdigitally coupled, so that strong coupling can be generated by adding coupling under the action of a magnetic field and coupling under the action of an electric field.

After adopting the present invention, in high-frequency modules and wireless communication devices, the bandpass filter of the present invention, which has a small loss of signals passing through the entire communication band, is used for filtering transmission signals and reception signals. Since the attenuation of the transmission signal and the reception signal by the band-pass filter is reduced, the reception sensitivity can be improved. In addition, since the amplification degree of the transmission signal and the reception signal can be reduced, the power consumption in the amplification circuit can be reduced. In this way, it is possible to obtain a high-frequency module and a wireless communication device with high reception sensitivity and low power consumption.

Description of drawings

The purpose, characteristics and advantages of the present invention can be further elucidated through the following detailed description and accompanying drawings.

FIG. 1 is a perspective view schematically showing the appearance of a bandpass filter according to a first embodiment of the present invention.

FIG. 2 is a schematic exploded perspective view of the bandpass filter shown in FIG. 1 .

3A to 3E are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 1 .

Fig. 4 is a sectional view taken along line A1 to A1' in Fig. 1 .

5 is a perspective view schematically showing the appearance of a bandpass filter according to a second embodiment of the present invention.

FIG. 6 is a schematic exploded perspective view of the bandpass filter shown in FIG. 5 .

7A to 7F are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 5 .

Fig. 8 is a sectional view along line A1 to A1' of Fig. 5 .

FIG. 9 is a perspective view schematically showing the appearance of a bandpass filter according to a third embodiment of the present invention.

FIG. 10 is a schematic exploded perspective view of the bandpass filter shown in FIG. 9 .

11A to 11H are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 9 .

Fig. 12 is a sectional view along line A1 to A1' of Fig. 9 .

13 is an exploded perspective view schematically showing a bandpass filter according to a fourth embodiment of the present invention.

Fig. 14 is an exploded perspective view schematically showing a bandpass filter according to a fifth embodiment of the present invention.

Fig. 15 is an exploded perspective view schematically showing a bandpass filter according to a sixth embodiment of the present invention.

FIG. 16 is an exploded perspective view schematically showing a bandpass filter according to a seventh embodiment of the present invention.

17A and 17B are explanatory views of the bandpass filter shown in FIGS. 15 and 16 .

Fig. 18 is an exploded perspective view schematically showing a bandpass filter according to an eighth embodiment of the present invention.

Fig. 19 is an exploded perspective view schematically showing a bandpass filter according to a ninth embodiment of the present invention.

20 is an exploded perspective view schematically showing a bandpass filter according to a tenth embodiment of the present invention.

21 is a block diagram showing a configuration example of a radio frequency module according to an eleventh embodiment of the present invention using the bandpass filter of the present invention and a wireless communication device using the same.

FIG. 22 is an exploded perspective view schematically showing a first modified example of the bandpass filter of the present invention.

Fig. 23 is an exploded perspective view schematically showing a second modified example of the bandpass filter of the present invention.

Fig. 24 is a graph showing simulation results of electrical characteristics of the bandpass filter of the present invention.

Fig. 25 is a graph showing simulation results of the transfer characteristics of the bandpass filter of the present invention.

FIG. 26 is a graph showing simulation results of transmission characteristics without the resonant electrode coupling conductor of FIG. 15. FIG.

FIG. 27 is a graph showing simulation results of transfer characteristics of an example of the bandpass filter of the present invention shown in FIG. 20 .

Fig. 28 is a graph showing simulation results of transmission characteristics of another example of the bandpass filter of the present invention shown in Fig. 20 .

Fig. 29 is a graph showing simulation results of transmission characteristics of another example of the bandpass filter of the present invention shown in Figs. 17A and 17B.

Fig. 30 is a graph showing simulation results of transmission characteristics of another example of the bandpass filter of the present invention shown in Fig. 18 .

FIG. 31 is a graph showing simulation results of transmission characteristics of the bandpass filter shown in FIG. 20 excluding the second resonant electrode.

Detailed ways

Hereinafter, preferred embodiments of the present invention will be described in detail with reference to the drawings.

Hereinafter, the bandpass filter of the present invention, a high-frequency module using the same, and a wireless communication device using the same will be described in detail with reference to the drawings.

(first embodiment)

FIG. 1 is a perspective view schematically showing the appearance of a bandpass filter according to a first embodiment of the present invention. FIG. 2 is a schematic exploded perspective view of the bandpass filter shown in FIG. 1 . 3A to 3E are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 1 . Fig. 4 is a sectional view taken along line A1 to A1' in Fig. 1 .

The bandpass filter of this embodiment is composed of the following components: a laminate 10 in which a plurality of dielectric layers 11 are stacked; a first ground electrode 21 arranged on the lower surface of the laminate 10; a second ground electrode 21 arranged on the upper surface of the laminate 10 Electrode 22; strip-shaped resonant electrodes 30a, 30b, 30c arranged laterally in the interlayer A of the laminated body 10; ring-shaped resonant electrodes 30a, 30b, 30c surrounded by the interlayer A of the laminated body 10. A ring-shaped ground electrode 23 connected to one end of the resonant electrodes 30a, 30b, and 30c; a strip-shaped input coupling electrode 40a disposed opposite to the resonant electrode 30a of the input stage in a different layer B of the laminate 10 ; In the interlayer B of the laminated body 10, the strip-shaped output coupling electrode 40b is arranged opposite to the resonant electrode 30b of the output stage; The first through conductors 51a, 51b, 51c of the dielectric layer 11, the auxiliary resonant electrodes 31a, 31b, 31c respectively connected to the resonant electrodes 30a, 30b, 30c; The electrodes 31a are arranged facing each other, and the auxiliary input-coupling electrode 41a connected to the resonant electrode 30a of the input stage by the second through-conductor 52a penetrating the dielectric layer 11; The auxiliary output coupling electrode 41b connected to the resonant electrode 30b of the output stage by the third through-conductor 52b penetrating the dielectric layer 11; arranged on the upper surface of the laminate 10, the auxiliary input-coupling electrode 41b is connected by the fourth through-conductor 53a penetrating the dielectric layer 11 Input terminal electrode 60a connected to 41a, and output terminal electrode 60b connected to auxiliary output coupling electrode 41b by fifth via conductor 53b penetrating dielectric layer 11, arranged on the upper surface of laminated body 10.

The first ground electrode 21 is arranged on the lower surface of the laminated body 10 ; the second ground electrode 22 is arranged on almost the entire surface of the upper surface of the laminated body 10 except around the input terminal electrode 60 a and the output terminal electrode 60 b. They are all connected to the ground potential and constitute a stripline resonator together with the resonant electrodes 30a, 30b, 30c.

The strip-shaped resonant electrodes 30a, 30b, and 30c form a stripline resonator together with the first ground electrode 21 and the second ground electrode 22, and one end is respectively connected to the ring-shaped ground electrode 23 and connected to the ground potential as 1/4 A wavelength resonator comes into play. In consideration of the effect of the electrostatic capacity generated between the auxiliary resonance electrodes 31a, 31b, 31c and the annular ground electrode 23, the respective lengths are set to be shorter than 1/4 of the wavelength in the center frequency of the bandpass filter. For example, if the center frequency is 4 GHz and the dielectric constant of the dielectric layer 11 is about 10, the length is set to be about 2 to 6 mm.

In addition, the resonant electrodes 30a, 30b, and 30c are arranged laterally in the interlayer A of the laminated body 10, and are edge-coupled with each other. The smaller the distance between the resonant electrodes 30a, 30b, and 30c, the stronger the coupling can be obtained. However, since it is not easy to manufacture if the distance is reduced, it is set to, for example, about 0.05 to 0.5 mm. Furthermore, the resonant electrodes 30a, 30b, and 30c have one end and the other end alternately arranged, interdigitatedly coupled to each other, and the coupling of the electric field and the coupling of the magnetic field are added together, and the coupling is stronger than that of the comb-like line coupling. . In this way, the resonant electrodes 30a, 30b, 30c are edge-coupled to each other and interdigitally coupled, and the frequency interval between the resonant frequencies in the respective resonant modes is designed to obtain far more than that of the existing technology. In the region where the filter of the 1/4 wavelength resonator can realize, it is appropriate for a UWB bandpass filter to have a wider passband width than about 40% of the bandband, and a moderate frequency interval.

In addition, the results of research have shown that if the resonant electrodes 30a, 30b, and 30c are interdigitally coupled and also broadside coupled to each other, since the coupling is too strong, in order to achieve a passband width of about 40% of the ratio band , is not ideal.

The ring-shaped ground electrode 23 is formed in a ring shape surrounding the resonant electrodes 30a, 30b, and 30c in the interlayer A of the laminate 10, and is connected to one end of the resonant electrodes 30a, 30b, and 30c. Furthermore, the ring-shaped ground electrode 23 itself is connected to the ground potential, and has a function of connecting one end of the resonant electrodes 30a, 30b, 30c to the ground potential. The ring-shaped ground electrode 23 makes it easy to connect one end of the interdigitated resonant electrodes 30a, 30b, and 30c to the ground electrode even when a bandpass filter is formed in a part of the module substrate. In addition, when the ring-shaped ground electrode 23 surrounds the resonant electrodes 30a, 30b, and 30c in a ring shape, leakage of electromagnetic waves generated by the resonant electrodes 30a, 30b, and 30c to the surroundings can be reduced. This effect is particularly useful in preventing adverse effects on other regions of the module substrate when a bandpass filter is formed in a part of the module substrate. Furthermore, it also has the function of shortening the length of the resonance electrodes 30a, 30b, and 30c by utilizing the capacitance generated between the ring-shaped ground electrode 23 and the auxiliary resonance electrodes 31a, 31b, and 31c to realize a compact bandpass filter.

The strip-shaped input-coupling electrode 40a is disposed in a layer B different from the layer A in which the resonant electrodes 30a, 30b, and 30c are arranged, and is disposed opposite to the resonant electrode 30a of the input stage as a whole, and spans the length of the resonant electrode 30a of the input stage. More than half of the area in the direction is opposite. In this way, the input coupling electrode 40a and the resonant electrode 30a of the input stage are broadside coupled, and the coupling is stronger than that of the edge coupling. In addition, the strip-shaped input-coupling electrode 40a is connected to the auxiliary input-coupling electrode 41a under the function of the second through-conductor 52a, and the connection point 71a between the input-coupling electrode 40a and the second through-conductor 52a is connected to the longitudinal direction of the input-coupling electrode 40a. Compared with the center of the resonant electrode 30a of the input stage, the end portion on the side closer to the other end of the resonant electrode 30a of the input stage, and the end portion on the opposite side are open ends. Furthermore, an electrical signal input from an external circuit is supplied to the input coupling electrode 40a via the connection point 71a. In this way, the input coupling electrode 40a and the resonant electrode 30a of the input stage are interdigitally coupled, and the coupling of the electric field and the coupling of the magnetic field are added, and the coupling is stronger than that of the comb-shaped linear coupling and the simple capacitive coupling. . Therefore, the input-coupling electrode 40a is broadly coupled with the input-stage resonant electrode 30a throughout its entirety, and interdigitatedly coupled, so that it is very strongly coupled with the input-stage resonant electrode 30a.

Similarly, the strip-shaped output coupling electrode 40b is arranged in a layer B different from the layer A in which the resonant electrodes 30a, 30b, and 30c are arranged, and the entire output-stage resonant electrode 30b is arranged opposite to the resonant electrode 30b of the output stage. More than half of the length direction of the area is opposite. In this way, the output coupling electrode 40b and the resonant electrode 30b of the output stage are broadside coupled, and the coupling is stronger than that of the edge coupling. In addition, the strip-shaped output coupling electrode 40b is connected to the auxiliary output coupling electrode 41b under the action of the third through conductor 52b, and the connection point 71b between the output coupling electrode 40b and the third through conductor 52b is connected to the longitudinal direction of the output coupling electrode 40b. Compared with the center of the resonant electrode 30b of the output stage, the end portion on the side closer to the other end of the resonant electrode 30b of the output stage, and the end portion on the opposite side are open ends. Then, an electrical signal input from an external circuit is supplied to the output coupling electrode 40b via this connection point 71b. In this way, the output coupling electrode 40b and the resonant electrode 30b of the output stage are interdigitally coupled, and the coupling of the electric field and the coupling of the magnetic field are added, and the coupling is stronger than that of the comb-shaped linear coupling and the simple capacitive coupling. . In this way, since the strip-shaped output coupling electrode 40b is broadside-coupled with the resonant electrode 30b of the output stage over its entirety, and coupled interdigitally, it is very strongly coupled with the resonant electrode 30b of the output stage.

In this way, because the input coupling electrode 40a and the resonant electrode 30a of the input stage are very strongly coupled, and the output coupling electrode 40b is very strongly coupled with the resonant electrode 30b of the output stage, even if it is far more than the 1/ The filter of the 4-wavelength resonator can achieve a wide passband in the region, and the insertion loss in the frequency between the resonance frequencies of the respective resonance modes can not be increased, and the entire region over the wide passband can be flattened. , and a band-pass filter with low-loss pass characteristics.

In addition, the shapes and dimensions of the input-coupling electrode 40a and the output-coupling electrode 40b are preferably set to be approximately the same as those of the input-stage resonant electrode 30a and the output-stage resonant electrode 30b. The distance between the input-coupling electrode 40a and the resonant electrode 30a of the input stage and the distance between the output-coupling electrode 40b and the resonant electrode 30b of the output stage are set at 0.01 to 0.5, for example, because the smaller the coupling, the stronger the coupling, but the more difficult it is to manufacture. about mm.

The auxiliary resonant electrodes 31a, 31b, and 31c are arranged in the interlayer B of the laminated body 10, and have regions facing the resonant electrodes 30a, 30b, 30c and regions facing the ring-shaped ground electrode 23, respectively. The area facing 30c is connected to the other end side of the resonant electrodes 30a, 30b, 30c by means of the first through-conductors 51a, 51b, 51c, and the first through-conductor penetrates through the areas opposite to the resonant electrodes 30a, 30b, 30c and the resonant electrodes 30a, 30b. , 30c between the dielectric layer 11. In the region where the auxiliary resonant electrodes 31a, 31b, 31c and the ring-shaped ground electrode 23 face each other, electrostatic capacitance is generated between the auxiliary resonant electrodes 31a, 31b, 31c and the ring-shaped ground electrode 23, so that the resonance electrodes 30a, 30b, 30c in length, a small bandpass filter can be obtained.

The auxiliary resonance electrodes 31a, 31b, and 31c are respectively connected to the other ends of the resonance electrodes 30a, 30b, and 30c, and extend therefrom to the side opposite to one end of the resonance electrodes 30a, 30b, and 30c. In this way, as will be described in detail later, the combination of the resonant electrode 30a of the input stage and the auxiliary resonant electrode 31a connected thereto and the combination of the input coupling electrode 40a and the auxiliary input coupling electrode 41a connected thereto form an overall are broadside-coupled, and also interdigitated, so that they are very strongly coupled. Similarly, the combination of the resonant electrode 30b of the output stage and the auxiliary resonant electrode 31b connected thereto and the combination of the output coupling electrode 40b and the auxiliary output coupling electrode 41b connected thereto are also broadside coupled as a whole, and also The coupling is interdigitated, so that a very strong coupling is possible.

The area of the opposing portion of the auxiliary resonant electrodes 31a, 31b, 31c and the ring-shaped ground electrode 23 is set to, for example, about 0.01 to 3 mm ² in order to balance the necessary size and the obtained electrostatic capacitance. The smaller the distance between the resonant electrodes 30a, 30b, 30c and the opposing portion of the ring-shaped ground electrode 23, the larger the capacitance can be generated. However, since it is not easy to manufacture, it is set to, for example, about 0.01 to 0.5 mm.

The auxiliary input-coupling electrode 41a is strip-shaped, and has an interlayer C different from the interlayer B in which the input-coupling electrode 40a and the output-coupling electrode 40b are arranged, and has a The area opposite to the input-coupling electrode 40a is arranged in a manner of connecting the area opposite to the input-coupling electrode 40a, and the area opposite to the input-coupling electrode 40a is connected to the input-coupling electrode 40a by a second through-conductor 52a, and the second through-conductor passes through the area opposite to the input-coupling electrode 40a The dielectric layer 11 between the region and the input coupling electrode 40a. In this way, the auxiliary input-coupling electrode 41a connected to the input-coupling electrode 40a and the auxiliary resonant electrode 31b connected to the resonant electrode 30a of the input stage are just vertically coupled, and the coupling is between the input-coupling electrode 40a and the resonant electrode 30a of the input stage. The couplings add up to become a stronger coupling as a whole.

Furthermore, since the end portion on the side opposite to the side connected to the second penetrating conductor 52a in the longitudinal direction of the auxiliary input coupling electrode 41a is connected to the input terminal electrode 60a disposed on the upper surface of the laminated body 10 by the fourth penetrating conductor 53a Therefore, the combination of the resonant electrode 30a of the input stage and the auxiliary resonant electrode 31a connected thereto, and the combination of the input coupling electrode 40a and the auxiliary input coupling electrode 41a connected thereto are broadside coupled as a whole, becoming The coupling under the action of the magnetic field and the coupling under the action of the electric field add a strong coupling. In this way, stronger coupling can be achieved than when the auxiliary input coupling electrode 41a is connected to the input terminal electrode 60a on the same side as the input coupling electrode 40a in the longitudinal direction.

耦合电极40a及输出耦合电极40b的层间B不同的层间C，具有与辅助谐振电极31b(该辅助谐振电极31b与输出级的谐振电极30b连接)相对的区域和与输出耦合电极40b相对的区域地配置，与输出耦合电极40b相对的区域利用第3贯通导体52b与输出耦合电极40b连接，第3贯通导体贯通位于输出耦合电极40b相对的区域与输出耦合电极40b之间的电介质层11。这样，与输出耦合电极40b连接的辅助输出耦合电极41b和与输出级的谐振电极30b连接的辅助谐振电极31b就被垂射耦合，该耦合与输出耦合电极40b和输出级的谐振电极30b之间的耦合相加，从而从整体上成为更加强的耦合。The auxiliary output coupling electrode 41b is strip-shaped, and is configured with the input

The interlayer C, which is different from the interlayer B of the coupling electrode 40a and the output coupling electrode 40b, has a region facing the auxiliary resonant electrode 31b (the auxiliary resonant electrode 31b is connected to the resonant electrode 30b of the output stage) and a region facing the output coupling electrode 40b. They are arranged in regions, and the region facing the output coupling electrode 40b is connected to the output coupling electrode 40b by a third through conductor 52b, and the third through conductor penetrates the dielectric layer 11 between the region facing the output coupling electrode 40b and the output coupling electrode 40b. In this way, the auxiliary output coupling electrode 41b connected to the output coupling electrode 40b and the auxiliary resonant electrode 31b connected to the resonant electrode 30b of the output stage are just vertically coupled, and the coupling is between the output coupling electrode 40b and the resonant electrode 30b of the output stage. The couplings add up to become a stronger coupling as a whole.

Furthermore, since the end portion on the side opposite to the side connected to the third penetrating conductor 52b in the longitudinal direction of the auxiliary output coupling electrode 41b is connected to the input terminal electrode 60b arranged on the upper surface of the laminated body 10 by the fifth penetrating conductor 53b . In this way, the combination of the resonant electrode 30b of the output stage and the auxiliary resonant electrode 31b connected thereto and the combination of the output coupling electrode 40b and the auxiliary output coupling electrode 41b connected thereto are interdigitally coupled as a whole, forming The coupling under the action of the magnetic field and the coupling under the action of the electric field add a strong coupling. In this way, stronger coupling can be realized than when the auxiliary output coupling electrode 41b is connected to the input terminal electrode 60b on the same side as the output coupling electrode 40b in the longitudinal direction.

In this way, the combination of the resonant electrode 30a of the input stage and the auxiliary resonant electrode 31a connected thereto and the combination of the input coupling electrode 40a and the auxiliary input coupling electrode 41a connected thereto are broadside coupled as a whole, and cross Finger coupling, very strongly coupled. Similarly, the combination of the resonant electrode 30b of the output stage and the auxiliary resonant electrode 31b connected thereto and the combination of the output coupling electrode 40b and the auxiliary output coupling electrode 41b connected thereto are also broadside coupled as a whole, and cross Finger coupling, very strongly coupled. Therefore, even with a very wide passband, it is possible to further reduce the increase in insertion loss in the frequencies located between the resonance frequencies of the respective resonance modes, and it is possible to obtain a flatter and lower loss over the entire region of the wide passband. pass characteristic bandpass filter.

In addition, the width of the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b is, for example, set to the same degree as the input-coupling electrode 40a and the output-coupling electrode 40b; the length of the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b is set, for example It is set to be slightly longer than the length of the auxiliary resonant electrodes 31a and 31b. The distance between the auxiliary input-coupling electrode 41a, the auxiliary output-coupling electrode 41b, and the auxiliary resonant electrodes 31a and 31b is preferably smaller in terms of a stronger coupling, but since it is not easy to manufacture, for example, Set to about 0.01 to 0.5 mm.

In this way, after adopting the bandpass filter of this example, it is possible to obtain far more than 40% of the ratio band of the region that can be realized by utilizing the filter of the 1/4 wavelength resonator of the prior art, throughout a very wide A high-performance band-pass filter that is flat throughout the pass band and has low-loss pass characteristics is suitable as a band-pass filter for UWB.

(second embodiment)

5 is a perspective view schematically showing the appearance of a bandpass filter according to a second embodiment of the present invention. FIG. 6 is a schematic exploded perspective view of the bandpass filter shown in FIG. 5 . 7A to 7F are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 5 . Fig. 8 is a sectional view along line A1 to A1' of Fig. 5 . In addition, in this embodiment, only the differences from the first embodiment will be described, and the same components will be given the same reference numerals, and will not be described again.

The characteristic part of the bandpass filter of this embodiment is that, for the interlayer A where the resonant electrodes 30a, 30b, 30c and the ring-shaped ground electrode 23 are arranged, the interlayer B where the auxiliary resonant electrodes 31a, 31b, 31c are arranged In the interlayer D on the opposite side, the second auxiliary resonant electrodes 32a, 32b, 32c are arranged so as to have a region facing the resonant electrodes 30a, 30b, 30c and a region facing the ring-shaped ground electrode 23, and the resonant electrodes 30a, 30b, The area facing 30c is connected to the other end side of the resonant electrodes 32a, 32b, 32c by the sixth through-conductor 54a, 54b, 54c, and the sixth through-conductor penetrates the area opposite to the resonant electrodes 30a, 30b, 30c and the resonant electrodes 30a, 30b , 30c between the dielectric layer 11.

In this way, since the capacitance between the second auxiliary resonance electrodes 32a, 32b, 32c and the annular ground electrode 23 is added to the capacitance between the auxiliary resonance electrodes 31a, 31b, 31c and the annular ground electrode 23, it is possible to make The capacitance between the open ends of the resonant electrodes 30a, 30b, 30c and the ring-shaped ground electrode 23 is further increased, and the length of the resonant electrodes 30a, 30b, 30c is further shortened, so that a smaller bandpass filter can be obtained. In addition, when the capacitance between the open ends of the resonant electrodes 30a, 30b, and 30c and the ring-shaped ground electrode 23 is not increased, compared with the bandpass filter of the first example of the embodiment of the present invention described above, Therefore, the planar shapes of the auxiliary resonant electrodes 31a, 31b, and 31c and the second auxiliary resonant electrodes 32a, 32b, and 32c can be reduced, so that even in this case, a more compact bandpass filter can be obtained. The area of the opposing portion of the second auxiliary resonant electrodes 32a, 32b, 32c and the ring-shaped ground electrode 23 is set to, for example, about 0.01 to 3 mm ² in consideration of the necessary size and the obtained electrostatic capacitance. The smaller the distance between the second auxiliary resonant electrodes 32a, 32b, 32c and the ring-shaped ground electrode 23, the larger the capacitance can be generated. However, since it is not easy to manufacture, it is set to about 0.01 to 0.5 mm, for example.

Thus, by using the band-pass filter of this example, it is possible to obtain a smaller band-pass filter than the band-pass filter of the first example of the embodiment of the present invention described above.

(third embodiment)

FIG. 9 is a perspective view schematically showing the appearance of a bandpass filter according to a third embodiment of the present invention. FIG. 10 is a schematic exploded perspective view of the bandpass filter shown in FIG. 9 . 11A to 11H are plan views schematically showing the upper and lower surfaces and between layers of the bandpass filter shown in FIG. 9 . Fig. 12 is a sectional view along line A1 to A1' of Fig. 9 . In addition, in this embodiment, only the differences from the above-mentioned embodiments will be described, and the same components will be assigned the same symbols, and will not be described again.

The characteristic part of the band-pass filter of this embodiment is that, for the layer C where the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are arranged, the input coupling electrode 40a, the output coupling electrode 40b, and the auxiliary resonant electrode 31a , 31b, 31c in the interlayer E of the laminated body 10 on the opposite side to the interlayer B, the first input-coupling strengthening electrode 81a, part of which faces the auxiliary input-coupling electrode 41a, and the first first input-coupling electrode 81a, part of which faces the auxiliary output-coupling electrode 41b, are arranged. Output coupling strengthening electrode 81b; Furthermore, for the layer E where the first input coupling strengthening electrode 81a and the first output coupling strengthening electrode 81b are arranged, it is opposite to the layer C where the auxiliary input coupling electrode 41a and auxiliary output coupling electrode 41b are arranged In the interlayer F of the stacked body 10 on the side, the second auxiliary input-coupling electrode 42a partly facing the first input-coupling strengthening electrode 81a and the second auxiliary output-coupling electrode 42b partly facing the first output-coupling strengthening electrode 81b are disposed. Furthermore, for the interlayer F where the second auxiliary input-coupling electrode 42a and the second auxiliary output-coupling electrode 42b are arranged, it is opposite to the interlayer E where the first input-coupling strengthening electrode 81a and the first output-coupling strengthening electrode 81b are arranged. In the interlayer G of the stacked body 10 on the side, the second input-coupling strengthening electrode 82a partly facing the second auxiliary input-coupling electrode 42a and the second output-coupling strengthening electrode 82b partly facing the second auxiliary output-coupling electrode 42b are disposed. .

In addition, the second auxiliary input coupling electrode 42a is connected to the fourth penetrating conductor 53a connecting the auxiliary input coupling electrode 41a and the input terminal electrode 60a, and the second auxiliary output coupling electrode 42b is connected to the fourth penetrating conductor 53a connecting the auxiliary output coupling electrode 41b and the output terminal electrode 60b. 5 through the conductor 53b. Moreover, the first input coupling strengthening electrode 81a and the second input coupling strengthening electrode 82a are connected to the auxiliary resonance electrode 31a connected to the resonance electrode 30a of the input stage by the seventh through conductor 55a; the first output coupling strengthening electrode 81b and the second The output coupling strengthening electrode 82b is connected to the auxiliary resonance electrode 31b connected to the resonance electrode 30b of the output stage through the eighth via conductor 55b.

After adopting the band-pass filter of this embodiment having such a structure, the coupling between the first input coupling strengthening electrode 81a and the second input coupling strengthening electrode 82a and the auxiliary input coupling electrode 41a and the second auxiliary input coupling electrode 42a, and the input The coupling between the coupling electrode 40a and the auxiliary input-coupling electrode 41a and the resonant electrode 30a of the input stage and the auxiliary resonant electrode 31a connected thereto are combined to form a stronger coupling. Similarly, the coupling between the first output coupling strengthening electrode 81b and the second output coupling strengthening electrode 82b and the auxiliary output coupling electrode 41b and the second auxiliary output coupling electrode 42b, and the resonance between the output coupling electrode 40b and the auxiliary output coupling electrode 41b and the output stage The coupling between the electrode 30b and the auxiliary resonant electrode 31b connected thereto is added to form a stronger coupling. In this way, even with a very wide passband width, it is possible to further reduce the increase in insertion loss in frequencies between the resonance frequencies of the respective resonance modes, and it is possible to obtain flatness over the entire region of the wide passband with low Loss of the pass characteristic of a bandpass filter.

(fourth embodiment)

13 is an exploded perspective view schematically showing a bandpass filter according to a fourth embodiment of the present invention. In addition, in this embodiment, the same code|symbol is attached|subjected to the part corresponding to the structure of the above-mentioned embodiment, and description is omitted.

The bandpass filter of this embodiment is composed of the following components: a laminated body in which a plurality of dielectric layers 11 are stacked; a first ground electrode 21 arranged on the lower surface of the laminated body; a second ground electrode 22 arranged on the upper surface of the laminated body; Band-shaped resonant electrodes (hereinafter sometimes referred to as "first resonant electrodes") 30a, 30b, 30c, and 30d arranged laterally in one layer A of the laminate; An annular ground electrode 23 formed in a ring around the electrodes 30a, 30b, 30c, and 30d and connected to one end of the resonant electrodes 30a, 30b, 30c, and 30d; Between layers B, a strip-shaped input-coupling electrode 40a arranged opposite to the resonant electrode 30a of the input stage and a strip-shaped output-coupling electrode 40b arranged opposite to the resonant electrode 30d of the output stage; The resonant electrode coupling conductor 32 having a region opposite to the respective resonant electrode is arranged in the interlayer H on the lower side of the space A. One end and the other end of the resonant electrode coupling conductor are connected to the ring-shaped through-conductor 51 as a medium. While the ground electrode 23 is connected, it is also electromagnetically coupled with the resonant electrode 30a of the input stage and the resonant electrode 30d of the output stage approximately equally; the input terminal electrode 60a connected to the input coupling electrode 40a and the output coupling electrode 60a are arranged on the laminated body. The electrode 40b is connected to the output terminal electrode 60b.

Although not shown in the figure, the first ground electrode 21 is arranged on the entire lower surface of the laminate (the back surface of the laminate layer 11 forming the resonant electrode coupling conductor 32), and the second ground electrode 22 is arranged on the surface of the laminate. The upper surface is disposed almost entirely except around the input terminal electrode 60a and the output terminal electrode 60b, which are connected to the ground potential and form a stripline resonator together with the resonant electrodes 30a, 30b, 30c, and 30d.

The strip-shaped resonant electrodes 30a, 30b, 30c, and 30d form a stripline resonator together with the first ground electrode 21 and the second ground electrode 22, and one end is connected to the ring-shaped ground electrode 23, respectively, and connected to the ground potential, thereby serving as A 1/4 wavelength resonator comes into play.

In addition, the resonant electrodes 30a, 30b, 30c, and 30d are arranged laterally in the interlayer A of the laminate, and are electromagnetically coupled (edge coupled) to each other. The smaller the distance between the resonant electrodes 30a, 30b, 30c, and 30d, the stronger the coupling can be obtained. However, since it is difficult to manufacture if the distance is reduced, it is set to, for example, about 0.05 to 0.5 mm. Furthermore, the resonant electrodes 30a, 30b, 30c, and 30d have one end and the other end alternately arranged, interdigitatedly coupled with each other, and the addition of electric field coupling and magnetic field coupling is stronger than comb-like linear coupling. ground coupling. After the resonant electrodes 30a, 30b, 30c, and 30d are edge-coupled to each other in this way, and interdigitatedly coupled, the frequency interval between the resonant frequencies in the respective resonant modes is set as the frequency interval between the resonant frequencies in the respective resonant modes, which is intended to be much higher than that of the conventional method. Moderate frequency spacing with a wider passband width than about 30% of the bandwidth is appropriate for a bandpass filter for UWB in the region where the conventional 1/4 wavelength resonator filter can realize.

In addition, research results have shown that, after the resonant electrodes 30a, 30b, 30c, and 30d are coupled interdigitally and also vertically coupled with each other, since the coupling is too strong, in order to achieve a passband width of about 30% of the ratio band, and not ideal.

In the embodiment shown in FIG. 13, four resonant electrodes are provided. However, even if the number of resonant electrodes in the present invention is four or more, as long as the loss is not large (upper limit), six resonant electrodes may be provided as will be described later.

The ring-shaped ground electrode 23 is formed in a ring shape surrounding the resonant electrodes 30a, 30b, 30c, and 30d in one interlayer A of the laminate, and is connected to one end of the resonant electrodes 30a, 30b, 30c, and 30d. Furthermore, the ring-shaped ground electrode 23 itself is connected to the ground potential, and has a function of connecting one end of the resonant electrodes 30a, 30b, 30c, and 30d to the ground potential. When one end of the resonant electrodes 30a, 30b, 30c, and 30d is directly connected to the first ground electrode 21 and the second ground electrode 22 without a through-conductor and the ring-shaped ground electrode 23 is provided, even if a bandpass filter is formed in a part of the module substrate Even in the case of an interdigitated resonant electrode 30a, 30b, 30c, and 30d, it is easy to connect one end of the resonant electrodes 30a, 30b, 30c, and 30d to the ground electrode. In addition, when the ring-shaped ground electrode 23 surrounds the resonant electrodes 30a, 30b, 30c, and 30d in a ring shape, leakage of electromagnetic waves generated by the resonant electrodes 30a, 30b, 30c, and 30d to the surroundings can be reduced. This effect is particularly useful in preventing adverse effects on other regions of the module substrate when a bandpass filter is formed in a part of the module substrate.

The strip-shaped input coupling electrode 40a is located in a layer different from the layer A in which the resonant electrodes 30a, 30b, 30c, and 30d are arranged (in the upper layer than the layer A in which the resonant electrodes 30a, 30b, 30c, and 30d are arranged). ) B is arranged to face the resonant electrode 30a of the input stage as a whole, and face to an area over half or more of the longitudinal direction of the resonant electrode 30a of the input stage. In this way, the input coupling electrode 40a and the resonant electrode 30a of the input stage are broadside coupled, and the coupling is stronger than that of the edge coupling. In addition, the connection point between the strip-shaped input-coupling electrode 40a and the through-conductor 50 is located at the end on the side closer to the other end of the resonant electrode 30a of the input stage than the center of the input-coupling electrode 40a in the longitudinal direction, and on the opposite side. The ends become open ends. Furthermore, an electrical signal input from an external circuit is supplied to the input coupling electrode 40a via this connection point. In this way, the input coupling electrode 40a and the resonant electrode 30a of the input stage are interdigitally coupled, and the coupling of the electric field and the coupling of the magnetic field are added, and the coupling is stronger than that of the comb-shaped linear coupling and the simple capacitive coupling. . Therefore, the input-coupling electrode 40a is broadly coupled with the input-stage resonant electrode 30a throughout its entirety, and interdigitatedly coupled, so that it is very strongly coupled with the input-stage resonant electrode 30a. In addition, the same applies to the output.

In this way, because the input coupling electrode 40a and the resonant electrode 30a of the input stage are very strongly coupled, and the output coupling electrode 40b is very strongly coupled with the resonant electrode 30b of the output stage, even if it is far more than the 1/ The filter of the 4-wavelength resonator can achieve a wide passband in the region, and the insertion loss in the frequency between the resonance frequencies of the respective resonance modes can not be increased, and the entire region over the wide passband can be flattened. , and a band-pass filter with low-loss pass characteristics.

The resonant electrode coupling conductor 32 is arranged in an interlayer different from the interlayer A in which the resonant electrodes 30a, 30b, 30c, and 30d are arranged (in a layer lower than the interlayer A in which the resonant electrodes 30a, 30b, 30c, and 30d are arranged). between) H, and one end is connected to the ground potential (annular ground electrode 23) in the vicinity of one end of the resonant electrode 30a of the input stage through the first through-conductor 51 as a medium, and the other end is through the first through-conductor 51 as a medium, In the vicinity of one end of the resonant electrode 30d of the output stage, it is connected to the ground potential (annular ground electrode 23), and has a region facing each resonant electrode so that the resonant electrode 30a of the input stage and the resonant electrode 30d of the output stage are approximately Equally electromagnetic field coupling. In the embodiment shown in FIG. 13, the resonant electrode coupling conductor 32 consists of an input pole coupling region opposite to the resonant electrode 30a of the input stage, an output pole coupling region opposite to the resonant electrode 30d of the output stage, and orthogonal to these regions respectively. The connection area connecting the input pole coupling area and the output pole coupling area to the ground constitutes a so-called "crank structure". With this structure, the side close to one end (short-circuit end) of the resonant electrode 30a of the input stage and the side close to one end (short-circuit end) of the resonant electrode 30d of the output stage are coupled together. Here, from the viewpoint of filter design, it is preferable to form the resonant electrode coupling conductor 32 in a point-symmetrical shape centering on a point equidistant from one end and the other end of the resonant electrode coupling conductor 32 . In particular, the shape shown in FIG. 13 is preferably used. However, other shapes can also be used, as long as they are point-symmetrical.

In this way, one end is connected to the ring-shaped ground electrode 23 on the side near one end (short-circuit end) of the resonant electrode 30a of the input stage, and the other end is connected to the side near one end (short-circuit end) of the resonant electrode 30d of the output stage. The resonant electrode coupling conductor 32 connected to the ring-shaped ground electrode 23 is coupled to one side near one end (short-circuit end) of the resonant electrode 30a of the input stage and one end (short-circuit end) of the resonant electrode 30d of the output stage. Together, the resonant electrode of the input stage and the resonant electrode of the output stage become L (inductive) coupling. On the other hand, adjacent resonance electrodes (between 30a and 30b, between 30b and 30c, and between 30c and 30d) of the resonance electrodes are also C (capacitively) coupled. This configuration constitutes a so-called elliptic function filter. In this way, one attenuation pole can be formed on each of the low-band side and the high-band side compared with the passband. Thus, it is possible to have filter characteristics with sharp attenuation outside the passband.

In addition, as an example of an elliptic function filter, for example, in the case of four-stage resonators, as long as the mutual coupling between the first-stage and second-stage resonators is (+), the mutual coupling between the second-stage and third-stage resonators The coupling is (+), the coupling between the third-level and fourth-level resonators is (+), and the coupling between the first-level and fourth-level resonators is (one), so it can be in the passband The lower side and the higher side of the comparison form an attenuation pole.

In this way, after adopting the bandpass filter of the present embodiment, it is possible to obtain a ratio band of 30% far beyond the region that can be realized by a filter using a conventional 1/4 wavelength resonator, and a very wide range. It is suitable as a bandpass filter for UWB that has a flat entire area of the passband and has low-loss pass characteristics, and has attenuation poles on the low-range side and high-range side compared with the passband, and is high-performance. bandpass filter.

(fifth embodiment)

FIG. 14 is an exploded perspective view schematically showing a bandpass filter according to a sixth embodiment of the present invention. The only structural difference from the fourth embodiment shown in FIG. 13 is that the resonant electrodes are made up of six stages of 30a, 30b, 30c, 30d, 30e, and 3f.

Also in the bandpass filter of this embodiment, one end is connected to the ring-shaped ground electrode 23 in the vicinity of one end (short-circuit end) of the resonant electrode 30a of the input stage through the first through-conductor 51, and then through the first through-conductor 51. The conductor 51 is used as a medium to connect the other end of the resonant electrode coupling conductor 32 connected to the annular ground electrode 23 near one end (short-circuit end) of the resonant electrode 30f of the output stage, so that one end (short-circuit end) of the resonant electrode 30a of the input stage is close to After one side of the resonant electrode 30d of the input stage and the resonant electrode of the output stage are coupled together, the resonant electrode of the input stage and the resonant electrode of the output stage become L (inductive) coupling. On the other hand, adjacent resonance electrodes (between 30a and 30b, between 30b and 30c, between 30c and 30d, between 30d and 30e, and between 30e and 30f) between the resonance electrodes are also C (capacitively) coupled. This configuration constitutes a so-called analog elliptic function filter. In this way, one attenuation pole can be formed on each of the low-band side and the high-band side compared with the passband. Thus, it is possible to have filter characteristics with sharp attenuation outside the passband.

In addition, in the so-called analog elliptic function filter, for example, in the case of 6-stage resonators, as long as the coupling between the first-stage and second-stage resonators is (+), the coupling between the second-stage and third-stage resonators is Resonance of (+), 3rd and 4th resonators coupled to each other (+), 4th and 5th resonators coupled to each other (+), 5th and 6th resonators If the coupling between the resonators is (+), and the coupling between the first and sixth resonators is (-), attenuation poles can be formed on the low and high side of the passband. Here, (+) is equivalent to C, and (-) is equivalent to L.

In this way, by employing the band-pass filter of this embodiment, it is possible to obtain a sharper band-pass filter than the band-pass filter of the fourth embodiment of the present invention described above.

(sixth embodiment)

Fig. 15 is an exploded perspective view schematically showing a bandpass filter according to a sixth embodiment of the present invention. The structural difference from the fourth embodiment shown in FIG. 13 is that in the interlayer B above the interlayer A in which the resonant electrodes 30a, 30b, 30c, and 30d and the ring-shaped ground electrode 23 are arranged, a The area opposite to the annular ground electrode 23 and the auxiliary resonant electrodes 31a, 31b, 31c, 31d in the area opposite to the resonant electrodes 30a, 30b, 30c, 30d; Auxiliary resonant electrodes 31 a , 31 b , 31 c , 31 d having regions facing the ring-shaped ground electrode 23 and regions facing the resonant electrodes 30 a , 30 b , 30 c , and 30 d are arranged in the interlayer D on the lower side of the interlayer A of the electrodes 23 . Furthermore, the resonant electrodes 30 a , 30 b , 30 c , and 30 d and the auxiliary resonant electrodes 31 a , 31 b , 31 c , and 31 d are connected by a second via conductor 52 penetrating through the dielectric layer 11 . In this way, since the capacitances between the auxiliary resonant electrodes 31a, 31b, 31c, and 31d and the annular ground electrode 23 are added, there is a gap between the other ends (open ends) of the resonant electrodes 30a, 30b, 30c, and 30d and the ground potential. The electrostatic capacitance is further increased, the length of the resonant electrodes 30a, 30b, and 30c can be shortened, and a smaller bandpass filter can be obtained.

Furthermore, in the sixth embodiment shown in FIG. 15 , a pair of auxiliary resonant electrodes 31 a , 31 b , 31 c , and 31 d are provided up and down. However, if the amount of shortening is small compared to the above-mentioned embodiment, only one of the upper side and the lower side of the interlayer A where the resonant electrodes 30a, 30b, 30c, and 30d and the ring-shaped ground electrode 23 are arranged can be used. A structure in which auxiliary resonant electrodes 31a, 31b, 31c, and 31d are provided.

In addition, along with the formation of the auxiliary resonant electrodes 31a and 31d, the interlayer A between the resonant electrodes 30a, 30b, 30c, and 30d and the ring-shaped ground electrode 23 and the interlayer A between the auxiliary resonant electrodes 31a, 31b, 31c, and 31d are arranged. Between layers C where B and D are different, an auxiliary input coupling electrode 41a is provided corresponding to the input coupling electrode 40a, and an auxiliary output coupling electrode 41b is also provided corresponding to the output coupling electrode 40b.

In this manner, by employing the band-pass filter of this embodiment, it is possible to obtain a smaller-sized band-pass filter than the band-pass filter of the fourth embodiment of the present invention described above.

In addition, the auxiliary input-coupling electrode 41a shown in FIG. 15 is strip-shaped and arranged to have a region facing the auxiliary resonant electrode 31a and a region facing the input-coupling electrode 40a, and the region facing the input-coupling electrode 40a is formed by a third through The conductor 53 is connected to the input-coupling electrode 40a, and the third through-conductor penetrates the dielectric layer 11 between the region facing the input-coupling electrode 40a and the input-coupling electrode 40a. Thus, the auxiliary input coupling electrode 41a and the auxiliary resonant electrode 31b are broadside coupled, and this coupling is added to the coupling between the input coupling electrode 40a and the resonant electrode 30a of the input stage, resulting in stronger coupling as a whole.

Similarly, the auxiliary output coupling electrode 41b is strip-shaped, and is arranged to have a region facing the auxiliary resonant electrode 31d and a region facing the output coupling electrode 40b. The electrodes 40b are connected, and the fourth penetrating conductor 54 penetrates the dielectric layer 11 between the region facing the output coupling electrode 40b and the output coupling electrode 40b. In this way, the auxiliary output coupling electrode 41b is broadside coupled with the auxiliary resonant electrode 31d, and this coupling is added to the coupling between the output coupling electrode 40b and the resonant electrode 30b of the output stage, thereby becoming a stronger coupling as a whole.

In this way, the combination of the resonant electrode 30a of the input stage and the auxiliary resonant electrode 31a connected thereto and the combination of the input coupling electrode 40a and the auxiliary input coupling electrode 41a connected thereto are broadside coupled as a whole, and cross Finger coupled and thus very strongly coupled. Similarly, the combination of the resonant electrode 30b of the output stage and the auxiliary resonant electrode 31b connected thereto and the combination of the output coupling electrode 40b and the auxiliary output coupling electrode 41b connected thereto are also broadside coupled as a whole, and cross Finger coupled and thus very strongly coupled. Therefore, even with a very wide passband, it is possible to further reduce the increase in insertion loss in the frequencies located between the resonance frequencies of the respective resonance modes, and it is possible to obtain a flatter and lower loss over the entire region of the wide passband. pass characteristic bandpass filter.

(seventh embodiment)

FIG. 16 is an exploded perspective view schematically showing a bandpass filter according to a seventh embodiment of the present invention. In this embodiment, the same reference numerals are assigned to the same components as those in the above-mentioned embodiment, and the description thereof may not be repeated. The band-pass filter of this embodiment is similar to the band-pass filter of the embodiment shown in FIG. The second resonant electrodes 33a and 33b are formed.

The bandpass filter of this embodiment is composed of the following components: a laminated body in which a plurality of dielectric layers 11 are stacked; a first ground electrode 21 arranged on the lower surface of the laminated body; a second ground electrode 22 arranged on the upper surface of the laminated body; Strip-shaped first resonant electrodes 30a, 30b, 30c, and 30d arranged laterally in one layer A of the laminate; The ring-shaped ground electrode 23 formed in a ring around it and connected to one end of the first resonant electrodes 30a, 30b, 30c, and 30d; the interlayer B on the upper side of one interlayer A of the laminated body, and the input stage The strip-shaped input-coupling electrode 40a arranged opposite to the resonant electrode 30a of the output stage and the strip-shaped output-coupling electrode 40b arranged opposite to the resonant electrode 30d of the output stage; the layer on the lower side than one interlayer A of the laminated body The resonant electrode coupling conductor 32 having a region opposite to the respective resonant electrode disposed between H, one end and the other end of the resonant electrode coupling conductor are connected to the ring-shaped ground electrode 23 through the first through-conductor 51 as an intermediary, It is also electromagnetically coupled with the resonant electrode 30a of the input stage and the resonant electrode 30d of the output stage substantially equally; the second resonant electrodes 33a and 33b are formed in the interlayer I below the interlayer H where the resonant electrode coupling conductor 32 is arranged. The second resonant electrodes 33a, 33b are arranged parallel to the first resonant electrodes 30a, 30b, 30c, 30d, one end is connected to the ground potential through the second through conductor, and the length is the same as that of the first resonant electrodes 30a, 30b, 30c, 30d is different; the input terminal electrode 60a connected to the input coupling electrode 40a and the output terminal electrode 60b connected to the output coupling electrode 40b are arranged on the upper surface of the laminated body.

Although not shown in the figure, the first ground electrode 21 is arranged on the entire lower surface of the laminate (the back surface of the laminate layer 11 where the second resonant electrodes 33a and 33b are formed), and the second ground electrode 22 is placed on the laminate. The upper surface of the body is disposed almost entirely except around the input terminal electrode 60a and the output terminal electrode 60b, and they are all connected to the ground potential, and form a stripline resonator together with the first resonant electrodes 30a, 30b, 30c, and 30d. .

In the embodiment shown in FIG. 16 , four first resonant electrodes are provided, but the number of first resonant electrodes of the present invention may be four or more, as long as the number (upper limit) of the loss is not large, For example, six resonant electrodes as described later may be provided.

The strip-shaped second resonant electrodes 33a, 33b are arranged in parallel to the first resonant electrodes 30a, 30b, 30c, 30d in the interlayer I below the interlayer H where the resonant electrode coupling conductor 32 is arranged, and have a length equal to The first resonant electrodes 30a, 30b, 30c, and 30d are different (in this embodiment, the length is short). In addition, one end of the second resonant electrodes 33a and 33b is connected to the ground potential (ring-shaped ground electrode 23 ) through the second penetrating conductor 52 as a medium. Specifically, the second resonant electrode 33a is connected to the vicinity of one end of the first resonant electrode 30b through the second penetrating conductor 52; connected near one end. With this structure, it has a resonant frequency near the cutoff frequency just outside the passband, and functions as a so-called reaction resonator (notch filter). In addition, the so-called "outside of the passband, near the cutoff frequency" refers to the band between the attenuation level formed by the resonant electrode coupling conductor 32 and the cutoff frequency; the so-called "attenuation level formed by the resonant electrode coupling conductor 32" means that In the structure in which the second resonant electrodes 33a and 33b are not arranged, the attenuation pole is formed on the low-band side or the high-band side of the passband.

Here, there may be at least one second resonant electrode, as long as the filter loss is not large. However, since it is formed point-symmetrically with respect to the center of the filter forming region, it becomes convenient to design the filter after it becomes a symmetrical equivalent circuit in an ordinary filter, so it is preferable to use a circular ground electrode 23 surrounded by The second resonant electrodes are arranged point-symmetrically with respect to the center of the filter region. Therefore, the bandpass filter of the present invention is preferably provided with an even number (four in this embodiment) of first resonant electrodes as shown in FIG. 16 and an even number (four in this embodiment) 2) the second resonant electrode; viewed from above, the line segment connecting one end of the resonant electrode 30a of the input stage and one end of the resonant electrode 30d of the output stage and the other end of the resonant electrode 30a of the input stage and the resonant electrode of the output stage The intersection point of the line segments at the other end of 30d is used as the center, and arranged point-symmetrically.

In addition, in this embodiment, the second resonant electrodes 33a, 33b are formed shorter than the first resonant electrodes 30a, 30b, 30c. However, this length depends on whether the attenuation pole is formed on the low-band side or the high-band side compared with the passband. That is, when the attenuation pole is formed on the low-range side compared with the passband, it is formed longer than the first resonant electrodes 30a, 30b, 30c; The resonance electrodes 30a, 30b, and 30c are formed short. In this example, since the attenuation pole is formed on the higher side than the passband, it is formed shorter than the first resonant electrodes 30a, 30b, and 30c.

In addition, in the present embodiment, the interlayer I where the second resonant electrodes 33a and 33b are arranged is lower than the interlayer H where the resonant electrode coupling conductor 32 is arranged, but the arrangement may be reversed.

With the configuration in which the strip-shaped second resonance electrodes 33a, 33b are provided in this way, sharper attenuation characteristics can be obtained than those obtained in a configuration in which the second resonance electrodes 33a, 33b are not arranged.

Here, when providing the strip-shaped second resonant electrodes, it is necessary to consider the amount of coupling between the second resonant electrodes and the first resonant electrodes. Specifically, when the second resonant electrode is longer than the first resonant electrode, the ratio of the length (area) overlapping the first resonant electrode with respect to the entire longitudinal direction of the second resonant electrode is small, so in order to obtain the amount of coupling , it is best to arrange it close to the first resonant electrode that has an interdigitated relationship (opposite to the side connected to the ground potential) when viewed from above. The resonant electrodes are arranged facing each other. On the other hand, when the second resonant electrode is shorter than the first resonant electrode, since the entire length direction of the second resonant electrode overlaps the first resonant electrode, in order to reduce the amount of coupling, it is preferable to have comb lines close to the top when viewed from above. (The same side connected to the ground potential) is arranged so that the first resonant electrode in the relationship is arranged, and it is particularly preferable that all areas of the second resonant electrode do not face the first resonant electrode in which comb lines exist when viewed from above. It is disposed close to the first resonant electrode having a relationship of comb lines to a certain extent. In addition, the adjustment of the coupling amount is also affected by the thickness of the dielectric layer interposed between the first resonant electrode and the second resonant electrode, the width of each resonant electrode, the area of the opposing portion, and the like. Therefore, it is preferable to place the second resonant electrode at a position where a desired amount of coupling can be obtained in consideration of these factors.

In this embodiment, the second resonant electrode 33a is arranged to face the first resonant electrode 30b when viewed from above, and the second resonant electrode 33b is arranged to face the first resonant electrode 30c when viewed from above.

Next, a case where the attenuation characteristic is improved by adjusting the coupling amount of the second resonant electrode will be described. For example, as shown in FIG. 28, when the required coupling amount cannot be obtained, although a sharp attenuation characteristic can be obtained in a band outside the passband and very close to the cutoff frequency, the attenuation formed by the second resonant electrode However, the high domain side of the pole (attenuation pole) produces a jump. On the other hand, as shown in FIG. 27 , when a desired coupling amount is obtained, the jitter shown in FIG. 28 does not occur, and a sharp attenuation characteristic without jitter can be obtained.

In this way, after adopting the band-pass filter of the present embodiment, it is possible to obtain a ratio band of 30% far exceeding the region that can be realized by a filter using a conventional 1/4 wavelength resonator, and it is very wide. The wide passband has a flat and low-loss pass characteristic throughout the entire area, and has attenuation poles on the low and high side compared to the passband. It is a high-performance bandpass filter for UWB. appropriate bandpass filter.

Furthermore, FIG. 17A is a schematic explanatory diagram of the resonant electrode coupling conductor 32 and the first resonant electrodes 30a, 30b, 30c, and 30d shown in top view 16, and FIG. 17B is a cross-sectional view of the resonant electrode coupling shown in FIG. 16. A schematic explanatory diagram of the conductor 32 and the first resonant electrodes 30a, 30b, 30c, and 30d, the input coupling electrode 40a, and the output coupling electrode 40b. As shown in FIG. 17A and FIG. 17B, in the resonant electrode coupling conductor 32, the input-stage coupling region 321 is strip-shaped. Viewed from above, it is preferable that the central axis extending to the length direction of the input-stage coupling region 321 does not overlap with the input-stage coupling region 321. The central axis extending in the longitudinal direction of the coupling electrode 40a is arranged overlappingly; the output stage coupling region 322 becomes a strip shape, and it is preferable to make the central axis extending in the longitudinal direction of the output stage coupling region 322 not overlap with the output coupling electrode 40b when viewed from above. The central axes extending in the longitudinal direction of the two are overlapped and arranged.

This is because after weakening the broadside coupling between the input stage coupling region 321 and the input coupling electrode 40a, the peak value of the λ/2 resonance of the transmitting resonant electrode coupling conductor 32 in the UWB operating frequency band and outside the passband can be suppressed, and the The reason for improving out-of-band characteristics.

Particularly preferably, as shown in FIG. 17B , the input-stage coupling region 321 is arranged so that it does not overlap with the central axis extending in the longitudinal direction of the input coupling electrode 40a when viewed from above, and does not overlap with the center axis extending in the longitudinal direction of the output coupling electrode 40b. The output stage coupling regions 322 are arranged so that their axes overlap. In this way, the coupling between the input coupling electrode 40a and the output coupling electrode 40b can be weakened while maintaining the coupling between the resonant electrode coupling conductor 32 and the first resonant electrodes 30a, 30b, 30c, and 30d. In addition, although the input-stage coupling region 321 is opposite to the resonant electrode 30a of the input stage, the so-called opposite here refers to the area where the input-stage coupling region 321 overlaps with the resonant electrode 30a of the input stage and is not exposed when viewed from above. The non-overlapping area of the , may increase the loss. The same applies to the relationship between the output stage coupling region 322 and the resonant electrode 30 b of the output stage.

(eighth embodiment)

Fig. 18 is an exploded perspective view schematically showing a bandpass filter according to an eighth embodiment of the present invention. As shown in FIG. 18 , based on the structure of the embodiment shown in FIG. 16 , it is preferable to arrange the input-coupling electrodes on the outer side than the arrangement area from the input-stage resonant electrode 30a to the output-stage resonant electrode 30d when viewed from above. 40a and the output coupling electrode 40b between the layers on the upper side, one end is connected to the ground potential to function as a 1/4 wavelength resonator, the strip-shaped input coupling resonant electrode 34a is electromagnetically coupled with the input coupling electrode 40a And the strip-shaped output coupling resonant electrode 34b coupled with the electromagnetic field of the output coupling electrode 40b.

With such a structure, since the input-coupling resonant electrode 34a and the output-coupling resonant electrode 34b function as a reaction resonator, it is possible to form another attenuation pole different from the attenuation pole formed by the second resonant electrode, and adjust the input-coupling resonant electrode 34a. By increasing the length of the output coupling resonant electrode 34b, the attenuation pole on the high-range side can be increased without changing the size of the passband, and the outer skirt characteristic can be improved (sharpened).

Here, the input-coupling resonance electrode 34a is coupled to the input-coupling electrode 40a, and the output-coupling resonance electrode 34b is coupled to the output-coupling electrode 40b. After the input-coupling resonant electrode 34a enters the inner side of the configuration area from the input-stage resonant electrode 30a to the output-stage resonant electrode 30d, the coupling between the input-coupling resonant electrode 34a and the input-coupling electrode 40a is too strong, and the input-coupling resonant electrode 34a and the input The coupling of the resonant electrode 30a of the stage is weakened, and the characteristics of the filter are lost. If it is arranged further inward, the coupling with the first resonant electrode 30b still loses the characteristics of the filter. On the other hand, when the input-coupling resonant electrode 34a is located on the same interlayer as the interlayer on which the input-coupling electrode 40a is placed or on the lower side, it couples with the input-stage resonant electrode 30a and loses filter characteristics.

This also applies to the output coupling resonance electrode 34b.

In addition, in this embodiment, the input coupling resonance electrode 34a and the output coupling resonance electrode 34b are provided from the viewpoint of design convenience. However, a configuration in which any one of them is provided may also be employed.

(ninth embodiment)

Fig. 19 is an exploded perspective view schematically showing a bandpass filter according to a ninth embodiment of the present invention. The only structural difference from the embodiment shown in FIG. 1 is that the first resonant electrodes are made up of six stages of 30a, 30b, 30c, 30d, 30e, and 3f.

Also in the bandpass filter of this embodiment, one end is connected to the ring-shaped ground electrode 23 in the vicinity of one end (short-circuit end) of the resonant electrode 30a of the input stage through the first through-conductor 51, and then through the first through-conductor 51. The conductor 51 is used as a medium to connect the other end of the resonant electrode coupling conductor 32 connected to the annular ground electrode 23 near one end (short-circuit end) of the resonant electrode 30f of the output stage, so that one end (short-circuit end) of the resonant electrode 30a of the input stage is close to After one side of the resonant electrode 30d of the input stage and the resonant electrode of the output stage are coupled together, the resonant electrode of the input stage and the resonant electrode of the output stage become L (inductive) coupling. On the other hand, between adjacent resonance electrodes of the six first resonance electrodes (between 30a and 30b, between 30b and 30c, between 30c and 30d, between 30d and 30e, between 30e and 30f) is also C (capacitive) coupling. This configuration constitutes a so-called analog elliptic function filter. In this way, one attenuation pole can be formed on each of the low-band side and the high-band side compared with the passband. Thus, it is possible to have filter characteristics with sharp attenuation outside the passband.

In addition, in the so-called analog elliptic function filter, for example, in the case of 6-stage resonators, as long as the coupling between the first-stage and second-stage resonators is (+), the coupling between the second-stage and third-stage resonators is Resonance of (+), 3rd and 4th resonators coupled to each other (+), 4th and 5th resonators coupled to each other (+), 5th and 6th resonators If the coupling between the resonators is (+) and the coupling between the first and sixth resonators is (-), attenuation poles can be formed on the low and high side of the passband. Here, (+) is equivalent to C, and (—) is equivalent to L.

As described above, by employing the band-pass filter of this embodiment, it is possible to obtain a sharper band-pass filter than the band-pass filter of the seventh embodiment of the present invention described above.

(tenth embodiment)

20 is an exploded perspective view schematically showing a bandpass filter according to a tenth embodiment of the present invention. The structural difference from the fourth embodiment shown in FIG. 16 is that in interlayer B above interlayer A in which first resonant electrodes 30a, 30b, 30c, and 30d and ring-shaped ground electrode 23 are arranged, a Auxiliary resonant electrodes 31a, 31b, 31c, 31d having a region facing the annular ground electrode 23 and regions facing the first resonating electrodes 30a, 30b, 30c, 30d; , 30d, and the interlayer D on the lower side of the interlayer A of the ring-shaped ground electrode 23, an auxiliary resonator having a region facing the ring-shaped ground electrode 23 and a region facing the first resonant electrodes 30a, 30b, 30c, and 30d is arranged. Electrodes 31a, 31b, 31c, 31d. Furthermore, the first resonance electrodes 30 a , 30 b , 30 c , and 30 d and the auxiliary resonance electrodes 31 a , 31 b , 31 c , and 31 d are connected by a third via conductor 53 penetrating through the dielectric layer 11 . In this way, since the electrostatic capacitance between the auxiliary resonant electrodes 31a, 31b, 31c, 31d and the annular ground electrode 23 is added, the other ends (open ends) of the first resonant electrodes 30a, 30b, 30c, 30d and the ground potential The capacitance between them is further increased, the lengths of the first resonant electrodes 30a, 30b, and 30c can be shortened, and a smaller bandpass filter can be obtained.

Furthermore, in the tenth embodiment shown in FIG. 20 , a pair of auxiliary resonant electrodes 31 a , 31 b , 31 c , and 31 d are provided up and down. However, if the amount of shortening is small compared to the above-mentioned embodiment, it is possible to adopt a method that only places the first resonant electrodes 30a, 30b, 30c, 30d and the interlayer A on the lower side. A configuration in which auxiliary resonant electrodes 31a, 31b, 31c, and 31d are provided in any one of them.

In addition, along with the formation of the auxiliary resonant electrodes 31a and 31d, between layers A where the first resonant electrodes 30a, 30b, 30c, and 30d and the ring-shaped ground electrode 23 are arranged and where the auxiliary resonant electrodes 31a, 31b, 31c, and 31d are arranged. Interlayer C having different interlayers B and D has an auxiliary incoupling electrode 41a corresponding to the incoupling electrode 40a and an auxiliary outcoupling electrode 41b corresponding to the outcoupling electrode 40b.

Here, in the seventh embodiment shown in FIG. 16, the second resonance electrodes 33a, 33b are formed shorter than the first resonance electrodes 30a, 30b, 30c, and 30d. However, when the lengths of the first resonance electrodes 30a, 30b, 30c, and 30d are shortened as described above, the second resonance electrodes 33a, 33b become longer. Therefore, as shown in FIG. 20, by forming the other end on the opposite side to the end connected to the ground potential so as to protrude toward one side and widen, an electrostatic capacity can be obtained between the ring-shaped ground electrode 23 and the length of the electrode can be shortened. The length of the second resonant electrodes 33a, 33b. The shape of the second resonant electrodes 33a and 33b is not only the shape shown in FIG. 20 but also a structure in which only the other end is bent or a shape formed in a T shape.

In addition, to adjust the amount of coupling between the first resonant electrode and the second resonant electrode, after making the second resonant electrode longer than the first resonant electrode, in order to increase the coupling amount, it is close to the first resonant electrode that has an interdigitated relationship when viewed from above. proceed.

In addition, although the second resonant electrode is apparently longer than the first resonant electrode, since the resonant frequency of the second resonant electrode is higher than that of the first resonant electrode, similar to the embodiment shown in FIG. On the high side of the comparison, there is a resonant frequency near the cutoff frequency.

In this way, by employing the band-pass filter of this embodiment, it is possible to obtain a smaller-sized band-pass filter than the band-pass filter of the seventh embodiment of the present invention described above.

(the eleventh embodiment)

FIG. 21 is a block diagram showing a configuration example of a high-frequency module 80 according to an eleventh embodiment of the present invention using the band-pass filter of the present invention and a radio communication device 85 using the same. The high-frequency module 80 of the present embodiment and the wireless communication device 85 using the same are configured using any one of the bandpass filters of the first to tenth embodiments of the present invention described above.

The high frequency module 80 of the present invention is made up of following parts: carry out the MAC (Medium Access Control) IC81 of medium access control; The PHY (physical layer) IC82 of the OFDM (Orthogonal Frequency Divison Multiplexing) signal of sending and receiving multi-band connected with it; A bandpass filter 83 is connected to it. The transmission signal output from the PHY IC 82 is transmitted from the antenna 84 after passing through the band-pass filter 83 and attenuating signals of frequencies outside the communication band. In addition, the reception signal received by the antenna 84 is input to the PHY IC 82 after passing through the band-pass filter 83, after attenuating signals of frequencies outside the communication band.

After adopting the high-frequency module 80 and the wireless communication device 85 of the present invention, the band-pass filter of the present invention, which has a small loss of signal passing through the entire area of the communication band, is used for filtering the transmission signal and the reception signal, thereby making the pass Since the attenuation of the received signal and the transmitted signal by the bandpass filter is reduced, the receiving sensitivity can be improved. In addition, since the amplification degree of the transmission signal and the reception signal can be reduced, the power consumption in the amplification circuit can be reduced. Therefore, high-performance high-performance high-frequency module 80 and wireless communication device 85 with high reception sensitivity and low power consumption can be obtained.

In the bandpass filter of the present invention, as the material of the dielectric layer 11 , resin such as epoxy resin and ceramics such as dielectric ceramics can be used, for example. For example, it is suitable to use dielectric ceramic materials such as BaTiO ₃ , Pb ₄ Fe ₂ Nb ₂ O ₁₂ , and TiO ₂ , and glass materials such as B ₂ O ₃ , SiO ₂ , Al ₂ O ₃ , and ZnO. A glass-ceramic material fired at a relatively low temperature. In addition, the thickness of the dielectric layer 11 is set to, for example, about 0.05 to 0.1 mm.

As materials for the above-mentioned various electrodes and penetrating conductors, for example, conductive materials mainly composed of Ag alloys such as Ag, Ag-Pd, and Ag-Pt, and Cu-based, W-based, Mo-based, and Pd-based conductive materials are preferably used. The thickness of the various electrodes is set to, for example, about 0.001 to 0.05 mm.

The bandpass filter of the present invention can be produced, for example, by the following method. Firstly, adding and mixing an appropriate organic solvent to the ceramic raw material powder to form a slurry, and then forming a ceramic green sheet by the doctor blade method. Next, through-holes for through-conductors are formed in the obtained ceramic green sheets using a puncher or the like, and conductive pastes such as Ag, Ag-Pd, Au, and Cu are filled to form through-conductors. Next, the various electrodes described above are formed on the ceramic green sheet by a printing method or the like. Finally, they are laminated, crimped using a hot press device, and fired at a temperature of 800 to 1050°C.

(Modification)

The present invention is not limited to the first to eleventh embodiments described above. Various changes and improvements can be made without departing from the scope of the present invention.

FIG. 22 is an exploded perspective view schematically showing a first modified example of the bandpass filter of the present invention. Fig. 23 is an exploded perspective view schematically showing a second modified example of the band-pass filter of the present invention, showing the formation region of the band-pass filter of the present invention when only one region of the module substrate is formed .

In addition, in these modified examples, only the differences from the above-mentioned embodiment will be described, and the same components will be assigned the same reference numerals, and will not be described again.

For example, in the first to third embodiments described above, an example including the auxiliary resonant electrodes 31 a , 31 b , and 31 c , the auxiliary input-coupling electrode 41 a , and the auxiliary output-coupling electrode 41 b has been described. However, for example, a configuration may be adopted that does not include auxiliary resonant electrodes 31a, 31b, 31c, auxiliary input coupling electrode 41a, and auxiliary output coupling electrode 41b like the bandpass filter shown in FIG. 22 . When increasing the size of the planar shape is not a problem, the auxiliary resonant electrodes 31a, 31b, and 31c are not necessarily required, and in this case, of course, the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b are also unnecessary.

In addition, in the above-mentioned first to tenth embodiments, examples including the input terminal electrode 60 a and the output terminal electrode 60 b have been described. However, when the bandpass filter is formed in one region of the module substrate, the input terminal electrode 60 a and the output terminal electrode 60 b are not necessarily required. For example, like the bandpass filter shown in FIG. 23 , the input wiring electrode 90a from the external circuit in the module substrate and the output wiring electrode 90a going to the external circuit in the module substrate are directly connected to the input coupling electrode 40a and the input coupling electrode 40a. The output coupling electrode 40b is connected to the structure. At this time, the connection point 91a of the input coupling electrode 40a and the input wiring electrode 90a becomes the position where the electrical signal input from the external circuit is supplied to the input coupling electrode 40a, and the connection point 91b of the output coupling electrode 40b and the output wiring electrode 90b becomes the position from the output signal. The coupling electrode 40b obtains the position of the electric signal output to the external circuit.

In addition, in the first to tenth embodiments described above, examples were described in which the input coupling electrode 40a, the strip-shaped output coupling electrode 40b, and the auxiliary resonant electrodes 31a, 31b, 31c, and 30d are arranged between the same layers of the laminate. However, the input coupling electrode 40a, the strip-shaped output coupling electrode 40b, and the auxiliary resonant electrodes 31a, 31b, 31c, and 30d can be arranged between different layers, and the input coupling electrode 40a, the strip-shaped output coupling electrode 40a, and the strip-shaped output coupling electrode 40a can also be arranged between different layers. In the coupling electrode 40b, auxiliary resonant electrodes 31a, 31b, 31c, and 30d may also be arranged between different layers.

In addition, in the first to third, sixth and tenth embodiments described above, examples were described in which the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b are arranged in the same interlayer space C of the laminated body 10 . However, a structure in which the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b are arranged between different layers of the multilayer body 10 may also be employed.

Furthermore, in the first to third embodiments described above, an example was described in which the three resonant electrodes 31a, 31b, and 31c are electromagnetically coupled to form a bandpass filter. However, for example, a configuration may be employed in which two or more resonant electrodes are electromagnetically coupled to form a bandpass filter. It can be selected according to the required electrical characteristics and allowable shape and size.

Furthermore, in the first to tenth embodiments described above, the example in which the first ground electrode 21 is arranged on the lower surface of the laminated body 10 and the second ground electrode 22 is arranged on the upper surface of the laminated body 10 has been described. However, for example, a dielectric layer may be further disposed below the first ground electrode 21 , or a dielectric layer may be further disposed above the second ground electrode 22 .

Furthermore, in the above-mentioned eleventh embodiment, an example of the high-frequency module 80 composed of the MACIC 81 for media access control, the PHY IC 82 connected thereto, and the bandpass filter 83 connected thereto was shown. However, the MAC IC 81 and the PHYIC 82 can also be formed using an integrated one-chip IC. In addition, for example, a high-frequency module 80 composed of only a PHY IC 82 and a bandpass filter 83 connected thereto may be used, and then a MAC IC 81 and an antenna 84 may be connected to form a wireless communication device 85.

In addition, the bandpass filter used by UWB has been described above as an example. But there is no doubt that the bandpass filter of the present invention is also effective in other applications requiring a wide band range.

(Example 1)

Next, specific examples of the electronic component of the present invention will be described.

Using the finite element method, the electrical characteristics of the bandpass filter having the configuration shown in FIGS. 1 to 4 were simulated and calculated. The calculation conditions are as follows: as the physical property value, the dielectric constant of the dielectric layer 11 = 9.4, the dielectric tangent of the dielectric layer 11 = 0.0005, and the conductivity of various electrodes = 3.0 × 10 ⁷ S/m; as the shape dimension, the resonance The electrodes 30a, 30b, and 30c have a width of 0.4mm and a length of 2.9mm, and the distance between adjacent resonant electrodes is 0.13mm; the width of the input coupling electrode 40a and the output coupling electrode 40b is 0.3mm, and the length is 2.5mm. The width of the input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b is 0.3 mm, and the length is 1.45 mm. Auxiliary resonant electrodes 31a, 31b, 31c are rectangular with a width of 0.4 mm and a length of 2.9 mm, which are arranged at a distance of 0.3 mm from the other ends of the resonant electrodes 30a, 30b, 30c, and then toward the resonant electrodes 30a, 30c, 30b, 30c have a width of 0.2mm and a length of 0.4mm in the shape of a rectangle; the input terminal electrode 60a and the output terminal electrode 60b are squares with a side of 0.3mm, and the distance from the second ground electrode 22 is 0.2mm; The ground electrode 21 , the second ground electrode 22 , and the ring-shaped ground electrode 23 have a width of 3 mm and a length of 5 mm, and the opening of the ring-shaped ground electrode 23 has a width of 2.4 mm and a length of 3 mm. The overall shape of the bandpass filter is 3 mm in width, 5 mm in length, and 0.91 mm in thickness, and the interlayer A is located at the center in the thickness direction. The intervals between the interlayer A and the interlayer B and between the interlayer B and the interlayer C are 0.065 mm, respectively. The thickness of various electrodes is 0.01 mm, and the diameter of various through conductors is 0.1 mm.

FIG. 24 is a graph showing the results of the simulation. The horizontal axis represents frequency, the vertical axis represents loss, and shows the pass characteristic ( S21 ) and reflection characteristic ( S11 ). According to the graph shown in FIG. 24, in the pass characteristic (S21), the region is far wider than that which can be realized by a filter using a conventional 1/4 wavelength resonator, and the specific band corresponds to 40%. In the frequency range of 3.2GHz to 4.7GHz, the loss is less than 1.5dB. In this way, excellent pass characteristics that are flat and low-loss over the entire wide pass band can be obtained, confirming the effectiveness of the present invention.

(Example 2)

Electromagnetic field simulation calculations for the transmission characteristics of the band-pass filter of the structure of FIG. 15 . As calculation conditions, dielectric constant=9.4, dielectric tangent=0.0005, and electrical conductivity=3.0×10 ⁷ S/m of the dielectric layer 11 were used. As the shape dimension of the design value put into the trial production, the width of the resonant electrodes 30a, 30b, 30c, and 30d is 0.4 mm, and the length is 2.85 mm. 0.15mm, and the interval between the resonant electrode 30b and the resonant electrode 30c is 0.15mm. The width of the input-coupling electrode 40 a and the output-coupling electrode 40 b is 0.3 mm and the length is 2.5 mm, and the width of the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b is 0.3 mm and the length is 1.45 mm. Auxiliary resonant electrodes 31a, 31b, 31c, 31d are rectangular with a width of 0.45 mm and a length of 0.8 mm, which are arranged at a distance of 0.3 mm from the other ends of the resonant electrodes 30a, 30b, 30c, 30d, and then toward The resonant electrodes 30 a , 30 b , 30 c , and 30 d have a rectangular shape with a width of 0.2 mm and a length of 0.4 mm. The input terminal electrode 60 a and the output terminal electrode 60 b are squares with a side of 0.3 mm, and the distance from the second ground electrode 22 is 0.2 mm. The outer shape of the first ground electrode 21 , the second ground electrode 22 , and the ring-shaped ground electrode 23 is 4 mm in width and 6 mm in length, and the opening of the ring-shaped ground electrode 23 is 2.4 mm in width and 3 mm in length. The overall shape of the bandpass filter is 3 mm in width, 5 mm in length, and 0.9 mm in thickness. The intervals between the interlayer C where the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b are arranged and the upper interlayer B where the auxiliary resonant electrodes 31a, 31b, 31c, and 31d are arranged are each 0.065mm. The thickness of various electrodes is 0.013 mm, and the diameter of various through conductors is 0.1 mm. The resonant electrode coupling conductor 32 to form an attenuation pole has a width of 0.2 mm and a central connection portion of 0.1 mm.

FIG. 25 is a graph showing the calculation results. The horizontal axis represents the frequency, the vertical axis represents the loss, and shows the transmission characteristic ( S21 ) and the reflection characteristic ( S11 ). According to the graph shown in Fig. 25, in the frequency range of 3.4 GHz to 4.6 GHz, which is equivalent to 30% of the specific band, there is a loss of less than 1.5 dB. Attenuation is extremely 1 in 5.3GHz. In this way, excellent pass characteristics in which flatness and low loss can be obtained over the entire wide pass band and sufficient attenuation poles are obtained outside the pass band have been confirmed, confirming the effectiveness of the present invention.

On the other hand, as a comparative example, electromagnetic field simulation calculations were performed for the transmission characteristics of the band-pass filter having the structure without the resonant electrode coupling conductor 32 of FIG. 15 . As calculation conditions, dielectric constant=9.4, dielectric tangent=0.0005, and electrical conductivity=3.0×10 ⁷ S/m of the dielectric layer 11 were used. As the shape dimension of the design value put into the trial production, the width of the resonant electrodes 30a, 30b, 30c, and 30d is 0.4 mm, and the length is 2.85 mm. 0.15mm, and the interval between the resonant electrode 30b and the resonant electrode 30c is 0.20mm. The width of the input-coupling electrode 40 a and the output-coupling electrode 40 b is 0.3 mm and the length is 2.5 mm, and the width of the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b is 0.3 mm and the length is 1.45 mm. Auxiliary resonant electrodes 31a, 31b, 31c, 31d are rectangular with a width of 0.45 mm and a length of 0.8 mm, which are arranged at a distance of 0.3 mm from the other ends of the resonant electrodes 30a, 30b, 30c, 30d, and then toward The resonant electrodes 30 a , 30 b , 30 c , and 30 d have a rectangular shape with a width of 0.2 mm and a length of 0.4 mm. The input terminal electrode 60 a and the output terminal electrode 60 b are squares with a side of 0.3 mm, and the distance from the second ground electrode 22 is 0.2 mm. The outer shape of the first ground electrode 21 , the second ground electrode 22 , and the ring-shaped ground electrode 23 is 4 mm in width and 6 mm in length, and the opening of the ring-shaped ground electrode 23 is 3 mm in width and 3 mm in length. The overall shape of the bandpass filter is 3 mm in width, 5 mm in length, and 0.9 mm in thickness. The intervals between the interlayer B and the interlayer C are 0.065 mm, respectively. The thickness of various electrodes is 0.013 mm, and the diameter of various through conductors is 0.1 mm.

FIG. 26 is a graph showing the calculation results. The horizontal axis represents the frequency, the vertical axis represents the loss, and shows the transmission characteristic ( S21 ) and the reflection characteristic ( S11 ). It can be seen from Fig. 26 that the attenuation outside the passband is gentle, and sufficient attenuation cannot be ensured.

(Example 3)

The electromagnetic field simulation calculates the transmission characteristics of the bandpass filter for the structure of FIG. 20 . As calculation conditions, dielectric constant=9.4, dielectric tangent=0.0005, and electrical conductivity=3.0×10 ⁷ S/m of the dielectric layer 11 were used. The thickness of the dielectric layer 11 is 0.3 mm for the uppermost layer and the lowermost layer among the seven layers, and 0.75 mm for the other layers. In addition, the first resonant electrodes 30a, 30b, 30c, and 30d have a width of 0.4 mm and a length of 2.85 mm, and the first resonant electrode (resonant electrode of the input stage) 30a, the first resonant electrode 30b, and the first resonant electrode 30c and the first resonant electrode The interval between one resonant electrode (resonant electrode of the output stage) 30d is 0.15mm, and the interval between the first resonant electrode 30b and the first resonant electrode 30c is 0.14mm. The width of the input-coupling electrode 40 a and the output-coupling electrode 40 b is 0.3 mm and the length is 2.5 mm, and the width of the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b is 0.3 mm and the length is 1.45 mm. The auxiliary resonant electrodes 31a, 31b, 31c, and 31d are rectangles with a width of 0.45 mm and a length of 0.8 mm, which are arranged at a distance of 0.3 mm from the other ends of the first resonant electrodes 30a, 30b, 30c, and 30d. It has a rectangular shape with a width of 0.2 mm and a length of 0.4 mm toward the first resonant electrodes 30a, 30b, 30c, and 30d. The input terminal electrode 60 a and the output terminal electrode 60 b are squares with a side of 0.3 mm, and the distance from the second ground electrode 22 is 0.2 mm. The outer shape of the first ground electrode 21 , the second ground electrode 22 , and the ring-shaped ground electrode 23 is 3 mm in width and 6 mm in length, and the opening of the ring-shaped ground electrode 23 is 2.4 mm in width and 3 mm in length. The overall shape of the bandpass filter is 3 mm in width, 5 mm in length, and 0.975 mm in thickness. The intervals between the interlayer C where the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b are arranged and the upper interlayer B where the auxiliary resonant electrodes 31a, 31b, 31c, and 31d are arranged are each 0.065 mm. The thickness of various electrodes is 0.013 mm, and the diameter of various through conductors is 0.1 mm. The width of the input-stage coupling region and the output-stage coupling region of the resonant electrode coupling conductor forming the attenuation pole is 0.3 mm, and the width of the connecting region is 0.1 mm.

In addition, the second resonant electrodes 33a, 33b acting as reaction resonators have a widened region (0.4 mm in width) protruding toward one side surface at the other end of a strip-shaped region with a width of 0.1 mm and a length of 3.4 mm. mm, length 0.36mm) shape. The position where the second resonant electrode 33a is provided is based on the position where the edge of the input stage of the first resonant electrode 30b on the side of the resonant electrode 30a and the edge of the second resonant electrode 33a are aligned to face each other, and is close to the input stage. The positions of the resonance electrodes 30a are shifted by 0.03 mm. Similarly, the position where the second resonant electrode 33b is provided is based on the position where the edge on the resonant electrode 30d side of the output stage of the first resonant electrode 30c viewed from above coincides with the edge of the second resonant electrode 33b, and is close to the output stage. The positions of the resonant electrodes 30d are shifted by 0.03 mm.

FIG. 27 is a graph showing the calculation results. The horizontal axis represents the frequency, the vertical axis represents the loss, and shows the transmission characteristics ( S21 ) and reflection characteristics ( S11 ). According to FIG. 27, in the pass characteristic (S21), in the frequency range of 3.4 GHz to 4.6 GHz corresponding to 30% of the specific band, there is a loss of less than 1.5 dB, and the attenuation is extremely 1 at 2.5 GHz outside the pass band. and extremely attenuated by 2 in 5.3GHz. In addition, jumping between attenuation electrodes on the high-range side is also suppressed. In this way, excellent pass characteristics in which flatness and low loss can be obtained over the entire wide pass band and sufficient attenuation poles are obtained outside the pass band have been confirmed, confirming the effectiveness of the present invention.

On the other hand, measurements were also performed on a case where the structure was the same as the above-mentioned structure except that the positions of the second resonant electrodes 33 a and 33 b were different. In this case, the edge of the input stage resonant electrode 30a side of the first resonant electrode 30b viewed from above and the edge of the second resonant electrode 33a face each other as a reference, and are shifted by 0.03mm away from the input stage resonant electrode 30a. Location. Similarly, the position where the second resonant electrode 33b is provided is based on the position where the edge of the output stage of the first resonant electrode 30c on the side of the resonant electrode 30d and the edge of the second resonant electrode 33b face each other as a reference, and is separated from the output stage. The positions of the resonant electrodes 30d are shifted by 0.03 mm.

FIG. 28 is a graph showing the measurement results. The horizontal axis represents the frequency, the vertical axis represents the loss, and shows the transmission characteristics ( S21 ) and reflection characteristics ( S11 ). According to the graph shown in FIG. 28 , in the pass characteristic (S21), there is one attenuation pole at 2.5 GHz outside the pass band and two attenuation poles at 5.3 GHz, as in the case of the characteristic shown in FIG. 27 , In the vicinity of the cutoff frequency, a sharp attenuation characteristic can be obtained, but a jump occurs between attenuation electrodes on the high side higher than that, which is somewhat disadvantageous compared with the characteristic shown in FIG. 27 . Therefore, in order to eliminate such jumping, it is necessary to adjust the position of the second resonant electrode.

In addition, in Fig. 27 and Fig. 28, a resonance peak can be seen near 9 GHz, and the out-of-band characteristics deteriorate. In UWB, since this vicinity is also used in the frequency band, it is desirable to improve it. Therefore, as shown in FIG. 17A and FIG. 17B , the input-stage coupling region 321 and the output-stage coupling region 322 are shifted outward from the central axis of the input-stage resonant electrode 30 a and the output-stage resonant electrode 30 d to arrange the resonant electrode coupling conductor 32 . Regarding parameters such as dimensions of other basic structures, the same structure as that of the above-mentioned embodiment is adopted. Fig. 29 shows the calculation results. As a result, the out-of-band characteristics up to 10 GHz can be improved to 30 dB or less.

Furthermore, FIG. 30 is a simulation of the same structure as the above-mentioned embodiment in terms of parameters such as the dimensions of the basic structure, and the input coupling resonance is arranged on the upper layer of the input coupling electrode 40a and outside the arrangement area of the first resonant electrodes 30a, 30b, 30c, and 30d. At the same time as the electrode 34a, the calculation result of the transmission characteristic S21 of the output coupling resonant electrode 34b and the structure of FIG. A new attenuation pole is generated near 5GHz, and a sharper skirt characteristic can be obtained.

In addition, the electromagnetic field simulation calculation of the structure in which the second resonant electrode is removed from the structure of FIG. 20 was also calculated. As calculation conditions, dielectric constant=9.4, dielectric tangent=0.0005, and electrical conductivity=3.0×10 ⁷ S/m of the dielectric layer 11 were used. The thickness of the dielectric layer 11 as a shape dimension of the design value put into trial production is 0.3 mm for the uppermost layer and the lowermost layer among the 6 layers, and 0.075 mm for the other layers. The first resonant electrodes 30a, 30b, 30c, and 30d have a width of 0.4mm and a length of 2.85mm. The distance between the electrodes (resonant electrodes of the output stage) 30d is 0.15mm, and the distance between the first resonant electrode 30b and the first resonant electrode 30c is 0.15mm. The width of the input-coupling electrode 40 a and the output-coupling electrode 40 b is 0.3 mm and the length is 2.5 mm, and the width of the auxiliary input-coupling electrode 41 a and the auxiliary output-coupling electrode 41 b is 0.3 mm and the length is 1.45 mm. The auxiliary resonant electrodes 31a, 31b, 31c, and 31d are rectangles with a width of 0.45 mm and a length of 0.8 mm, which are arranged at a distance of 0.3 mm from the other ends of the first resonant electrodes 30a, 30b, 30c, and 30d. It has a rectangular shape with a width of 0.2 mm and a length of 0.4 mm toward the first resonant electrodes 30a, 30b, 30c, and 30d. The input terminal electrode 60 a and the output terminal electrode 60 b are squares with a side of 0.3 mm, and the distance from the second ground electrode 22 is 0.2 mm. The outer shape of the first ground electrode 21 , the second ground electrode 22 , and the ring-shaped ground electrode 23 is 3 mm in width and 6 mm in length, and the opening of the ring-shaped ground electrode 23 is 2.4 mm in width and 3 mm in length. The overall shape of the bandpass filter is 3 mm in width, 5 mm in length, and 0.9 mm in thickness. The intervals between the interlayer C where the auxiliary input-coupling electrode 41a and the auxiliary output-coupling electrode 41b are arranged and the upper interlayer B where the auxiliary resonant electrodes 31a, 31b, 31c, and 31d are arranged are each 0.065 mm. The thickness of various electrodes is 0.013 mm, and the diameter of various through conductors is 0.1 mm. The width of the input stage coupling region and the output stage coupling region of the resonant electrode coupling conductor forming the attenuation pole is 0.2 mm, and the width of the connecting region is 0.1 mm.

FIG. 31 is a graph showing the calculation results. The horizontal axis represents the frequency, the vertical axis represents the loss, and shows the transmission characteristics ( S21 ) and reflection characteristics ( S11 ). According to Fig. 31, in the pass characteristic (S21), in the frequency range of 3.4GHz to 4.6GHz corresponding to 30% of the specific band, there is a loss of less than 1.5dB, and the attenuation is extremely small at 2.5GHz outside the bandwidth. And the attenuation is extremely 1 in 5.3GHz. In this way, excellent pass characteristics that are flat and low-loss over a wide bandwidth and ensure sufficient attenuation poles outside the bandwidth can be obtained, but there is no sharp attenuation as compared with the present invention.

In this way, the effectiveness of the present invention including the second resonant electrode can be confirmed.

The present invention can be carried out in other various forms within the range not departing from the gist or main characteristics thereof. Therefore, the above-mentioned embodiment is merely an illustration in the final analysis, and the scope of the present invention is described in the "claims" and is not restricted by the description herein. Furthermore, all modifications and changes belonging to the "claims" are within the scope of the present invention.

Claims (17)

1. A bandpass filter having: a laminate stacking a plurality of dielectric layers; a first ground electrode, the first ground electrode is disposed on the lower side of the laminate and connected to a ground potential; a second ground electrode, the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential; A plurality of strip-shaped resonant electrodes arranged laterally between one layer of the laminate and coupled with each other in an electromagnetic field, one end of which is connected to a ground potential, and functions as a 1/4 wavelength resonator ; strip-shaped input-coupling electrodes, these strip-shaped input-coupling electrodes are disposed between layers different from the one layer of the stack, and are electromagnetically coupled to the resonant electrodes of the input stage among the plurality of resonant electrodes; Strip-shaped output coupling electrodes, these strip-shaped output coupling electrodes are disposed between layers different from the one layer of the laminate, and are electromagnetically coupled to the resonant electrodes of the output stage among the plurality of resonant electrodes; an input-side through-conductor (52a, 50), which penetrates through the dielectric layer and is connected to the input-coupling electrode, and supplies an electrical signal input from an external circuit to the input-coupling electrode; and an output-side penetrating conductor (52b, 50), which penetrates the dielectric layer and is connected to the output coupling electrode, and obtains an electrical signal output to an external circuit from the output coupling electrode, The one end and the other end of each of the plurality of resonant electrodes are arranged alternately; The input coupling electrode is arranged to face more than half of the lengthwise region of the resonant electrode across the input stage, and the position where the input-side through-conductor is connected is closer to the input side than the center of the lengthwise direction. one side of the other end of the resonant electrode of the stage; The output coupling electrode is arranged to face an area spanning more than half of the length direction of the resonant electrode of the output stage, and the position where the output-side through-conductor is connected is closer to the output side than the center of the length direction. one side of the other end of the resonant electrode of the stage. 2. The bandpass filter according to claim 1 , wherein a ring-shaped ground electrode is disposed, and the ring-shaped ground electrode is formed as a ring surrounding the plurality of resonant electrodes between the layers. shape, connected to the one end of the plurality of resonant electrodes and connected to the ground potential. 3. The bandpass filter according to claim 2, wherein an auxiliary resonant electrode is arranged corresponding to each of the plurality of resonant electrodes, and the auxiliary resonant electrode is in a layer different from the one layer. between the ring-shaped ground electrode and the resonant electrode, and the region opposed to the resonant electrode is connected to the other end side of the resonant electrode by a first through-conductor. The first through-conductor penetrates through the dielectric layer between the region where the resonant electrode faces and the resonant electrode. 4. A bandpass filter having: a laminate stacking a plurality of dielectric layers; a first ground electrode, the first ground electrode is disposed on the lower side of the laminate and connected to a ground potential; a second ground electrode, the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential; A plurality of strip-shaped resonant electrodes arranged laterally between one layer of the laminate and coupled with each other in an electromagnetic field, one end of which is connected to a ground potential, and functions as a 1/4 wavelength resonator ; strip-shaped input-coupling electrodes disposed between layers different from the one layer of the laminate, and electromagnetically coupled to a resonant electrode of the input stage among the plurality of resonant electrodes; and strip-shaped output coupling electrodes disposed between layers different from said one layer of said laminate, and electromagnetically coupled to a resonant electrode of an output stage among said plurality of resonant electrodes, The one end and the other end of each of the plurality of resonant electrodes are arranged alternately; The input-coupling electrode is arranged to face more than half of the region in the longitudinal direction of the resonant electrode of the input stage, and a position for supplying an electric signal input from an external circuit is closer to the center of the longitudinal direction than to the center of the input stage. a side of said other end of the resonant electrode of the input stage; The output-coupling electrode is disposed so as to face a region spanning more than half of the resonant electrode in the longitudinal direction of the output stage, and a position at which an electric signal output to an external circuit is obtained is closer to the center than the center in the longitudinal direction. side of the other end of the resonant electrode of the output stage, The bandpass filter is further provided with a ring-shaped ground electrode formed between the one layer in a ring shape surrounding the plurality of resonant electrodes, and connected to all of the plurality of resonant electrodes. One end is connected and connected to ground potential, An auxiliary resonant electrode is arranged corresponding to each of the plurality of resonant electrodes, and the auxiliary resonant electrode is arranged in a layer different from the one layer and has a region facing the ring-shaped ground electrode and a region opposite to the ring-shaped ground electrode. The area opposite to the resonant electrode is connected to the other end side of the resonant electrode by a first through conductor, and the first through conductor penetrates the area opposite to the resonant electrode to the other end side of the resonant electrode. the dielectric layer between the resonant electrodes, The bandpass filter also has: an auxiliary input-coupling electrode configured to have an auxiliary input-coupling electrode connected to a resonance electrode of the input stage among the plurality of auxiliary resonance electrodes in a layer different from the one layer and further a layer different from the layer. The region facing the resonant electrode and the region facing the input-coupling electrode are connected to each other closer to the center of the input-coupling electrode than the center of the length direction of the input-coupling electrode by a second through-conductor. On one side of the other end of the resonant electrode of the input stage, the second through conductor penetrates through the dielectric layer between the input coupling electrode and the input coupling electrode; and an auxiliary output coupling electrode configured to have an auxiliary output coupling electrode connected to a resonance electrode of the output stage among the plurality of auxiliary resonant electrodes in a layer different from the one layer and further a different layer. A region facing the resonant electrode and a region facing the output coupling electrode are connected to a region that is closer to the output coupling electrode than the center of the output coupling electrode in the longitudinal direction by a third through conductor. On one side of the other end of the resonant electrode of the output stage, the third through-conductor penetrates through the dielectric layer between a region facing the output-coupling electrode and the output-coupling electrode. 5. A bandpass filter having: a laminate stacking a plurality of dielectric layers; a first ground electrode, the first ground electrode is disposed on the lower side of the laminate and connected to a ground potential; a second ground electrode, the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential; Four or more strip-shaped resonant electrodes arranged laterally in a layer of the laminated body so as to be electromagnetically coupled to each other, with one end of each connected to a ground potential as 1/4 wavelength The resonator works; strip-shaped input-coupling electrodes disposed between layers above the one layer of the laminate, and connected to the resonance electrodes of the input stage among the four or more resonance electrodes. Electromagnetic field coupling; strip-shaped output-coupling electrodes disposed between layers above the one layer of the laminated body, and connected to the resonance electrodes of the output stage among the four or more resonance electrodes. electromagnetic field coupling; and a resonant electrode coupling conductor arranged in an interlayer lower than the one interlayer of the laminated body, one end of which passes through a first through-conductor, and is connected to the resonant electrode of the input stage. The vicinity of one end is connected to the ground potential, and the other end is connected to the ground potential in the vicinity of the one end of the resonant electrode of the output stage through a first through conductor, and the resonant electrode coupling conductor has a resonant electrode coupled to the input stage. an area opposite to the resonant electrode of the output stage, and the electromagnetic field coupling to the resonant electrode of the input stage and the electromagnetic field coupling to the resonant electrode of the output stage are substantially equal, The one end and the other end of each of the four or more resonant electrodes are arranged alternately; The input-coupling electrode is arranged to face more than half of the region in the longitudinal direction of the resonant electrode of the input stage, and a position for supplying an electric signal input from an external circuit is closer to the center of the longitudinal direction than to the center of the input stage. a side of said other end of the resonant electrode of the input stage; The output-coupling electrode is disposed so as to face a region spanning more than half of the resonant electrode in the longitudinal direction of the output stage, and a position at which an electric signal output to an external circuit is obtained is closer to the center than the center in the longitudinal direction. one side of the other end of the resonant electrode of the output stage. 6. The bandpass filter according to claim 5, wherein the resonant electrode coupling conductor is composed of the following three regions: the input stage coupling region opposite to the resonant electrode of the input stage, and the output stage The output stage coupling region facing the resonant electrode of the stage, and the connection region orthogonally connected to the input stage coupling region and the output stage coupling region respectively. 7. The bandpass filter according to claim 5 or 6, characterized in that: a ring-shaped ground electrode is arranged, and the ring-shaped ground electrode is formed between the one layer to surround the four or more resonant electrodes The surrounding ring is connected to the one end of the resonant electrode and connected to the ground potential. 8. The bandpass filter according to claim 7, wherein an auxiliary resonant electrode is arranged corresponding to each of the four or more resonant electrodes, and the auxiliary resonant electrode is different from the one layer. The interlayer is arranged so as to have a region facing the ring-shaped ground electrode and a region facing the resonant electrode, and the region facing the resonant electrode is connected to the other part of the resonant electrode by using a second through-conductor. One end side is connected, and the second penetrating conductor penetrates through the dielectric layer between the region where the resonance electrode faces and the resonance electrode. 9. band-pass filter as claimed in claim 8, is characterized in that, possesses: Auxiliary input-coupling electrodes, the auxiliary input-coupling electrodes are disposed between layers different from the one interlayer and the interlayer on which the auxiliary resonant electrodes are disposed, and have the same characteristics as the four or more auxiliary resonant electrodes The area opposite to the auxiliary resonant electrode connected to the resonant electrode of the input stage and the area opposite to the input coupling electrode, the area opposite to the input coupling electrode uses a third through-conductor, and the lengthwise direction of the input coupling electrode The center is connected to a side closer to the other end of the resonant electrode of the input stage, and the third through-conductor penetrates through the dielectric layer between the input-coupling electrode and the input-coupling electrode. ;and Auxiliary output coupling electrodes, the auxiliary output coupling electrodes are disposed between layers different from the one interlayer and the interlayer on which the auxiliary resonant electrodes are arranged, so as to be connected to the four or more auxiliary resonant electrodes The region opposite to the auxiliary resonant electrode connected to the resonant electrode of the output stage and the region opposite to the output coupling electrode, the region opposite to the output coupling electrode uses a fourth through conductor, and the lengthwise direction of the output coupling electrode The center is connected to one side closer to the other end of the resonant electrode of the output stage, and the fourth penetrating conductor penetrates the dielectric layer between the output-coupling electrode-facing region and the output-coupling electrode . 10. A bandpass filter having: a laminate stacking a plurality of dielectric layers; a first ground electrode, the first ground electrode is disposed on the lower side of the laminate and connected to a ground potential; a second ground electrode, the second ground electrode is disposed on the upper surface of the laminate and connected to a ground potential; Four or more strip-shaped first resonant electrodes arranged laterally in a layer of the laminated body so as to be electromagnetically coupled to each other, one end of each of which is connected to a ground potential, as 1/4 wavelength resonator plays a role; strip-shaped input-coupling electrodes disposed between layers above the one layer of the laminate, and connected to the resonance electrodes of the input stage among the four or more resonance electrodes. Electromagnetic field coupling; strip-shaped output-coupling electrodes disposed between layers above the one layer of the laminated body, and connected to the resonance electrodes of the output stage among the four or more resonance electrodes. Electromagnetic field coupling; a resonant electrode coupling conductor arranged in an interlayer lower than the one interlayer of the laminated body, one end of which passes through a first through-conductor, and is connected to the resonant electrode of the input stage. The vicinity of one end is connected to the ground potential, and the other end is connected to the ground potential in the vicinity of the one end of the resonant electrode of the output stage through a first through conductor, and the resonant electrode coupling conductor has a resonant electrode coupled to the input stage. a region opposite and a region opposite to the resonant electrode of the output stage and having substantially equal electromagnetic field coupling to the resonant electrode of the input stage and electromagnetic field coupling to the resonant electrode of the output stage; and one or more second resonant electrodes, the one or more second resonant electrodes are arranged in an interlayer lower than one interlayer of the laminate and different from the interlayer where the resonant electrode coupling conductor is arranged, Parallel to the first resonant electrode, one end of which is connected to the ground potential through a second through-conductor, formed in a strip shape with a length different from that of the first resonant electrode, and has resonance near the cutoff frequency on the outside of the passband frequency, The one end and the other end of each of the four or more first resonant electrodes are alternately arranged; The input-coupling electrode is arranged to face more than half of the region in the longitudinal direction of the resonant electrode of the input stage, and a position for supplying an electric signal input from an external circuit is closer to the center of the longitudinal direction than to the center of the input stage. a side of said other end of the resonant electrode of the input stage; The output-coupling electrode is disposed so as to face a region spanning more than half of the resonant electrode in the longitudinal direction of the output stage, and a position at which an electric signal output to an external circuit is obtained is closer to the center than the center in the longitudinal direction. one side of the other end of the resonant electrode of the output stage. 11. The bandpass filter according to claim 10, characterized in that: the resonant electrode coupling conductor is composed of the following three regions: an input stage coupling region opposite to the resonant electrode of the input stage, and the output stage The output stage coupling region facing the resonant electrode of the stage, and the connection region orthogonally connected to the input stage coupling region and the output stage coupling region respectively. 12. The bandpass filter according to claim 10 or 11, characterized in that: an even number of the first resonant electrodes is provided, and an even number of the second resonant electrodes is also provided; Viewed from above, the line segment connecting one end of the resonant electrode of the input stage and one end of the resonant electrode of the output stage and the other end of the resonant electrode of the input stage and the other end of the resonant electrode of the output stage The intersection point of the line segments is the center, and the second resonant electrodes are arranged point-symmetrically. 13. The bandpass filter according to any one of claims 10 to 12, characterized in that: a ring-shaped ground electrode is arranged, and the ring-shaped ground electrode is formed between the one layer to surround the four or more layers. The ring shape around the first resonant electrode is connected to the one end of the first resonant electrode and connected to the ground potential. 14. The bandpass filter according to claim 13, wherein an auxiliary resonant electrode is arranged corresponding to each of the four or more first resonant electrodes, and the auxiliary resonant electrode is connected to the one layer Different layers are arranged so as to have a region facing the ring-shaped ground electrode and a region facing the first resonant electrode, and the region facing the first resonant electrode is connected to the The other end side of the first resonant electrode is connected, and the third penetrating conductor penetrates through the dielectric layer between a region where the first resonant electrode faces and the first resonant electrode. 15. band-pass filter as claimed in claim 14, is characterized in that, possesses: Auxiliary input-coupling electrodes, the auxiliary input-coupling electrodes are disposed between layers different from the one layer and the layer on which the auxiliary resonant electrodes are arranged, and are arranged to have a connection with the input of the four or more auxiliary resonant electrodes. The region opposite to the auxiliary resonant electrode connected to the resonant electrode of the stage and the region opposite to the input coupling electrode, the region opposite to the input coupling electrode uses a fourth through-conductor, and the center of the longitudinal direction of the input coupling electrode The fourth penetrating conductor penetrates through the dielectric layer between the input-coupling electrode and the input-coupling electrode; and Auxiliary output coupling electrodes, the auxiliary output coupling electrodes are disposed between layers different from the one interlayer and the interlayer on which the auxiliary resonant electrodes are arranged, so as to have The region opposite to the auxiliary resonant electrode connected to the resonant electrode of the second stage is arranged in such a manner that the region opposite to the output coupling electrode uses a fifth through-conductor, and the longitudinal direction of the output coupling electrode The center of the output stage is connected to the side closer to the other end of the resonant electrode of the output stage, and the fifth through-conductor passes through the dielectric between the region facing the output coupling electrode and the output coupling electrode. layer. 16. A high-frequency module, characterized by comprising the band-pass filter according to any one of claims 1-15. 17. A wireless communication device comprising the bandpass filter according to any one of claims 1 to 15 or the high frequency module according to claim 16.

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