CN101132151B - a power converter - Google Patents
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- CN101132151B CN101132151B CN200710075763A CN200710075763A CN101132151B CN 101132151 B CN101132151 B CN 101132151B CN 200710075763 A CN200710075763 A CN 200710075763A CN 200710075763 A CN200710075763 A CN 200710075763A CN 101132151 B CN101132151 B CN 101132151B
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Abstract
本发明公开了一种电源变换器，包括第一、二变压器，第一、二箝位器件，第一、二开关管，第一、二电感和谐振网络，第一变压器包括第一原边绕组和第一副边绕组，第二变压器包括第二原边绕组、第二副边绕组，第一开关管、第一原边绕组、第二原边绕组、第二开关管串联后跨接在输入电源上，谐振网络连接在第一原边绕组和第二原边绕组的中间节点及第一开关管和/或第二开关管与输入电源的连接节点之间，第一电感跨接在第一原边绕组上，第二电感跨接在第二原边绕组上，第一箝位器件和第二箝位器件分别为第一原边绕组和第二原边绕组提供复位通路，第一开关管和第二开关管的相位错开。本发明工作效率，避免了直通危险、可靠性好。
The invention discloses a power converter, which includes first and second transformers, first and second clamping devices, first and second switch tubes, first and second inductors and a resonant network, and the first transformer includes a first primary winding and the first secondary winding, the second transformer includes the second primary winding, the second secondary winding, the first switching tube, the first primary winding, the second primary winding, and the second switching tube are connected in series to the input On the power supply, the resonant network is connected between the middle node of the first primary winding and the second primary winding and the connection node between the first switching tube and/or the second switching tube and the input power supply, and the first inductor is connected across the first On the primary winding, the second inductor is connected across the second primary winding, the first clamping device and the second clamping device respectively provide reset paths for the first primary winding and the second primary winding, and the first switching tube The phase of the second switching tube is staggered. The invention has working efficiency, avoids the danger of through-through, and has good reliability.
Description
Technical field
The present invention relates to a kind of supply convertor.
Background technology
Fig. 1 is the structural representation of existing two-transistor forward converter, and two switching tube S1, S2 of this converter are conducting simultaneously not, and is straight-through dangerous, the reliability height, but switching tube S1, S2 are difficult for the soft switch of realization, and this transducer effciency is low, and volume is big.Fig. 2 is the structural representation of existing half-bridge LLC converter, and this converter has the efficient height, the advantage that volume is little, and switching tube S1, S2 can be operated in soft on off state, but because switching tube has straight-through danger, reliability is not high enough.
Summary of the invention
The present invention is exactly in order to overcome above deficiency, has proposed a kind of efficient height, supply convertor that reliability is high.
Technical problem of the present invention is solved by following technical scheme: a kind of supply convertor, comprise first transformer, first clamping device, second clamping device, first switching tube, the second switch pipe, described first transformer comprises the first former limit winding and the first secondary winding, also comprise second transformer, first inductance, second inductance and resonant network, described second transformer comprises the second former limit winding, the second secondary winding, described first switching tube, the first former limit winding, the second former limit winding, after connecting successively, the second switch pipe is connected across on the input power supply of supply convertor, described first inductance is connected across on the first former limit winding, described second inductance is connected across on the second former limit winding, described first clamping device is connected between the input power supply of the first former limit winding and supply convertor, described second clamping device is connected between the input power supply of the second former limit winding and supply convertor, and described first clamping device and second clamping device are respectively the first former limit winding and the second former limit winding provides reset paths; Described resonant network comprises resonant inductance, first resonant capacitance, and described resonant inductance first end is connected to the intermediate node of the first former limit winding and the second former limit winding, and second end links to each other with the input power supply positive output end of supply convertor through first resonant capacitance.
Preferably, described resonant inductance second end also links to each other with the input power-output of supply convertor through second resonant capacitance.
Described first clamping device is a diode, and its anode links to each other with the input power-output of supply convertor, and its negative electrode links to each other by the positive output end of described first switching tube with the input power supply of supply convertor; Described second clamping device is a diode, and its negative electrode links to each other with the input power supply positive output end of supply convertor, and its anode links to each other by the negative output terminal of described second switch pipe with the input power supply of supply convertor.
Described first switching tube and second switch pipe alternately turn on and off.
The input power supply of described supply convertor also comprises regulating circuit, and described regulating circuit detects the corresponding adjusting of output voltage of supply convertor and imports the voltage that power supply is exported.
Described first inductance and second inductance are respectively the magnetizing inductance of the first limit winding and the magnetizing inductance of the second former limit winding.
Also comprise first rectifying device, second rectifying device and filtering device, the described first secondary winding, the output of the second secondary winding are connected on the filtering device after first and second rectifying device rectification respectively.Also comprise first rectifying device, second rectifying device and filtering device, the described first secondary winding, the output of the second secondary winding are connected on the filtering device after first and second rectifying device rectification respectively.
Described first clamping device is connected between the input power-output of first former limit winding one end and supply convertor, and described second clamping device is connected between the input power supply positive output end of second former limit winding one end and supply convertor.
Also comprise the 3rd transformer, the 4th transformer, the 3rd clamping device, the 4th clamping device, the 3rd switching tube, the 4th switching tube, the 3rd inductance, the 4th inductance and second resonant network, described the 3rd transformer comprises the 3rd former limit winding and the 3rd secondary winding, described the 4th transformer comprises the 4th former limit winding and fourth officer limit winding, described the 3rd switching tube, the 3rd former limit winding, after connecting successively, the 4th former limit winding and the 4th switching tube be connected across on the input power supply of supply convertor, described second resonant network is connected between the connected node of input power supply of the intermediate node of the 3rd former limit winding and the 4th former limit winding and the 3rd switching tube and/or the 4th switching tube and supply convertor, described the 3rd inductance is connected across on the 3rd former limit winding, described the 4th inductance is connected across on the 4th former limit winding, described the 3rd clamping device is connected between the input power supply of the 3rd former limit winding and supply convertor, described the 4th clamping device is connected between the input power supply of the 4th former limit winding and supply convertor, described the 3rd clamping device and the 4th clamping device are respectively the 3rd former limit winding and the 4th former limit winding provides reset paths, described the 3rd switching tube and the 4th switching tube alternately turn on and off, described first switching tube, the 3rd switching tube, the second switch pipe is identical with the switching frequency of the 4th switching tube, described first switching tube and the 3rd switching tube turn on and off the 0-1/4 switch periods that staggers, described second switch pipe and the 4th switching tube turn on and off the 0-1/4 switch periods that staggers.
The beneficial effect that the present invention is compared with the prior art is: supply convertor of the present invention combines the advantage of two-transistor forward converter and half-bridge LLC converter, the device operating state is similar to half-bridge LLC converter on the one hand, high efficiency, connect with switching tube owing to transformer simultaneously, avoided straight-through danger, the reliability height.
Description of drawings
Fig. 1 is the structural representation of existing two-transistor forward converter;
Fig. 2 is the structural representation of existing half-bridge LLC converter;
Fig. 3 is the structural representation of the specific embodiment of the invention one;
Fig. 4 is the work wave schematic diagram of the specific embodiment of the invention one;
Fig. 5 is the current direction schematic diagram that the specific embodiment of the invention one is operated in the phase I;
Fig. 6 is the current direction schematic diagram that the specific embodiment of the invention one is operated in second stage;
Fig. 7 is the current direction schematic diagram that the specific embodiment of the invention one is operated in the phase III;
Fig. 8 is the current direction schematic diagram that the specific embodiment of the invention one is operated in the quadravalence section;
Fig. 9 is the current direction schematic diagram that the specific embodiment of the invention one is operated in five-stage;
Figure 10 is the current direction schematic diagram that the specific embodiment of the invention one was operated in for the 6th stage;
Figure 11 is the current direction schematic diagram that the specific embodiment of the invention one was operated in for the 7th stage;
Figure 12 is the current direction schematic diagram that the specific embodiment of the invention one was operated in for the 8th stage;
Figure 13 is the current direction schematic diagram that the specific embodiment of the invention one was operated in for the 9th stage;
Figure 14 is the current direction schematic diagram that the specific embodiment of the invention one was operated in for the tenth stage;
Figure 15 is the parameter schematic diagram relatively of the switching tube of the switching tube of the specific embodiment of the invention one and existing half-bridge LLC converter;
Figure 16 is that the current ratio of resonant inductance of the resonant inductance of the specific embodiment of the invention one and existing half-bridge LLC converter is than schematic diagram;
Figure 17 is that the current ratio of former limit winding of the former limit winding of the specific embodiment of the invention one and existing half-bridge LLC converter is than schematic diagram;
Figure 18 is that the current ratio of rectifying device of the rectifying device of the specific embodiment of the invention one and existing half-bridge LLC converter is than schematic diagram;
Figure 19 is that the voltage ratio of rectifying device of the rectifying device of the specific embodiment of the invention one and existing half-bridge LLC converter is than schematic diagram;
Figure 20 is the structural representation of the specific embodiment of the invention two;
Figure 21 is the structural representation of the specific embodiment of the invention three;
Figure 22 is the structural representation of the specific embodiment of the invention four;
Figure 23 is the structural representation of the specific embodiment of the invention five;
Figure 24 is the structural representation of the specific embodiment of the invention six.
Embodiment
Also in conjunction with the accompanying drawings the present invention is described in further details below by concrete execution mode.
Embodiment one
As shown in Figure 3, a kind of supply convertor comprises the first transformer T1, the second transformer T2, the first clamping device D4, the second clamping device D3, the first switching tube S1, second switch pipe S2, resonant inductance Lr, the first resonant capacitance Cr1, the second resonant capacitance Cr2, the first inductance L m1, the second inductance L m2, the first rectifying device D1, the second rectifying device D2 and filtering device C1.The described first transformer T1 comprises the first former limit winding, the first secondary winding, and the described second transformer T2 comprises the second former limit winding, the second secondary winding.The described first resonant capacitance Cr1, the second resonant capacitance Cr2 and resonance inductance L r form resonant network.
Be connected across after the described first switching tube S1, the first former limit winding, the second former limit winding and the second switch pipe S2 series connection on the input power supply Vin.The phase shifting of described first switching tube S1 and second switch pipe S2, the angle that staggers can be 0 degree-180 degree; Preferably, the first switching tube S1 and second switch pipe S2 alternation, i.e. both phase shifting 180 degree.The described first clamping device D4 is connected between the first former limit winding and the input power supply Vin, and the described second clamping device D3 is connected between the second former limit winding and the input power supply Vin.The described first clamping device D4 is a diode, and its anode links to each other with the negative output terminal of input power supply, and its negative electrode links to each other with the positive output end of input power supply by the described first switching tube S1; The described second clamping device D3 is a diode, and its negative electrode links to each other with the positive output end of input power supply, and its anode links to each other with the negative output terminal of input power supply by described second switch pipe S2.
The described first clamping device D4 and the second clamping device D3 are respectively the first former limit winding and the second former limit winding provides reset paths, and its principle that resets is identical with two-transistor forward converter.The described first resonant capacitance Cr1 be connected across input power supply Vin after the second resonant capacitance Cr2 is connected on, described resonant inductance Lr one end is connected to the first former limit winding and the second former limit winding intermediate node, and the other end is connected between the first resonant capacitance Cr1 and the second resonant capacitance Cr2.
The described first inductance L m1 is connected across on the first former limit winding, and the described second inductance L m2 is connected across on the second former limit winding.The described first inductance L m1 can be the magnetizing inductance of the first former limit winding, also can be external independent inductance, and the described second inductance L m2 can be the magnetizing inductance of the second former limit winding, also can be external independent inductance.Preferably, the first inductance L m1 and the second inductance L m2 are magnetizing inductance (promptly be integrated in the first transformer T1 and the second transformer T2 in), the component number that can deperm like this, thus reduce the volume of supply convertor of the present invention.
The described first secondary winding, the output of the second secondary winding are connected on the filtering device C1 after the first rectifying device D1, the second rectifying device D2 rectification respectively.The described first rectifying device D1 is first diode, and the described second rectifying device D2 is second diode, and described filtering device C1 is a filter capacitor.Described first diode anode links to each other with the first secondary winding in-phase end, and negative electrode links to each other with filter capacitor, and described second diode anode links to each other with the second secondary winding in-phase end, and negative electrode links to each other with filter capacitor.
As shown in Figure 4, we analyze the course of work of above-mentioned supply convertor, analyze for convenient, we suppose the capacity identical (Cr1=Cr2) of the first resonant capacitance Cr1 and the second resonant capacitance Cr2, the sensibility reciprocal of the first inductance L m1 and the second inductance L m2 identical (Lm1=Lm2), the first transformer T1 and the second transformer T2 are identical, and be desirable transformer, the capacity of filter capacitor C1 is enough big, and the first switching tube S1 and second switch pipe S2 comprise parasitic capacitance and parasitic diode in parallel respectively.In Fig. 4, I (Lm1), I (Lm2) are respectively the electric currents that flows through the first inductance L m1, the second inductance L m2, I (Tp1), I (Tp2) are respectively the electric currents that flows through the first former limit winding, the second former limit winding, and V (S1-drive), V (S2-drive) are respectively the driving voltages of the first switching tube S1, second switch pipe S2; I (D1), I (D2) are respectively the electric currents by the first rectifier diode D1, the second rectifier diode D2; I (Lr) then is the electric current by resonant inductance Lr.The course of work of above-mentioned supply convertor comprised as the next stage:
Phase I: shown in Fig. 4,5, begin to finish to the t1 moment (electric current corresponding to second switch pipe S2 is 0) from the t0 moment (S2 is open-minded corresponding to the second switch pipe).This stage is wiped the inductance L r that shakes, the first inductance L m1, and the second inductance L m2, the first resonant capacitance Cr1, the second resonant capacitance Cr2 participates in resonance.Because the first inductance L m1 and the second inductance L m2 are equivalent to by connecting with resonant inductance Lr after the first clamping device D4 and the second switch pipe S2 parallel connection again, the equivalent inductance of resonance is Lr+Lm/2, and the first rectifier diode D1 and the second rectifier diode D2 kept turn-offing in this stage.
Second stage: shown in Fig. 4,6, begin to finish to the t2 moment (electric current corresponding to resonant inductance Lr is 0) from the t1 moment (electric current corresponding to second switch pipe S2 is 0).Voltage in this stage on the second inductance L m2 is output voltage clamp, and the electric current on the second inductance L m2 is linear to be increased, and the electric current of the first inductance L m1 is linear to descend, and the electric current of the first inductance L m1, two slopes that descend are identical with electric current increase slope on the second inductance L m2.This stage interior resonance inductance L r, the first resonant capacitance Cr1, the second resonant capacitance Cr2 participates in resonance.
Phase III: shown in Fig. 4,7, begin to finish to the t3 moment (electric current corresponding to the first inductance L m1 is 0) from the t2 moment (corresponding to the electric current 0 of resonant inductance Lr).This stage and difference on last stage are: at resonant inductance Lr, the first resonant capacitance Cr1, the second resonant capacitance Cr2 participates under the situation of resonance, and the electric current on the resonant inductance Lr reduces again after being increased to maximum gradually.
The quadravalence section: shown in Fig. 4,8, t3 (electric current corresponding to the first inductance L m1 is 0) constantly begins (to turn-off) end constantly corresponding to second switch pipe S2 to t4.The first clamping device D4 turn-offs in this stage, and resonant inductance Lr, the first resonant capacitance Cr1 and the second resonant capacitance Cr2 continue to keep resonance, and the electric current on the second inductance L m2 continues linear increasing.The parasitic capacitance generation resonance of the first inductance L m1 and the first switching tube S1, the voltage on the first switching tube S1 descends.We know in half-bridge LLC converter shown in Figure 2, realize soft switch thereby resonance occurs between the parasitic capacitance of Lr and switching tube, and Lm is bigger than Lr usually.Therefore supply convertor of the present invention needs the voltage of chien shih switching tube when longer to drop to enough low.
Five-stage: shown in Fig. 4,9, from t4 constantly (turn-off) corresponding to second switch pipe S2 begin to t5 constantly (open-minded) corresponding to the first switching tube S1 finish.Two switching tubes all are in off state in this stage.The second clamping device D3 is open-minded in this stage, and the electric current on the second inductance L m2 descends, and the second rectifier diode D2 turn-offs.The resonance of the parasitic capacitance of the first inductance L m1 and the first switching tube S1 continues to keep, and the voltage of the first switching tube S1 continues to descend.
At above-mentioned the 4th, five-stage, the minimum voltage of the first switching tube S1 is not 0 generally speaking, if the transfer ratio of transformer (turn ratio) is N, output voltage is Vout, then the electric current of the first inductance L m1 reaches minimum when the first switching tube S1 voltage equals N*Vout, and the minimum voltage of the first switching tube S1 is provided by following formula: and Vs1=Vin-2 (N * Vout).In modular design, Vout is more lower slightly than Vin/ (2N), so Vs1 can omit height a bit than 0.
The 6th stage: shown in Fig. 4,10, begin constantly to finish constantly to t6 from t5.The course of work and the phase I in this stage are similar.
The 7th stage: shown in Fig. 4,11, begin constantly to finish constantly to t7 from t6.The course of work and the second stage in this stage are similar.
The 8th stage: shown in Fig. 4,12, begin constantly to finish constantly to t8 from t7.The course of work and the phase III in this stage are similar.
The 9th stage: shown in Fig. 4,13, begin constantly to finish constantly to t9 from t8.The course of work and the quadravalence section in this stage are similar.
The tenth stage: shown in Fig. 4,14, begin constantly to finish constantly to t10 from t9.The course of work and the five-stage in this stage are similar.
By above-mentioned analysis as can be known, the course of work of supply convertor of the present invention is similar to half-bridge LLC converter shown in Figure 2, the first switching tube S1, second switch pipe S2 open under the voltage low like this near Vin-2N * Vout, and the cut-off current of the first switching tube S1, second switch pipe S2 is that the electric current converted of full load is much smaller than load, has reduced switching loss.Simultaneously, the electric current of output rectifier diode is reduced to zero and also keeps turn-offing, and does not have reverse-recovery problems, makes that the switching loss of whole supply convertor is very little.
To be described further effect of the present invention by experiment below.
Compare (to simplify the analysis, we connect ideal diode as the output rectifier diode with the 150V Schottky tube) with half-bridge LLC converter shown in Figure 2: we have carried out emulation to two kinds of supply convertors respectively, and simulated conditions sees Table 1
Table 1
| Project | Supply convertor of the present invention | Project | Half-bridge LLC converter |
| Vin | 400V | Vin | 400V |
| S1，S2 | IRFP460 | S1，S2 | IRFP460 |
| Lm1，Lm2 | 400uH | Lm | 200uH |
| Lr | 30uH | Lr | 30uH |
| Cr1，Cr2 | 46nF | Cr | 92nF |
| D3，D4 | MUR460 |
| Project | Supply convertor of the present invention | Project | Half-bridge LLC converter |
| The turn ratio (Turn rate) | 4∶1 | The turn ratio (Turn rate) | 4∶1 |
| Switching frequency (Switching frequency) | 100kHz | Switching frequency (Switching frequency) | 100kHz |
| Load | 2.2ohm | Load | 2.2ohm |
| D1，D2 | Schottky tube series connection ideal diode | D1，D2 | Schottky tube series connection ideal diode |
As shown in figure 15, both switching tube waveforms are comparatively similar, and the output voltage that emulation obtains supply convertor of the present invention is that 46.95V, peak current are 9.57A, and the output voltage of half-bridge LLC converter is that 47.62V, peak current are 8.8A.The switch tube voltage of supply convertor of the present invention descends slowlyer, and the voltage when its switching tube is opened is 90V rather than 0, and when the switch tube voltage of half-bridge LLC converter is opened is 0V.Even so the switching tube loss of supply convertor of the present invention has only 5.73W, and the switching tube loss of half-bridge LLC converter is 4.87W, and both are more or less the same.
As shown in figure 16, supply convertor of the present invention is very similar with the electric current of the resonant inductance of half-bridge LLC converter.Current peak of the resonant inductance of supply convertor of the present invention (peak current) and effective value (RMS) are respectively 9.13A and 6.49A, and current peak of the resonant inductance of half-bridge LLC converter (peak current) and effective value (RMS) are respectively 8.8A and 6.3A.
As shown in figure 17, the primary impedance Rp that supposes primary impedance Rp1, the Rp2 of supply convertor of the present invention and half-bridge LLC converter satisfies: Rp1=Rp2=2Rp, the loss of then former limit relatively be: former limit loss=2* (the 2*4.952)/6.32=2.47 of former limit loss of the present invention/half-bridge LLC converter.
As shown in figure 18, the current waveform of the rectifying device (output diode) of supply convertor of the present invention and half-bridge LLC converter almost is the same.
Figure 19 is that the voltage waveform of the rectifying device (output diode) of supply convertor of the present invention and half-bridge LLC converter compares schematic diagram, the voltage of the output diode of supply convertor of the present invention is 143.08V, and is bigger than the voltage of the output diode of half-bridge LLC converter.Supply convertor of the present invention can use 200V Schottky (schottky) diode, and can use the 150Vschottky diode among the LLC.Emulation obtains the second clamping device D3 of supply convertor of the present invention and the power of the first clamping device D4 is 0.37W.
Relatively see Table 2 from what top emulation can obtain loss
| Project | Supply convertor of the present invention | Half-bridge LLC converter |
| The power loss of S1 (AVE) | 5.73W | 4.87W |
| The power loss of S2 (AVE) | 5.73W | 4.87W |
| The power loss of D1 | 17.07W (diode：0.8V) | 15.15W (diode：0.7V) |
| The power loss of secondary | 2W | 2W (hypothesis) |
| The power loss on former limit | 4.94W | 2W (hypothesis) |
| The power loss of magnetic core of transformer (Power loss of Transformer core) | 4W (hypothesis) | 4W (hypothesis) |
| The power loss of D3, D4 | 0.74W | 0 |
| The power loss of Lr | 2W (hypothesis) | 2W (hypothesis) |
| Total-power loss | 42.21W | 34.89W |
| Gross output | 1002.3W | 1030.9W |
| Efficient | 95.79％ | 96.62％ |
Under the situation of identical parameters,, but still has 95.79% high efficiency as can be seen from the above table though the efficient of supply convertor of the present invention is lower by 0.83% than the efficient of half-bridge LLC converter.Below supply convertor of the present invention is led directly to analysis: output is equivalent to directly receive electric capacity and does not receive inductance in supply convertor of the present invention, may someone will still to worry the problem that leads directly to, and we discuss by logical example.
When the first switching tube S1 and second switch pipe S2 conducting simultaneously, their electric current can be represented by following formula: Is=(Vin-2*N*Vo)/(2Lp) * ts, Is is the electric current that the first switching tube S1 and second switch pipe S2 conducting simultaneously produce in the formula, Vin is an input supply voltage), N is the transformer turn ratio, Vo is an output voltage, and Lp is the former limit of a transformer leakage inductance, and ts is the time of the first switching tube S1 and second switch pipe S2 conducting simultaneously.
Suppose that the former limit of transformer leakage inductance is 4uH, can obtain the electric current under the different straight-through times:
If ts=100ns, Is=0.31A;
If ts=200ns, Is=0.61A;
If ts=2.5us, Is=7.63A;
If ts=5.0us, Is=15.3A.
Because the switching frequency of switching tube is 100kHz, ts=5us, even this means conducting always in the first switching tube S1 and half switch periods of second switch pipe S2, and the peak current that increases also has only 15.3A.
Based on the above discussion as can be known, supply convertor of the present invention can bear two switching tubes of chien shih conductings simultaneously when sufficiently long, thereby has solved straight-through problem.
Switching tube in the supply convertor of the present invention is worked as switching tube and diode in the half-bridge LLC converter with diode.Though the efficient of supply convertor of the present invention is more lower slightly than half-bridge LLC converter, but still belong to high efficiency.It is straight-through dangerous that supply convertor of the present invention can be avoided, the reliability height.
Embodiment two
As shown in figure 20, this embodiment is with the difference of embodiment one: this embodiment is merged into a resonant capacitance Cr with the first resonant capacitance Cr1, the second resonant capacitance Cr2, and this resonant capacitance Cr is connected between ground (input power supply negative terminal) and the resonant inductance Lr.The components and parts of the required use of this embodiment are few, and operation principle and embodiment one are basic identical, and the main distinction is to flow through the electric current difference of power supply Vin, and this embodiment has reduced device, but it is big to flow through the ripple current of power supply Vin.
Embodiment three
As shown in figure 21, this embodiment is with the difference of embodiment two:
The resonant capacitance Cr of this embodiment is connected between input power positive end and the resonant inductance Lr.
The components and parts of the required use of this embodiment are few, and cost is low.
Embodiment four
As shown in figure 22, this embodiment is with the difference of embodiment one: the input power supply of this embodiment also comprises regulating circuit, and described regulating circuit detects the voltage that the corresponding adjusting input of output voltage power supply is exported.So just can make the frequency of switching tube keep constant substantially, make it be operated in that (Lr Cr1+Cr2) on the frequency, thereby raises the efficiency, reduces loss near resonance.
In this embodiment, because the frequency of switching tube is constant substantially, the frequency that can select to close pipe is for very near resonance frequency, when input voltage or output current variation, by regulating circuit the voltage that outputs to forward converter is changed on the contrary, thereby make output voltage voltage stabilizing required voltage.Because operating frequency is near resonance frequency and constant substantially, very near sinusoidal wave, switching loss is also very little simultaneously, thereby makes transformer obtain very high efficient for resonance current.
Embodiment five
As shown in figure 23, this embodiment is with the difference of embodiment one: this embodiment is equivalent to the supply convertor of two embodiments one in parallel, and two embodiments can reduce input, output ripple.
The supply convertor of this embodiment also comprises the 3rd transformer T11, the 4th transformer T21, the 3rd clamping device D41, the 4th clamping device D31, the 3rd switching tube S11, the 4th switching tube S21, the 3rd inductance L m11, the 4th inductance L m21 and second resonant network, described the 3rd transformer T11 comprises the 3rd former limit winding and the 3rd secondary winding, described the 4th transformer T21 comprises the 4th former limit winding and fourth officer limit winding, described the 3rd switching tube S11, the 3rd former limit winding, be connected across on the input power supply after the 4th former limit winding and the 4th switching tube S21 series connection, described second resonant network is connected intermediate node and the 3rd switching tube S11 and/or the 4th switching tube S21 of the 3rd former limit winding and the 4th former limit winding and imports between the connected node of power supply, described the 3rd inductance L m11 is connected across on the 3rd former limit winding, described the 4th inductance L m21 is connected across on the 4th former limit winding, described the 3rd clamping device D41 is connected between the 3rd former limit winding and the input power supply, described the 4th clamping device D31 is connected between the 4th former limit winding and the input power supply, described the 3rd clamping device D41 and the 4th clamping device D31 are respectively the 3rd former limit winding and the 4th former limit winding provides reset paths, the operating frequency of described the 3rd switching tube S11 and the 4th switching tube S21 is identical with second switch pipe S2 with the first switching tube S1, described the 3rd switching tube S11 and the 4th switching tube S21 alternately turn on and off, the described first switching tube S1, the 3rd switching tube S11, second switch pipe S2 is identical with the switching frequency of the 4th switching tube S21, described first switching tube S1 and the 3rd switching tube S11 0-1/4 switch periods that staggers, described second switch pipe S2 and the 4th switching tube S21 0-1/4 switch periods that staggers, preferred 1/4 switch periods, thus the degree that ripple is reduced is the highest.
Because two forward converters current waveform separately is near half-sine wave, if staggered 90 degree are in parallel, when one road output current was maximum, another road output current was 0 or near 0, thereby the output ripple electric current is reduced greatly.Similarly, the ripple current of input current also reduces greatly.Ripple current reduce favourable input and output filtering.
Embodiment six
As shown in figure 24, this embodiment is with the difference of embodiment five: the input power supply of this embodiment also comprises regulating circuit, and described regulating circuit detects the voltage that the corresponding adjusting input of output voltage power supply is exported.So just can make the frequency of switching tube keep constant substantially, make it be operated in that (Lr Cr1+Cr2) on the frequency, thereby raises the efficiency, reduces loss near resonance.
Above content be in conjunction with concrete preferred implementation to further describing that the present invention did, can not assert that concrete enforcement of the present invention is confined to these explanations.For the general technical staff of the technical field of the invention, without departing from the inventive concept of the premise, can also make some simple deduction or replace, all should be considered as belonging to protection scope of the present invention.
Claims (9)
1. supply convertor, comprise first transformer (T1), first clamping device (D4), second clamping device (D3), first switching tube (S1), second switch pipe (S2), described first transformer (T1) comprises the first former limit winding and the first secondary winding, it is characterized in that: also comprise second transformer (T2), first inductance (Lm1), second inductance (Lm2) and resonant network, described second transformer (T2) comprises the second former limit winding, the second secondary winding, described first switching tube (S1), the first former limit winding, the second former limit winding, after connecting successively, second switch pipe (S2) is connected across on the input power supply of supply convertor, described first inductance (Lm1) is connected across on the first former limit winding, described second inductance (Lm2) is connected across on the second former limit winding, described first clamping device (D4) is connected between the input power supply of the first former limit winding and supply convertor, described second clamping device (D3) is connected between the input power supply of the second former limit winding and supply convertor, and described first clamping device (D4) and second clamping device (D3) are respectively the first former limit winding and the second former limit winding provides reset paths; Described resonant network comprises resonant inductance (Lr), first resonant capacitance (Cr1), described resonant inductance (Lr) first end is connected to the intermediate node of the first former limit winding and the second former limit winding, and second end links to each other with input power supply positive output end through first resonant capacitance (Cr1).
2. supply convertor according to claim 1 is characterized in that: described resonant inductance (Lr) second end also links to each other with the input power-output of supply convertor through second resonant capacitance (Cr2).
3. supply convertor according to claim 1, it is characterized in that: described first clamping device (D4) is a diode, its anode links to each other with the input power-output of supply convertor, and its negative electrode links to each other with the input power supply positive output end of supply convertor by described first switching tube (S1); Described second clamping device (D3) is a diode, and its negative electrode links to each other with the input power supply positive output end of supply convertor, and its anode links to each other with input power-output by described second switch pipe (S2).
4. supply convertor according to claim 3 is characterized in that: described first switching tube (S1) and second switch pipe (S2) alternately turn on and off.
5. supply convertor according to claim 1 is characterized in that: the input power supply of described supply convertor also comprises regulating circuit, and described regulating circuit detects the output voltage of supply convertor, the voltage that corresponding adjusting input power supply is exported.
6. according to the arbitrary described supply convertor of claim 1 to 5, it is characterized in that: described first inductance (Lm1) and second inductance (Lm2) are respectively the magnetizing inductance of the first former limit winding and the magnetizing inductance of the second former limit winding.
7. according to the arbitrary described supply convertor of claim 1 to 5, it is characterized in that: also comprise first rectifying device (D1), second rectifying device (D2) and filtering device (C1), the described first secondary winding, the second secondary winding are exported respectively through being connected on the filtering device (C1) after first and second rectifying device rectification.
8. according to the arbitrary described supply convertor of claim 1 to 5, it is characterized in that: described first clamping device (D4) is connected between the input power-output of first former limit winding one end and supply convertor, and described second clamping device (D3) is connected between the input power supply positive output end of second former limit winding one end and supply convertor.
9. according to the arbitrary described supply convertor of claim 2 to 5, it is characterized in that: also comprise the 3rd transformer (T11), the 4th transformer (T21), the 3rd clamping device (D41), the 4th clamping device (D31), the 3rd switching tube (S11), the 4th switching tube (S21), the 3rd inductance (Lm11), the 4th inductance (Lm21) and second resonant network, described the 3rd transformer (T11) comprises the 3rd former limit winding and the 3rd secondary winding, described the 4th transformer (T21) comprises the 4th former limit winding and fourth officer limit winding, described the 3rd switching tube (S11), the 3rd former limit winding, after connecting successively, the 4th former limit winding and the 4th switching tube (S21) be connected across on the input power supply of supply convertor, described second resonant network is connected between the connected node of input power supply of the intermediate node of the 3rd former limit winding and the 4th former limit winding and the 3rd switching tube (S11) and/or the 4th switching tube (S21) and supply convertor, described the 3rd inductance (Lm11) is connected across on the 3rd former limit winding, described the 4th inductance (Lm21) is connected across on the 4th former limit winding, described the 3rd clamping device (D41) is connected between the input power supply of the 3rd former limit winding and supply convertor, described the 4th clamping device (D31) is connected between the input power supply of the 4th former limit winding and supply convertor, described the 3rd clamping device (D41) and the 4th clamping device (D31) are respectively the 3rd former limit winding and the 4th former limit winding provides reset paths, described the 3rd switching tube (S11) and the 4th switching tube (S21) alternately turn on and off, described first switching tube (S1), the 3rd switching tube (S11), second switch pipe (S2) is identical with the switching frequency of the 4th switching tube (S21), described first switching tube (S1) and the 3rd switching tube (S11) turn on and off the 0-1/4 switch periods that staggers, described second switch pipe (S2) and the 4th switching tube (S21) turn on and off the 0-1/4 switch periods that staggers.
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| CN200710075763A CN101132151B (en) | 2007-08-15 | 2007-08-15 | a power converter |
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| CN200710075763A CN101132151B (en) | 2007-08-15 | 2007-08-15 | a power converter |
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| CN101132151B true CN101132151B (en) | 2010-05-26 |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN101860235B (en) * | 2010-05-04 | 2013-01-09 | 华为技术有限公司 | Magnetic integration transfer circuit system |
| CN102769381A (en) * | 2012-07-04 | 2012-11-07 | 中国科学院光电研究院 | A soft-switching dual-transistor forward switching power supply circuit based on magnetic switches |
| CN103760401A (en) * | 2014-01-17 | 2014-04-30 | 西安理工大学 | System and method for testing leakage current of zinc oxide arrester |
| US9509220B2 (en) * | 2014-01-24 | 2016-11-29 | Texas Instruments Incorporated | Bi-modal voltage converter |
| TWI559667B (en) * | 2015-12-08 | 2016-11-21 | 財團法人工業技術研究院 | Soft-switching auxiliary circuit |
| CN105553272A (en) * | 2015-12-09 | 2016-05-04 | 燕山大学 | Straight-through prevention half-bridge LLC resonance converter |
| US10003275B2 (en) * | 2016-11-11 | 2018-06-19 | Texas Instruments Incorporated | LLC resonant converter with integrated magnetics |
| KR102020648B1 (en) | 2017-05-26 | 2019-09-11 | 주식회사 솔루엠 | Transformer and LLC Resonant Converter having the same |
| CN111884510B (en) * | 2019-09-29 | 2022-02-11 | 株洲中车时代电气股份有限公司 | Gain frequency modulation method and related device |
| CN118889856A (en) | 2019-12-11 | 2024-11-01 | 台达电子工业股份有限公司 | Power conversion circuit and applicable power converter |
| CN113328633A (en) * | 2021-05-17 | 2021-08-31 | 国网宁夏电力有限公司电力科学研究院 | Interleaved four-channel low-current ripple LLC resonant converter |
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