CN100527644C - Radio system, radio transmitter, and radio receiver - Google Patents

Abstract

A radio system having an improved phase noise characteristic and a thereby improved communication quality, a radio transmitter, and a radio receiver. In the radio system, a radio transmitter (101) transmits a multiplexed signal so multiplexed that a pilot signal transmitted at the center frequency. A radio receiver (151) comprises an antenna (152) for receiving a radio signal from the radio transmitter (101), a distributor (159) for distributing the received signal received by the antenna (152) to two directions, a bandpass filter (160) for extracting a signal component corresponding to the pilot signal having the same center frequency as one of the distributed signals distributed by the distributor (159), a delay corrector (162) for delaying the other of the distributed signals, and a quadrature demodulator (163) for multiplying the frequency of the signal component corresponding to the pilot signal extracted by the bandpass filter (160) by the frequency of the other signal delayed by the delay corrector (162) and performing quadrature demodulation.

Description

Wireless system, wireless transmitting device and wireless receiving device

technical field

The present invention relates to a wireless system, a wireless transmitting device, and a wireless receiving device, and particularly relates to a wireless system, a wireless transmitting device, and a wireless receiving device having excellent phase noise characteristics.

Background technique

Various techniques have been conventionally used to provide wireless systems with superior phase noise characteristics. For example, Patent Document 1 discloses an example of a conventional wireless system having excellent phase noise characteristics. In this wireless system, in order to improve the phase noise characteristics, a local noise canceller as shown in FIG. 14 is included.

The operation of the local noise canceller will be described with reference to FIGS. 14 and 15 . FIG. 15 is a characteristic diagram showing the frequency characteristics of respective components of the local noise canceller shown in FIG. 14 .

The input signal is set as shown in FIG. 15A, the modulated IF signal (BST-OFDM) and the pilot carrier (PILOT) are multiplexed, and the input phase noise (thick oblique lines) is superimposed.

Here, suppose the frequency of the input pilot carrier is f _PLT , the frequency of the input signal is f _sig , and the input phase noise is θ(t), because the input phase noise θ(t) is superimposed on f _PLT and f _sig , so As follows:

f _PLT ∠θ(t)

f _sig ∠θ(t)

Next, the input signal A is distributed by the distributor 50, one of which is output to the pilot branch, and the other is output to the signal branch. In the pilot branch, one signal distributed by the distributor 50 is band-limited by a band-pass filter 51 , and only the pilot carrier component passes through to be extracted, and further limited and amplified by a limiter amplifier 52 .

At this time, the frequency characteristics of the output signal B from the bandpass filter 51 and the output signal C from the limiting amplifier 52, as shown in 15B·C, the IF signal component is eliminated, leaving only the pilot carrier component and the superimposed The input phase noise θ(t).

At this time, a delay occurs in the bandpass filter 51. If the delay time is τ _BPF1 , input phase noise θ(t-τ _BPF1 ) delayed by τ _BPF1 is superimposed on the input pilot carrier frequency f _PLT , As follows:

f _PLT ∠θ(t-τ _BPF1 )

On the other hand, in the signal branch, the local oscillation signal D is output from the local oscillation unit 60 . Here, the frequency characteristic of the local oscillation signal D output from the local oscillation unit 60 is, as shown in FIG. 15D , the signal of the local oscillation frequency (LO) and the local oscillation phase noise superimposed thereon.

则在系统内的局部振荡信号频率f_LO上叠加着系统内的局部振荡信号相位噪声如下所示：Here, suppose the frequency of the local oscillation signal in the system is f _LO , and the phase noise of the local oscillation signal in the system is

Then the phase noise of the local oscillation signal in the system is superimposed on the frequency f _LO of the local oscillation signal in the system As follows:

Next, in the signal branch, the signal output from the distributor 50 passes through the frequency converter 61, undergoes frequency conversion with the local oscillation signal D from the local oscillation unit 60, and outputs the converted signal E.

Here, the frequency characteristic of the signal E output from the frequency converter 61 includes a sum component and a difference component of the input signal A and the local oscillation signal D as shown in FIG. 15E . Therefore, the relationship between the various signal components contained in the signal E and the superimposed phase noise is as follows:

Moreover, the frequency-converted signal E is passed through the band-pass filter 62 to limit the frequency band and only the difference component is passed, thereby outputting the signal F from the band-pass filter 62. The frequency characteristic of the signal F is as shown in FIG. 15F, and the sum component of E is obtained by Elimination leaves only the differential quantities.

At this time, a delay occurs in the bandpass filter 62. If the delay time is set to τ _BPF2 , it is superimposed on the phase noise of the extracted difference component, and a delay of τ _BPF2 occurs, and each signal component included in the signal F and The relationship between the superimposed phase noise is as follows:

Next, the signal F is delayed by the delay corrector 63 so as to be equivalent to the delay time of the band-pass filter 51 of the pilot branch, and the signal G is output.

Here, regarding the delay time τ _BPF1 of the band-pass filter 51, the delay time of the band-pass filter 62 is τ _BPF2 and the delay time of the delay corrector 63 is Δt,

τ _BPF1 = τ _BPF2 +Δt

Then, the delay corrector 63 adds a delay Δt to the signal F so as to be equivalent to the delay time difference between the pilot branches so that the above formula holds.

As a result, the frequency characteristic of the signal G does not change, as shown in Fig. 15G, the relationship between each signal component contained in the signal G and the superimposed phase noise, adding a delay Δt to the phase noise is as follows:

Next, the signal G of the signal branch and the signal C of the pilot branch output from the limiting amplifier 52 are subjected to frequency conversion by the frequency converter 70 to output a signal H.

Here, the frequency characteristic of the signal H output from the frequency converter 70 is as shown in FIG. 15H , and there are a sum component and a difference component between the signal G and the signal C. Therefore, the relationship between the various signal components contained in the signal H and the superimposed phase noise is as follows:

Here, as described above, the delay corrector 63 adds a delay Δt to make the delay time difference between the signal branch and the pilot branch equivalent, so that the following expression is established,

τ _BPF1 = τ _BPF2 +Δt

Reorganize the expression so that it looks like this:

Here, if you pay attention to the difference component, you will find that the frequency of the output signal component is the frequency (f _LO ) of the local oscillation signal in the system, that is, it is constant, regardless of the frequency of the input signal. In addition, when paying attention to the pilot carrier, it will be found that the input and output of the side-band of the signal are inversely related to each other.

也就是，局部振荡信号的相位噪声

足够小时，输入的信号的相位噪声能够充分地被减轻而被输出。In addition, the phase noise of the output signal, the input phase noise θ(x) is eliminated and replaced by the phase noise of the local oscillator signal in the system

That is, the phase noise of the local oscillator signal

When it is small enough, the phase noise of the input signal can be sufficiently mitigated to be output.

Then, the signal H subjected to frequency conversion by the frequency converter 70 is band-limited by the band-pass filter 71 so that only the difference component and the signal component are passed, and a signal I is generated. The frequency characteristic of the signal I is as shown in FIG. 15I, H The sum component and the pilot carrier component in the difference component are eliminated, leaving only the signal component of the difference component. The relationship between the signal component contained in the signal I and the superimposed phase noise is as follows:

According to the principle of carrier synchronization and noise cancellation of the above-mentioned local noise canceller, even if, for example, a frequency deviation occurs in the input signal, an output signal at a frequency corresponding to a highly stable local oscillation frequency can be obtained with high frequency accuracy generated by the local oscillation unit 60 , thereby canceling the frequency deviation of the input signal.

当系统内的局部振荡信号的相位噪声

足够小时，输入的信号的相位噪声能够充分地被减轻而被输出。In addition, the phase noise of the output signal, the phase noise θ(x) superimposed on the input signal is eliminated, and only the phase noise of the local oscillation signal in the system is replaced

When the phase noise of the locally oscillating signal within the system

When it is small enough, the phase noise of the input signal can be sufficiently mitigated to be output.

[Patent Document 1] JP-A-2002-152158

Contents of the invention

The problem to be solved by the invention

However, in the conventional wireless system, the phase noise θ(x) generated in the local oscillation unit 60 is not eliminated, or the phase noise is increased according to the ratio of 20*log (integer multiple of the frequency), when the frequency of the local oscillation unit 60 When it is high, there will be a problem that the influence of the phase noise θ(x) will degrade the communication quality.

The present invention aims to provide a wireless system, a wireless transmission device, and a wireless reception device in which phase noise characteristics are improved to improve communication quality.

Solution to the problem

The structure adopted by the wireless system of the present invention includes a wireless sending device and a wireless receiving device. The wireless sending device includes: a sending unit that sends a modulated signal that does not carry a signal on a center frequency and has the same center frequency as the center frequency. The wireless signal that the pilot frequency signal of frequency carries out multiplex processing; The wireless receiving device comprises: Antenna, receives described wireless signal; Distributing unit, distributes the received signal received by antenna into two directions; Extracting unit, from described In the signal of one side allocated by the allocation unit, the signal component corresponding to the pilot signal is extracted and output; the delay addition unit is given to delay and output the signal of the other party allocated by the allocation unit; and the quadrature The demodulation unit performs frequency multiplication on the output signal of the extraction unit and the output signal of the delay addition unit, and performs quadrature demodulation.

The structure adopted by the wireless receiving device of the present invention includes: an antenna for receiving a wireless signal, the wireless signal is a modulated signal that does not carry a signal on the center frequency and a pilot signal having the same center frequency as the center frequency for multiplexing The wireless signal; the distribution unit, which distributes the received signal received by the antenna into two directions; the extraction unit, from the signal of one side distributed by the distribution unit, the signal corresponding to the pilot signal having the same center frequency as the distribution unit The components are extracted and output; the delay addition unit delays and outputs the signal of the other party allocated by the allocation unit; the quadrature demodulation unit extracts the signal components corresponding to the pilot signal extracted by the extraction unit The other signal delayed by the delay adding unit is subjected to frequency multiplication and quadrature demodulation. The quadrature demodulation unit includes: a phase shift unit, which performs a 90-degree phase shift on the signal component corresponding to the extracted pilot signal; a first frequency multiplier, which adds the delayed The signal of the other party is multiplied by the signal component corresponding to the pilot signal that has undergone the 90-degree phase shift; the second frequency multiplier performs the signal of the other party with the added delay and The signal component corresponding to the pilot signal is multiplied; and another delay addition unit is added to the signal component corresponding to the pilot signal multiplied by the second frequency multiplier, and the phase shift Bit cells produce the same delay as the delay.

In the wireless transmitting device of the present invention, the wireless transmitting device multiplexes a modulated signal that does not carry a signal on a central frequency and a pilot signal having the same central frequency as the central frequency, and transmits the multiplexed signal, using The following structure includes: a modulation signal generation unit that generates the modulation signal; a local oscillation signal generation unit that generates a local oscillation signal; an orthogonal modulation unit that uses the local oscillation signal generated by the local oscillation signal generation unit, Carrying out frequency multiplication operation on the modulation signal to increase the frequency and perform quadrature modulation; a delay adding unit, adding a delay to the local oscillation signal generated by the local oscillation signal generating unit; and a synthesizer, by The quadrature modulated signal by the quadrature modulation unit is multiplexed with the local oscillating signal as a pilot signal, and the local oscillating signal is added by the delay adding unit to make the phase of the quadrature modulated signal bit-matched delayed signals.

Beneficial Effects of the Invention

According to the present invention, it is possible to provide a wireless system, a wireless transmission device, and a wireless reception device that improve communication quality by improving phase noise characteristics.

Description of drawings

FIG. 1 is a block diagram showing the configuration of a wireless system according to Embodiment 1 of the present invention;

FIG. 2 is a characteristic diagram showing frequency characteristics of individual signals in a wireless system;

FIG. 3 is a diagram for explaining the configuration of a quadrature demodulator of the radio receiving apparatus shown in FIG. 1;

FIG. 4 is a block diagram showing the configuration of a wireless system according to Embodiment 2;

FIG. 5 is a block diagram showing the configuration of a wireless system according to Embodiment 3;

FIG. 6 is a block diagram showing the configuration of a radio system according to Embodiment 4;

7 is a block diagram showing the configuration of a wireless system according to Embodiment 5;

FIG. 8 is a block diagram showing the configuration of a wireless system according to Embodiment 6;

FIG. 9 is a diagram for explaining frequency characteristics of transmission signals of the wireless system of FIG. 8;

FIG. 10 is a block diagram showing the configuration of a radio system according to Embodiment 7;

FIG. 11 is a block diagram showing the configuration of a radio system according to Embodiment 8;

FIG. 12 is a block diagram showing the configuration of a radio system according to Embodiment 9;

FIG. 13 is a block diagram showing a configuration of a radio transmission device having a configuration different from that of the radio transmission device shown in FIG. 1;

FIG. 14 is a block diagram showing the configuration of a local noise canceller included in a conventional wireless system; and

FIG. 15 is a characteristic diagram showing the frequency characteristics of respective components of the local noise canceller of FIG. 14 .

Detailed ways

Embodiments of the present invention will be described in detail below with reference to the drawings.

(Embodiment 1)

First, a radio system according to this embodiment will be described with reference to the drawings.

FIG. 1 is a block diagram showing the configuration of a wireless system according to the present embodiment. As shown in FIG. 1 , the wireless system 100 includes a wireless transmitting device 101 and a wireless receiving device 151 .

The radio transmission device 101 includes: a transmission baseband unit 110 that generates a baseband signal; and a transmission unit 120 that performs predetermined processing on the baseband signal and transmits it as an RF signal.

In the transmitting baseband unit 110 , the modulated signal generating unit 111 generates a modulated signal and supplies it to the pilot signal combining unit 112 . In addition, although the modulated signal is described here as multi-carrier CDMA, any modulated signal can be processed as long as it does not carry a signal at the center frequency portion on the frequency axis, such as an OFDM signal.

The pilot signal combining section 112 combines the modulated signal (M-CDMA) obtained from the modulated signal generating section 111 and the pilot signal (PILOT) obtained from the pilot signal generating section 113 , and supplies them to the transmitting section 120 .

In addition, the pilot signal is located at the center of the frequency axis of the modulated signal, and the frequency of the pilot signal is f _PILOT , where f _PILOT =0 [Hz].

On the other hand, in transmission unit 120 , local oscillation unit 121 generates a local oscillation signal using the reference signal generated by reference signal oscillation unit 122 , and supplies it to quadrature modulator 123 .

Orthogonal modulator 123 utilizes the local oscillation signal from local oscillation unit 121 to carry out quadrature modulation on the modulated signal output from the pilot signal synthesis unit 112 of the above-mentioned transmission baseband unit 110 and the composite signal of the pilot signal, and provides it to the multiplication device 124.

Multiplier 124 converts the signal quadrature-modulated by quadrature modulation section 123 into a radio signal using the local oscillation signal obtained from local oscillation section 125 . This radio signal is amplified by amplifier 126 and then transmitted via antenna 127 . In addition, here, it is assumed that local oscillator 125 generates a local oscillator signal using the reference signal generated from reference signal oscillator 122 , and local oscillator 121 and local oscillator 125 generate local oscillator signals in synchronization.

On the other hand, in wireless receiving device 151 , antenna 152 receives a wireless signal transmitted from wireless transmitting device 101 . The received wireless signal is amplified by the amplifier 153 and supplied to the multiplier 154 .

The multiplier 154 converts the frequency of the radio signal amplified by the amplifier 153 using the local oscillation signal generated by the local oscillation unit 155 , and supplies the frequency to the bandpass filter 156 . In addition, the local oscillation unit 155 generates a local oscillation signal using the reference signal generated by the reference signal oscillation unit 157 .

The bandpass filter 156 extracts only the signal of a desired frequency band from the signal frequency-converted by the multiplier 154 . The signal extracted by the bandpass filter 156 is amplified by the amplifier 158 and supplied to the distributor 159 .

The divider 159 divides the signal obtained by the bandpass filter 156 through the amplifier 158 into two branches of a modulated signal branch and a pilot branch.

In the pilot branch, the bandpass filter 160 extracts only the pilot signal component from the signal distributed by the distributor 159 . The extracted pilot signal is amplified by amplifier 161 and supplied to quadrature demodulator 163 . Also, when the level of the input signal to the quadrature demodulator 163 is kept constant only through the pilot branch, that is, only through the amplifier 161, distortion occurs only in the pilot branch, and the quadrature demodulator 163 The output will have residual phase noise. Therefore, assuming that the input signal level supplied to the distributor 159 is Pin [dBm], the power loss from the distributor 159 is α [dB], the power loss of the bandpass filter 160 is β [dB], and the power loss of the amplifier 161 is If the gain is γ [dB], the input signal level Pin supplied to the distributor 159 is set to be approximately proportional to the output level (Pin+γ-α-β) of the amplifier 161 . As a result, distortion of the pilot branch can be prevented.

On the other hand, in the modulation signal branch, the delay corrector 162 delays the signal obtained from the distributor 159 so as to be synchronized with the signal arriving at the quadrature demodulator 163 via the pilot branch, and supplies the signal to the quadrature demodulator 163. demodulator 163 .

The quadrature demodulator 163 multiplies the signals obtained from the pilot branch and the modulated signal branch, performs quadrature demodulation, and supplies the signal to the receiving baseband unit 164 .

Next, the operation of the wireless system 100 will be described with reference to FIG. 1 and FIG. 2 .

FIG. 2 is a characteristic diagram showing the frequency characteristics of individual signals in the wireless system 100 . In addition, FIGS. 2A to 2G show the frequency characteristics of the signals in the portion in which the corresponding Roman characters are added in FIG. 1 .

Synthesized signal A of the modulated signal and the pilot signal output from baseband section 110 has the frequency characteristics shown in FIG. 2A . In addition, as described above, here the pilot signal is located at the center of the frequency axis of the modulated signal, and if the frequency of the pilot signal is f _PILOT , then f _PILOT =0 [Hz].

Synthesized signal A is frequency-converted into a radio signal by transmission unit 120 and output from antenna 127 .

The radio frequency f _RF of the modulation signal included in the radio signal output by the antenna 127, and the radio frequency f _{RF_PILOT} of the pilot signal are as follows:

f _RF =f _CDMA +f _Lo1 +f _Lo2

f _{RF_PILOT} =f _PILOT +f _Lo1 +f _Lo2

In addition, it is assumed that the frequency of the modulation signal generated by the modulation signal generation unit 111 is _fCDMA , the frequency of the local oscillation signal generated by the local oscillation unit 125 is _fLo1 , and the frequency of the local oscillation signal generated by the local oscillation unit 121 is _fLo2 .

Here, in transmission section 120, composite signal A is output as a wireless signal by superimposing phase noise of local oscillation section 121 at quadrature modulator 123 and phase noise of local oscillation section 125 at multiplier 124. In addition, phase noise is also superimposed on the wireless signal in the propagation path from the output of the antenna 127 to the reception of the antenna 152 .

Therefore, assuming that the sum of the transmitting unit 120 and the phase noise superimposed on the propagation path is θ(t), the wireless signal B received by the antenna 152 has the frequency characteristic as shown in FIG. 2B , expressed as follows:

f _RF ∠θ(t)

f _{RF_PILOT} ∠θ(t)

的局部信号，所以该局部信号具有如图2C所示的频率特性，表示如下：The radio signal B received by the antenna 152 is amplified by the amplifier 153 and subjected to frequency conversion by the multiplier 154 . Here, since the local oscillation unit 155 generates

The local signal, so the local signal has the frequency characteristics shown in Figure 2C, expressed as follows:

并提供给带通滤波器156。Therefore, the phase noise of the local oscillation unit 155 is superimposed on the frequency-converted signal by the multiplier 154

And provided to the bandpass filter 156.

The bandwidth of the bandpass filter 156 is set to the frequency of the difference output from the multiplier 154, that is, f _RF - f _Lo1 and f _{RF_PILOT} - f _Lo1 are extracted. Therefore, the signal D output from the amplifier 158 has a frequency characteristic as shown in FIG. 2D, expressed as follows:

Next, the signal D is distributed by the distributor 159, one of which is output to the modulation signal branch, and the other is output to the pilot frequency branch.

In the pilot branch, since the bandpass filter 160 is set to extract only the pilot signal component, the bandpass filter 160 extracts only the pilot signal component from the allocated signal D and outputs it.

At this time, a delay τ ₁ is superimposed on the signal D through the bandpass filter 160 and the amplifier 161 . Therefore, the output signal E of the amplifier 161 has a frequency characteristic as shown in FIG. 2E, expressed as follows:

On the other hand, in the modulated signal branch, the signal D is superimposed with a delay such that the following formula holds: Δt=τ ₁ +τ ₂ , via the delay corrector 162 . In addition, _τ2 is a delay generated inside the quadrature demodulator 163 which will be described later. Therefore, the signal F output from the delay corrector 162 has a frequency characteristic as shown in FIG. 2F, which can be represented by the following formula:

Next, the signal E and the signal F are quadrature demodulated after being multiplied by the quadrature demodulator 163 . Specifically, as shown in FIG. 3 , the quadrature demodulator 163 includes: a delay corrector 171 , a 90-degree phase shifter 172 , a multiplier 173 , and a multiplier 174 .

The signal E is input to a delay corrector 171 and a 90-degree phase shifter 172 . The 90-degree phase shifter 172 shifts the phase of the signal E by 90 degrees and outputs it to the multiplier 174 . At this time, a delay τ ₂ occurs in the 90-degree phase shifter 172 .

The delay corrector 171 performs correction so that the signal E is delayed by the same delay τ ₂ as that produced by the 90-degree phase shifter 172 .

The signal F is input to the multiplier 173 and the multiplier 174 , multiplied by the output signals from the delay corrector 171 and the 90-degree phase shifter 172 , and a signal G is output. Since the signal F is corrected by the delay corrector 162 in consideration of the delay amount _τ2 inside the quadrature demodulator 163, the phases of the signals multiplied by the multiplier 173 and the multiplier 174 match. Therefore, ideal demodulation can be performed.

Therefore, the signal G output from the quadrature demodulator 163 has a frequency characteristic as shown in FIG. 2G, and can be represented by the following formula:

(f _RF -f _Lo1 )-(f _{RF_PILOT} -f _Lo1 )

It is sorted using the conditions of f _PILOT = 0Hz and Δt = τ ₁ + τ ₂ , as shown below:

f _CDMA∠0

This means that the phase noise superimposed on the transmitting unit 120 , the propagation path and the local oscillation unit 155 is completely eliminated, and the modulated signal generated by the modulated signal generating unit 111 is demodulated by the wireless receiving device 151 . That is, phase noise superimposed on the received signal can be eliminated, and phase noise generated in the system of the receiving wireless unit can be removed at the same time.

As described above, the wireless transmission device 101 performs multiplexing so that the pilot signal is carried on the center frequency of the transmission signal and transmits; the wireless reception device 151 performs frequency multiplication by the pilot signal having the same frequency error and phase noise as the reception signal , the phase noise that occurs in the system is also used to perform frequency multiplication by signals with the same phase noise. Thereby, the frequency error and phase error included in the received signal can be removed, and the phase error generated in the system can be completely removed, so that a wireless system with excellent phase noise characteristics can be provided.

In addition, when the pilot signal is extracted by the band-pass filter 160, since the phase noise outside the frequency band of the band-pass filter 160 cannot be extracted, the phase noise has a frequency characteristic as shown in FIG. 2G. However, this phase noise is suppressed by local oscillation unit 121 , local oscillation unit 125 , and local oscillation unit 155 .

由此能够忽略该影响。另外，局部振荡单元121以及局部振荡单元125，通过相同的处理，也能够抑制带通滤波器160的频段外的相位噪声θ(t)。For example, the local oscillation unit 155 is configured as a PLL frequency synthesizer, and the loop bandwidth is designed to be not larger than the bandwidth of the bandpass filter 160 . This can suppress the phase noise outside the pass frequency band of the bandpass filter 160 shown in Figure 2C

This influence can thus be ignored. In addition, local oscillation section 121 and local oscillation section 125 can also suppress phase noise θ(t) outside the frequency band of band-pass filter 160 by the same process.

In addition, in the present embodiment, as the local frequency oscillating in the local oscillator 155 of the radio receiving device 151, a local oscillation signal having the same frequency (f _Lo1 ) as the local oscillation signal generated by the local oscillator 125 of the radio transmitting device 101 is used. signal, but a frequency below 2×RF frequency (f _Lo1 +f _Lo2 ) and different from RF can be used. Of course, the same frequency (f _Lo2 ) as the local oscillation signal generated by the local oscillation unit 121 can also be eliminated. phase noise.

In addition, in this embodiment, the structure of the transmitting baseband unit 110 and the transmitting unit 120 is set as a superheterodyne (superheterodyne) method, as long as it can transmit the frequency axis of the modulated signal as shown in FIG. 2A. Any method is acceptable, such as direct conversion (direct conversion).

In this way, according to the first embodiment, the wireless receiving device 151 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. The wireless signal that the frequency signal is multiplexed; The distributor 159 distributes the received signal received by the antenna 152 into two directions; The bandpass filter 160, from the signal of one side distributed by the distributor 159, will have The signal component corresponding to the pilot signal of the same center frequency of the center frequency is extracted; the delay corrector 162 gives the signal of the other party allocated by the distributor 159 a delay; The signal component corresponding to the pilot signal extracted by the unit 160 and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Thus, since the received wireless signal is a wireless signal in which a modulated signal carrying no signal on the center frequency and a pilot signal having the same center frequency as the above-mentioned center frequency are multiplexed, the conventional example shown in the prior art The local oscillation unit 60 and the frequency converter 61 in the signal branch of the local noise canceller become unnecessary, and the phase noise of the local oscillation signal generated by the local oscillation unit 60 also disappears in the signal in the signal branch ( signal F) on. Thereby, the phase error generated in the system can also be completely eliminated, so that a wireless system having excellent phase noise characteristics can be realized.

Moreover, the above-mentioned quadrature demodulator 163 includes: a 90-degree phase shifter 172, which performs a 90-degree phase shift on the signal component corresponding to the pilot signal extracted by the band-pass filter 160; The corrector 162 adds the delay signal (signal E) and the signal component corresponding to the pilot signal to which the phase shift of 90 degrees has been applied; the multiplier 173 adds the delay signal (signal E) by the delay corrector 162 E) multiplying the signal components corresponding to the pilot signals extracted by the bandpass filter 160; and the delay corrector 171, adding The same delay as occurs with the 90 degree phase shifter 172 .

Thus, by appropriately setting the amount of delay added by the delay corrector 162 , it is possible to match the phase of the signal multiplied by the multiplier 173 and the multiplier 174 , thereby realizing ideal demodulation.

(Embodiment 2)

FIG. 4 is a block diagram showing the configuration of a wireless system according to the second embodiment. In addition, the only difference between the wireless receiving device 351 of the wireless system 300 shown in FIG. 4 and the wireless receiving device 151 of the wireless system 100 in the first embodiment is that a Amplifier 352, while other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

In this embodiment, comparing the modulation signal branch and the pilot signal branch, it can be found that: because the pilot signal branch has a band-pass filter 160, the NF characteristics and the C/N characteristics at the time of a weak electric field are worse than the modulation signal branch, so In wireless receiving device 351 , amplifier 352 is added between distributor 159 and bandpass filter 160 .

In the radio reception device 351 , the amplifier 352 amplifies the signal D distributed by the distributor 159 in the pilot branch, and supplies it to the bandpass filter 160 .

The bandpass filter 160 extracts only the pilot signal component from the signal amplified by the amplifier 352 . The extracted pilot signal is amplified by amplifier 161 and supplied to quadrature demodulator 163 .

In this way, by adding the amplifier 352 in the preceding stage of the bandpass filter 160, the NF characteristic of the pilot branch and the C/N characteristic at the time of a weak electric field can be improved.

In addition, a directional coupler or the like can be used to improve the isolation characteristics of the distributor 159 . In such a case, by adding an amplifier 352 between the distributor 159 and the bandpass filter 160, the NF characteristic of the pilot branch and the C/N characteristic at the time of a weak electric field can be improved.

As described above, it is possible to realize a wireless system having excellent NF characteristics of the pilot branch, C/N characteristics in a weak electric field, and excellent phase noise characteristics.

In this way, according to the second embodiment, the wireless receiving device 351 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. The wireless signal that multiplexes frequency signal; Distributor 159, distributes the received signal that receives by antenna 152 into two directions; The signal component corresponding to the pilot signal of the same center frequency is extracted; the delay corrector 162 gives the signal of the other party allocated by the distributor 159 a delay; and the quadrature demodulation unit 163 extracts the bandpass filter 160 The resulting signal component corresponding to the pilot signal and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Furthermore, an amplifier 352 is provided in the wireless receiving device 351 to amplify the signal distributed by the distributor 159 (the signal supplied to the pilot branch) and output it to the bandpass filter 160 .

In this way, since the NF characteristic of the signal (signal E) input to the quadrature demodulator 163 via the pilot branch and the C/N characteristic at the time of a weak electric field can be improved, the phase noise characteristic can be further improved.

(Embodiment 3)

FIG. 5 is a block diagram showing the configuration of a radio system according to Embodiment 3. As shown in FIG. In addition, the wireless receiving device 451 of the wireless system 400 shown in FIG. The receiving baseband unit 454 of the receiving power calculation unit 453 is provided instead of the receiving baseband unit 164, and other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

Here, when the power received by the antenna 152 changes, the power input to the amplifier 161 also changes accordingly. Also, the delay value of the delay corrector 162 cannot be determined as a single value when the delay occurring in the pilot branch varies. In this embodiment, taking this problem into consideration, variable gain amplifier 452 is added instead of amplifier 158 , and reception baseband unit 454 provided with received power calculation unit 453 is used instead of reception baseband unit 164 .

The received power calculation unit 453 calculates the power of the received signal B according to the power of the signal G output by the quadrature demodulator 163 . Also, the receiving baseband unit 454 supplies a control signal based on the calculation result to the variable gain amplifier 452 so as to control the gain. As a result, the power input to the distributor 159 can be kept constant, and as a result, the delay occurring in the pilot branch can be kept constant, so that the delay value of the delay corrector 162 can be determined as a single value.

As described above, even if the received power varies, it is possible to realize a wireless system having excellent phase noise characteristics.

In this way, according to Embodiment 3, the wireless receiving device 451 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. The wireless signal that multiplexes frequency signal; Distributor 159, distributes the received signal that receives by antenna 152 into two directions; The signal component corresponding to the pilot signal of the same center frequency is extracted; the delay corrector 162 gives the signal of the other party allocated by the distributor 159 a delay; and the quadrature demodulation unit 163 extracts the bandpass filter 160 The resulting signal component corresponding to the pilot signal and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Moreover, the wireless receiving device 451 is provided with: a received power calculation unit 453, which calculates the received power value of the received signal based on the amplitude of the output signal of the quadrature demodulator 163; and a variable gain amplifier 452 arranged in front of the distributor 159 stage, according to the calculated received power value to amplify the received signal.

Accordingly, even if the received power received by antenna 152 varies, amplification can be performed according to the received power value, and the power input to distributor 159 can be kept constant. As a result, the delay occurring in the pilot branch can be kept constant. Thereby, even if the received power changes, it is possible to prevent deterioration of the phase noise characteristics.

(Embodiment 4)

FIG. 6 is a block diagram showing the configuration of a radio system according to Embodiment 4. As shown in FIG. In addition, compared with the wireless receiving device 451 of the wireless system 400 in the third embodiment, the wireless receiving device 551 of the wireless system 500 shown in FIG. The baseband unit 554 replaces the receiving baseband unit 454, and the other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

The receiving baseband unit 554 obtains the signal G from the quadrature demodulator 163 , and calculates the power of the received signal B according to the power of the signal G through the receiving power calculation unit 453 . Furthermore, the receiving baseband unit 554 supplies control signals based on the calculation result to the variable gain amplifier 552 and the variable gain amplifier 452 so as to control the gains.

Thus, assuming that the gain variable range of the variable gain amplifier 452 is G1dB, the gain variable range of the variable gain amplifier 552 is G2dB, and the overall gain variable range of the system is (G1+G2)dB, which can correspond to a wider range The receiving level changes.

As described above, even if the received power varies over a wide range, it is possible to realize a wireless system having excellent phase noise characteristics.

(Embodiment 5)

FIG. 7 is a block diagram showing the configuration of a radio system according to Embodiment 5. As shown in FIG. In addition, the wireless receiving device 651 of the wireless system 600 shown in FIG. 453 and the receiving baseband unit 654 of the temperature delay deviation calculation unit 653 to replace the receiving baseband unit 454; the delay corrector 655 is used to replace the delay corrector 162, and other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

In this embodiment, the temperature sensing unit 652 , the temperature delay deviation calculation unit 653 and the delay corrector 655 are provided considering that the temperature-derived delay variation of the amplifier 161 causes errors in eliminating phase noise.

The reception baseband unit 654 stores the measured value of the delay variation with respect to temperature of the amplifier 161 .

The temperature delay deviation calculating unit 653 included in the receiving baseband unit 654 calculates the delay deviation based on the temperature data measured by the temperature sensing unit 652 . The receiving baseband unit 654 supplies a control signal according to the calculation result to the delay corrector 655 so as to control the delay value of the delay corrector 655 .

In addition, although the case where the temperature sensing unit 652, the temperature delay deviation calculation unit 653, and the delay corrector 655 are provided in the wireless receiving device 451 of Embodiment 3 has been described here, any of Embodiments 1 to 4 can be applied. .

As described above, it is possible to realize a wireless system with excellent phase noise characteristics even when the delay of the amplifier changes with temperature changes.

Thus, according to Embodiment 5, the wireless receiving device 651 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. The wireless signal that is multiplexed by the frequency signal; the distributor 159 distributes the received signal received by the antenna 152 into two directions; The signal components corresponding to the pilot signal of the same center frequency of the center frequency are extracted; the delay corrector 655 gives the signal of the other party allocated by the distributor 159 a delay; and the quadrature demodulation unit 163 uses the bandpass filter The signal component corresponding to the pilot signal extracted at 160 and the other signal delayed by the delay corrector 655 are subjected to frequency multiplication and quadrature demodulation.

Moreover, the wireless receiving device 651 also includes: a temperature sensing unit 652, which measures the temperature; a temperature delay deviation calculation unit 653, which calculates the delay amount based on the above-mentioned temperature; a delay corrector 655, which changes the additional delay based on the calculated above-mentioned delay amount .

Therefore, even when the delay of the amplifier of the pilot branch changes with temperature, the delay corrector 655 can correct the change of the delay, thereby matching the input signal supplied to the quadrature demodulator 163. phase, thereby improving the phase noise characteristics.

(Embodiment 6)

FIG. 8 is a block diagram showing the configuration of a radio system according to Embodiment 6. In FIG. In addition, the wireless receiving device 751 of the wireless system 700 shown in FIG. 8 is different from the wireless receiving device 151 of the wireless system 100 in Embodiment 1 only in that the quadrature demodulator 163 is replaced by a multiplier 752; The receiving baseband unit 753 is used to replace the receiving baseband unit 164, and other structures are the same. In addition, the only point that the pilot signal superimposed on the transmission signal is multiplexed near the center of the modulated signal, that is, at a frequency shifted by Δf from the center, as shown in FIG. 9 , is different from the above-mentioned embodiment. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

The multiplier 752 multiplies the signal E amplified by the amplifier 161 and the signal F delayed by the delay corrector 162 , and outputs it to the reception baseband section 753 . In addition, the band-pass filter 160 is adjusted so as to extract, from the signal distributed by the distributor 159, a pilot signal component having a frequency shifted by Δf from the above-mentioned center.

Here, the signal G output from the multiplier 752 can be expressed as follows:

$<span\; class="notranslate">\; (</span>{\mathrm{<span\; class="notranslate">\; f</span>}}_{\mathrm{<span\; class="notranslate">\; RF</span>}}<span\; class="notranslate">\; -</span>{\mathrm{<span\; class="notranslate">\; f</span>}}_{\mathrm{<span\; class="notranslate">\; Lo</span>}\mathrm{<span\; class="notranslate">\; 1</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; (</span>{\mathrm{<span\; class="notranslate">\; f</span>}}_{\mathrm{<span\; class="notranslate">\; RF</span>}<span\; class="notranslate">\; \_</span>\mathrm{<span\; class="notranslate">\; PILOT</span>}}<span\; class="notranslate">\; -</span>{\mathrm{<span\; class="notranslate">\; f</span>}}_{\mathrm{<span\; class="notranslate">\; Lo</span>}\mathrm{<span\; class="notranslate">\; 1</span>}}<span\; class="notranslate">\; )</span>$

It is sorted using the conditions of f _PILOT = 0Hz and Δt = τ ₁ + τ ₂ , as shown below:

f _CDMA +Δf∠Δθ(t-Δt)

The receiving baseband unit 753 applies predetermined processing to the output signal of the multiplier 752 to obtain a baseband signal.

Here, assuming that the frequency of Δf is lower than the RF frequency or the IF frequency, the phase noise Δθ(t-Δt) has a very small value, and thus has little influence on the receiving characteristics of the receiving baseband section 753 . Therefore, the present embodiment is very suitable for the Low-IF method or the like for demodulation using a low-frequency signal.

In this way, by multiplexing the pilot signal superimposed on the transmission signal near the center of the modulated signal and using the multiplier 752 instead of the quadrature demodulator 163, it is possible to support reception methods such as the Low-IF method. Furthermore, it is possible to realize a wireless system having excellent phase noise characteristics. In addition, this configuration is similarly applicable to each radio reception device of the radio system of Embodiment 2 to Embodiment 5.

(Embodiment 7)

FIG. 10 is a block diagram showing the configuration of a radio system according to Embodiment 7. As shown in FIG. In addition, the radio receiving device 851 of the radio system 800 shown in FIG. 853 to replace the receiving baseband unit 164; the bandwidth variable bandpass filter 854 to replace the bandpass filter 160; the PLL frequency synthesizer 855 to replace the local oscillation unit 155, while other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

The filter bandwidth control unit 852 controls the bandwidth of the bandwidth-variable bandpass filter 854 by providing a signal for controlling the bandwidth.

Thus, even when the interval between the frequency of the modulated signal and the frequency of the pilot signal is changed, the bandwidth of the variable bandwidth bandpass filter 854 can be controlled by the filter bandwidth control section 852 to extract the pilot signal.

However, since the phase noise outside the frequency band of the variable bandwidth bandpass filter 854 cannot be extracted, the phase noise suppression characteristic will deteriorate.

Then, replace the local oscillation unit 155 with the PLL frequency synthesizer 855, the filter bandwidth control unit 852 controls the loop bandwidth of the PLL frequency synthesizer 855, and the loop bandwidth is set to the bandwidth of the bandwidth variable bandpass filter 854 or If the bandwidth is lower than this bandwidth, phase noise in the frequency band of the variable bandwidth bandpass filter 854 can be suppressed.

In this manner, by controlling the bandwidth of the variable bandwidth bandpass filter 854 and the loop bandwidth of the PLL frequency synthesizer 855 , phase noise outside the frequency band of the variable bandwidth bandpass filter 854 can be suppressed. In addition, this configuration is similarly applicable to each radio reception device of the radio system of Embodiment 2 to Embodiment 6.

As described above, even when the interval between the frequency of the modulation signal and the frequency of the pilot signal is changed, it is possible to realize a wireless system having excellent phase noise characteristics. In addition, by configuring the wireless system of the present invention as described above, it is possible to adapt to a plurality of communication systems in which the frequencies of modulation signals and the frequency intervals of pilot signals are different.

In this way, according to Embodiment 7, the wireless receiving device 851 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. frequency signal multiplexed wireless signal; distributor 159, distributes the received signal received by antenna 152 into two directions; bandwidth variable bandpass filter 854, from the signal of one side distributed by distributor 159, will have The signal component corresponding to the pilot signal of the same center frequency as its center frequency is extracted; The delay corrector 162 gives the signal of the other party allocated by the distributor 159 a delay; The signal component corresponding to the pilot signal extracted by the bandpass filter 854 and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Moreover, the wireless receiving device 851 is adapted to the superheterodyne method, and further includes: a filter bandwidth control unit 852, which generates a control signal for controlling the filter bandwidth; and a PLL frequency synthesizer 855, which controls the bandwidth of the local oscillation signal based on the control signal and performs Oscillation; and the multiplier 154, which is arranged in the front stage of the distributor 159, performs frequency multiplication operation with the received signal received by the antenna 152 and the local oscillation signal whose bandwidth is controlled by the PLL frequency synthesizer 855; the bandwidth variable bandpass filter 854. Change the extracted bandwidth based on the foregoing control signal.

Thus, by controlling the bandwidth of the variable bandwidth bandpass filter 854 and the loop bandwidth of the PLL frequency synthesizer 855, phase noise outside the band of the variable bandwidth bandpass filter 854 can be suppressed, thereby improving phase noise characteristics. In addition, it is also possible to respond to a signal in which the frequency of the received modulation signal and the frequency interval of the pilot signal are different.

(Embodiment 8)

FIG. 11 is a block diagram showing the configuration of a radio system according to Embodiment 8. As shown in FIG. The radio receiving device 951 of the radio system 900 shown in FIG. 952 and variable gain amplifier 953; replace the receiving baseband unit 454 with the receiving baseband unit 954, and the other structures are the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

The receiving baseband unit 954 obtains the signal G from the quadrature demodulator 163 , and calculates the power of the received signal G through the receiving power calculation unit 453 . Furthermore, the receiving baseband unit 954 supplies control signals based on the calculation result to the variable gain amplifier 952 and the variable gain amplifier 953 so as to control the gains.

Thus, it is assumed that the gain variable range of the variable gain amplifier 452 is G1dB, the gain variable range of the variable gain amplifier 952 and the variable gain amplifier 953 is G3dB, and the gain variable range of the whole system is (G1+G3)dB , can correspond to a wider range of reception level changes.

In addition, the case where the variable gain amplifier 952 and the variable gain amplifier 953 are added to the subsequent stages of the quadrature demodulator 163 in the third embodiment has been described here, but it is also applicable to any of the fourth and fifth embodiments. .

Thus, according to the eighth embodiment, the wireless receiving device 951 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal on the center frequency and a guided signal having the same center frequency as the center frequency. The wireless signal that is multiplexed by the frequency signal; the distributor 159 distributes the received signal received by the antenna 152 into two directions; The signal component corresponding to the pilot signal of the same center frequency of the center frequency is extracted; The delay corrector 162 gives the signal of the other party distributed by the distributor 159 a delay; The signal component corresponding to the pilot signal extracted at 160 and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Moreover, in the wireless receiving device 951, a reception power calculation unit 453 is provided to calculate the reception power value of the reception signal based on the amplitude of the output signal of the quadrature demodulator 163; and a variable gain amplifier 952 and a variable gain amplifier 953, according to The calculated received power value is used to amplify the signal quadrature demodulated by the quadrature demodulator 163 .

Accordingly, even if the received power varies over a wide range, it is possible to prevent deterioration of the phase noise characteristics.

(Embodiment 9)

FIG. 12 is a block diagram showing the configuration of a radio system according to Embodiment 9. In FIG. The wireless receiving device 1051 of the wireless system 1000 shown in FIG. The structure is the same. Therefore, descriptions of the same structures will be omitted below, and only differences will be described.

Here, as in the signal D, when the pilot signal component is carried on the center frequency, there is a possibility that a DC offset may occur and the reception characteristics may deteriorate.

Therefore, the band limiting filter 1052 is set to remove only the pilot signal component from the signal obtained from the distributor 159 . Accordingly, the signal F of the output signal from the delay corrector 162 of this embodiment is in a state where there is no peak corresponding to the pilot signal component in the center frequency region.

Furthermore, by the quadrature demodulator 163, after the signal F and the signal E from which the peak corresponding to the pilot signal component in the center frequency region has been removed are multiplied, quadrature demodulation is performed, and the signal is supplied to the receiving baseband unit 164 . As a result, the peak corresponding to the pilot signal component in the center frequency region of the signal input to the quadrature demodulator 163 is removed by the band limiting filter 1052 of the modulation signal branch. The influence of the DC offset of the signal of the quadrature demodulator 163 . Therefore, it is possible to prevent the signal input from quadrature demodulator 163 to reception baseband unit 164 from being distorted, thereby improving reception characteristics. That is, by preventing distortion due to DC offset, reception characteristics can be improved.

Thus, according to Embodiment 9, the wireless receiving device 1051 is provided with an antenna 152 for receiving a wireless signal which is a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency. The wireless signal that multiplexes frequency signal; Distributor 159, distributes the received signal that receives by antenna 152 into two directions; The signal component corresponding to the pilot signal of the same center frequency is extracted; the delay corrector 162 gives the signal of the other party allocated by the distributor 159 a delay; and the quadrature demodulation unit 163 extracts the bandpass filter 160 The resulting signal component corresponding to the pilot signal and the other signal delayed by the delay corrector 162 are subjected to frequency multiplication and quadrature demodulation.

Moreover, the wireless receiving device 1051 further includes a frequency band limiting filter 1052, which is arranged in the preceding stage of the delay corrector 162, and divides the signal component corresponding to the pilot signal having the same center frequency from the signal distributed by the distributor 159 eliminate.

Thereby, the peak corresponding to the pilot signal component in the center frequency region of the signal input from the bandwidth limiting filter 1052 to the quadrature demodulator 163 is removed, whereby the input to the quadrature demodulator can be removed. 163 signal DC offset effects. Therefore, it is possible to prevent the signal input from quadrature demodulator 163 to reception baseband unit 164 from being distorted, thereby improving reception characteristics.

(Embodiment 10)

This embodiment relates to a radio transmission device having a configuration different from that of radio transmission device 101 in Embodiments 1 to 9. In the wireless communication device 101, the pilot signal is multiplexed by the transmitting baseband unit 110 so as to be located at the center of the frequency axis of the modulated signal, whereby DC may be generated on the signal input from the transmitting baseband unit 110 to the quadrature modulator 123. offset, thus deteriorating the reception characteristics at the receiving end. Therefore, in the present embodiment, the pilot is placed at the center of the frequency axis of the quadrature-modulated signal. Furthermore, a local oscillation signal is used as the pilot signal.

As shown in FIG. 13 , the wireless transmission device 1101 of this embodiment includes: a transmission baseband unit 1110 that generates a baseband signal; and a transmission unit 1120 that performs predetermined processing on the baseband signal and transmits it as an RF signal.

In the transmitting baseband unit 1110 , a modulated signal generating unit 1111 generates a modulated signal, and inputs the I component and Q component of the modulated signal to the quadrature modulator 123 of the transmitting unit 1120 . In addition, although the modulated signal is described here as an example of multi-carrier CDMA, any modulated signal can be processed as long as the center frequency part on the frequency axis does not carry a signal, such as an OFDM signal. .

Distributor 1121 distributes the local oscillation signal from local oscillation unit 121 and inputs it to quadrature modulator 123 and delay corrector 1122 .

The delay corrector 1122 adds a delay to make the following two times the same: the local oscillating signal distributed by the distributor 1121 is input to the quadrature modulator 123, and the quadrature modulator 123 utilizes the local oscillating signal to perform quadrature modulation on the modulated signal The time until the signal is input to the synthesizer 1123 ; the time until the local oscillation signal distributed by the distributor 1121 is input to the synthesizer 1123 . That is, the delay corrector 1122 adds a delay to obtain the same phase.

The combiner 1123 combines the output signal of the quadrature modulator 123 and the output signal from the delay corrector 1122 , and inputs it to the multiplier 124 . In addition, among the signals output from the synthesizer 1123 at this time, a local oscillation signal (a signal generated by the local oscillation unit 121 ) serving as a pilot signal is placed at the center of the frequency axis of the quadrature-modulated signal.

Thus, according to Embodiment 10, it is possible to transmit a signal in which the influence of the DC offset is removed, and a modulated signal carrying no signal on the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed and generated. wireless signal.

(other embodiments)

(1) In Embodiment 1 to Embodiment 10, the wireless transmission device 101 and the wireless transmission device 1101 applicable to the superheterodyne method have been described. However, the present invention is not limited to this, but can also be applied to the direct conversion method. In this case, in wireless transmission device 101 and wireless transmission device 1101, multiplier 124 and local oscillator 125 are unnecessary, and the output signal of quadrature modulator 123 is a wireless frequency.

(2) In Embodiments 1 to 9, radio reception apparatuses to which the superheterodyne method is applied have been described. However, the present invention is not limited to this, but can also be applied to a direct modulation method. At this time, the multiplier 154, the local oscillation unit 155, the bandpass filter 156, and the reference signal oscillation unit 157 in the wireless receiving device of each of the above-mentioned embodiments are all unnecessary, and the input signal provided to the distributor 159 is a radio frequency .

This specification is based on Japanese Patent Application No. 2004-089725 filed on March 25, 2004 and Japanese Patent Application No. 2005-82443 filed on March 22, 2005. This content is hereby incorporated by reference in its entirety.

Industrial Applicability

The wireless system, wireless transmitting device, and wireless receiving device of the present invention have the effect of improving phase noise characteristics, and are suitable for various wireless communication devices such as mobile phones, PHS, wireless LANs, and wireless systems composed of these devices.

Claims (9)

1. radio receiver comprises:

Antenna receives wireless signal, and the modulation signal of carrying signal and pilot signal with centre frequency identical with described centre frequency are not carried out multiplexing wireless signal to this wireless signal for will be on centre frequency;

Allocation units will be distributed into both direction by the received signal that described antenna receives;

Extraction unit, from the side's that described allocation units distributed signal, the pairing signal component of pilot signal that will have the centre frequency identical with it extracts;

Postpone extra cell, give delay the opposing party's that described allocation units distributed signal; And

The quadrature demodulation unit, the corresponding signal component of described pilot signal that described extraction unit is extracted and added the described the opposing party's who postpones signal by described delay extra cell carries out the frequency multiplication computing, and carries out quadrature demodulation,

Wherein, described quadrature demodulation unit comprises:

The phase-shifts unit carries out 90 phase-shifts of spending to the pairing signal component of the described pilot signal that extracts;

The first frequency multiplier carries out multiplying with the described signal that has added the described the opposing party who postpones with the pairing signal component of described pilot signal that has carried out described 90 degree phase-shifts;

The second frequency multiplier carries out multiplying with described signal and the pairing signal component of described pilot signal that has added the described the opposing party who postpones; And

Another postpones extra cell, to carrying out the pairing signal component of described pilot signal of multiplying by this second frequency multiplier, the additional identical delay of delay that is produced with described phase-shifts unit.

2. radio receiver as claimed in claim 1, comprising:

Amplifying unit amplifies the described side's that described allocation units distributed signal, and to described extraction unit output.

3. radio receiver as claimed in claim 1, comprising:

The received power computing unit based on the amplitude of the output signal of described quadrature demodulation unit, calculates the received power value of described received signal; And

The variable gain amplifying unit is disposed at the prime of described allocation units, amplifies described received signal according to described received power value.

4. radio receiver as claimed in claim 1 comprises:

Temperature measurement unit is measured temperature; And

Delay amount calculating part is based on described temperature computation retardation;

Wherein, described delay extra cell changes additional delay based on the described retardation that calculates.

5. radio receiver as claimed in claim 1, comprise that the frequency multiplication unit replaces described quadrature demodulation unit, the pairing signal component of described pilot signal that this frequency multiplication unit extracts described extraction unit and the output signal of described delay extra cell are carried out frequency multiplication and are calculated.

6. radio receiver as claimed in claim 1, the radio receiver for a kind of suitable superhet mode comprises:

The filter bandwidht control unit, the control signal of generation control filters bandwidth;

The local signal oscillating unit, based on described control signal, the bandwidth of control local oscillation signal is vibrated;

The frequency multiplication unit is disposed at the prime of described allocation units, and described received signal and the controlled local oscillation signal of described bandwidth are carried out frequency multiplication;

Wherein, described extraction unit changes the bandwidth of extraction based on described control signal.

7. radio receiver as claimed in claim 1, comprising:

The received power computing unit based on the amplitude of the output signal of described quadrature demodulation unit, calculates the received power value of described received signal; And

The variable gain amplifying unit according to described received power value, will carry out the signal that quadrature demodulation handles by the quadrature demodulation unit and amplify.

8. radio receiver as claimed in claim 1, comprising:

The frequency range restriction filter is disposed at the prime of described delay extra cell, and from described the opposing party's that described distributor distributed signal, the pairing signal component of pilot signal that will have the centre frequency identical with it is eliminated.

9. wireless base station apparatus, this wireless base station apparatus will be on centre frequency not the modulation signal of carrying signal and pilot signal with centre frequency identical with described centre frequency carry out multiplexingly, and this multiplexed signals sent, comprising:

The modulation signal generation unit generates described modulation signal;

The local oscillation signal generation unit generates local oscillation signal;

The quadrature modulation unit, the described local oscillation signal of utilizing described local oscillation signal generation unit to be generated is carried out the frequency multiplication computing to described modulation signal, with the lifting frequency, and carries out quadrature modulation;

Postpone extra cell, additional delay on the described local oscillation signal that described local oscillation signal generation unit is generated; And

Synthesizer, will by described quadrature modulation unit carried out the signal after the quadrature modulation with carry out as the local oscillation signal of pilot signal multiplexing, this local oscillation signal be by described delay extra cell additional make with this quadrature modulation after the signal of the delay that is complementary of the phase place of signal.

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